EP0197767A2 - Video signal processing apparatus - Google Patents
Video signal processing apparatus Download PDFInfo
- Publication number
- EP0197767A2 EP0197767A2 EP86302468A EP86302468A EP0197767A2 EP 0197767 A2 EP0197767 A2 EP 0197767A2 EP 86302468 A EP86302468 A EP 86302468A EP 86302468 A EP86302468 A EP 86302468A EP 0197767 A2 EP0197767 A2 EP 0197767A2
- Authority
- EP
- European Patent Office
- Prior art keywords
- signal
- circuit
- output signal
- input
- video signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
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Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/76—Television signal recording
- H04N5/91—Television signal processing therefor
- H04N5/92—Transformation of the television signal for recording, e.g. modulation, frequency changing; Inverse transformation for playback
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N9/00—Details of colour television systems
- H04N9/64—Circuits for processing colour signals
- H04N9/646—Circuits for processing colour signals for image enhancement, e.g. vertical detail restoration, cross-colour elimination, contour correction, chrominance trapping filters
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/76—Television signal recording
- H04N5/91—Television signal processing therefor
- H04N5/911—Television signal processing therefor for the suppression of noise
Definitions
- the present invention relates to a video signal processing apparatus for use in a video taperecorder (VTR).
- VTR video taperecorder
- a recursive filter To raise the S/N ratio of the video signal processed in VTR's, a recursive filter has been used for video signal processing.
- the recursive filter involves a delay circuit for delaying the video signal by 1H or 2H (H: horizontal synchronization period).
- the filter feeds output of the delay circuit back to the input thereof to average the signal noise, thus raising the video signal S/N ratio.
- the video signal processing apparatus of the present invention comprises: a delay circuit for delaying an input signal by a predetermined time; a first operational circuit for conducting addition or subtraction operation between an output signal of the delay circuit and an input video signal; a nonlinear processing circuit which receives an output signal of the first operational circuit to generate first and second output signals, the first output signal having a gain of K which decreases with an increase of the absolute value of the input signal level and becomes zero when the absolute value exceeds a specified value, the second output having a gain of 1/2 (1+K); a second operational circuit which conducts addition or subtraction operation between the first output signal of the nonlinear processing circuit and the input video signal and outputs the operation result to the input of the delay circuit; and a third operational circuit for conducting addition or subtraction operation between the second output signal of the nonlinear processing circuit and the input video signal.
- Figure 1 (a) is a block diagram showing the first embodiment of the color signal processing apparatus according to the present invention.
- Figures 1 (b) and 1 (c) show the input/ output (I/O) characteristics of the nonlinear processing circuit in the first embodiment.
- the input video signal is the NTSC carrier chrominance signal.
- the carrier chrominance signal is inputted through an input terminal 1 and enters a subtractor 2 which subtracts an output signal of a nonlinear processing circuit 8 from the input carrier chrominance signal.
- the output signal of the subtractor 2 enters a 1H delay circuit 3;
- the output signal of the 1H delay circuit 3 is added to the carrier chrominance signal by an adder 4.
- the output signal of the adder 4 is fed to nonlinear processing circuits 5 and 8 which constitute a nonlinear processor 9.
- the output signal of the nonlinear processing circuit 8 is fed back to the subtractor 2.
- the output signal of the nonlinear processing circuit 5 is subtracted from the carrier chrominance signal by a subtractor 6.
- the output signal of the subtractor 6 is fed to an output terminal 7.
- the nonlinear processing circuits 5 and 8 are assumed to have linear characteristics with gains of 1/2 (K + 1) and K, respectively.
- the transfer runction G 1 (S) from the input terminal 1 to the output terminal of the adder 4 is expressed by the
- the transfer function G 0 (S) from the input terminal 1 to the output terminal 7 is expressed by the following formula:
- the transfer function G 1 (S) provides a comb filter characteristic having peaks at the frequencies of integral multiples of the horizontal synchronization frequency fH, and nodes at the frequencies of (integer + 1/2) multiples of fH.
- the transfer function G 0 (S) provides a comb filter characteristic having peaks at the frequencies of (integer + 1/2) multiples of the horizontal synchronization frequency fH and nodes at the frequencies of integral multiples of fH.
- the frequency characteristic is indicated by the curve and the carrier chrominance signal spectrum by the shades, with frequency along the axis of abscissa and gain along the axis of ordinate.
- the above description is based on the assumption that the non-linear processing circuit 8 has a constant gain of K.
- the constant gain will result in a constant feedhack even with a large output signal of the affer 4, or with a low vertical correlation, and therefore will cause a downwar color offset when color changes in the vertical direction.
- non-linear characteristics are given to the gains of the non-linear processing circuits 5 and 8 to prevent the downward color offset.
- Figures 1 (b) and 1 (c) show the I/O characteristics of the non-linear processing circuit 8 and 5, respectively, employed in the present embodiment of the invention.
- the non-linear precessing circuit 8 provides a limitter characteristic so that it has no output when the input signal level is high. Specifically, when the color signal correlation is low, the input signal level to the nonlinear processing circuit 8 becomes large so that the nonlinear processing circuit 8 does not produce an output signal to be fed back to the delay circuit 3. Becaus of the absence of the signal feedback, the present embodiment is free from downward color offset.
- the nonlinear processing circuit 5 is set to have a gain of 1/2 (1 + K) for the gain of K of the nonlinear processing circuit 8.
- the nonlinear processing circuit 8 With an input signal level of "3", for instance, the nonlinear processing circuit 8 outputs "1".
- the gain of the non- linear processing circuit 5 for the input level of "3” is "2/3" as the result of the calculation of 1/2 (1 + 1/3).
- the output signal of the circuit 5, which is the product of the input.”3" and the gain "2/3", is therefore "2".
- the output signal of the nonlinear processing circuit 5 for each input level can be set according to the I/O characteristic of the nonlinear processing circuit 8.
- the reason for setting the I/O characteristic of the nonlinear processing circuit 5, as described above, is to attain "1" as a peak gain of G 0 (S).
- the carrier chrominance signal is a PAL signal
- a 2H delay circuit is used in place of the 1H delay circuit because the carrier chrominance signal provides correlation at intervals of 2H.
- the non-linear processing circuit 8 may have a gain which decreases as the input signal level absolute value increases and which becomes zero when the input signal level absolute value exceeds a specified value.
- the non-linear processing circuit 5 may have a gain expressed as 1/2.(1 + K), where K is the gain of the non-linear processing circuit 8. The circuits having such gains can be easily realized by known art.
- the embodiment of Figure 1 (a) can better be realized by a digital circuit.
- the 1H delay circuit 3 can be configured by a shift register.
- the non-linear circuits 5 and 8 are each configured by a read-only memory (ROM).
- the output signal of the adder 4 is applied to the ROM as an address signal, and the ROM outputs a data signal stored in the address specified by the address signal.
- any non-linear characteristic can be easily realized for each of the non-linear circuits 5 and 8.
- FIG. 3 shows an example of the present invention applied for processing a demodulated chrominance difference signal or a luminance signal.
- the R-Y signal and B-Y signal are examples of the chrominance difference signals.
- the signal processor circuit for one of the two chrominance difference signals is shown in Figure 3; the other chrominance difference signal is processed in a separate but identical signal processor circuit as shown in Figure 3.
- the chrominance difference signal inputted through the input terminal 1 enters a subtractor 2 which subtracts an output signal of the nonlinear processing circuit 8 from the input chrominance difference signal.
- the output signal of the subtractor 2 enters the 1H delay circuit 3.
- the output signal of the 1H delay circuit 3 is subtracted from the input chrominance difference signal by a subtractor 10.
- the result is then inputted to the nonlinear processing circuit 5 and to the nonlinear processing circuit 8 from which the signal is fed back to the subtractor 2.
- the output signal of the nonlinear processing circuit 5 is subtracted from the input chrominance difference signal by the subtractor 6, the result being outputted to the output terminal 7.
- the nonlinear processing circuits 5 and 8 are assumed to,have linear cnaracteristics, with gains of 1/2 (K + 1) and K, respectively.
- the transfer function H 1 (S) from the input terminal 1 to the output terminal of the subtractor 10 is expressed by the following formula:
- the transfer function H 1 (S) provides a comb filter characteristic having peaks at the frequencies of (integer + 1/2) multiples of the horizontal synchronization frequency fH and nodes at the frequencies of integral multiples of fH.
- the transfer function H O (S) provides a comb filter characteristic having peaks at the frequencies of integral multiples of the horizontal synchronization frequency fH and nodes at the frequencies of (integrer + 1/2) multiples of fH.
- the frequency characteristic of H 0 (S) is indicated by the curve and the chrominance difference signal (or luminance signal) spectrum by the shades, with frequency along the axis of abscissa and gain along the axis of ordinate.
- the chrominance difference signal spectrum alone is outputted to the output terminal 7, whereby the color signal S/N ratio is improved.
- the second embodiment of the invention is also free from downward color offset which could occur in the absence of vertical correlation of the chrominance difference signal, as well as from vertical resolution deterioration. The principle for preventing downward color offset and vertical resolution deterioration is not described here because it is the same as in the first embodiment.
- a third embodiment of the invention will now be described with reference to Figure 4.
- a nonlinear processing circuit 12 corresponds to the nonlinear processing circuit 8 of the first embodiment.
- a nonlinear processing circuit 12, an adder 11 and a coefficient circuit 13 correspond to the non- linear processing circuit 5 of the first embodiment.
- the gain between the outputs of the adder 4 and adder 11 is 1 + K, and therefore the gain between the outputs of the adder 4 and the coefficient circuit 13 is 1/2 (1 + K ).
- the gain between the outputs of the adder 4 and adder 11 of the third embodiment corresponds to the gain of the nonlinear processing circuit 5 of the first embodiment, in which gain is 1/2 (1 + K) assuming that the gain of the nonlinear processing circuit 8 is K, as described earlier.
- the third embodiment yields the same effect as the first embodiment while invol- ing only one nonlinear processing circuit. Specific operation of the third embodiment is omitted here because it is the same as that of the first embodiment.
- the embodiment of Figure 4 can also better be realized by a digital circuit in the similar way to the first embodiment.
- the 1H delay circuit 3 can be configured by a shift register.
- the non-linear circuit 12 can be configured by a ROM.
- the coefficient circuit 13 can be configured by a shift register or a multiplier.
- Figure 5 is a block diagram of a fourth embodiment of the present invention.
- the fourth embodiment is comparable to the second embodiment.
- the subtractor 10 is used in place of the adder 4.
- the operation of the fourth embodiment is completely the same as that of the second embodiment and
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- Engineering & Computer Science (AREA)
- Multimedia (AREA)
- Signal Processing (AREA)
- Processing Of Color Television Signals (AREA)
Abstract
Description
- The present invention relates to a video signal processing apparatus for use in a video taperecorder (VTR).
- To raise the S/N ratio of the video signal processed in VTR's, a recursive filter has been used for video signal processing. The recursive filter involves a delay circuit for delaying the video signal by 1H or 2H (H: horizontal synchronization period). The filter feeds output of the delay circuit back to the input thereof to average the signal noise, thus raising the video signal S/N ratio.
- With the conventional circuit construction, however, when the video signal has a low vertical correlation, i.e. when the signal input to the recursive filter shows a sudden change, the filter cannot follow the output change promptly. If such a circuit is used in processing color signals, a delay in color change causes a downward color offset (color offset in a downward direction on the TV screen due to the color signal delay with respect to the luminance signal). If the luminance signal is processed with this circuit, the vertical resolution will deteriorate.
- It is an object of the present invention to provide a video signal processing apparatus that does not cause the downward color offset when passing the carrier chrominance signal through a recursive filter which incorporates 1H or 2H delay circuit.
- It is also an object of the present invention to provide a video signal processing apparatus which does not cause downward color offset when passing the chrominance difference signal through a recursive filter incorporating a 1H or 2H delay circuit, and which does not cause deteriorated vertical resolution when passing the luminance signal through the recursive filter.
- To achieve the above objects, the video signal processing apparatus of the present invention comprises: a delay circuit for delaying an input signal by a predetermined time; a first operational circuit for conducting addition or subtraction operation between an output signal of the delay circuit and an input video signal; a nonlinear processing circuit which receives an output signal of the first operational circuit to generate first and second output signals, the first output signal having a gain of K which decreases with an increase of the absolute value of the input signal level and becomes zero when the absolute value exceeds a specified value, the second output having a gain of 1/2 (1+K); a second operational circuit which conducts addition or subtraction operation between the first output signal of the nonlinear processing circuit and the input video signal and outputs the operation result to the input of the delay circuit; and a third operational circuit for conducting addition or subtraction operation between the second output signal of the nonlinear processing circuit and the input video signal.
-
- Figure 1 (a) is a block diagram showing a first embodiment of the present invention;
- Figures 1 (b) and 1 (c) are charts showing input/output characteristics of the nonlinear processing circuit in the first embodiment of the present invention;
- Figure 2 (a) is a chart showing the frequency characteristics and the carrier chrominance signal spectrum of the first embodiment of the present invention;
- Figure 2 (b) is a chart showing the frequency characteristics and the spectrum of color difference or luminance signal of the second embodiment of the present invention;
- Figure 3 is a block diagram showing a second embodiment of the present invention;
- Figure 4 is a block diagram showing a third embodiment of the present invention; and
- Figure 5 is a block diagram showing a fourth embodiment of the present invention.
- Some embodiments of the present invention will be described below with reference to the accompanying drawings. Figure 1 (a) is a block diagram showing the first embodiment of the color signal processing apparatus according to the present invention. Figures 1 (b) and 1 (c) show the input/ output (I/O) characteristics of the nonlinear processing circuit in the first embodiment. In this case, the input video signal is the NTSC carrier chrominance signal.
- The carrier chrominance signal is inputted through an
input terminal 1 and enters asubtractor 2 which subtracts an output signal of anonlinear processing circuit 8 from the input carrier chrominance signal. The output signal of thesubtractor 2 enters a1H delay circuit 3; The output signal of the1H delay circuit 3 is added to the carrier chrominance signal by anadder 4. The output signal of theadder 4 is fed tononlinear processing circuits nonlinear processor 9. The output signal of thenonlinear processing circuit 8 is fed back to thesubtractor 2. The output signal of thenonlinear processing circuit 5 is subtracted from the carrier chrominance signal by asubtractor 6. The output signal of thesubtractor 6 is fed to anoutput terminal 7. Thenonlinear processing circuits input terminal 1 to the output terminal of theadder 4 is expressed by the following formula: -
- The transfer function G1 (S) provides a comb filter characteristic having peaks at the frequencies of integral multiples of the horizontal synchronization frequency fH, and nodes at the frequencies of (integer + 1/2) multiples of fH. The transfer function G0 (S) provides a comb filter characteristic having peaks at the frequencies of (integer + 1/2) multiples of the horizontal synchronization frequency fH and nodes at the frequencies of integral multiples of fH. In Figure 2 (a), the frequency characteristic is indicated by the curve and the carrier chrominance signal spectrum by the shades, with frequency along the axis of abscissa and gain along the axis of ordinate.
- As shown in Figure 2 (a), since energy of the carrier chrominance signal spectrum concentrates at the frequencies of (integer + 1/2) multiples of fH, the carrier chrominance signal spectrum alone is outputted to the
output terminal 7, whereby the color signal S/N ratio is improved. G1 (S) has peaks at the frequencies of integral multiples of the horizontal synchronization frequency, the spectra at which frequencies increase when the carrier chrezinance signal has a lower vertical correlation. Accordingly, a non-correlation signal is obtained at the onput terminal of theadder 4. The non-correlation signal is then fed back to thesubtractor 2 through thenon-linear processing circuit 8. - The above description is based on the assumption that the
non-linear processing circuit 8 has a constant gain of K. The constant gain will result in a constant feedhack even with a large output signal of theaffer 4, or with a low vertical correlation, and therefore will cause a downwar color offset when color changes in the vertical direction. In this embodiment of the invention, non-linear characteristics are given to the gains of thenon-linear processing circuits - Figures 1 (b) and 1 (c) show the I/O characteristics of the
non-linear processing circuit non-linear precessing circuit 8 provides a limitter characteristic so that it has no output when the input signal level is high. Specifically, when the color signal correlation is low, the input signal level to thenonlinear processing circuit 8 becomes large so that thenonlinear processing circuit 8 does not produce an output signal to be fed back to thedelay circuit 3. Becaus of the absence of the signal feedback, the present embodiment is free from downward color offset. Moreover, according to the first embodiment of the invention, thenonlinear processing circuit 5 is set to have a gain of 1/2 (1 + K) for the gain of K of thenonlinear processing circuit 8. With an input signal level of "3", for instance, thenonlinear processing circuit 8 outputs "1". In this case, the value of K is "1/3" (K = 1f 3 = 1/3). Hence, the gain of the non-linear processing circuit 5 for the input level of "3" is "2/3" as the result of the calculation of 1/2 (1 + 1/3). The output signal of thecircuit 5, which is the product of the input."3" and the gain "2/3", is therefore "2". Thus, the output signal of thenonlinear processing circuit 5 for each input level can be set according to the I/O characteristic of thenonlinear processing circuit 8. The reason for setting the I/O characteristic of thenonlinear processing circuit 5, as described above, is to attain "1" as a peak gain of G0 (S). When the carrier chrominance signal is a PAL signal, a 2H delay circuit is used in place of the 1H delay circuit because the carrier chrominance signal provides correlation at intervals of 2H. - The
non-linear processing circuit 8 may have a gain which decreases as the input signal level absolute value increases and which becomes zero when the input signal level absolute value exceeds a specified value. Thenon-linear processing circuit 5 may have a gain expressed as 1/2.(1 + K), where K is the gain of thenon-linear processing circuit 8. The circuits having such gains can be easily realized by known art. - The embodiment of Figure 1 (a) can better be realized by a digital circuit. The
1H delay circuit 3 can be configured by a shift register. Thenon-linear circuits adder 4 is applied to the ROM as an address signal, and the ROM outputs a data signal stored in the address specified by the address signal. By use of the ROM, any non-linear characteristic can be easily realized for each of thenon-linear circuits - A second embodiment of the present invention will now be described referring to Figure 3 which shows an example of the present invention applied for processing a demodulated chrominance difference signal or a luminance signal. The R-Y signal and B-Y signal are examples of the chrominance difference signals. The signal processor circuit for one of the two chrominance difference signals is shown in Figure 3; the other chrominance difference signal is processed in a separate but identical signal processor circuit as shown in Figure 3. The chrominance difference signal inputted through the
input terminal 1 enters asubtractor 2 which subtracts an output signal of thenonlinear processing circuit 8 from the input chrominance difference signal. The output signal of thesubtractor 2 enters the1H delay circuit 3. The output signal of the1H delay circuit 3 is subtracted from the input chrominance difference signal by asubtractor 10. The result is then inputted to thenonlinear processing circuit 5 and to thenonlinear processing circuit 8 from which the signal is fed back to thesubtractor 2. The output signal of thenonlinear processing circuit 5 is subtracted from the input chrominance difference signal by thesubtractor 6, the result being outputted to theoutput terminal 7. - Similar to the previous embodiment, the
nonlinear processing circuits input terminal 1 to the output terminal of thesubtractor 10 is expressed by the following formula: -
- The transfer function H1 (S) provides a comb filter characteristic having peaks at the frequencies of (integer + 1/2) multiples of the horizontal synchronization frequency fH and nodes at the frequencies of integral multiples of fH. The transfer function HO (S) provides a comb filter characteristic having peaks at the frequencies of integral multiples of the horizontal synchronization frequency fH and nodes at the frequencies of (integrer + 1/2) multiples of fH. In Figure 2 (b), the frequency characteristic of H0 (S) is indicated by the curve and the chrominance difference signal (or luminance signal) spectrum by the shades, with frequency along the axis of abscissa and gain along the axis of ordinate.
- As indicated in Figure 2 (b), since energy of the chrominance difference signal spectrum concentrates at the frequencies of integral multiples of fH, the chrominance difference signal spectrum alone is outputted to the
output terminal 7, whereby the color signal S/N ratio is improved. The second embodiment of the invention is also free from downward color offset which could occur in the absence of vertical correlation of the chrominance difference signal, as well as from vertical resolution deterioration. The principle for preventing downward color offset and vertical resolution deterioration is not described here because it is the same as in the first embodiment. Moreover, according to the second embodiment of the invention, since two chrominance difference signals are processed by the separate but identical circuits, it is possible prevent downward color offset for both hue and saturation factor variations only by taking appropriate measures against the downward color offset according to the vertical correlation of each chrominance difference signal level. - A third embodiment of the invention will now be described with reference to Figure 4. A
nonlinear processing circuit 12 corresponds to thenonlinear processing circuit 8 of the first embodiment. Anonlinear processing circuit 12, an adder 11 and acoefficient circuit 13 correspond to the non-linear processing circuit 5 of the first embodiment. - Providing that a coefficient of the
coefficient circuit 13 is "1/2" and the gain of thenonlinear processing circuit 12 is K, the gain between the outputs of theadder 4 and adder 11 is 1 + K, and therefore the gain between the outputs of theadder 4 and thecoefficient circuit 13 is 1/2 (1 + K). The gain between the outputs of theadder 4 and adder 11 of the third embodiment corresponds to the gain of thenonlinear processing circuit 5 of the first embodiment, in which gain is 1/2 (1 + K) assuming that the gain of thenonlinear processing circuit 8 is K, as described earlier. Thus, with thenonlinear processing circuit 12, adder 11 andcoefficient circuit 13, assuming the function of thenonlinear processing circuit 5 of the first embodiment, the third embodiment yields the same effect as the first embodiment while invol- ing only one nonlinear processing circuit. Specific operation of the third embodiment is omitted here because it is the same as that of the first embodiment. - The embodiment of Figure 4 can also better be realized by a digital circuit in the similar way to the first embodiment. The
1H delay circuit 3 can be configured by a shift register. Thenon-linear circuit 12 can be configured by a ROM. Thecoefficient circuit 13 can be configured by a shift register or a multiplier. - Figure 5 is a block diagram of a fourth embodiment of the present invention. The fourth embodiment is comparable to the second embodiment. The
subtractor 10 is used in place of theadder 4. The operation of the fourth embodiment is completely the same as that of the second embodiment and
Claims (10)
Applications Claiming Priority (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP70257/85 | 1985-04-03 | ||
JP60070257A JPS61228792A (en) | 1985-04-03 | 1985-04-03 | Chrominance signal processor |
JP60140814A JPH06105978B2 (en) | 1985-06-27 | 1985-06-27 | Video signal processor |
JP140814/85 | 1985-06-27 |
Publications (3)
Publication Number | Publication Date |
---|---|
EP0197767A2 true EP0197767A2 (en) | 1986-10-15 |
EP0197767A3 EP0197767A3 (en) | 1988-07-27 |
EP0197767B1 EP0197767B1 (en) | 1992-06-17 |
Family
ID=26411421
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP86302468A Expired - Lifetime EP0197767B1 (en) | 1985-04-03 | 1986-04-03 | Video signal processing apparatus |
Country Status (4)
Country | Link |
---|---|
US (1) | US4760449A (en) |
EP (1) | EP0197767B1 (en) |
KR (1) | KR900008236B1 (en) |
DE (1) | DE3685676T2 (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP0278786A1 (en) * | 1987-02-13 | 1988-08-17 | Victor Company Of Japan, Limited | Noise reducing circuit for video signal |
US10771682B2 (en) | 2016-04-14 | 2020-09-08 | Arnold & Richter Cine Technik Gmbh & Co. Betriebs Kg | Camera viewfinder |
Families Citing this family (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5144434A (en) * | 1989-07-13 | 1992-09-01 | Canon Kabushiki Kaisha | Video signal processing device using look-up table |
US5325203A (en) * | 1992-04-16 | 1994-06-28 | Sony Corporation | Adaptively controlled noise reduction device for producing a continuous output |
Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4302768A (en) * | 1978-12-14 | 1981-11-24 | Matsushita Electric Industrial Co., Ltd. | System for reducing or suppressing noise components in television signal |
DE3116811A1 (en) * | 1980-04-28 | 1982-04-08 | Sony Corp., Tokyo | "VIDEO SIGNAL PROCESSING CIRCUIT" |
GB2098023A (en) * | 1981-05-04 | 1982-11-10 | Philips Nv | Noise suppression circuit or a video signal |
DE3412529A1 (en) * | 1983-04-07 | 1984-10-18 | Victor Company Of Japan, Ltd., Yokohama, Kanagawa | NOISE REDUCTION CIRCUIT FOR A VIDEO SIGNAL |
Family Cites Families (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS60121885A (en) * | 1983-12-05 | 1985-06-29 | Victor Co Of Japan Ltd | Noise decreasing circuit of image signal |
KR890004220B1 (en) * | 1984-06-30 | 1989-10-27 | 마쯔시다덴기산교 가부시기가이샤 | Picture signal processing system |
JPS61121574A (en) * | 1984-11-19 | 1986-06-09 | Hitachi Ltd | Video signal processing circuit |
-
1986
- 1986-04-01 US US06/846,819 patent/US4760449A/en not_active Expired - Lifetime
- 1986-04-02 KR KR1019860002487A patent/KR900008236B1/en not_active IP Right Cessation
- 1986-04-03 DE DE8686302468T patent/DE3685676T2/en not_active Expired - Fee Related
- 1986-04-03 EP EP86302468A patent/EP0197767B1/en not_active Expired - Lifetime
Patent Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4302768A (en) * | 1978-12-14 | 1981-11-24 | Matsushita Electric Industrial Co., Ltd. | System for reducing or suppressing noise components in television signal |
DE3116811A1 (en) * | 1980-04-28 | 1982-04-08 | Sony Corp., Tokyo | "VIDEO SIGNAL PROCESSING CIRCUIT" |
GB2098023A (en) * | 1981-05-04 | 1982-11-10 | Philips Nv | Noise suppression circuit or a video signal |
DE3412529A1 (en) * | 1983-04-07 | 1984-10-18 | Victor Company Of Japan, Ltd., Yokohama, Kanagawa | NOISE REDUCTION CIRCUIT FOR A VIDEO SIGNAL |
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP0278786A1 (en) * | 1987-02-13 | 1988-08-17 | Victor Company Of Japan, Limited | Noise reducing circuit for video signal |
US4792855A (en) * | 1987-02-13 | 1988-12-20 | Victor Company Of Japan, Ltd. | Noise reducing circuit for video signal |
US10771682B2 (en) | 2016-04-14 | 2020-09-08 | Arnold & Richter Cine Technik Gmbh & Co. Betriebs Kg | Camera viewfinder |
Also Published As
Publication number | Publication date |
---|---|
EP0197767B1 (en) | 1992-06-17 |
KR860008681A (en) | 1986-11-17 |
DE3685676D1 (en) | 1992-07-23 |
KR900008236B1 (en) | 1990-11-06 |
US4760449A (en) | 1988-07-26 |
DE3685676T2 (en) | 1993-01-28 |
EP0197767A3 (en) | 1988-07-27 |
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