DE2319520A1 - PHASE SHIFTER TREMULANCE DEVICE - Google Patents

Description

The invention "relates to electrical musical instruments and in particular a phase shift tremulant device for an electric musical instrument, such as an electronic one Organ.

In the case of an electronic organ, it has to be considered musical The frequency and / or the amplitude proved to be attractive to change the tones produced by the organ with a frequency between four and eight Hertz. This periodic Changes are known as "vibrato" when they are primarily in frequency, and as a "tremolo", if it is mainly the · amplitude (sound

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ORIGINAL INSPECTED

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strength) concern. Certain advanced electronic Organs provide a combined vibrato-tremolo effect generate that for the purposes of the following description referred to as the "tremulance" effect. With the tremulance effect become both the frequency and the amplitude of a certain tone with a frequency of approximated 6.7 Hz varies. In known electronic organs, several methods have been used to produce the vibrato, tremolo and / or tremulance effects applied.

If a pure vibrato effect was desired, it existed the usual known method is to determine the frequencies of the Control oscillators to change a predetermined value at a frequency of about 6.7 Hz, This causes -that the height of the generated tone is above and below the setpoint frequency with the desired frequency of 6.7 Hz changes.

If a pure tremolo effect was desired, there was the usual known method is to reinforce the Organ amplifier circuit with the desired frequency of to vary approximately 6.7 Hz * This creates natural a periodic change in the amplitude of the generated Tones with a frequency of 6.7 Hz.

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To achieve the further developed tremulance effect, the so-called Leslie playback device has been used "for most organs, with a tremulance effect is generated by mechanical means using the Doppler principle. In such a facility the acoustic sound wave is moved periodically by rotating a loudspeaker or a deflector leaves"

In order to avoid certain problems and limitations inherent in mechanical tremulance devices, the phase shift device of the present invention was developed. In short, a signal whose waveform corresponds to a certain musical tone is fed to a phase splitter. In the phase splitter, the signal is split into two output signals, one of which is in phase with the incoming signal and the second is 180 out of phase with the incoming signal. The output signal is then supplied to a first phase shifter, where it undergoes periodic Phasennach- and -voreilung with a frequency of approximately 6.7 Hz, the second signal from the phase splitter is applied to a second phase shifter, in which is also periodic Phasennach- and - advance with the 6.7 Hz frequency

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holds. The outputs of the two phase shifters are then routed through separate amplifier channels to separate speakers.

As a result of the periodic lead and lag of the signals emitted by each loudspeaker, the acoustic effect of a frequency deviation arises. This frequency deviation results as a result of the increasing and decreasing number of waveforms at the transition between
the speaker and the listener. The size of the frequency deviation is the phase change rate and
proportional to the magnitude of the phase shift. If the listener listens to the right and left loudspeakers at the same time, their signals mix acoustically, so that a periodic cancellation and amplification of the
Sound arises. From this it can be seen that not only the frequency of the sound reaching the listener is in
periodically, but also the amplitude of the sound is varied.

Although known phase shifting methods for eliciting the tremulance effect relatively satisfactory A number of problems have arisen, particularly when highly appealing

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and accurate reproductions are desired. The various voices produced by the electronic organ differ in harmonic content. When a "particular voice is treated with known phase-shifting techniques, the resulting acoustic effect, due to the difference in phase shift between the harmonic and primary signals making up the voice, may not be most pleasing to such a voice. In fact, the use of two playback channels, which is generally useful for most tremulance effects, to produce an unsatisfactory sound for a yiolin voice,

According to the invention, a two-channel phase shifting method is used used to generate the tremulant. There is one in each of the right and left channels Number of phase shifter networks connected in cascade. Each network contains a light response resistor and an associated lamp which is coupled to a trernulance oscillator via a suitable circuit.

A number of different tremulance effects that affect a special organ parts are made possible by means of a Se Ha It arrangement in different. Kouiblnationes. together.

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For example, the one approaches a beaked flute part applied phase shift 720 ° in both the right and left channels, while a Violin part is shifted by less than 360 ° in just one channel. Every different voice is out of phase to the. most appealing acoustic re ^ to achieve a giving effect.

The lamps in the two channels are driven by separate oscillator waveforms that have different shapes' and are out of phase. As a result, the phase shift created in the right channel is no doubling or simple relation of the phase shift caused in the left channel, When voices treated by the two channels are acoustically combined, the resulting effect is most pleasant and experience has shown that it is superior to the known tremulance effects «, Various other changes are to promote the operation and resulting effect of the tremulant circuits has been made, as will be explained.

An object of the invention is to provide an improved one Tremulance circuit, the optional phase shift networks combined in different configurations,

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around the tremulance effect on the then to be "treated" Trim instrument part.

Another object of the invention is to provide an improved two-channel tremulance circuit in which an oscillator and associated circuitry for controlling the variable waveforms Create impedance elements in the two channels.

Another object of the invention is to provide an improved tremulance circuit, which is a more comfortable Sound quality generated for a wide variety of organ parts than was previously possible.

Other objects and features of the invention will be apparent from the following description and drawing.

Although an illustrative embodiment of the Invention shown in the drawing 'and described here in detail, the invention is in many various forms may be implemented, and it should be understood that the present disclosure is intended only as a Design example for the principles of the invention is to be considered and the invention is not based on the illustrated. Embodiment is limited.

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In the drawing show:

Pig. 1 is a block diagram of an electronic organ with the tremulance device according to the invention;

Fig. 2 is partly a block diagram and partly a schematic circuit diagram of the tremulance device shown in block form in Fig. 1, wherein the Phase splitter is shown individually;

3 is a schematic circuit diagram of the part of the tremulance device, shown in block form in Figure 2;

FIG. 4 is a simplified schematic circuit diagram of a single stage of the phase shifter used in FIG. 3; FIG.

Figures' 5A, 5B, 50, 5D, 5B, 5F

Waveforms illustrating the signals different from that shown in the remaining figures electronic organ.

In Fig. 1, the phase shifter tremulance device is illustrated as a block diagram installed in an electronic organ. Each from a number of organ tone generators

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20, labeled E through F, contains one Main or control oscillator that generates a square wave at a frequency that corresponds to the corresponding tone in the highest octave on the organ manual. Each tone generator 20 also includes dividing circuits, which divide the control oscillator frequency by multiples of two and typically provide outputs which Divisions by two, four, eight and sixteen correspond. In this way, each tone generator generates 20 frequencies, which correspond to the specified tone in all five octaves on the organ manual.

Each of the five frequency outputs from all twelve tone generators 20 is fed to a distribution circuit 22. This thus receives sixty signals as inputs, each of which has a frequency that is the basic frequency corresponds to a tone that can be played on the organ. The dividing circuit 22 operates with a Keyboard circuitry composed of a SoIomanual 24, an accompanying manual 26 and a pedal manual 28 is operated. Each of these manuals has signals Fundamental frequencies through which correspond to the notes or tones played by the organist. For example, if the key corresponding to the note E in the upper octave of the solo manual is pressed, the dem works Manual 24 associated circuit with the distribution

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circuit 22 together in such a way that a waveform with associated fundamental frequency and harmonic content pass through it can. The operation of the companion manual 26 and pedal manual 28 is similar to general is known.

Typically, that is let through by solo manual 24 Signal a sawtooth wave as shown at 30 is. The sawtooth wave is simulated that suitable low-wave signals generated by the tone generators 20 are added so that a step-shaped Waveform is created. It is desirable to have a sawtooth wave come to this point because of such a waveform not only the desired basic frequency, but also contains all harmonics of this frequency. As a result, this waveform is well suited for further shaping, which must be carried out in such a way that the various - Voices generated by the organ can be reproduced.

A solo voice circuit 34 is used to tune the through treat the solo manual 24 as a sawtooth wave to produce a tone with a desired timbre can be. The voice circuit 34 is a passive one Network with a suitable filter circuit to prevent the Contains sawtooth wave. round frequency and upper wool frequency

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Selectively attenuate sequences so that different pre-selected timbres are generated. For example, if the If the violin rocker is pressed for the solo manual, the associated piiter circuit acts on the content of the sawtooth wave at fundamental frequency and harmonic frequencies in such a way that the amplification and reproduction of the resulting Waveform to create a flang with the timbre of a violin will.

For example, the tuning circuit 34 can act on the incoming waveform to produce beaked or violin voices or complex voices. An accompaniment voice circuit 36 and a pedal voice circuit 38 perform en _u speaking functions for signals that are output from the accompaniment manual 26 and from the pedal manual 28, respectively.

The three signals exiting solo voice circuit 34 are individually connected to a corresponding solo beaked flute preamplifier 40, a violin preamplifier 42 and a solo complex preamplifier 44. The one formed by the accompaniment voice circuit 36 Signal goes to the accompaniment preamplifier 46. These preamplifiers act in such a way that they carry the signals amplify before further signal processing.

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The appropriately shaped and amplified signals proceed from the circuits 4-0, 42, 44 and 46 to a hand-held tone regulator 50. In the tone regulator 50 becomes an ohmic network with different potentiometers to balance the signal strength of the incoming Signals are used in such a way that the outgoing signals have suitable amplitude in relation to each other to have. The four signals that correspond to the beaked flute, violin, complex and accompaniment parts are now Via individual lines 52, 53 »54 and 55 to a tremulance circuit 60, which forms part of the invention ". The circuit 60 is made with conventional toggle switches operated, which are arranged on the side block of the organ. By presetting these switches appropriately the organist can determine whether the solo and / or accompanying manual tones generated by the phase shift tremulance circuit the invention should arrive. When the circuit 60 is preset to have a tremu-1-anz effect for example to give to the Solostimm.signal, then such a signal is in the phase shifter tremulance circuit fed according to the invention before further amplification by the organ amplifier circuit. When the organist uses a certain voice the tremulance effect does not want to submit, arranges suitable

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position of the circuit 60 assigned. Counter, that the signal goes straight to the non-tremulating preamplifier 62 runs through the organ amplifier circuit before further processing. .

The various avenues for tuning through the circuit are as follows;

First, it is assumed that the circuit 60 is set to produce a violin timbre in a non-tremulating Way generated. In such a pail, the signal is sent over a line 65 and only transmitted to a preamplifier 66 for the left channel. This way the signal will only come from the left speaker the organ produces. This result has proven to be musically desirable through empirical determination proven when a violin tuning is preselected.

Second, assume that the voice circuit 60 is preset in such a way that either a close-up flute tuning or a complex voice is given when playing the solo manual and that such Voicing can be produced without a separation effect target. In such a pail, the circuit 60 is preset so that that of the beaked flute tuning

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or the complex vocalization corresponds to the waveform via a line 68 to the non-tremulating preamplifier 62. The desired vocalization occurs in both the left and right speakers without the tremulance effect. If the accompanying signal is to remain without a tremulance effect, a suitable presetting of the circuit 60 causes the accompanying complex signal Wqqt to also be sent to the line 68; non-rectifying preamplifier 62 runs,

Several examples will now be given if selected voices are to be produced with the tremulance effect. For example, if the beaked flute part is selected on the solo manual and circuit 60 is set to tremulant, the beaked flute waveform is transmitted on line 75 directly to a phase shifter $ 7 for the right channel and a kias shifter 80 for the left channel, as explained below, the phase shifters 78 and 80 cause a periodic lead> - and lag of the phase of the continuous signal with a frequency of about 6.7 Hz. iomit will make it through

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the right phase shifter 78 with respect to the signal the phase "accelerates and decelerates continuously" when it is sent via an output line 82 to the preamplifier 72 for the right channel is transmitted. In the same way, the signal on line 75, the is supplied to the left phase shifter 80, a similar continuous, periodic post and Subject to advance of the phase. The resulting output signal on a line 84 is then disconnected coupled to the left preamplifier 66. The output from the right preamplifier 72 and from the left preamplifier 66 is amplified independently in each case and given to the right "or to the left loudspeaker, the are separated from each other. If you listen to these two speakers, the resulting acoustic effect is a periodic change in frequency and amplitude, which naturally creates the tremulance effect.

The periodic phase change in the phase shifter pair 78, 80 is controlled by a main or control tremulance oscillator 90 causes which generates a left control signal. This is sent to a lamp control circuit 92 for the left channel, which is the phase shifter. 30 assigned for the left channel. A second signal

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passed through a double shaping circuit 94 to generate a different right control signal. The circuit 94 is with the control circuit 96 for Connected the right lamp associated with the right phase shifter 78 * Energize the lamp control circuits lamps which reduce the impedance of the photosensitive ^ control variable impedance elements in each phase shifter. These variable impedance elements are retained, that eiβ a phase shift in accordance with effect their impedance. The control signals are different in terms of their offset and waveform, to produce different phase shifts in the right and left channels, whereby a pleasant acoustic effect is produced, as will be explained.

It should now be assumed that a complex tuning for the solo manual can be achieved by suitable pre-setting of the the rockers assigned to the voice circuit 34 have been selected is. When such a vocalization the tremulance effect is to be subjected, the circuit 60 allows the signal corresponding to the complex tuning to a Line 98 run to an input of an accompanying complex phase splitter 100 forms. In the phase splitter 100, the complex tuning signal is divided into two signals

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split up, one of which is in phase with the one «, incoming signal and 'has one waveform identical to this and the other of which is against the incoming one Signal is 180 out of phase, but otherwise has an identical waveform. The in-phase The signal arrives at the via an output line 102 Phase splitter 80 for the left channel. The phase-shifted signal is sent via an output line 104 to the Phase shifter 78 transmitted for the right channel. Thereafter, the mode of operation corresponds to that described above with the exception that the one coming to the phase shifter pair Input waveform is 180 out of phase.

It is now assumed that the accompaniment complex tuning to be subjected to a tremulance effect. Of the Circuit 60 is suitably adjusted so that the accompanying signal is sent via lines 98 to a phase splitter 100 got. In the phase splitter 100 is the accompanying signal split into two separate signals whose waveforms match the input waveform. In contrast to that Complex signal, the phase splitter 100 does not reverse the phase of one of the output signals. In this way they are Signals carried over lines 102 and 104 to their respective phase shifters, both in phase with

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the input signal representing the accompaniment voice.

Finally, it is assumed that violin tuning 'for the 'upper solo manual has been chosen "and is to be subjected to the tremulance effect. In such a pail the circuit 60 is set appropriately so that the Violin signal via a line 108 and then via the Line 102 only to phase shifter 80 for the left Canal runs. As noted earlier, the violin tuning is isolated and on the left channel only limited. The left channel phase shifter 80 then processes the incoming violin tuning signal in the same way as previously described.

According to the invention, a large number of 'tremulance effects can be obtained as described above. In contrast to the Leslie mechanical playback system, at all organ parts have the same type of tremulance effect are subject, the device according to the invention enables one tailored to the particular tuning Tremulance effect. Plus, this one is tailored or individual tremulance effects with known ones Tremulance devices of the phase shifter type do not possible because the phase switch networks are not in

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different combinations of the above Kind of could be switched. Since the beaked flute part, for example, is closely related to a pure sine wave approximates with a low harmonic content, it can have a larger phase shift without causing a be subjected to unpleasant sound. The phase inversion of the complex signal in the accompanying phase splitter 100 before introduction-to phase shifters 78 and 80 for the right and left channels produce a different tremulance effect that is applied to that voice is compared with the accompanying voice, which has not experienced any phase reversal from the phase shift. the Violin part is treated with phase shift only in the left channel, which creates another tremulance effect arises. This versatility of producing a number of tremulant effects in a single device is a noticeable port step compared to the known tremulance devices.

Pig. 2 shows the circuit 60 and the companion complex phase splitter 100 in detail. The right phase shifter 78 and the left phase shifter 80 and the associated ' Circuit arrangements are illustrated with further details, but in the form of a block diagram.

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To explain the operation of the phase splitter 10, it is assumed that the tuning circuit 34 of FIG. 1 has been set in such a way that a complex stimulus fee on the solo manual is passed. In this case, a signal on the line 54 is present. For simplicity, it will be assumed that there are no signals on lines 52, 53 and 55. It is also assumed that a switch 120 in the circuit 60 is preset as shown in solid line so that the complex tuning signal is transmitted on a line 122. The signal then passes through a suitable input network to the base of a transistor 124. The transistor 124 has a pair of outputs, one appearing on its collector electrode 126 and the other appearing on its emitter electrode 127. The output on collector 126 is 180 ° out of phase with respect to the input applied to the base of transistor 124, ie it is phase reversed with respect to the latter. This phase-reversed output is then coupled via an RC network to line 104, which sends the signal to the input of the second stage 78b of the right-hand phase shifter, which is formed by two cascaded stages 78a and 78b. The signal appearing at the emitter 127! is in phase with that applied to line 122

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Input signal. This signal is sent over a wire 130 coupled to the emitter of a transistor 132. There the signal on line 130 is emitter coupled to transistor 132, that is at the collector electrode 134 of the transistor 132 occurring signal in phase with the signal on the line 122. This at the collector 134 occurring, in-phase signal is sent to the line 102 for transmission to the input of a second stage 80b of the left phase shifter, which is connected in cascade Stages 80a and 80b consists, capacitor coupled, in this way there are two output signals on the lines 104 and 102 are generated when a solo complex signal passes through the phase splitter 100. The signal on the Line 102 is in phase and identical to the input signal (with the exception of * the gain), and that other signal on line IO4 is 180 ° out of phase against the input signal, but otherwise (with the exception of the gain) identical to this.

The reason for splitting the solo complex tuning signaHsin two signals phase-shifted by 180 before coupling to a single stage of a phase-split network for each channel lies in the fact that experience has shown that such a signal is the most sensitive

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wish. Tremulance effect with respect to the solo— Complex voice generated. Palls is not wanted that Solo complex signal on input line 54 to the tremulance effect to submit, the. "switch will be 120 in the position shown with the dashed line switched, so that the signal arrives on line 68. The signal then goes directly to the non-tr emulating Preamp ^ 62 and then to the right and to the left preamplifier 72 or 66.

It is now assumed that the accompaniment complex vocalization as well as the SOlo-Eomplex tuning on the SoIomanual should be subjected to the tremulance effect. In such a pail, the holders are 120 and 140 in the positions shown in Fig. 2 'with solid lines brought. The signal on line 122 is handled in the same way as previously described. The accompanying signal is transmitted on a line 142 to a base electrode of a transistor 144. The transistor stage 144 becomes diminishing in the case of the accompanying signal their impedance is used to enable the Emitter input of transistor 126 (right output stage) and the emitter input of transistor 132 (left output stage) be controlled. After being amplified by transistor 144, the accompanying signal is sent to the

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line 130 RC coupled and then to the emitter 127 of the Tranaistors 124 pushed open "The accompanying signal mixed up deal with the solo complex signal in transistor 124 # so that the exit of the right channel is created. In the same way Way is the accompaniment voicing signal to the Emitter of transistor 132 is supplied where it is calibrated mixed with the solo complex signal to produce the output for the left channel. It is noted that for the accompanying signal has both the right channel output and the left channel output in phase with the Entrance are. This is because, unlike Experience has shown that the solo complex voice has the most appealing tremulance effect, to which the accompanying complex voice can be subjected, then arises when both the exit of the right Channel and the output of the left channel are fed to the phase shifters in phase.

Each phase shift circuit 78 and 80 includes two stages, labeled a and b. Any level can generate a dynamic phase shift of almost 360 ° »This is the maximum when using both levels achievable phase shift about 720 °. Both the solo complex and the accompaniment complex voice are only

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coupled to the output stage of each phase shifter circuit and thus subjected to a dynamic phase shift of less than 360 °. The reason is as follows: Each complete voice has a large harmonic content. In the phase shift circuit, due to the use of the RL circuit, higher frequencies are subjected to greater phase shifts. When a complex voice is processed by the phase shift circuit, the higher harmonics get more phase shift than the lower harmonics. This results in a rather unpleasant musical tone if the complex signal is subjected to too great a phase shift. Experience has shown that a phase shift of 360 ° provides good tremulance for complex tones without causing dissonance effects as a result of more extreme shifts in higher harmonics.

The base of transistor 132 is connected to a capacitor 150 AC coupled to a reference potential source or ground 152, creating an ordinary basic attitude arises. This circuit has good output-input isolation characteristics and thus prevents crosstalk between the left and right channels. According to the invention induced tremulance effect would essentially destroyed if these channels are not suitable

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net are separated from each other. The failure, - the electrically isolate lines 102 and 104 from each other, would result in a signal path that the outputs of the first stages of the left phase shifter and the right Would connect the phase shifter. If this were the case the outputs of the two stages would be connected to each other electrically mix «This would be the intended one Destroy the effect of these two levels, since the tremulance effect is realized according to the invention when the Outputs from two separate channels in the room acoustically be mixed.

When the accompaniment complex voice is not subjected to tremulance is to be, the switch 140 is brought into the position shown by dashed lines, and the signal is on the line 55 reaches the preamplifier 62 via the line 68.

It is now assumed that the violin timings instead of the solo complex tuning for the solo manual will. In such a pail, a switch 160 will do so set as with the solid line in Pig. 2 is shown. The violin timing signal then becomes transmitted on line 35, from where it is via an "RC network is fed directly into line 102. 'Vie As noted earlier, violins are preferred only in the left channel. Should the use of tre-

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are mulanz not desired on the · Violin, sef ^Λ, the switch 160 is in the dashed lines ^" 'brought ■ location ,, so that the signal on the line 53 for''''reaches the line 65, since Viölinstimmen musical n.' tir in. the left channel "are preferred, the Viölinstimmgebungssignal au is in turn directly via line 65 ■ the gated amplifier" 66 füo? i? n left channel crosses "wear.

^When: elected to DEM solo Manual - Schnabelf lötenstiifiine the Tretnulanz-Ef f ect ■ to be subjected ,, the Sehalter 170 so ■ "wird- set, as shown by ausgezogener- line" .The Schnabelflötenstimmgebungssignal is then on.. .... line 75 and via the lines 75a and 75b transmitted to the first phase shifter stage 78a of the right channel and the first phase shifter stage 80a of the left channel · There will notice _r that- the "- ■. Schnabelflötehstimmungssignal τοπ the complex Fha-. senteiler 100 is not dealt with »With the beak flute tuning signal it is not necessary to split the signal into two separate channels to prevent side coupling, since the signal is fed into the first stage of each phase shifter and not into the output stage as in the case of complex signals. ₌ When the signals are fed in, they run independently

dependent on each other in the two separate channels. In addition, it should be particularly pointed out that only that Beaked flute signal subjected to the two stages of phase shift in the right and left channels i.e. a phase shift of approximately 720 ° takes place. Such signal processing is musical Relationship desirable because the beaked flute part has almost a pure Sinjius wave, i.e. it includes you very low Oberwalden content. With a beaked flute part it is therefore possible to shift the signal more in phase because of the lack of harmonics prevents dissonant sound even when large phase shift is applied. The size Phase shift is useful because it gives a very strong tremulance effect on a beaked flute voice is particularly pleasant. Two phase shift stages are used to effect the larger phase shift en used. After the beaked flute tuning signals have passed through the right and left channels of the phase shift circuitry, they will be over lines 82 and 84 separately to the preamplifier for the right channel and to the preamplifier 66 for created the left channel.

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If there is no tremulance of the beaked flute tuning signal is to be achieved, the switch 170 is brought into the position shown in dashed lines, and the beaked flute tuning signal reaches V preamplifier 62 on line 68.

The operation of the phase shift circuitry and associated stages is in Jig. 3, 4 and 5 shown and is explained in connection with these. To achieve a phase shift tremulance effect the electrical phases of the left and right channels must be periodic at a frequency of approximately 6.7 Hz be brought to lead and lag. According to the invention, the electrical phases of the right and left channel signals running over almost 360 ° in spring pair of cascaded stages in which the left and right phase shifters are rotated.

In making this puncture, the phase shift circuitry delivers according to the invention a more pleasant tremulance effect than the known technique the phase shift in that it is the phase of the lower frequency harmonics less than the phase which dynamically shifts higher frequency harmonics.

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This gives a result that can be described as a percentage constant frequency deviation resulting from the the following reason is highly desirable. if low-frequency harmonics of a musical signal (for example, those below 200 Hz) Dynamically phase shifted over a significant number of degrees (e.g., approximately 720) at 6.7 Hz frequency the perceived frequency change due to the Doppler effect is quite extreme. This follows because the number of periods, the frequency of which deviates upwards or downwards from the nominal frequency, from the Tremulance frequency and the number of degrees of dynamic phase shift depends. If the Hertz number, by which the frequency deviates is significant compared to the target frequency, the percentage frequency deviation becomes be pretty big. This percentage frequency deviation is the critical factor in making a desired one Tremulance. For example, if high frequency harmonics by the same number of degrees with the same Tremulance frequency such as lower frequency harmonics would be out of phase with the percent frequency deviation of the lower frequency harmonics be greater than the percentage due to the difference in the setpoint frequencies Frequency deviation of high frequency harmonics. this is a serious disadvantage of the known phase

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slide tremulance devices as it is in musical Relationship is pleasant, an approximately equal percentage frequency deviation regardless of the target frequency to have. The phase shifters according to the invention do this in a manner explained below.

The principle of operation of the yer- applied phase shifter circuits can be related can be understood with FIG. 4. A single lamp 200 illuminates a light dependent resistor 202. When an AC signal is supplied on line 204 to the Base electrode of a transistor 206 is applied, is the signal at a collector electrode 208 of the transistor 206 out of phase with the applied signal by 180 ° on line 204. Also, the signal at an emitter electrode 210 of transistor 206 is in phase with the applied signal. This provides two outputs that are 180 out of phase. The collector electrode 208 is coupled to an output line via an inductance 212, which is connected to a node between the inductance 212 and the IiGht dependentη Resistor 202 is connected.

Assuming that the lamp 200 does not burn, obtain

the light-dependent resistor 202. no light, so that his resistance is high. It is believed that the

has when he does not receive any light. In this case: 1s ¹ ; ii: 'ε 3i'"l" fictivity 212 unloaded, so that no alternating current flows through it. The output is a shifted signal on line 214 that is in phase with the signal on collector 208. "This signal is 180 ° out of phase with the input signal on line 204. When lamp 200 is energized and begins to glow, a point is reached at which the resistance of light resistor 202 equals the inductive reactance of inductor 212 . At this point, the combined wiring of inductance 212 and light-dependent resistor 202 should cause the output voltage and input voltage to lag by 90 °. When the light-dependent resistor 202 is finally fully illuminated, it has its lowest resistance and the in-phase component at emitter 21C predominates on output line 214. Thus, assuming a short-circuit condition in light-dependent resistor 202, the output on line 214 is in phase with the input on line 204

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be. When the 2CC lamp returns to its perfect state Darkness is brought about, the phase of the voltage on line 214 shifts again by 180 to the phase of the input on line 204. In this way, the phase of the signal on line 214, when the lamp 200 is lit and darkened, with With respect to the input on line 204 progressively brought to Vcreilen or to compartmentalizing. Although the simplified phase shifter circuit in Pig. 4 an inductor 212 is used, it is obvious to use a capacitive element instead. In this pail viurd the direction of the phase shift when alternating Lights and Kichtlights of lamp 200 opposite to the direction of the phase shift that results when using an inductive element.

With reference to Pig. 3 and the first stage 78a of the right Phase shifter it is noted that a capacitor 400 is in the phase shifter circuitry. The capacitor 400 forms a series resonant circuit with the inductor 212. When a signal with a frequency, which is below the resonant frequency of the series resonant circuit, is applied to the line 204, outweighs the Effect of the capacitor 400, and the phase shifter

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circuitry works in a capacitive Y / shape. When a signal occurs at a frequency which is above the ReihenresonanzfrequeEz on line 204, the phase shifter circuit arrangement operates in an inductive Äfeise ^T. In a preferred embodiment of the invention, capacitor 4CC has a value of 10 yuF and inductance 212 has a value of 0.350 H. This results in a series resonance frequency of 84 Kz. Semit is used for signals applied to line 204 with frequencies below 84 Hs caused dynamic phase shifting caused in a lease that is opposite to the pLichtung for applied signals ni t frequencies above 84 Hz. Thus, signals appearing on line 214 having a frequency below 84 Hz are caused to continuously change in phase in accordance with the light guidance of lamp 200. Signals on line 204 with frequencies above 84 Hz are also continuously changed in phase with the lighting of lamp 200, but in the opposite direction with respect to signals with a frequency below 84 Hz.

The phase shifter just described is followed by one Phase reversal circuit using a Darlington amplifier

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220 used. This provides a high input impedance for the smallest load and a shared load low impedance to drive the second phase shifter,

The second phase shifter corresponds to the one described

first phase shifter and a capacitor in series with the inductor 222. This is a series resonant circuit dui "ch the capacitor 402 and the inductor 222 formed wiederuB) which is connected to the collector electrode of the Darlington amplifier 2 20th A Ii chtabhängiger resistor 224 is is coupled to the center of Darlington amplifier 22C and is actuated by lamp 200. In a preferred embodiment of the phase shifter under consideration here, capacitor 402 has a value of 40 μF and inductance 222 has a value of 0.350 H, with one being Series resonance frequency of 42 Hz. Thus, signals applied in this phase shifter with a frequency below 42 Hz are dynamically phase shifted in the same direction as signals with a frequency below 84 Hz in the first part of this phase shifter. Applied signals with frequencies between 42 and 84 Hz dynamically out of phase in a direction opposite to that of Ri attention to the phase shift is that in the first

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Phase senia "overshadowed" -. Collateral is effected. Signals with frequencies over 84 Ez will of course be in the same direction in two phase shifters dynamically phase shifted. The output of the second phase shifter goes to the output transistor 226 is applied before feeding into the second stage of the right phase shifter.

The third phase shifter and the fourth phase shifter which are the second stage of the right phase shifter 78b operate in a similar way to the first and second phase shifters in the first stage of the right one Phase shifter. However, the capacitor 404 has in one preferred embodiment a value of 2) uF, and the Inductance 406 has a value of 0.350 H, resulting in a series resonance frequency of 190 Hz. The condenser 408 has a value of 10 / uF, and the inductance 410 has a value of 0.350 H, resulting in a series resonance frequency of 84 Hz. In this way In the second stage of the right phase shifter, all signals and frequencies above 190 Hz are in the same Direction of both phase shifters dynamically phase shifted. All signals with frequencies below 84 Hz will be also dynamically out of phase in the same direction, but this direction is opposite to the

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Shift direction for signals with frequencies above 190 Hz. Pure signals with a frequency range - between 64 and 19c Hz becomes the direction of the dynamic phase shift in the first phase shifter opposite to the shift direction in the second phase shifter.

The practical effect of selecting the resonance frequency of each of the four phase shifters in that described above Way is to reduce the dynamic phase shift for signals with frequencies below 190 Hz. For example, a 50 Hz signal turns into the opposite Direction of the first and second phase shifters dynamically out of phase. Egg gives a partial Cancellation of the phase shift effect, since the resulting phase shift is the difference in the individual dynamic Phase shifts is. However, in the third and fourth phase shifters, the phase shift direction is for the 50 Hz signal equal, so the total phase shift is the sum of the two individual dynamic phase shifts. .Fatur-I are for all signals with frequencies greater than; 190 Hz dynamic phase shifts in all four Phase shifters additive, resulting in a dynamic phase shift of approximately 720 °, as each

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the four phase shifters a shift of almost 180 ° can cause. Since the dynamic phase shift of signals with frequencies below 190 Hz is smaller than that of Signals with frequencies above 190 Hz as a result of the selective cancellation of the phase shift effect through interaction is the four phase shifter, the resulting percentage frequency deviation of signals with the target frequency below and above 190 Hz brought closer to the state of equality than with known phase-shift trenulancy controls considerations.

The left phase shifter with the first and second stage is identical to the right phase shifter in FIG first and second stage. Therefore a detailed! Description of the left channel of the phase shift circuitry is not required. One to line 75a or signal applied to 75b passes through both the first and second stages of their respective ones Phase shifter to achieve a phase shift of around 710. If the signal only in the second Stage b of their corresponding channel phase shifter fed becomes, as is the case with signals applied to lines 104 and 102, there will be a phase shift reached by only about 355 °. As previously mentioned

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only the beak soldering tuning signal becomes subjected to a phase shift of 71C ° to one to obtain the desired stronger tremulance.

It's a gradual lead and lag of the phase To bring about with the phase shifter for the right fan, the lamp 2CO must periodically from a dark to a luminous state can be controlled. The excitation of the right and left channel lamps is initial controlled by a tremulance oscillator 90 which is a 6.7 Hz signal to a tremulance P todulation direction supplies. Two out-of-phase outputs are provided by oscillator 90, which is shown in detail in FIG Pig, 3 is shown.

The tremulance oscillator 90 includes transistors 250, 252 and 254 ·· When transistor 250 conducts, positive charging voltage is applied via resistors 256 and 257 a capacitor 260. As the voltage across capacitor 260 increases, the collector current increases accordingly of transistor 254. The voltage at the collector of transistor 254 then drops towards ground potential. When the voltage at the collector drops towards earth potential, a signal falls on a η. · Ίΐ dem

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Collector of transistor 254 connected line 262 also in the direction of ground potential, whereby the base modulation for transistor 252 falls. This causes transistor 252 to be non-conductive to pass, whereby its collector potential increases. When the potential is at the collector of the transistor 252 increases, the transistor 250 is brought out of the conductive state. The capacitor 26C discharges then through the resistors 257, 256 and through a resistor 264. When the voltage of the capacitor 260 decreases, the collector current of transistor 254 decreases, thereby increasing its collector voltage caused. When the voltage-at the collector of the transistor 254 increases, the signal on line 262 increases, adding an increased base level to the Transistor 252 arises. Thereafter, transistor 250 returns to a conductive state, and that just described The period of oscillation begins again.

The frequency of oscillation is governed by the RC time constant of capacitor 260 and resistors 256, 257 and 264. The W _e rt of the resistor 256 is variable and is selected so that an oscillation frequency of approximately 6.7 Hz is generated. When the oscillator is

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231952Q

vibrates, a square wave arises on one Output line 270, and another square wave that out of phase with the foregoing is available on line 272. These output lines are on the right channel lamp control circuit or coupled to the left channel lamp control circuit

The square wave signal on output line 27C is given to the double shaping circuit 94. The circuit 94 is used to generate a double frequency pulse which is only coupled to the lamp control circuit 96 of the right phase shifter. in the essentially, the double forming circuit acts like a double switch, one side of which is on. the positive going part of the input signal and the other side responds to the negative going part. The outputs of the two sides are then combined to form a To deliver control signal with doubled frequency output.

The operation of the double shaping circuit 94 will be described assuming that a positive going Square wave is received on line 270. A pair of capacitors 280, 282 differentiate the square pulse, to increase positive and negative running impulses

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as shown at 284, the positive going pulse causes transistor 286 to provide an output pulse on line 287; Causes the negatively ver ~ current pulse ", that a transistor 290 enters the conductive state, and outputs a second pulse on line 287th In this V / else the combined offset, extending to the right lamp control circuit 96 appear signals between the end it A resistor 292. In FIG. 5A, the double-frequency pulses generated at the resistor 292 are shown with the curve 300.

When a pulse arrives, transistor 302 turns on right lamp control circuit 96 in the conductive Condition pre-tensioned. As a result, a cascaded transistor 304 is similarly biased. When transistor 304 conducts, it supplies current on line 306 to lamp 20C. As a result of this, the light intensity of the lamp 200 is controlled by the waveform 300 (Pig. 5A) which is between the ends of resistor 292 is applied.

The arrangement of the left lamp control circuit 92 is identical to the arrangement just described for

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231952g

the. right lamp control unit ^ sscbal ^ ng 96. JeaccL leuchvc ^ ^/! .jo larip '.- J.2.L Ji: eggs; · Γ1 u.! -. T ^ cLr · ^r · ..; ·· 80 for the llnkwn channel ,, da k «n« double If er onlyέ, Η '^ οΙ. & Κ-.υ.ϊι ^ -. .v? 'i.-cl; .ft .the tremulance oscillator 90 and lamp control circuitry ,, .not in the same way as. the lamp 200 in the phase shifter 78 for the .right channel, but the lamp 320 is excited by a signal 322, .das in Pig. 5B is shown. Thus, the two controlling waveforms 300 and 322, which are shown in combined form in FIG. 5C, "are time-shifted and produce an alternating or alternating effect. It has been found, according to experience," that a highly desirable form of the tremul ' num is generated with the 'signals "shown in Fig. 5. -""'':"'"" .. "~

Since the waveform of the. Generating the most desirable tremulance effect according to the invention are critical, they will be considered in greater detail - in the: right, ICanal is created .. The · = ■. ^; . Waveform; 300 be, ^{a second pulse 332 'results from a first pulse 33 0} J. ^ ¹¹¹ , These double pulses cause: because of the. of the "lamp, own · thermal delay / · not: dai3. the lamp.pe. 200; lights up twice. - On the other hand:. · j · - the first pulse 330 causes the

309

COPY BAb ORIGINAL

Lamp, so that the light output of the lamp when applied of pulse 332 increases faster than would occur without preheating. When the pulse 332 goes to zero returns, the decrease in the light output of the - lamp follows not the waveform of the trailing edge of the pulse 332, because the light output according to the thermal Delay of the lamp decreases. ", ·. '-. ■ <..'".

Although the exact Lichtansprechkurve of the lamp is not shown under the control of the waveform 300 200, such a control waveform is used to compensate for certain non-linearities in the response curve of the lamp ¹ and the associated light-dependent resistance. The resulting resistance value of each light dependent resistor in the phase shifter for the right channel is given by curve 340 in Mg. .5A -, _ as a puncture of time. shown. With reference to -tlFig. 5A it is noted that. . the resistance value of lichtabhängigea 'resistance of the right channel, "when the pulse falls 332 to zero, as the waveform indicated by the designated 332a part until later after a substantial time"' - space begins to rise. As stated above, ge. ^: . ^; This happens because the light output of the lamp 200 does not stop immediately when its control voltage is removed

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becomes, but only slowly wears off. This ergilot a Delay before the lighting of the light-dependentη Resistance ceases so that the increase in its resistance value is delayed, like waveform 340 shows. When the voltage pulse 330 is applied to the lamp 2GO, this does not immediately result in a Light output. This causes a smaller time delay, when the light-dependent resistance begins to fall with respect to a resistance value. As you can read above pulse 330 also causes lamp 200 to be preheated so that upon application of pulse 332 lights up very quickly, causing a rapid drop in the resistance value of the light-dependent resistor as illustrated by part 340a of curve 340. This change in the value of the light dependent resistor causes the phase shifting circuitry shifts the phase of a passing signal in such a way that the frequency deviation of the signal changes as shown by curve 344 (Pig. 5D).

Similarly, the resistance of each light dependent resistor in the phase shifter is for the left one Canal as a puncture of time through curve 346 in

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Fig. 5B. The creation of such a thing as the The pulse shown at 322 gives the V / i of the status curve 346, which then gives a frequency deviation to the left channel as illustrated by curve 350 (FIG. 5'S) is.

It has been found that the frequency deviation shown as curve 344 in Figure 53 gives a very desirable tolerance effect. In contrast to known l'inulance effects, the control waveforms and the circuit arrangement according to the invention are designed so that there is no continuous phase change, as has been typical up to now. In contrast, the frequency deviation of the signal, as illustrated by waveform 344, occurs in spaced time zones in that between times t .. and tp the frequency deviates in a gradual, almost sinusoidal manner below and above the desired frequency. However, the frequency does not deviate during the period between tp and t ₁ , but essentially remains at a desired value. This pause or lack of continuous frequency deviation is believed to be partly responsible for the improved tremulance effect achieved in accordance with the invention.

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The acoustic interaction between thinking, right and the left channel of the organ to create a change in amplitude or the tremolo effect can be understood with reference to Fig. 5F which shows the envelope of the Beat between the output signals of the left and right channel shows. The Modulati ο nshiill curve illustrates the volume changes that each Equal-spaced channel speakers would hear a 1000 Hz sine wave in the left and in the has been fed into the right channel, each such wave being dynamically-phase-shifted in a continuous manner has been. The improvement of the tremulance. The effect arises from the different parts of the Circuitry and waveforms as previously described became.

As can be seen from Figs. 5D and 5E, the frequency deviation occurs in the right channel (curve 344) not during the same time period as the frequency deviation in the left channel (curve 350), but the frequency deviations in the right and left channels occur alternately with each other because the larger frequency deviation period in the right channel (i.e. the period between t. and t ") with respect to that of the larger one

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Left channel sequence deviation period delayed will. The resulting acoustic effect is one more or less continuous amplification and cancellation of waveforms, producing a desired change in amplitude results. It is assumed that the alternate occurrence of the frequency deviation periods continues to the contributes to an improved tremulance effect. Besides, the resulting pleasant tremulance effect for most of the individual tremulance effects available that are selective with the establishment through the previously described Combination of phase shift circuits realized can be.

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Claims (18)

Claims 1 J Means for producing various periodic changes in electrical signals which have various Represent musical instruments characterized by a number of sources of electrical signals, each of which has a different harmonic content to suit different musical instruments, a number Phase shifting devices, each of which is variable Has devices which are controllable to the phase shift of the corresponding phase shifter device to change, oscillator devices coupled to the variable devices periodically changing the phase shift applied by each phase shifting device of the said number is caused, circuit devices for connecting said number of phase shifting devices in different circuits, each of which produces different amounts of phase shift, and switching devices for coupling various 3098 44 / O467 Sources of the stated number of different circuits which use the stated number of phase shifting devices combine to produce different periodic changes in the signals from the various sources to create. 2. Device according to claim 1, characterized in that that said plurality of sources includes a first source of a first electrical signal and a second source of a second electrical signal, wherein the second electrical signal has a greater harmonic content than the first signal has that said number of phase shifting devices first phase shifting devices, the are responsive to first variable devices to produce a first variable phase offset is, and has second phase shifting devices that act on second variable devices such respond that a second variable phase shift deviation it is caused that said circuit devices form a first circuit around the first and serially connecting second phase shifting devices to produce an overall phase shift which is approximately equal to the sum of the first and second phase shift deviations, and a 309844/0467 second circuit "form the first phase shifting devices to be connected in parallel, so that an overall phase shift is generated which is approximately equal to the second phase shift, and that said Switching devices said first source with said first circuit and said second source with the said second. Connect circuit. 3 »Device according to claim 2, characterized by first channel devices for processing and reproduction said electrical signals and second channel devices for processing and reproducing said ones electrical signals, the acoustic interaction of the electrical signals reproduced by the first and second channel devices is a tremulant one periodic change and characterized in that said first and second phase shifting means are arranged in the first channel devices that said number of phase shifting devices third phase shifting devices based on third variable Devices for generating a third phase shift deviation respond, and has fourth phase shifting devices that respond to fourth variable devices for the purpose of generating a fourth phase shift 309844/0467 address exercise deviation, the third and fourth Phase shift devices in the second channel devices are arranged so that the circuit devices form a third circuit to the third and fourth To connect phase shifting devices in series so that an overall phase shift is produced, which is approximately equal to the sum of the third and fourth phase shift deviations, and that the circuit device form a fourth circuit in order to connect the third phase switching devices in parallel, see above that a total phase shift is produced which is approximately equal to the fourth phase shift deviation, and that said switching device said first source and said second source to said first circuit and to said, respectively second circuit and coupled to predetermined circuits, which are arranged in the second ifanal devices. 4. Device according to claim 3 »characterized in that that the switching device simultaneously couples the first source to the first circuit and to the third circuit, 5. Device according to claim 3 »characterized in that the switching device is the second source at the same time 09844/0467 couples to the second circuit and to the fourth circuit . 6. The device according to claim 5> characterized in that the switching device has reversing devices for generating a phase shift of approximately 180 ° and that the switching device switches the Urr. reversing device between the second source and the second or fourth circuit to thereby connect to äi e second and fourth phase shifter device to apply a pair of electrical signals that are un 180 out of phase. 7. Device according to claim 5, characterized in that the circuit device includes isolating means for dividing the second signal from the second source into two split in-phase parts, and that the switching device, the disconnectors with the second and fourth circuit connects in order in this way to the second and fourth phase shifting devices ei-n pair to apply in-phase signals without causing side coupling between the first and second channel devices. 8. Device according to claim 3> characterized in that that the switching device is the second source of the 309844/0487 separates the second E ~ analvorri rnicht., 'so that the second Signal processed only in the first Fanalvorriehcungen will. 9. Device according to claim 1, characterized by first channel devices to "^ elaborate and reproduce" of electrical signals and second channel devices to process and play back the named electrical signals, each phase shifting device a first stage arranged in the first channel devices and a corresponding one in said channel devices arranged second stage and each stage has a variable device which 'to change their phase shift is adjustable, and characterized in that the switching device has the stages of the phase shifting device in respective circuits in each of the first and second channel devices with each other connects, and that the oscillator device means for generating various control signals and means for coupling the various control signals to the variable devices in the interconnected in the first and second channel devices, respectively Has steps to different phase shift deviations in those of the first and second 309844/0467 Duct devices processed electrical signals to create. 10. Setup to generate a periodic change in an electrical signal representing an IuRik voice, characterized by a source of said electrical signal, first channel devices connected to coupled to the source for processing the electrical signal are and have first phase shift devices, having a first variable device that is adjustable around that in the first channel devices to change generated phase shift deviation, second channel devices sent to the source for processing of the electrical signal are coupled and "second phase shifting devices have, which have a second variable device that is adjustable to the in the second channel devices generated phase shift r to change deviation, oscillator device / to generate of a pair of different control signals with different periodic changes, the oscillator devices Have devices to said pair of control signals individually to the first and second to couple variable device, so that different phase shift deviations in the first and second 309844/0467 Channel devices generated v / earth, and to the first and playback devices coupled to second channel devices to respond to said periodic change to the difference in phase shift deviation between those in the first and second fan devices to reproduce electrical signals. 11. Device according to claim 10, characterized in that that the Gszi llaforvorri rect devices for phase shifting of the pair of control signals and that the first variable device and the second variable device respond to the phase shifted control signals such that they offset phase deviations in the first and second liana! devices and thereby creating an alternating or alternating effect in said periodic change. 12. Device according to claim 11, characterized in that said phase shifting device wave shaping devices for changing the waveform of an oscillation signal, with one of the control signals in of the waveform is the oscillation signal and the other control signal is in the waveform of the waveform shaping device generated, modified waveform. 309844/0467 13. Device according to claim 10, characterized in that that the first variable device responds to one of the control signals coupled thereto in such a way that recurring Periods of the phase shift are generated, with each recurring period having a first time component, the first phase shifting device to produce a substantially continuous frequency deviation controls, and has a second time component which controls the first phase shifting device so that substantially no frequency deviation occurs. 14. Device according to claim 13, characterized in that the oscillator device has devices for phase shifting of one of the pair of control signals, the second variable device responding to the phase shifted Control signal responds in such a way that a third time component, which has a substantial frequency deviation in the second channel devices is caused to alternate with said first time portion. 15. Device according to claim 10, characterized in that each of the variable devices has light-dependent impedance genera with an impedance value ₉ which corresponds to the incident light energy ₉ first Lamp devices for controlling the amount of light energy, which 'hits the impedance device in the first channel devices, second lamp pen devices to control the amount of light energy applied to the Impedance device in the second channel devices occurs, and the aforementioned individually coupling Devices that send the pair of control signals "to the first "or couple the second lamp device. 16. Device according to claim 15, characterized in that the oscillator device doubling devices for causing the one control signal to include a pair of pulses, the other control signal has a single pulse for each pair of pulses generated by the doubling devices. 17. A device according to claim 15, characterized in that each phase shift device is transistor devices rides first and second output electrodes and a control electrode and devices coupling the control electrode to the electrical signal to be processed, as well as has reactance devices coupled between the first output electrode and a node and that the borrowed (»dependent impedance device between the second 309844/0467 The output electrode and the node are coupled, to cause the electrical signal at the node to have a phase shift equal to the impedance value corresponds to the impedance device. 18. Device according to claim 17, characterized in that each of the first phase shifting devices and the second phase shifting devices has a number of transistor devices, reactance devices and light-dependent impedance devices, that the node to which _: the first switched transistor device is assigned in each phase shifting device is in series with the control electrode of the next transistor device and that the lamp device for. each channel device causes substantially the same light energy to strike all of the light-dependent impedance devices in the associated channel devices simultaneously. 309844/0467 Blank page