DE1541373B2 - TRANSMISSION SYSTEM FOR MESSAGES CONTAINING BINARY CODES - Google Patents

Description

The invention relates to a transmission system for binary codes containing messages.

The invention also relates to an arrangement for transmitting binary code signals by means of a high frequency device capable of time division multiplexed telephone signals transmitted through the PCM system.

It is known that a polyphase modulation arrangement is usually used for the method for Transferring information by binary code signals, e.g. B. PCM signals and telegraph code signals, is used.

On the other hand, it is also known that in addition to the frequency division and time division methods the method of the polyphase modulation arrangement as a method for multiplying a transmission line can be used. The last-mentioned polyphase modulation arrangement requires however, a carrier wave that is associated with the received wave for the purpose of demodulation in the Phase is synchronous, with the result that the equipment becomes expensive, and therefore this system is disadvantageous from the point of view of cost and reliability.

The FDM-FM system, i.e. the frequency multiplex FM transmission system, is for an arrangement for the transmission of multiplex telephone channels has been used by a high frequency device. However, this arrangement requires a very precise reference value for such conditions, since the transmission property, the noise suppression the transmission arrangement and the efficiency of the equipment can be very high must to meet this requirement, which makes the equipment very expensive. But if one Telephone multiplex arrangement with time division used by the PCM system in place of the usual FDM-FM system are the above Conditions are far less precise, and sufficient performance can be achieved through a relatively simple Equipment that is not costly can be achieved. This results from the fact that the structure of the channel part in particular, the PCM connection equipment is simpler than the structure of the FDM connection arrangement, and therefore the high frequency device can also be simple in structure.

The invention is based on the object of a transmission system for binary codes devices for synchronizing the transmission carrier wave with the received carrier wave, like this one before especially when receiving.

The object is achieved by the invention specified in claim 1.

According to the invention, a pulse train representing the binary codes can thus be demodulated and can be regenerated by passing the transmitted phase-shifted wave through a phase discriminator runs, resulting in a particularly simple circuit arrangement.

With this simple circuit arrangement, a multiplex transmission can be created, which transmits a train of pulses representing the binary codes.

Exemplary embodiments of the invention are shown in the drawing, in which are

F i g. Figure 1 is a schematic representation of equipment according to the invention used in radio frequency transmission PCM codes are used,

F i g. FIG. 2 is an illustration of the method of converting the waveforms for explaining FIG Embodiment according to FIG. 1,

F i g. 3 shows the frequency spectrum of the transmission wave,

F i g. 4 shows a block diagram of a further embodiment of the invention,

F i g. Fig. 5 is an illustration of the method of converting the waveform by the embodiment according to FIG. 4,

F i g. Figure 6 is an illustration of the vector diagram of the phase of the wave in each interval of Figure 6. 5,

F i g. 7 is an illustration of the waveform of the transmission wave when the waveform of the modulated Wave F i g. 5 corresponds, and

F i g. 8 is a diagram corresponding to the waveforms of FIG. 6th

F i g. 1 shows the transmitter 1, the receiver 2, the transmitting antenna 8, the receiving antenna 9, the input terminal 3 of the binary code, e.g. The PCM signals representing the information to the waveform converter 4 for converting the input pulse trains into various square waves, as described below with reference to FIGS. 2 described through the phase modulator 5 for modulating the phase of the lower carrier frequency the pulse signals, the frequency up converter 6 for increasing the output of the phase modulator 5 on the high frequency, the local transmitter oscillator 7 for supplying the local transmitter oscillation frequency to the frequency up converter 6, the frequency down converter 11 for converting the from high frequency coming to the receiver into the intermediate frequency oscillation with low frequency, the local local oscillator 10 for supplying the local local oscillation frequency to the Frequency down converter for converting the frequency on the input side, the demodulator 12 for demodulating the output of the frequency down converter 11 into the original signals and the output terminal 13 of the demodulated binary code signals.

According to FIG. 1, P _{a are} the binary code trains which are the original PCM signal inputs. These pulse trains are shown in FIG. 2 shown under (a) or (b). The in F i g. The pulse trains shown in FIG. 2 (a) are monopolar, and the pulse trains shown in FIG. Pulse trains shown in Figure 2 (b) are bipolar.

As in Fig. 2 (a) or (b) are shown form a certain number of bits, e.g. B. 7 bits, from original PCM signals one channel. For example 24 channels form one frame, i. H. an impulse train. The digits (21) to (27) of the codes form a channel, and F i g. 2 (b) shows a case where binary codes "1" are present at positions (21), (22), (25) and (27), i.e. the code formation is 1100101. In this embodiment of the invention, the train of successive pulses is turned into one train converted from square waves as shown in FIG. 2 (c), each of which has a wave width of Γ has what the pulse interval between two adjacent pulses from the train of consecutive Impulses emanating from the first impulse. In the case of FIG. 2 (a) and (b) these are e.g. B. the pair (21) and (22) and the pair (25) and (27). The waveform conversion can be done by the

Waveform converter 4 (Fig. 1) take place, the ζ. Β. includes a flip-flop circuit. In the embodiment the F i g. 1 the phase of the intermediate frequency of the microwaves is represented by a square wave train, which is the output of the waveform converter 4, modulated by means of the phase modulator 5, and a kind of phase-shifted wave is obtained as the output of the phase modulator 5. The phase this phase-shifted wave takes the same shape as F i g. 2 (c) on, but the current one Frequency change is shown in FIG. 2 (d). Then the phase shifted wave (an intermediate frequency in the present embodiment) with the local transmission oscillation frequency in the Frequency up converter 6 mixed and transmitted and as a microwave from the transmitting antenna 8 submitted.

The microwave input, which has been received by the receiving antenna 9, is on the receiving side is mixed with the local received oscillation frequency by the frequency down converter 11, whereby a phase-shifted wave of the intermediate frequency, that of that mentioned above, is obtained phase shifted wave is equivalent. When this phase-shifted wave through the demodulator 12 is demodulated, are shown in FIG. 2 (d) waveforms shown at (30), (31), (32) and (33) are instantaneous Obtain waveforms with frequency change. In the present embodiment, an FM demodulator known in high frequency technology can be used as demodulator 12.

This is because the phase of the phase shifted wave changes, as in FIG. 2 (c) and the instantaneous frequency change Δ f is given by

Δ f = / "ζ) Θ ,

where f _{0 is} the center frequency (the intermediate frequency in the present embodiment) of the phase-shifted wave and Θ is the shift in the phase of the phase-shifted wave.

These waveforms of the output of the demodulator 12, as shown in FIG. 2 (d) are the Restoration of the original waveforms Signals, and this shows that the PCM transmission is carried out by a high frequency device can be.

F i g. 3 shows the result of the actual calculation of the energy distribution of the sideband contained in the phase-shifted wave signal. As can be seen from this illustration, the energy distribution has an infinite extent, but the majority of the energy is in the range of ω ₀ ± 2 ω _χ if m _{0 is} the angular frequency of the center frequency of the phase-shifted wave and ω _χ = 2 π / 2 T when the period of the repeating frequency of the original PCM signal is T. There is therefore no problem in practice if only this area is transmitted.

In the case of the transmission of 24 channels, e.g. B. ^ _{1 are} expressed as 2 W ₁ = 1.5 MHz, so that the bandwidth required for transmission is the bandwidth of ± 1.5 MHz = 3 MHz.

In the case of transmission of PCM signals the conditions of the relationship between the signals are low, so that in the embodiment of Fig. 4 waveforms of the PCM signals P _einl, P _in2 and P _in3, each multiplied by such a unit. B. 24 channels, can be converted by the waveform converters WC ₁ , WC ₂ and WC ₃ in the above manner. Furthermore, the phases of a plurality of carrier waves (intermediate frequencies in the present embodiment) are modulated by the phase modulators PM ₁ , PM ₂ and PM ₃ , whereby phase-shifted waves are obtained. These then go through band pass filters BPF ₁ , BPF ₂ and BPF ₃ , which have a bandwidth of ± 2 W ₁ , as described above. The frequencies of this wave are then multiplied and at the same time they are amplified or their frequencies converted, which also makes it possible to transmit them by placing them in a single high frequency band with a width of about 20 MHz.

It is also an advantage of the invention that it can be carried out at low cost.

In another embodiment of the invention in which another method of converting the Waveform is used, the PCM signals in the case of a bipolar pulse train z. B. by one shown in FIG. 5 (a) shown pulse train. But if you want, these signals to multiply and z. B. to be transmitted by a radio frequency arrangement, it is necessary to use the Modulate high frequency carrier wave in some way. In the present embodiment this modulation is carried out by the polyphase modulation arrangement.

In the following description of the four-phase modulation, consider a case where the PCM codes are the bipolar pulses shown in Fig. 5 (a). In this example, as in the previous example, 7 bits form a channel and the positions of each bit are denoted by (41) to (47). The codes of FIG. 5 (a) therefore represent the codes of 1110110. This pulse train is converted into a square wave A as shown in FIG. 5 (b), the wave width of which is the interval between two adjacent pulses, e.g. B. (41) and (43) from the positive polar pulses of the pulse train, and converted into a square wave B , which is shaped by the negative polar pulses in the same way as described above. This process can be carried out in a simple manner, for. B. be carried out by a known flip-flop circuit.

On the other hand, the phases of the two carrier waves are individually modulated by the square waves A and B with a phase difference of 90 ° from one another. In this case the degree of modulation is ± nβ in both waves. These two modulated waves can be represented by vectors / 11-3, J32-4, / 13-5, B 4-6, as shown in FIG. 6 shows that have a phase difference of π / 2 in order. Some parts of these vectors overlap in time, so that by combining these two modulated waves, vectors can be obtained which rotate over time, e.g. B. OP, OQ, OR and OS, as shown in Fig. 6, depending on the type of time overlap. When the original signals of the PCM codes have such a form as shown in FIG. 5 (a), this time overlap relationship is P, Q, R and S as shown in FIG. 5 (d) is shown. Thus, the PCM code train is in

an arrangement of modulated polyphase waves (modulated four-phase waves in the present case Embodiment) converted with a phase difference of 90 ° to each other.

When the modulated polyphase waves (four phases in the embodiment) are e.g. B. by a Radio frequency equipment can use the original PCM codes from the modulated ones Waves on the receiving side through the use of a standard frequency discriminator be demodulated. Since a frequency discriminator gives an output that is proportional to Speed of phase change, waveforms as shown in FIG. 5 (e) are shown, generated because the wave of the instantaneous frequency change serves as an output. These coincide with the timing the pulse train of the original PCM codes. Therefore, the original signals from this pulse train by using a known monostable multivibrator in a simple way Way to be obtained.

However, those represented by the vector diagram of FIG. 6 signals a sideband that extends infinitely, so that there is still a little difficulty that should be solved before the actual transmission takes place. In particular, it is in the case of transmission by a high frequency device usually imperative that the frequency band is preserved.

The signals that have been assembled and not further modified as indicated by the vector diagram of FIG. 6 have infinite frequency components as described above, however, the major part of the energy is concentrated within a certain frequency bandwidth, so that, in practice, the information contained in the original position can be completely transmitted using only a certain frequency band is transmitted. This band is the carrier frequency ± 1/2 T (Hz). In the case of PCM codes of 24 channels, e.g. B. the carrier frequency ± 750 kHz.

This can be shown in the following way. To make the description general, it will be assumed that the original signal corresponds to the one shown in FIG. 8 (i). The waveform A corresponding to the original signal is shown in FIG. 8 (ii). Waveform B shows F i g. 8 (iii).

The wave modulated by waveform B can be represented as coscu “t, and the waveform modulated by signal A can be expressed as

A (i) sin co "t,

This results in

A (t) = - Si (ω
and

ti

_ Γ sin χ

■ dx

The composite wave phase angle of A (f) sin ω _ο ί and cos a> _o t can be expressed as

AU) =

there".

= ω _ο ί + tan ^] Γ— Si (ω _ο ί) Ί.

where A (t) can be expressed by the following equation, taking into account the fact that the composite wave passes through the band-pass filter having the cut-off angular frequency at ω _ο ± ω _α :

as

The instantaneous frequency can be expressed

άΦ

sin cu "i
T ⁵ -

1 + - Si I

An output that is proportional to the second term on the right-hand side of this equation, occurs at the output of the frequency discriminator. If now

2 π 2Ύ

(i.e., the condition of the bandwidth described above) holds, the above results Value to:

When f = nT (n = 0), the value becomes 0 and

if t = o, the value becomes - ω _α .

TC

This produces a waveform as shown in FIG. 7 is obtained. This waveform shows that the amplitude is always zero by the time the other pulses are present (ie ί = nT) and therefore the amplitude of the other pulses is not affected. Therefore, the information can be transmitted precisely through the tape

. 2π

- «- 2Γ

be transmitted.

Claims (3)

Patent claims: 1. Transmission system for binary codes containing messages in the form of a train of unipolar or bipolar pulses with a transmitter and a receiver, characterized in that the transmitter has a waveform converter to convert the codes containing pulse train into one or two trains of square waves with a width of Rectangular waves equal to the distance between two consecutive "1" pulses in the Pulse train, one or two carrier wave generators and one or two phase modulators, which shift the phases of the carrier waves, and that the receiver contains a Phase discriminator for demodulating the transmitted phase shifted waves into one contains the pulse train containing binary codes. 2. Arrangement according to claim 1 for unipolar pulses, characterized by a bandpass filter with a bandwidth of ± 2 ω ₁ ((U ₁ = 2 π / 2 Τ, where T is the period of the repeating frequency of the pulse train representing the binary codes) for the output wave of the phase modulator. 3. Arrangement according to claim 1 for bipolar pulses, characterized by a bandpass filter with a bandwidth equal to the repeating frequency of the pulse train that the represents binary code, is, for the output shaft of one of the two phase modulators connected downstream Mixing device. For this purpose 2 sheets of drawings 109 543/297