DE10355697B4 - Circuit and method for harmonic harmonic compensation of an amplified sinusoidal signaling signal - Google Patents

Abstract

Circuit for harmonic oscillation compensation of an amplified sinusoidal signaling signal (SS), comprising:
(a) an amplification unit (2031) amplifying the sinusoidal signaling signal (SS), due to non-linear amplification by the amplification unit (2031), N harmonic harmonics to the sinusoidal signaling signal (SS) with associated phase differences and associated amplitudes, so that in the non-steady state a distorted feedback signal (rk) is formed,
(b) an adaptation unit (40) which calculates from the feedback signal (rk) the N phase differences (φ _iH ) and the N amplitudes (A _iH ) for a compensation _signal (KS), and
(c) a signaling generator (2013) which generates a compensation _signal (KS) as a function of the N calculated phase differences (φ _iH ) and the N calculated amplitudes (A _iH ), wherein in the non-linear amplification of the sinusoidal signaling signal ( SS) and the compensation signal (KS) by the amplification unit (2031) the compensation signal (KS) compensates the N harmonic harmonics of the amplified sinusoidal signaling signal (SS).

Description

The The invention relates to a circuit and a method for compensation harmonic harmonics of an amplified sinusoidal signaling signal.

The Technical field of the invention relates to the transmission of voice data in a baseband and the simultaneous transmission of data in one higher Frequency band over a common subscriber line. In simultaneous transmission of language and data about a common subscriber line is the problem that within an integrated data / voice subscriber line circuit (SLIC) interference occur between the speech signal and the data signal. A problem are the signaling signals with a high signal level (for example the TTX (teletax) signal, which is at a frequency of 12 or 16 kHz up to 5 Vrms on the subscriber line) and whose higher harmonic harmonics caused by non-linear properties of the amplifier the subscriber line circuit (SLIC) are caused. These harmonic harmonics disturb upstream signals the ADSL data transmission (ADSL = Asymmetric Digital Subscriber Line).

So far were the generated harmonic harmonics of signaling signals with a high signal level, for example the TTX signal, after the The state of the art is not suppressed.

The emergence of such a disturbance of the ADSL upstream by the harmonics of a signaling signal (SS) or the TTX signal is indicated by the figures, 1a . 1b and 1c , shown in a row.

1a shows the frequency band of a conventional analog telephone (POTS, POTS = Plain Old Telephone Service). The analog voice frequency band is a baseband limited by an upper cutoff frequency f _POTS , which is usually at 3.4 kHz. In addition, a signaling signal (SS) may occur at 12 kHz or 16 kHz. If this POTS signal (voice signal + signaling signal) is amplified by means of a subscriber line circuit (SLIC) for transmission via a subscriber line, harmonic harmonics of the signaling signal (SS) occur due to non-linear characteristics of the gain of the subscriber line circuit (SLIC). TTX signal on.

In 1b the signals are shown after amplification by the subscriber interface card. In addition to the POTS and the TTX signal occur at all multiples of the frequency f ₀ TTX TTX harmonics (TTX-OS) (at 2f _0, 3f _0, ...) on.

In 1c the frequency bands are drawn on a subscriber line, via which both POTS data and ADSL data (ADSL) are transmitted. As you can see, the TTX harmonics (1st TTX-OS, 2nd TTX-OS, etc.) disturb the frequency band ADSL-Up at the frequencies 2f ₁ , 3f ₁ , etc.

The publication US 6,157,680 A describes a method and apparatus for adaptively canceling non-linear, band-external, acoustic distortions within a DSL device.

The publication US 6,570,514 B1 discloses a compensator for compensating for linearity errors in a device, wherein a fundamental signal and linearity error branching signals are generated. The compensator comprises an interpolator for generating an interpolated signal, an exponentiator for generating an interpolated compensation signal and a phase shifter. The phase shifter shifts a phase between the fundamental signal and the interpolated compensation signal such that linearity error branching signals are canceled and the fundamental signal is maintained.

The Reference 6,545,535 B2 describes a predistortion technique by means of high-pass filtering, so that a distortion compensation by the Predistortion for specific frequencies for which another distortion compensation is needed is performed.

The Object of the present invention is therefore a device and a method of harmonic harmonic compensation a reinforced sinusoidal Signaling signal, so that the data stream disturbing harmonic harmonics are compensated.

According to the invention this Task by a circuit with the features of the claim 1 and by a method having the features of the claim 24 solved.

The circuit for compensating for harmonics of a sinusoidal signaling signal has
a gain unit that is sinusoidal Signaling amplified signal due to a non-linear amplification by the amplification unit N harmonics to the sinusoidal signaling signal with associated phase differences and associated amplitudes arise, so that in the non-steady state, a distorted feedback signal is formed. Furthermore, the circuit has
an adaptation unit which calculates from the feedback signal the N phase differences and the N amplitudes of the harmonic harmonics, and a signaling generator which generates a compensation signal in response to the N calculated phase differences and the N calculated amplitudes, wherein in the non-linear amplification of the sinusoidal signaling signal and the compensation signal by the amplification unit, the compensation signal compensates the N harmonic harmonics of the amplified sinusoidal signaling signal.

The inventive device or the inventive method thus ensures that ADSL data in a higher frequency band without interference from harmonic harmonics of the signaling signal transferable are.

advantageous Refinements and developments of the invention will become apparent the dependent claims, and the description with reference to the drawings.

According to one preferred embodiment of the invention is the circuit for compensation of harmonics of a reinforced sinusoidal signaling signal provided in a local exchange.

According to one preferred embodiment of the invention adds the signaling generator the sinusoidal Signaling signal with the compensation signal to a pre-distorted Signaling signal.

According to one preferred embodiment of the invention is the amplification unit provided in a subscriber line circuit.

According to one Another preferred embodiment of the invention is the signaling generator in a coding / decoding unit integrated and the adaptation unit is in a switch ADSL modem intended.

According to one Another preferred embodiment of the invention are in the switching ADSL modem an ADSL calculation unit and a first interface device is provided, which the distorted Signaling signal from an analog to a digital signal converts and from the digital distorted signaling signal by means of the ADSL calculation unit Signal / noise ratio parameter calculates which of the adaptation unit for calculating the N phase differences and the N amplitudes the signal / noise ratio parameters to be provided.

One Advantage of this development is that the already calculated in a central office ADSL modem Signal / noise ratio parameters can be used the adaptation unit already preprocessed data (signal / noise ratio parameters) for calculating the N phase differences and the N amplitudes for disposal to deliver.

According to one Another preferred embodiment of the invention are in the coding / decoding unit a second interface device, a signal processing unit, a summing unit and a first DA converter provided, wherein the second interface device from the first interface device N calculated phase differences and N calculated amplitudes receives and wherein the summing unit provides that provided by the signaling generator predistorted signaling signal with one of the signal processing unit encoded digital information signal to form a digital Summation signal added, and wherein the digital summation signal by means of the first DA converter from a digital to an analog summation signal is converted.

According to one Another preferred embodiment of the invention, the gain unit and the first DA converter over coupled a first analog low-pass filter, which is the analog Summation signal filters.

An advantage of this development is that all signals which are above a cutoff frequency f _POTS for POTS signals are filtered.

According to one Another preferred embodiment of the invention, the gain unit and the switch ADSL modem via a serial Interconnection of an analog isolating filter and a first AD converter coupled, wherein the analog separation filter, the distorted signaling signal the first AD converter, which provides the distorted signaling signal from an analog signal to a digital signal.

According to one Another preferred embodiment of the invention are the signaling generator and the adaptation unit is provided in the encoding / decoding unit.

According to one Another preferred embodiment of the invention are in the coding / decoding unit a second analog low-pass filter and a second AD converter are provided.

According to one Another preferred embodiment of the invention, the gain unit and the analogue separation filter over a current measuring device coupled, so that by means of the current measuring device provided within the subscriber line circuit, the distorted signaling signal becomes.

One Advantage of this preferred development is that by means of the current measuring device the distorted signaling signal already within the subscriber line circuit to disposal stands. Advantageously, thus the data for generation of the predistorted signaling signal exclusively in the coding / decoding unit provided.

According to one Another preferred development within the coding / decoding unit is the second analog low-pass filter and the second AD converter provided which the current measuring device and the adaptation unit couple to the distorted signaling signal low-pass filters and from an analog to a digital signal to change.

One Advantage of this preferred embodiment of the invention is that prevented by the second analog low-pass filter aliasing effects become.

According to one Another preferred embodiment of the invention are outside the encoding / decoding unit, a third analog low-pass filter and a third AD converter is provided, which the current measuring device and couple the adaptation unit together to receive the distorted signaling signal low-pass filters and from an analog to a digital signal convert.

One Advantage of this preferred embodiment of the invention is that Components, here the third analog low-pass filter and the third AD / DA converters inherent in a local exchange for fulfillment other functionalities are present, can be exploited. Thus limited neither processing the distorted signaling signal the encoding / decoding unit still on the subscriber interface ADSL modem.

According to one Another preferred embodiment of the invention are the phase differences digital phase difference coefficients and the amplitudes digital Amplitude coefficient.

One Advantage of this preferred development is that thus the phase differences and the amplitudes can be digitally processed.

According to one Another preferred embodiment of the invention, the signaling generator a sinusoidal signal generator for generating the first harmonic Oscillation on which input one of a frequency coefficient memory for the first harmonic wave provided frequency coefficient signaling signal receives and digitally provides a first harmonic output on the output side.

According to one Another preferred embodiment of the invention, the signaling generator each a sinusoidal signal generator for generating the ith harmonic Oscillation on which the input side of a frequency coefficient memory for the i-th harmonic wave provided frequency coefficients for the i-th harmonic oscillation and the digital phase difference coefficient receives and On the output side digitally provides an i-th harmonic oscillation.

According to one Another preferred embodiment of the invention, the signaling generator a rise control generator on whose output signal is linked with the amplitude coefficient, which in an amplitude coefficient memory is present, a rise control signal is generated which indicates the increase the first harmonic vibration and the i-th harmonic Vibration controls.

One Advantage of this preferred development is that ensured by the rise control generator is that the signaling signal increases attenuated. Would that be Signaling signal not damped would rise this disturb the speech signal and the participant would hear a crack in the pipe.

According to one Another preferred embodiment of the invention, the signaling generator an amplitude increase compensation means which receives the rise control signal and for every i-th harmonic oscillation generates an i-th Rise control signal, which with the respective i-th harmonic oscillation multiplied for slew control is, where by a multiplication of the i-th harmonic Oscillation with the i-th slew control signal respectively provided an increase-controlled i-th harmonic oscillation becomes.

An advantage of this preferred development is that by means of the amplitude increase compensation means for each ith harmonic oscillation, an increase control of the respective signal for matching the slew control to the 1-th harmonic oscillation.

According to one Another preferred embodiment of the invention, the signaling generator each one initialization amplitude memory for the ith harmonic oscillation, which provides an initialization amplitude coefficient, which adds the amplitude of the amplitude coefficient to the amplitude coefficient i th harmonic oscillation an i-th Rise control signal generated by a multiplication of the respective increase-regulated i th harmonic Oscillation with the i-th slew control signal one each increase-controlled and amplitude-controlled i-th harmonic oscillation provided.

One Advantage of this preferred development is that by means of the N Amplitude control signals the amplitude of the respective signal not only muted but this amplitude is also adjusted according to their value is.

According to one Another preferred embodiment of the invention, the signaling generator a summation unit, all of which are up-regulated and amplitude-controlled i-th harmonic oscillations to form the predistorted Signaling signal with the sinusoidal signaling signal added.

One Advantage of this preferred embodiment of the invention is that the sum of all rise-controlled and amplitude-controlled i-th harmonic vibrations with i≥2 1st harmonic = 2nd harmonic) the compensation signal form and the compensation signal is added to the signaling signal form the predistorted signaling signal.

According to a further preferred embodiment of the invention, the digital phase difference coefficients are digital delta phase difference coefficients and the digital amplitude coefficients are digital delta amplitude coefficients, wherein a delta coefficient (φ _iH , A _iH ) is the difference between the respective coefficient to be set and the respective initialization coefficient ( phi _iH , IAKi.H).

One Advantage of this preferred embodiment of the invention is that through the use of delta coefficients computing time and computational resources within of the signaling generator can be saved.

According to one Another preferred embodiment of the invention, the sine wave signal generator for Generation of the first harmonic and the sinusoidal signal generators for generating the i-th harmonic oscillation according to the principle a lookup table are organized.

Of the Advantage of this preferred embodiment of the invention is that By using a look-up table (LUT) the stages of each i-th harmonic oscillation are simply phase-shifted.

advantageously, exists as well a linear relationship between the phase coefficients and the actual Phase rotation.

The Invention will be described below with reference to the schematic figures specified embodiments explained in more detail. It shows:

1 the superimposition of the band schemes in the transmission of voice, signaling and ADSL data via a subscriber line according to the prior art.

2 a schematic block diagram of a circuit according to the invention for the compensation of harmonics of a sinusoidal signaling signal.

3 a block diagram of a first preferred embodiment of the invention.

4 a block diagram of a second preferred embodiment of the invention.

5 a block diagram of a third preferred embodiment of the invention.

6 a detailed block diagram of the signaling generator according to the invention of the local exchange.

In all figures are the same or functionally identical elements - if otherwise stated - with the same reference numerals have been provided.

2 shows a schematic block diagram of a circuit according to the invention for the compensation of harmonics of a sinusoidal signaling signal SS.

Here are in 2 a subscriber terminal 10 and a local exchange 20 shown which via a subscriber line 1020 , on which the sinusoidal signaling signal SS is applied in the steady state, are connected.

The adaptation unit 40 is a feedback signal rk that in a processing unit 41 is generated, fed. The adaptation unit calculates according to a predefined adaptation algorithm (eg golden section search) 40 N phase differences φ _iH the associated i-th harmonic oscillation iH and N amplitudes A _iH the associated i-th harmonic vibration iH and this provides the downstream signaling generator 2013 to disposal.

The signaling generator 2013 generates in dependence on the N phase differences φ _iH and the N amplitudes A _iH a predistorted signal signal vorSS, wherein the predistorted signal signal vorSS consists of the sinusoidal signal SS and a compensation signal KS (cf. 6 ), wherein at one through the amplification unit 2031 carried out amplification of the predistorted signal SignalSS before the higher-frequency compensation signal KS compensates the harmonic of the amplified sinusoidal signaling signal SS, so that the output of the amplification unit 2031 is the amplified sinusoidal signaling signal SS without harmonics.

3 shows a block diagram of a first preferred embodiment of the circuit according to the invention.

3 shows how 2 a subscriber terminal 10 , which via a subscriber line 1020 with a local exchange 20 connected is. On the subscriber line 1020 is the sinusoidal signaling signal SS on.

3 shows that the reinforcement unit 2031 in a subscriber line circuit 203 is provided. In addition, the signaling generator 2013 in a coding / decoding unit 201 integrated and the adaptation unit 40 is in a switch ADSL modem 206 integrated.

The switch ADSL modem 206 has an ADSL calculation unit 2061 and a first interface device 2062 to convert the feedback signal rk, which in this case corresponds to the ADSL received signal, from an analog to a digital signal and from the feedback signal by means of the ADSL calculation unit 2061 To calculate the signal / noise ratio parameters, so that the adaptation unit 40 to calculate the N phase differences φ _iH and the N amplitudes A _iH, the signal / noise ratio parameters SNRP are provided.

The coding / decoding unit 201 has a second interface device 2012 a signal processing unit 2011 , a summation unit 207 and a first DA converter 2014 on. The second interface device 2012 receives from the first interface device 2062 the switch ADSL modem 206 N calculated phase differences φ _iH and N calculated amplitudes A _iH .

The summation unit 207 adds that from the signaling generator 2013 provided predistorted signal SignalSSSS (see. 6 ) with one of the signal processing unit 2011 coded digital information signal dIS.

The first DA converter 2014 converts the digital summation signal dΣS to an analog summation signal aΣS.

Further shows 3 that the reinforcing unit 2031 and the first DA converter 2014 via a first analog low-pass filter 202 coupled, wherein by means of the first analog low-pass filter 202 the analog summation signal aΣS is low-pass filtered.

Also will be in 3 shown that the reinforcement unit 2031 and the switch ADSL modem 206 via a serial connection of an analog separation filter 204 and a first AD converter 205 coupled, the analog separation filter 204 showing the functionality of the processing unit 41 satisfied, the feedback signal rk the first AD converter 205 provides. The first AD converter converts the feedback signal rk from an analog signal to a digital signal to allow the feedback signal rk from the digital ADSL calculation unit 2061 the switch ADSL modem 206 can be processed. It should be mentioned that in the units 204 and 206 only parts of the ADSL receive path, which are relevant to the invention, are shown.

4 shows a block diagram of a second preferred embodiment of the circuit according to the invention.

Unlike the in 3 is in 4 both the signaling generator 2013 as well as the adaptation unit 40 in the coding / decoding unit 201 intended.

Unlike the in 3 First preferred embodiment are in the second preferred embodiment of the 4 the amplification unit 2031 and the adaptation unit 40 not via the data path analogue separation filter 204 , first AD converter 205 and switch ADSL modem 206 coupled. The reinforcement unit 2031 and the adaptation unit 40 are via a current measuring device 2032 , a second analog low-pass filter 2015 and via a second AD converter 2016 coupled. Here is the current measuring device 2032 in the subscriber line circuit 203 provided and the second analog low-pass filter 2015 as well as the second AD converter 2016 are in the coding / decoding unit 201 arranged.

The current measuring device 2032 , please check the functionality of the processing unit ( 41 ), the function already has the feedback signal (rk) inside the subscriber line circuit 203 provide.

That of the current measuring device 2032 provided feedback signal rk is from the second analog low-pass filter 2015 low-pass filtered to avoid aliasing effects. The low-pass filtered feedback signal rk is obtained by means of the second AD converter 2016 converted to a digital signal to from the adaptation unit 40 to be processed digitally.

The further data path from the adaptation unit 40 to the amplification unit 2031 is the same as after 3 ,

5 shows a block diagram of a third preferred embodiment of the circuit according to the invention.

In contrast to 4 is the current measuring device 2032 and the adaptation unit 40 the at in 5 illustrated embodiment does not have a second low-pass filter 2015 and via a second AD converter 2016 within the coding / decoding unit 201 coupled. The feedback signal rk is obtained by tapping the voltage on the subscriber line 1020 and by a subsequent voltage division in a voltage divider 2019 then to a serial interconnection of a third analog low-pass filter 2017 and a third AD converter 2018 to feed, the components 2017 . 2018 already in the coding / decoding unit 201 and the voltage divider 2019 already in the local exchange 20 are included, among other things, for other functionalities, eg. Measuring purposes (Linetesting), are needed. This third preferred embodiment of the invention demonstrates the flexibility of the invention, with inherent components 2017 . 2018 and 2019 within the local exchange 20 be exploited.

6 shows a detailed block diagram of the signaling generator according to the invention 2013 the local exchange 20 ,

The input signals of the signaling generator 2013 are the N phase _coefficients φ _iH and the N amplitude _coefficients A _iH for the compensation _signal . The fundamental wave or harmonic oscillation has the frequency f ₁ and the second harmonic oscillation has the frequency f ₂ = 2 · f ₁ , etc. The output is the predistorted signal signal before SS, which is the sum of a sinusoidal signaling signal SS and a compensation signal KS is provided.

6 shows that in the signaling generator 2013 a sinusoidal signal generator for generating the first harmonic oscillation 51 is provided, which input side one of the frequency coefficient memory for the first harmonic oscillation 511 provided frequency _coefficient signaling signal f _1.H receives and the output side, a first harmonic vibration 1.H as a sine wave with maximum amplitude (full scale sinus) digitally provides.

The second harmonic oscillation (2.H) is the first harmonic oscillation (2.H) with f ₂ = 2 · f ₁ , etc.

In addition, for each i-th harmonic oscillation iH there is in each case a sinusoidal signal generator for generating the ith harmonic oscillation 5i integrated. A sinusoidal signal generator for generating the i-th harmonic oscillation 5i receives on the input side one of a frequency coefficient memory for the i-th harmonic oscillation 5ii provided frequency coefficients for the i-th harmonic oscillation f _iH and the digital phase difference coefficient φ _iH and an i-th initialization phase coefficient phi _iH , which of an initialization phase coefficient memory for the ith harmonic oscillation ( 9ii ), and provides, on the output side, an ith harmonic vibration as a full scale sinusoidal digital signal.

Without limitation of generality are in 6 only three sinusoidal signal generators for generating an i-th harmonic oscillation 52 . 53 . 54 shown.

Also shows 6 that in the signaling generator 2013 a rise control generator 60 is provided. The output of the slew-control generator 60 is multiplied by an amplitude _coefficient A _1.H to generate a rise _control signal ARS which controls the rise of the first harmonic and the ith harmonic each. The amplitude _coefficient A _1.H is in an amplitude coefficient memory 81 saved.

Further shows 6 that in the signaling generator 2013 an amplitude increase compensation means 70 is integrated. The amplitude increase compensation means 70 receives on the input side the ith harmonic Vibrations iH, with i≥2, and the slew control signal ARS. The amplitude increase compensation means 70 generates an ith rising control signal i.ARS for every ith harmonic oscillation.

By a multiplication of the i-th harmonic oscillation i.H. with the respective i-th slew control signal i.ARS becomes respectively generates an increase-controlled i-th harmonic oscillation ai.H.

6 shows that in the signaling generator 2013 each an initialization amplitude memory for the ith harmonic oscillation 8i iH is integrated for every i-th harmonic oscillation iH. This provides an initialization amplitude coefficient IAKi.H which, when added to the amplitude coefficient A _{iH, generates} an _ith amplitude control signal i.AmRS, wherein multiplication of the respective rise-controlled i-th harmonic oscillation ai.H by the respectively i-th amplitude control signal i.AmRS in each case an increase-controlled and amplitude-controlled i-th harmonic oscillation aai.H is generated.

6 also shows that in the signaling generator 2013 a summation unit 110 is integrated. By means of the summation unit 110 All of the rise-controlled and amplitude-controlled i-th harmonic oscillation aai.H are added to the sinusoidal signaling signal SS to form a predistorted signal vorSS. Here, the added rise-controlled and amplitude-controlled i-th harmonic oscillation aai.H form the compensation signal KS with i≥2.

10

Subscriber terminal

1020

Local loop

20

Local exchange

201

Encoding / decoding

2011

Signal processing unit

2012

second Interface means

2013

Signaling generator

2,014

first DA converter

2015

second analog low-pass filter

2016

second ADC

2017

third analog low-pass filter

2018

third ADC

2019

voltage divider

202

first analog low-pass filter

203

Subscriber line interface circuit

2031

amplification unit

2032

Current measuring device

204

analog separating filter

205

first ADC

206

Central office ADSL modem

2061

ADSL calculation unit

2062

first Interface means

207

summing

2030

connecting cable between the

Local exchange and the

communicator

3020

connecting cable between the

communicator and the

Local exchange

40

adaptation unit

41

processing unit

51

Sinewave generator to produce the first

harmonious vibration

511

Frequency coefficient memory for the first

harmonious vibration

5i

Sinewave generator for producing the i-th har

monic Oscillation (for i> = 2)

5ii

Frequency coefficient memory for the i-th

harmonious Oscillation (for i> = 2)

60

Rise-regulation generator

70

Amplitude increase-compensation device

81

Amplitude coefficient memory

8i

Initialisierungsamplituden memory for the i-th

harmonious vibration

9ii

Initialization phases coefficient memory for the

i-th harmonic oscillation (for i> = 2)

110

Summation unit

SS

signaling signal

1.h

first harmonic vibration

i.H

i-th harmonic oscillation (for i> = 2)

rk

Feedback signal

_φiH

Phasenendifferenz the ith harmonic vibration

to the initialization signal

Vorss

predistorted signaling signal

KS

compensation signal

SNRP

Signal / noise ratio parameter

A _iH

amplitude the ith harmonic vibration

dIS

digital information signal

dΣS

digital Summation signal

aΣS

analog Summation signal

f _1.H

Frequency coefficient signaling signal

f _iH

frequency coefficient for the i-th harmonic

vibration

ARS

Increase control signal

i.ARS

i-th Increase control signal

ai.H

increase regulated ith harmonic vibration

IAKi.H

i-th Initialisierungsamplituden coefficient

phi _iH

i-th Initialization phases coefficient

i.AmRS

i-th Amplitude control signal

aai.H

increase regulated and amplitude-controlled i-th

harmonious vibration

Claims (24)

Circuit for harmonic oscillation compensation of an amplified sinusoidal signaling signal (SS), comprising: (a) an amplification unit ( 2031 ) which amplifies the sinusoidal signaling signal (SS), due to non-linear amplification by the amplification unit (FIG. 2031 ) N harmonic harmonics to the sinusoidal signaling signal (SS) with associated phase differences and associated amplitudes arise, so that in the non-steady state, a distorted feedback signal (rk) is formed, (b) an adaptation unit ( 40 ) which calculates from the feedback signal (rk) the N phase differences (φ _iH ) and the N amplitudes (A _iH ) for a compensation _signal (KS), and (c) a signaling generator ( 2013 ), in response to the N calculated phase differences (φ _iH ) and the N calculated amplitudes (A _iH ) generates a compensation _signal (KS), wherein in the non-linear amplification of the sinusoidal signaling signal (SS) and the compensation signal (KS) the amplification unit ( 2031 ) the compensation signal (KS) compensates the N harmonic harmonics of the amplified sinusoidal signaling signal (SS). Circuit according to Claim 1, characterized in that the circuit for compensation of harmonics of an amplified sinusoidal signaling signal (SS) in a local exchange ( 20 ) is provided. Circuit according to one of the preceding claims, characterized in that the signaling generator ( 2013 ) sums the sinusoidal signaling signal (SS) with the compensation signal (KS) to a pre-distorted signaling signal (vorSS). Circuit according to one of the preceding claims, characterized in that the amplification unit ( 2031 ) in a subscriber line circuit ( 203 ) is provided. Circuit according to one of the preceding claims, characterized in that the signaling generator ( 2013 ) in a coding / decoding unit ( 201 ) and the adaptation unit ( 40 ) in a switch ADSL modem ( 206 ) is provided. Circuit according to one of the preceding claims, characterized in that in the exchange ADSL modem ( 206 ) an ADSL calculation unit ( 2061 ) and a first interface device ( 2062 ) which converts the feedback signal (rk) from an analog to a digital signal and from the digital feedback signal (rk) by means of the ADSL calculation unit ( 2061 ) Signal-to-noise ratio parameter (SNRP), which of the adaptation unit ( 40 ) for the calculation of the N phase differences (φ _iH ) and the N amplitudes (A _iH ) the signal / noise ratio parameters (SNRP) are provided. Circuit according to Claim 5, characterized in that in the coding / decoding unit (201) a second interface device ( 2012 ), a signal processing unit ( 2011 ), a summing unit ( 207 ) and a first DA converter ( 2014 ), the second interface device ( 2012 ) from the first interface device ( 2062 ) _Receives N calculated phase differences (φ _iH ) and N calculated amplitudes (A _iH ), and wherein the summation unit ( 207 ) that of the signaling generator ( 2013 ) provided pre-distorted signaling signal (vorSS) with one of the signal processing unit ( 2011 ) encoded digital information signal (dIS) to form a digital summation signal (dΣS), and wherein the digital summation signal (dΣS) from a digital to an analog summation signal (aΣS) by means of the first DA converter ( 2014 ) is converted. Circuit according to one of the preceding claims, characterized in that the amplification unit ( 2031 ) and the first DA converter ( 2014 ) via a first analogue low-pass filter ( 202 ) which filters the analog summation signal (aΣS). Circuit according to one of the preceding claims, characterized in that the amplification unit ( 2031 ) and the switch ADSL modem ( 206 ) via a serial connection of an analog separation filter ( 204 ) and a first AD converter ( 205 ), wherein the analog separation filter ( 204 ) the functionality of the processing unit ( 41 ) and the feedback signal (rk) to the first AD converter ( 205 ) which converts the feedback signal (rk) from an analog signal to a digital signal. Circuit according to one of the preceding An claims, characterized in that the signaling generator ( 2013 ) and the adaptation unit ( 40 ) in the coding / decoding unit ( 201 ) are provided. Circuit according to one of the preceding claims, characterized in that in the coding / decoding unit (201) a second analogue low-pass filter ( 2015 ) and a second AD converter ( 2016 ) are provided. Circuit according to one of the preceding claims, characterized in that the amplification unit ( 2031 ) and the analog low-pass filter ( 2015 ) via a current measuring device ( 2032 ), which the functionality of the processing unit ( 41 ) are coupled, so that by means of the current measuring device ( 2032 ) within the subscriber line circuit ( 203 ) the feedback signal (rk) is provided. Circuit according to one of the preceding claims, characterized in that within the coding / decoding unit (201) a second analogue low-pass filter ( 2015 ) and a second AD converter ( 2016 ) are provided, which the current measuring device ( 2032 ) and the adaptation unit ( 40 ) to low-pass-filter the feedback signal (rk) and convert it from an analog to a digital signal. Circuit according to one of the preceding claims, characterized in that within the coding / decoding unit (201) a third analogue low-pass filter ( 2017 ), a third AD converter ( 2018 ) and a voltage divider ( 2019 ) are provided, which the current measuring device ( 2032 ) and the adaptation unit ( 40 ) over the voltage divider ( 2019 ) to low-pass-filter the feedback signal (rk) and convert it from an analog to a digital signal. A circuit according to claim 1, characterized in that the phase differences (φ _iH ) are digital phase difference _coefficients (φ _iH ) and the amplitudes (A _iH ) are digital amplitude _coefficients (A _iH ). Circuit according to one of the preceding claims, characterized in that the signaling generator ( 2013 ) comprises: a sinusoidal signal generator for generating the first harmonic oscillation ( 51 ) which inputs one of a frequency coefficient memory for the first harmonic oscillation ( 511 Frequency coefficient signaling signal provided) receives (f _1.h) and on the output side, a 1-th harmonic (1.h) digitally provides. Circuit according to one of the preceding claims, characterized in that the signaling generator ( 2013 ) comprises: a sinusoidal signal generator for generating the ith harmonic oscillation ( 5i ), which inputs one of a frequency coefficient memory for the ith harmonic oscillation ( 5ii frequency coefficient for the ith harmonic oscillation (f _iH ), an ith initialization _phase coefficient phi _iH , which is _dependent on an initialization _phase coefficient memory for the ith harmonic oscillation ( _FIG . 9ii ) and receives the digital phase difference _coefficient (φ _iH ) and provides an i-th harmonic (iH) digitally on the output side. Circuit according to one of the preceding claims, characterized in that the signaling generator ( 2013 ): a rise control generator ( 60 ) whose output signal is linked to the amplitude _coefficient (A _1.H ) which is _stored in an amplitude coefficient memory ( 81 ), a slew control signal (ARS) is generated which controls the rise of the first harmonic and the ith harmonic. Circuit according to one of the preceding claims, characterized in that the signaling generator ( 2013 ) comprises: an amplitude increase compensation means ( 70 ) which receives the slew control signal (ARS) and for each i-th harmonic (iH) generates an i-th slew control signal (i.ARS) which is multiplied by the i-th harmonic (iH) for slew control respectively in each case an increase-controlled i-th harmonic oscillation (ai.H) is provided by multiplying the respective i-th harmonic oscillation (iH) by the respective i-th slew control signal (i.ARS). Circuit according to one of the preceding claims, characterized in that the signaling generator ( 2013 ) each have an initialization amplitude memory for the i-th harmonic oscillation ( 8i ) which provides an initialization amplitude coefficient (IAKi.H) which, added to the amplitude coefficient A _{iH, generates} the amplitude of the i-th harmonic oscillation an ith amplitude control signal (i.AmRS), wherein multiplication of the respectively up-regulated i- Each of the i-th amplitude control signal (i.AmRS) is an increase-controlled and amplitude-controlled i-th harmonic oscillation (aai.H) is provided th harmonic oscillation (ai.H). Circuit according to one of the preceding claims, characterized in that the signali generator ( 2013 ) comprises: a summation unit ( 110 ), which adds all the rise-controlled and amplitude-controlled i-th harmonic oscillations (aai.H) to the formation of the predistorted signaling signal (vorSS) with the sinusoidal signaling signal (SS). Circuit according to one of the preceding claims, characterized in that the digital phase difference _coefficients (φ _iH ) are digital delta-phase difference _coefficients (φ _iH ) and the digital amplitude _coefficients (A _iH ) are digital delta-amplitude coefficients (A _iH ), wherein a delta coefficient (φ _iH , A _iH ) is the difference between the respective coefficient to be set and the respective initialization coefficient (phi _iH , IAKi.H). Circuit according to one of the preceding claims, characterized in that the sinusoidal signal generator for generating the first harmonic oscillation ( 51 ) and the sinusoidal signal generators for generating the ith harmonic oscillation ( 5i ) are organized according to the principle of a look-up table. A method for harmonic harmonic compensation of a boosted sinusoidal signaling signal (SS), comprising the steps of: (a) amplifying the sinusoidal signaling signal (SS), due to non-linear amplification by the amplification unit (SS); 2031 ) N harmonic harmonics to the sinusoidal signaling signal (SS) with associated phase differences and associated amplitudes arise, so that a distorted signaling signal is formed, (b) calculating the N phase differences (φ _iH ) and the N amplitudes (A _iH ) for a compensation _signal (KS ) from a fed back from the distorted signaling signal feedback signal (rk) by means of an adaptation unit ( 40 ), and (c) generating a compensation _signal (KS) as a function of the N calculated phase differences (φ _iH ) and the N calculated amplitudes (A _iH ) by means of a signaling generator ( 2013 ), wherein in the non-linear amplification of the sinusoidal signaling signal (SS) and the compensation signal (KS) by the amplification unit ( 2031 ) the higher-frequency compensation signal (KS) compensates for the N harmonic harmonics of the amplified sinusoidal signaling signal (SS).