CN85102323B - Fm demodulator - Google Patents
Fm demodulator Download PDFInfo
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- CN85102323B CN85102323B CN85102323A CN85102323A CN85102323B CN 85102323 B CN85102323 B CN 85102323B CN 85102323 A CN85102323 A CN 85102323A CN 85102323 A CN85102323 A CN 85102323A CN 85102323 B CN85102323 B CN 85102323B
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- demodulator
- demodulation
- low pass
- differential amplifier
- pass filter
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Abstract
The present invention relates to an FM demodulator in a phase locked loop system. A phase locked loop comprises a phase detector, an amplifier, a loop filter, and a voltage controlled oscillator, wherein a part of the amplifier is composed of a differential amplifier circuit which has a constant current source and is driven by a constant current. The center frequency of frequency demodulation signals of the constant current source is changed with the current of the constant current source and responds to slope rate demodulation signals in the phase locked loop; Furthermore, a low pass filter with a passing band of a demodulation signal frequency band is arranged in a system path between the differential amplifier circuit and the constant current source.
Description
The invention relates to the FM demodulator circuit arrangement of demodulate frequency-modulated signals.
In using the communication satellite television broadcasting system, use frequency modulation (FM) TV signal, in the receiver that receives this class broadcasting, need the faint radio wave that comes out from satellite transmission is demodulated into vision signal.Because PLL(phase-locked loop) FM(frequency modulation) utilization has fabulous characteristic to demodulator in the weak electric signal field, thereby often is used.Fig. 1 shows the PLL-FM modem device of general use.PLL-FM closed loop demodulator comprises a phase discriminator 2, one amplifier 3, one loop filter 4 and a voltage controlled oscillator (VCO) 5, FM signal is sent into the PLL-FM demodulator by input 1, and by demodulation, draw an incoming line to voltage controlled oscillator (VCO) 5 from output 6, it picks up demodulates television signals.In this FM demodulator, the frequency that the beat that is produced by phase discriminator 2 becomes branch to have is signal frequency poor of frequency input signal and the voltage controlled oscillator 5 of input 1, and it is by amplifier 3 amplifications; Loop filtering whole 4 is adjusted its phase place and gain; After this, the output signal of loop filter 4 is fed to the frequency of oscillation control end of voltage controlled oscillator 5, because closed loop makes beat composition frequency can become 0 effect, closed loop act as a FM demodulator, produce in the frequency of oscillation control input end of voltage controlled oscillator 5 as the TV signal of original input FM signal.Thereby the demodulation frequency band of FM demodulator is by the gain of amplifier in the closed loop 3 and loop filter 4 and phase characteristic decision, and can be limited to minimum necessary bandwidth; Therefore when electric field was faint, demodulation characteristics was fabulous.
Fig. 2 illustrates the demodulation bandwidth characteristic of common PLL-FM demodulator among Fig. 1.If meet the following conditions, the reference frequency f of input signal and voltage controlled oscillator 5 just
0Phase error and the phase error sum in closed loop be ± 90 ° or littler, and the gain of ring is greater than 1, then the PLL circuit among Fig. 1 is synchronous, thereby the frequency of oscillation of voltage controlled oscillator 5 can be offset according to frequency input signal, as the output of FM demodulator, the voltage and and the reference frequency f that are applied to voltage controlled oscillator 5 have just been produced like this
0With the proportional direct voltage of difference along the frequency input signal of frequency of oscillation characteristic curve 7, so just obtained the function of FM demodulator, frequency range in this locking range is corresponding to the frequency demodulation bandwidth, can distinguish from the loop conditions of above-mentioned phase-locked loop, along with the phase error in the increase closed loop of loop gain reduces, thereby increase the frequency demodulation bandwidth.In addition, even under the identical situation of gain, diminish with phase distortion in closed loop, the frequency demodulation bandwidth increases.
But on the other hand, as the inherent characteristic of FM demodulator, it has a threshold property, thus when the C/N(carrier wave/noise of input FM signal) during than step-down, S/N(signal/noise) than can unexpected variation.This threshold value is by the decision of the noise content of demodulation, when by the noise content of demodulation more after a little while, in other words, when the narrow bandwidth of demodulation noise, threshold value moves to lower C/N ratio.In order to produce narrow demodulation noise bandwidth, just need to adjust the gain characteristic of PLL to the arrowband.
As mentioned above, the PLL-FM demodulator that hope obtains having following characteristic, in range of video, it has high-gain and wide demodulation frequency band, and when frequency was higher than video, gain diminished suddenly, and the demodulation bandwidth is narrow, to improve threshold value.
The closed loop gain characteristic of PLL-FM demodulator shown in Figure 1 has under the hysteresis-leading situation of filter as loop filter of less phase distortion the 6dB of the attenuation rate of level and smooth attenuation characteristic curve when 2 frequencys multiplication by ring wave filter 4 decisions in use.Thereby when demodulation has the video FM signal of big frequency deviation, for guaranteeing the video demodulator bandwidth, the shortcoming that the result brings noise bandwidth to broaden and threshold value become to reduce, unfavorable factor on the other hand be, when threshold value selected when better, the video demodulator bandwidth narrows down, to demodulation can not be realized, when use except that lag behind-other narrow band filter of leading filter is during as loop filter 4, the phase distortion increase in the closed loop, increase gain though make, the demodulation bandwidth is broadened.
One of purpose of the present invention is to eliminate the above-mentioned shortcoming of PLL-FM demodulator, and a FM demodulator is provided, and wherein utilizes the ball bearing made using device just can reach the narrow and good threshold value of gain frequency band (gain band) in the ring, and no matter the size of video skew.
In the present invention, owing to used a device, the centre frequency of demodulator demodulation frequency band is along with restituted signal drifts about, and is narrow in the characteristic of demodulation ring midband, and uses simple mechanism to improve threshold level.
Feature of the present invention will describe in detail by accompanying drawing.
Fig. 1 illustrates the circuit arrangement of general PLL-FM demodulator;
Fig. 2 is illustrated in the characteristic curve of PLL-FM demodulator among Fig. 1;
Fig. 3 and 4 is respectively the circuit diagram and the performance diagram of setting forth the principle of the invention;
Fig. 5 illustrates the installation drawing according to FM demodulator embodiment of the present invention;
Fig. 6 illustrates the circuit diagram of demodulation band shift circuit one example used in the present invention;
Fig. 7 and 8 is the performance diagrams that are set forth in invention operation principle among Fig. 5;
Fig. 9,10 and 11 shows the installation drawing of the demodulation band shift circuit improved form of the embodiment of the invention in Fig. 5;
Figure 12 is other installation drawing of invention example;
Figure 13 and 14 illustrates the circuit diagram of demodulation band shift circuit one example of the present invention's use;
Figure 15 and 16 performance diagrams of setting forth the invention operation principle among Figure 12;
Figure 17,18 and 19 shows the installation drawing of other embodiment of the present invention.
By the embodiment in the accompanying drawing, describe the present invention in detail below.Fig. 3 and Fig. 4 illustrate schematic diagram of the present invention.Fig. 3 illustrates by transistor Q
1And Q
2The differential amplifier of forming, it also comprises by transistor Q
4And Q
5The constant-current source that the mirror image circuit constitutes.And supposition is used the part of this differential amplifier as amplifier 3 in the demodulator of PLL-FM shown in Fig. 1, transistor Q
1Base stage 8a and transistor Q
2Base stage 8b import as balanced signal; Signal is from transistor Q
1Collector electrode is by transistor Q
3Output; Transistor Q
3Output 9 be connected to loop filter 4.When changing the electric current of constant-current source with variable resistor 10, as shown in Figure 4, centre frequency is f
1Demodulation characteristics curve 11 be f according to the change in voltage that is applied to voltage controlled oscillator to centre frequency along frequency of oscillation characteristic curve 7
2 Demodulation characteristics curve 12, and this moment, loop gain and phase place did not all change, so demodulation characteristics 11 is identical with 12 demodulation bandwidth.
Fig. 5 illustrates an example of FM demodulator of the present invention, differential amplifier be connected on amplifier 3 in the PLL-FM demodulator ' back level, one output 15 of differential amplifier 14 is received loop filter 4, and another output 16 is connected to constant-current source 13 by low pass filter (LPL) 17, amplifier 18 and voltage changer 19.The electric current of constant-current source 13 can change by the restituted signal of differential amplifier 14, like this by constant-current source 13, and differential amplifier 14, low pass filter 17, amplifier 18 and voltage changer 19 have constituted demodulation band shift circuit 100.The frequency characteristic of low pass filter 17 is set up in the arrowband LPL(low pass at PLL intermediate ring road filter 14) filter can be placed in the system from differential amplifier 14 outputs 16 to the arbitrary position the constant-current source 13.Under such arrangement, in the restituted signal scope of PLL-FM demodulator, with respect to the restituted signal component in low pass filter 17 passbands, electric current is changed in the constant-current source 13, the drift of frequency demodulation frequency band, thus the broadband demodulator characteristic obtained, consider the restituted signal composition in low pass filter 17 cut-off frequencies on the other hand, filter 17 does not change the electric current of constant-current source 13, can obtain like this by amplifier 3 ', the usual demodulation bandwidth of differential amplifier 14 and loop filter 4 decisions.When selecting the bandwidth of video signal for use as the passband of low pass filter 17, frequency demodulation bandwidth that can the broadening vision signal, thus this reduces amplifier 3 ' and the gain of differential amplifier 14, and by making by the demodulation noise bandwidth improvement threshold value that narrows down.
Fig. 6 illustrates an embodiment of demodulation band shift circuit 100, moves in order to control FM demodulator demodulation band of the present invention shown in Figure 5.Restituted signal is by the transistor Q of differential amplifier 14
2Collector electrode draw.Use a transistor Q
6, the hysteresis-advanced version low pass filter by being made up of resistance 20,21 and electric capacity 22 (among Fig. 5 17) makes difference channel 14 and PLL closed loop irrelevant.The constant-current source that restituted signal driven by low pass filter is used for differential amplifier (among Fig. 5 13), like this, when input FM signal frequency uprises, transistor Q
1Collector voltage uprise and transistor Q
2The collector voltage step-down, transistor Q in the constant-current source
4The base voltage step-down, transistor Q flows through
4Electric current reduce, the demodulation bandwidth moves on to higher frequency side, transistor Q
2Collector voltage controlled, until become constant voltage, and the demodulation bandwidth is according to input FM signal frequency drift.Such demodulation band shift circuit 100 has nothing to do with the closed loop of PLL, even like this ring gain of band shift circuit 100 is transferred greatly, also improves control sensitivity and does not influence the PLL-FM demodulation characteristics.As an example, this purpose can be by increasing transistor Q
2Collector resistance 20 easily realize.
The working condition of these circuit shown in Figure 7.When input has centre frequency f
0The FM signal time, can obtain having a centre frequency f by what a represented
0The demodulation bandwidth, when the input signal frequency deviation was △ f, the band control action of moving made transistor Q
2Collector voltage constant, thereby make the demodulation bandwidth shown in b, its center only has been offset 1/2 △ f.On the other hand, when input signal skew-△ f, same demodulation bandwidth shown in C, its carrier deviation is-△ f 1/2, suppose that now maximum frequency deviation 2 * △ f is 17MHz, the demodulation bandwidth may be half of maximum frequency deviation, i.e. 8.5MHz before skew.
This coupling collar gain of naming a person for a particular job is discussed.In Fig. 6 band shift circuit 100, when the gain of supposing differential amplifier 14 is A
1, from transistor Q
2To transistor Q
4The band gain that moves ring be A
2, the overall gain A of this circuit
0Can be expressed as
A
0=A
1(1+A
2/A
2+1)
Work as A
2Be worth when big circuit overall gain A
0Be 2 times that differential amplifier 14 gains, work as A
2When very little, A
0Equal A
1
Fig. 8 illustrates the relation between these gains.When the gain of PLL was A, at this moment, having maximum video f ' was irrealizable for the band of the frequency demodulation bandwidth of 17MHz moves.Suppose that the characteristic curve of PLL closed loop represented by X, band moves the irrealizable part of specific characteristic curve X PLL closed loop characteristic curve during few 6dB in gain and represents with Y, use the present invention then can obtain the characteristic curve of representing with solid line Z, also can obtain necessary gain at the highest video f ' like this, and surpassing f ' time when frequency, gain reduces 6dB, like this, the noise bandwidth is narrow, and threshold value has been improved.Gain increase that should be in low frequency range has embodied band and has moved effect, and band shift circuit 100 forms a loop, and nature adds because band moves ring, and the increase that the increase of phase error can utilize band to move the ring gain diminishes.
Fig. 9 illustrates the embodiment of another band shift circuit 100.In this embodiment, band moves loop gain has increased.PNP transistor Q
7And Q
8An amplifying circuit that constitutes is connected on differential amplifier circuit transistor Q
2Low pass filter on the output and current source transistor Q
4Between, Q
7And Q
8Forming the gain of amplifying circuit can at random adjust by resistance 23,24,25 and 26, reduces to minimum thereby make because band moves the increase of the adding PLL phase error of ring.
Figure 10 and 11 illustrates other form of implementation of band shift circuit 100 of the present invention.As shown in figure 10, the function of moving control ring by band is because current source transistor Q
4Variations in temperature and the electric current that produces change and are suppressed, and can remove transistor Q in the mirror image circuit like this
5The formation of low pass filter 17 has more than and is limited to resistance 21 and electric capacity 22 on the one hand, also can use electric capacity 27 and/or 28, in other words, perhaps in these elements is used, and perhaps they are all is utilized the formation filter, in this case, these elements can be placed on band and move on any position of ring obviously, make the band of demodulation bandwidth change move ring and to separate the closed loop of calling for PLL-FM irrelevant, so working stability.In addition, supply the closed-loop bandwidth characteristic of PLL-FM demodulation to need not the broadband operation, thereby such loop is constituted easily.Have again, when using FM demodulator of the present invention as heterodyne receiver a part of, even when changing the input signal centre frequency cause FM demodulator and change owing to the heterodyne receiver local frequency, the centre frequency of demodulator also can automatic deviation, and the distortion of restituted signal is reduced.
In addition, when being received in low frequency the FM signal of big frequency shift arranged, must greatly mobile demodulation frequency band.
Figure 12 illustrates another embodiment of FM demodulator of the present invention.Differential amplifier 14 with constant-current source 13 be connected amplifier 3 in the PLL-FM demodulator ' final stage, the output signal of differential amplifier is by shunt, one tunnel output links to each other with loop filter 4, and another road links to each other with constant-current source 13 with voltage changer 19 by amplifier 29, low pass filter 30, use the electric current of the restituted signal control constant-current source 13 of differential amplifier 14 outputs to change, like this with regard to the centre frequency of mobile demodulation bandwidth.Low pass filter 30 can be arranged in the final stage of voltage changer 19.Constant-current source 13, differential amplifier 14, voltage changer 19, amplifier 29 and low pass filter 30 have constituted band and have transfered from one place to another under escort demodulation circuit 200.
Figure 13 illustrates an embodiment of the band shift circuit 200 that is used for mobile FM demodulator demodulation bandwidth of the present invention.The output of the PLL closed loop of differential amplifier 14 is taken out by along separate routes and by a PNP transistor Q, transistor Q, collector electrode connect transistor Q
5Collector electrode, transistor Q, emitter connect positive source by resistance 33 because like this, when the input FM signal uprises, transistor Q
1Collector voltage uprise, flow through transistor Q, electric current reduce transistor Q
4The base voltage step-down, transistor Q flows through
4Electric current reduce, the frequency demodulation bandwidth moves on to high frequency side, obviously, according to the function of the low pass filter of forming by resistor 31 and capacitor 32 30, the realization that above-mentioned demodulation band moves only with low pass filter 30 passbands in signal correction.
Transistor Q, the size of emitter resistance 33 determined the sensitivity that the demodulation band moves, though moving wide numerical value along with resistor 33 reduces and increases, but under arranging like this, the dc balance of differential amplifier needs to realize that the resistance of resistance 33 can not be selected very for a short time like this on the centre frequency of input FM signal.Therefore, as shown in figure 14, comprise transistor Q
10 Constant pressure source 133 be connected on power supply one side of resistance, the resistance of resistance 33 can be selected very for a short time like this, makes the demodulation bandwidth that big moving range can be arranged, when the resistance of selecting resistance 33 makes transistor Q
1And Q
2Collector voltage when always equating, the demodulation bandwidth moves and makes input FM signal always be positioned at the center of demodulation bandwidth, Figure 15 illustrates its working condition.When the input centre frequency is f
0Input FM signal the time because the dc balance of differential amplifier guarantees then have centre frequency f
0The demodulation frequency band by a ' expression, when input signal departs from △ f, differential amplifier transistor Q
1Output voltage increase, yet the constant-current source electric current reduces, transistor Q
2Collector voltage become and equal transistor Q
1Collector voltage, so because this voltage makes differential amplifier balance well, it is (f that demodulation bandwidth like this moves on to by b ' expression centre frequency
0+ △ f) position.When frequency input signal is f
0During-△ f, it is f that the demodulation bandwidth moves on to centre frequency similarly
0The reposition that-△ f represents with c ', because the demodulation bandwidth is three times of demodulation bandwidth that band moves not have realization, so the about 10dB of 1/3(that band moves gain when not realizing is reduced in the PLL closed loop gain), thereby improved threshold value, because demodulation band shift circuit 200 does not have to form ring as shown in figure 16, when the demodulation band was offset, ring gain characteristic Z ' presented the characteristic of the narrow band filter 30 in the demodulation band shift circuit 200, and this is effective to the demodulation that has the FM signal of big frequency deviation when the low frequency.
So just make that the noise bandwidth becomes very little in closed loop, thereby improved threshold value.And then when using FM demodulator of the present invention as the demodulation part of heterodyne machine, both made because the centre frequency change restituted signal of the FM demodulator input signal that the change of heterodyne receiver local oscillation frequency causes can distortion yet, because demodulation always realizes in the centre frequency of demodulation bandwidth.
Use such characteristic, the frequency band that just may pass through the narrow band filter 30 in the constriction demodulation band shift circuit 200 is almost to direct current formation AFC circuit.In this case, as shown in figure 17,, can add amplitude limiter circuit in the final stage of amplifier 29 in order to avoid being used for the AFC misoperation that the demodulation band moves.
Though the present invention has been done elaboration with reference to the embodiment among Figure 12, wherein the output of differential amplifier 14 along separate routes, and utilized restituted signal, but the present invention is not only for this device, the restituted signal that drives the constant-current source 13 of differential amplifier 14 can have this polarity, when the output voltage of difference amplifier increases, reduce the electric current of constant-current source.Same obvious be the output signal that can use PLL-FM demodulator shown in Figure 180, perhaps use the signal of telling in the pre-amplifier of differential amplifier shown in Figure 19.
On the other hand, though differential amplifier is placed in the prime of loop filter, invention is not limited to such position.Obviously, also differential amplifier can be placed in the first order or the centre position of amplifier in the closed loop.
As mentioned above, in the present invention, the centre frequency of PLL-FM demodulator demodulation bandwidth is offset corresponding to restituted signal, the feasible FM signal of such effect with big video frequency deviation, use simple device just can realize demodulation, even when the skew of FM frequency input signal, the still demodulation that can realize, and improved threshold value significantly.
Claims (17)
1, the FM demodulator that has phase-locked loop, its phase-locked loop comprises:
Be used to detect the phase discriminator of a FM signal,
The amplifier that links with described phase discriminator,
The loop filter that links with described amplifier,
The voltage controlled oscillator that links with described loop filter and described phase discriminator,
It is characterized in that described FM demodulator has a demodulation band shift circuit, this circuit comprises:
Be connected in the differential amplifier between described amplifier and the described loop filter,
Be connected to described differential amplifier and provide the constant-current source of constant current to it,
The low pass filter of the FM restituted signal of its input response phase demodulation output, one of its output links with described constant-current source, and its frequency characteristic is to have than the narrower bandwidth of described loop filter passband.
2, the FM demodulator described in the claim 1, an input that it is characterized in that wherein said low pass filter are that the output with described differential amplifier links.
3, the FM demodulator described in the claim 1 is characterized in that an input of wherein said low pass filter and described amplifier link.
4, the FM demodulator described in the claim 1, the input and the described loop filter that it is characterized by wherein said low pass filter link.
5, any one described FM demodulator in the claim 1 to 4 is characterized by wherein said demodulation band shift circuit and also is included in electric pressure converter between described low pass filter and the described constant-current source.
6, the FM demodulator described in the claim 1 or 2, it is characterized by wherein said differential amplifier and have first and second outputs that are used to produce inversion signal, first output of described loop filter and described differential amplifier links, and second output of described low pass filter and described differential amplifier links.
7, the FM demodulator described in the claim 1, the passband that it is characterized by wherein said low pass filter are chosen as and equal the vision signal frequency band substantially.
8, the FM demodulator described in the claim 1 or 3, the output and the described differential amplifier that it is characterized by wherein said amplifier link, and another output and described low pass filter link.
9, the FM demodulator described in the claim 1 or 4 is characterized in that an output of described loop filter and described low pass filter link, and another output of described voltage controlled oscillator and described loop filter links.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN85102323A CN85102323B (en) | 1985-04-01 | 1985-04-01 | Fm demodulator |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN85102323A CN85102323B (en) | 1985-04-01 | 1985-04-01 | Fm demodulator |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN85102323A CN85102323A (en) | 1987-01-10 |
| CN85102323B true CN85102323B (en) | 1987-02-04 |
Family
ID=4792427
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN85102323A Expired CN85102323B (en) | 1985-04-01 | 1985-04-01 | Fm demodulator |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN85102323B (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101359970B (en) * | 2008-09-28 | 2011-07-27 | 无锡市晶源微电子有限公司 | Automobile radio circuit having pilot signal suppression |
-
1985
- 1985-04-01 CN CN85102323A patent/CN85102323B/en not_active Expired
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101359970B (en) * | 2008-09-28 | 2011-07-27 | 无锡市晶源微电子有限公司 | Automobile radio circuit having pilot signal suppression |
Also Published As
| Publication number | Publication date |
|---|---|
| CN85102323A (en) | 1987-01-10 |
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