CN2855003Y - Device for regulating light of stage - Google Patents

Abstract

The utility model relates to a device for regulating light of stage, which is characterized in that: the device includes a signal inputting and processing parts (1) comprising a signal inputting unit and a signal processing unit, a controlling-generating paerts (2) comprising a microcomputer controlling unit and a feedback unit, and an execution parts (3) comprising a main IGBT unit, an assistant IGBT unit, a filter unit and a controlled unit; the signal inputting end of the controlling-generating paerts (2) is connected with the outputting end of the signal inputting and processing parts (1), the controlling outputting end is connected with the inputting end of the execution parts (3), the feedback inputting end is connected with the outputting end of the execution parts (3) by the feedback unit, the feedback outputting end is connected with the feedback inputting end of the signal inputting and processing parts (1). The output current and voltage of the utility model are all the sine wave which can conveniently drive the load such as electromotor, and is applyed to all kinds of load light adjusting and load voltage adjusting.

Description

A kind of device for regulating ligth of stage illumination lamp

Technical field

The utility model relates to a kind of device for regulating ligth of stage illumination lamp, is a kind of stage special I GBT sinusoidal dimmer, and its input current and voltage and output current and voltage all are sinusoidal wave.Belong to the light of stage equipment technical field.

Background technology

At present, the light of stage industry extensively adopts one-way SCR and the bidirectional triode thyristor power component as dimmer, and its advantage is: the voltage and current capacity that bears is higher, and control Driver Circuit is simple, and the device heating amount is little, heat radiation and protective circuit economy.

Its operation principle is: send control signal by control desk, change the phase angle pulse into by dimmer and trigger controllable silicon through special-purpose scr triggering device, controllable silicon is turn-offed by the ac main circuit voltage zero-cross.When following one-period, repeat identical action.Phase angle pulse original position difference, ac main circuit voltage waveform be by the area difference after cutting, thereby realized outputing to the power difference on the bulb, reaches the purpose of light modulation.Under the resistive load (controllable silicon dimmer is difficult to use under the inductive load), original ac main circuit voltage and current is sinusoidal wave, and the voltage and current that outputs to after the copped wave on the bulb only is a sinusoidal wave part.The effect of filter inductance makes the forward position of this sinusoidal segment ripple become fillet, expands into rich upright leaf-size class number, except bigger first-harmonic, also has 3,5,7,9,11,13,15 as can be seen ... Deng harmonic wave.The harmonic wave proportion increases with the increase that triggers the phase angle.

In the upright leaf-size class number of richness, the component that frequency is identical with power frequency is called first-harmonic, and frequency is that the component of first-harmonic integral multiple (greater than 1) is called harmonic wave, and harmonic number is the ratio of integers of harmonic frequency and fundamental frequency.

When the phase angle pulse position was identical, the relation of harmonic wave and first-harmonic was unfixed, and filter inductance is big more, and then harmonic wave is more little, and first-harmonic is big more.This is because thereby the effect that the bigger inductance inhibition impulse current inhibition alternating current of series connection distorts is better, is cut the more slick and sly of the sinusoidal wave forward position change in back thereby make.Because being cut the slick and sly degree in sinusoidal wave forward position, back is that the alternating current aberration rate is corresponding with step response, thereby the rise time is adopted in the light modulation field that is described in of this relation.Here it is why the rise time be the bigger the better (certainly, the Q value of series inductance hour, the rise time is big more, means that then the inductance heating is big more, the landing of output voltage is wanted greatly).

Because the existence of harmonic wave, there is following major defect in existing controllable silicon dimmer:

(1) make the element in the electrical network produce additional harmonic loss, reduce the efficient of generating, transmission of electricity and power consumption equipment, a large amount of harmonic waves flows through the neutral line can make the overheated even breaking out of fire of circuit.Influence the normal operation of various electric equipments, make motor generation mechanical oscillation, noise and overheated, make the transformer part seriously overheated, make apparatus overheats such as capacitor, cable, make ageing of insulation, the lost of life is so that damage.

(2) cause parallel resonance and series resonance local in the electrical network, thereby harmonic wave is amplified, more powerful controllable silicon dimmer is equipped with smaller transformer, often cause parallel resonance and series resonance local in the electrical network, the voltage fluctuation that makes power voltage supply shows that up to tens volts the light fixture bright dipping is exactly irregular flash of light.

(3) can cause the misoperation of relaying protection and automatics, and make the electrical measuring instrument metering inaccurate.Can produce contiguous communication system and disturb, the lighter produces noise, reduces communication quality, and weight person causes information dropout, makes the communication system can't operate as normal.Can make dimmer send noise and generation electromagnetic radiation, can make filament produce sharp-pointed noise, make the performers and clerks and the audience in performance place uncomfortable.

Because harmonic voltage and harmonic current in the utility network all can cause very big harm to power consumption equipment and electrical network itself, world many countries has all been issued the national standard of restriction mains by harmonics, or is formulated the regulation of restriction harmonic wave by authoritative institution.Its basic principle is the harmonic current that the restriction harmonic source injects electrical network, the mains by harmonics voltage control in allowed limits, makes the electric equipment that is connected in the electrical network avoid Harmonic Interference and operate as normal.The 3C forcible authentication of China has proposed strict restriction to harmonic source.The output harmonic wave of controllable silicon dimmer has exceeded the limits value that the 3C forcible authentication proposes harmonic source widely.The controllable silicon dimmer that the electrical network public hazards are serious is withdrawn from the market at last.

The utility model content

The purpose of this utility model is for the output that overcomes existing stage adjusting light device produces the adverse effect that harmonic wave brings, and a kind of device for regulating ligth of stage illumination lamp is provided.

The purpose of this utility model can reach by taking following measure:

A kind of device for regulating ligth of stage illumination lamp, its design feature is: comprise signal input and processing section, control signal generating portion and operating part; Signal input processing section comprises signal input unit and signal processing unit, and the control signal generating portion comprises that microcomputer control unit and feedback unit constitute, and operating part comprises main IGBT unit, auxilliary IGBT unit, filter unit and controlled power unit; The signal input part of control signal generating portion connects the signal output part of signal input processing section, the input that control signal output ends connects operating part, the feedback signal input connects feedback signal output, feedback signal output connection signal input and the processing section of operating part by feedback unit feedback signal input.

Signal input and processing section receive DMX control signal and Artificial Control signal, export to the control signal generating portion after treatment; The control information that control signal generating portion acknowledge(ment) signal microprocessing unit is sent, and comprehensive controlled the power section voltage, electric current and the load state that feed back, produce the pwm signal of control IGBT, simultaneously, finish report information such as the voltage that returns from high-power part, electric current, temperature, overload, short circuits to the signal microprocessing unit; Operating part produces sine voltage and current signal is exported to controlled power section, and the moving market condition of power section is fed back to the control signal generating portion.Described power section can be light of stage or other power terminations.

Purpose of the present invention further also can reach by taking following measure:

Signal input processing section comprises DMX signal input channel, keyboard circuit, display circuit, rotary encoder, memory and signal processor, the signal output part of DMX signal input channel, keyboard circuit, display circuit, rotary encoder connects a signal input part of signal processor respectively, the signal output part of signal processor connects the signal input part of control generating portion, and signal processor is provided with the feedback signal output that a feedback signal input connects the control generating portion; Described DMX signal input channel can comprise more than one the road or two the tunnel.

Described DMX signal input channel has two identical electric paths, each electric path is formed by connecting by input signal terminal, level shifting circuit, photoelectric isolating circuit, signal shaping pre-process circuit, by the external input signal of input signal terminal, connect the signal input part of signal processor by the output of shaping pre-process circuit.

Signal processor is made of two sixteen bit microcomputer chips or 32 microcomputer chips and peripheral cell thereof.

The control generating portion is made of computer control unit and some feedback circuits of built-in Control Software, described feedback circuit comprises short-circuit condition feedback circuit, current feedback circuit, overload feedback circuit, voltage feedback circuit, overtemperature feedback circuit, and feedback signal output, signal output part that the signal input part of described feedback circuit connects controlled power model respectively connect the feedback signal input of importing the processing section respectively.

The computer control unit is made of sixteen bit microcomputer chip or 32 microcomputer chips, memory chip and peripheral cells thereof.

Operating part is by control unit, main IGBT unit, auxilliary IGBT unit, the soft switch of active nondestructive buffering, input LC filter circuit and output LC filter circuit, and main IGBT unit is constituted or is made of two IGBT elements by a rectifier bridge and an IGBT element; Auxilliary IGBT unit is made of two IGBT elements; The input that the input connection power frequency power input signal of input LC filter circuit, output connect main IGBT unit, the output of main IGBT unit connects the input of auxilliary IGBT unit, and the output of auxilliary IGBT unit connects the input of controlled power frequency power model by output LC filter circuit.

Main IGBT, auxilliary igbt chip are the photoelectric-isolated insulated gate bipolar transistor, and its drive current is 150A, withstand voltage 1200V, have malfunction feedback and malfunction soft turn-off function; The switching speed of maximum 500uS.

For the voltage and current precision that makes feedback improves, current feedback circuit and voltage feedback circuit adopt linear optical coupling respectively.

Each feedback loop adopts active lossless or low-loss to cushion soft switch.

The signal processor of signal input processing section is connected by the microcomputer control unit of serial line interface with the control signal generating portion.

The microcomputer control unit of control signal generating portion is connected with six input LC filter circuits of operating part by six winding displacements.

The utlity model has following outstanding beneficial effect:

1, maximum characteristics of the present invention are that photoelectric-isolated insulated gate bipolar transistor (IGBT) is as the controlling and driving parts, whole control process is finished by microcomputer chip control, its input, output voltage waveforms all are sinusoidal wave, and the operating voltage waveform that makes light of stage is for sinusoidal wave.Because input voltage of the present invention and electric current all are Sine Wave Amplitude Modulations, output current and voltage all are sinusoidal wave, output voltage changes from 0 to 220V with control signal, output current and its amplitude of output voltage same-phase change with load, therefore, fundamentally eliminated the harmonic problem of controllable silicon dimmer, the harmonic wave proportion drops to below 1%.

2, the utility model is owing to adopt high-speed CPU to produce the PWM modulating wave, (operating frequency is high more up to 50KHz for operating frequency, output current and voltage approach sine wave more), drive advanced IGBT and export to load with the AC sine wave that produces 0～220V, therefore, can reduce the volume of filter inductance and electric capacity with the frequency work of 50KHz, and the noise that guarantees to produce is outside people's audibility range.The utility model is divided into 256 grades with the carrier frequency of 50KHz, makes resolution for output voltage less than 0.4%, promptly less than 0.9V (power-frequency voltage of utility network is 220V).The utility model is very little (less than 1%) owing to not having low-order harmonic, harmonic wave total amount.This has guaranteed the perfection of output waveform effectively.

3, because the utility model adopts insulated gate bipolar transistor (IGBT) to do high power device, so the utility model do not have the restriction of minimum load, has perfect output protection setting, and the weight of filter inductance is greatly reduced.Be suitable for any power frequency supply, comprise the electrical network of remote mountain areas, island minor scale power net, small power station, diesel generation, the power supply of the out of use poor quality of controllable silicon dimmer such as dc inversion electricity and the power supply of low capacity.Minimum output voltage can be set be used for fluorescent lamp, the light modulation of neon light even load.Drive motor class load easily.In addition, also be applicable to all types of load light modulations, and be applicable to all types of load pressure regulation.

Description of drawings

Fig. 1 is a schematic block circuit diagram of the present utility model.

Fig. 2 is the schematic block circuit diagram of input of the utility model signal and processing section.

Fig. 3 is the schematic block circuit diagram of an embodiment of the utility model.

Fig. 4 is the schematic block circuit diagram of the external signal input of an embodiment of the utility model.

Fig. 5 is the schematic block circuit diagram of the human-computer dialogue signal input of an embodiment of the utility model.

Fig. 6 is the circuit theory diagrams of the operating part of an embodiment of the utility model.

Fig. 7 is traditional filter circuit schematic diagram

Fig. 8 is the filter circuit schematic diagram of the operating part of an embodiment of the utility model.

Fig. 9 is the schematic block circuit diagram of the control generating portion of an embodiment of the utility model.

Figure 10 is the computer program flow chart of input of the utility model signal and processing section.

Figure 11 is waveform input signal figure of the present utility model.

Figure 12 is signal output waveform figure of the present utility model.

Figure 13 is the change of current oscillogram of the operating part of the utility model embodiment.

Embodiment

With reference to Fig. 1, present embodiment is made of signal input and processing section 1, control signal generating portion 2 and operating part 3.

With reference to Fig. 2, Fig. 3, signal input processing section 1 comprises DMX signal input channel 11, keyboard circuit 12, display circuit 13, rotary encoder 14, memory 15 and signal processor 16, the signal output part of DMX signal input channel 11, keyboard circuit 12, display circuit 13, rotary encoder 14 connects a signal input part of signal processor 16 respectively, the signal output part of signal processor 16 connects the signal input part of control generating portion 2, and signal processor 16 is provided with the feedback signal output that a feedback signal input connects control generating portion 2.

With reference to Fig. 4, DMX signal input channel 11 has two identical electric paths, each electric path is formed by connecting by input signal terminal 110, level shifting circuit 111, photoelectric isolating circuit 112, signal shaping pre-process circuit 113, by input signal terminal 110 external input signals, connect the signal input part of signal processor 16 by the output of shaping pre-process circuit 113.

With reference to Fig. 5, constitute the human-computer dialogue circuit by keyboard circuit 12, display circuit 13, rotary encoder 14, photophore 17 and signal processor 16 indications.

Signal processor 16 is built-in signal handler, this program can be finished work such as the self study of start parameter adaptive, signal reception, system parameter setting and corrected Calculation the most optimized parameter, and its concrete work is as shown in figure 10.

In the present embodiment: keyboard circuit 12 can be formed by connecting by button commonly used and peripheral electron element, and display circuit 13 can be made of LCD, and rotary encoder 14 is known rotary encoder commonly used.Input signal terminal 110 can be the pins type splicing ear, level shifting circuit 111 can be made of the common voltage change-over circuit, photoelectric isolating circuit 112 can be made of photoelectricity isolated tube commonly used and peripheral cell thereof, and signal shaping pre-process circuit 113 can be made of shaping circuit commonly used.Signal processor 16 can by sixteen bit can 32 computer chip and peripheral cell thereof constitute.Memory 15 can be made of storage chip commonly used.

With reference to Fig. 3 and Fig. 9, control generating portion 2 comprises the microcomputer control unit and the feedback unit of built-in Control Software; Control generating portion 2 comprises the microcomputer control unit and the feedback unit of built-in Control Software; Microcomputer control unit comprises control microprocessor 20 and signal allocation and drive output 27; Described feedback circuit comprises short-circuit condition feedback circuit 22, current feedback circuit 23, overload feedback circuit 24, voltage feedback circuit 25, overtemperature feedback circuit 26, and feedback signal output, signal output part that the signal input part of described feedback circuit connects controlled power model respectively connect the feedback signal input of importing processing section 1 respectively.

In the present embodiment: the computer control unit can be made of sixteen bit microcomputer chip or 32 microcomputer chips 20, memory 21 and peripheral cells thereof, and memory 21 can be made of storage chip commonly used.Short-circuit condition feedback circuit 22, overload feedback circuit 24, overtemperature feedback circuit 26 can be made of convectional signals feedback circuit respectively.Current feedback circuit 23, voltage feedback circuit 25 can be made of optocoupler feedback circuit commonly used.

The built-in control supervisor of computer control unit, its work of finishing as shown in Figure 9.

With reference to Fig. 6 and Fig. 9, operating part 3 is by control unit 30, main IGBT unit 31, auxilliary IGBT unit 32, the soft switch of active nondestructive buffering, input LC filter circuit 33 and output LC filter circuit 34, and main IGBT unit 31 is constituted or is made of two IGBT elements by a rectifier bridge and an IGBT element; Auxilliary IGBT unit 32 is made of two IGBT elements; The input that the input connection power frequency power input signal 35 of input LC filter circuit 33, output connect main IGBT unit 31, the output of main IGBT unit 31 connects the input of auxilliary IGBT unit 32, and the output of auxilliary IGBT unit 32 connects the input of controlled power frequency power model 36 by output LC filter circuit 34.

Described control unit 30 is carried out brightness adjustment control, has the function that drives and protect main IGBT, auxilliary IGBT, have the function of power parameter, and have following characteristic: drive current is 150A, withstand voltage 1200V, has malfunction feedback and malfunction soft turn-off function; The switching speed of maximum 500uS.Main IGBT unit, auxilliary IGBT unit are the photoelectric-isolated insulated gate bipolar transistor.

Control unit 30 is accepted the PWM control information that control generating portion 2 is sent, and main IGBT is implemented the PWM control of 50KHz.For saving cost, improve reliability, present embodiment adopts the strategy of a rectifier bridge and a main IGBT, to replace the scheme of two main IGBT.

In whole system; the device of most critical is main IGBT; its stable operation is most important; thereby the control of main IGBT unit and the protection must be very reliable; because control unit 30 is mainly used to control and protects main IGBT unit, therefore, control unit 30 can adopt up-to-date application-specific integrated circuit (this IC can buy) in the present embodiment on market; main IGBT control and protection are greatly simplified, and reliability greatly improves.This application-specific integrated circuit has following characteristic: can drive 150A, the IGBT of 1200V; Photoelectricity is isolated, the malfunction feedback; The switching speed of maximum 500uS; The soft shutoff of malfunction etc.

For the voltage and current precision that makes feedback improves, the current feedback of present embodiment and voltage feedback circuit can adopt linear optical coupling.

For making " IGBT sinewave dimmer " obtain high performance and high efficient, each bar feedback loop adopts the change of current of the soft switch resonance circuit of state-of-the-art active nondestructive buffering, the harmless meaning is that switching loss is very little, energy nondestructively feeds back in the electrical network and goes, thereby, the loss of IGBT switch is accounted for by original switching loss and leading become present switching loss and account for less importantly, and reliability significantly improves.Circuit is by the inlet wire filter inductance, the inlet wire filter capacitor, and main IGBT, rectifier bridge, two auxiliary IGBT, output inductor, output filter capacitor is formed.Circuit has made full use of the additional capacitor of IGBT, and stray inductance waits the reluctant parameter of traditional commutation mode, makes the conducting of IGBT switch and ends big di/dt and dv/dt can not occur, thereby effectively guaranteed the work safety of IGBT.For guaranteeing the reliability and stability of the IGBT change of current, the devices at full hardware structure is adopted in the driving of auxiliary IGBT, comprising the state-detection of power circuit, the PWM of two IGBT produces.

Disturbance harmonic oscillation problem when solving unloaded and underloading, present embodiment adopts controlled filtering technique.By the PWM waveform that main IGBT produces, frequency can not directly be exported to load up to 50KHz.Thereby introduced LC filtering (because the damping coefficient of LC filter is low, the efficient height).When unloaded and underloading, be superimposed with disturbance harmonic oscillation on the fundamental voltage output of voltage, its frequency of oscillation and undamped nature frequency of oscillation ω n are approaching, when input supply voltage Ui connects, between transient periods such as sudden change, the transient voltage resonance peak will make filter capacitor and converter power switch IGBT be in dangerous condition.For addressing this problem, increase a RC branch road in addition, and constitute controllable resonant damping LC output filter together with former LC.

With reference to Fig. 6, the utility model adopts the soft switch commutation technique of active nondestructive buffering.Inlet wire filter inductance L1, inlet wire filter capacitor C1, (VF1 encapsulates soft-recovery diode VD1 to main IGBT altogether, VC1), the high speed rectifier bridge (encapsulates soft-recovery diode D1 altogether, encapsulates soft-recovery diode D2 altogether, encapsulate soft-recovery diode D3 altogether, encapsulate soft-recovery diode D4 altogether), auxiliary IGBT (VF2 encapsulates soft-recovery diode VD2, interelectrode capacitance VC2 altogether), auxiliary IGBT (VF3, encapsulate soft-recovery diode VD3 altogether, interelectrode capacitance VC3), filter inductance L2, inlet wire filter capacitor C2, controlled filter capacitor C3, controlled filter resistance R1, load L.

The operation principle of Fig. 6 is as follows:

For discussing conveniently, suppose D1, D2, D3, D4, VD1, VD2, the VD3 pressure drop is zero.VF1, VF2, VF3 conduction voltage drop are zero.Because main IGBT VF1 switching frequency is up to 50KHz, power frequency 50Hz just comparatively speaking, thereby in each change of current stage, no matter power frequency sine wave is positive half wave or negative half-wave, all is considered as direct current and handles.

(1) during positive half wave, after VF1 opened, D1, D4 conducting stored certain energy in loop inductance L2, commutation course, electric current in the inductance L 2 and direction (forward) are constant, are load current I0, because L2 is bigger, thereby, in each change of current stage, can think invariable; Also store certain energy in loop inductance L1, electric current in the inductance L 1 and direction (forward) are constant, are load current I0.

(2) when VF1 turn-offs beginning, VC1, VC3 voltage are zero, and VC2 is an input instantaneous voltage this moment.Electric current in the inductance L 1 and direction (forward) are constant.

In the VF1 turn off process, electric current is to the C1 charging and through D1, the D4 part to the I0 among the VC1 charging afterflow simultaneously formation L2 among the L1; The VC2 discharge, VD3 afterflow, the another part of the I0 among the formation L2.

(3) treat that VC2 discharge finishes, when VC1 was charged to this moment input instantaneous voltage, the voltage that is added on the VF3 was zero.VF3 is open-minded, the VD2 afterflow, and it is constant to keep I0 by the energy storage of L2.At this moment the voltage that is added on the VF3 only is its pressure drop (1.5 volts of less thaies).

(4) finish to the change of current of VF3 by VF1.The energy storage of L1 continues VC1 and C1 charging, until the electric current in the inductance L 1 drops to zero, VC1 and C1 are charged to maximum.Then, C1 discharges through L1, the current reversal among the L1.Design circuit parameter L 1, the resonance frequency of C1 are at 14KHz, and the switching frequency of main IGBT is up to 50KHz; for protecting main IGBT and C1; we only require that the forward current of L1 has decline by a relatively large margin, and VC1 and C1 are charged to a rational value, the change of current of opening that promptly enters VF1.

(5) open in the process of VF1, at first VC1 discharge forces between the collector and emitter of VF3 and turn-offs voluntarily because of bearing back-pressure, and the while, VD2 also turn-offed because of bearing back-pressure.Respectively provide part conducting electric current by L1 and C1, one makes VC2 charging, VD3 afterflow, the I0 of its two afterflow L2.When the VC1 discharge off, VC2 charges to this moment input instantaneous voltage when being C1 voltage, and VF1 finishes open-minded.

(6) finish to the change of current of VF1 by VF3.The L1 electric current continues to increase, and the C1 discharging current continues to reduce, until the electric current in the inductance L 1 reaches I0, the C1 discharge drops to power-frequency voltage.For the change of current of opening of VF1 is next time prepared.

When (7) bearing half-wave, similar when situation and positive half wave.When VF1 opened, D2, D3 conducting stored certain energy in loop inductance L2, commutation course, and electric current in the inductance L 2 and direction (oppositely) are constant, are load current I0, because L2 is bigger, thereby, in each change of current stage, can think invariable; Also store certain energy in loop inductance L1, electric current in the inductance L 1 and direction (oppositely) are constant, are load current I0.

(8) when VF1 turn-offs beginning, VC1, VC2 voltage are zero, and VC3 is an input instantaneous voltage this moment.Electric current in the inductance L 1 and direction (oppositely) are constant.

In the VF1 turn off process, electric current is to the C1 charging and through D2, the D3 part to the I0 among the VC1 charging afterflow simultaneously formation L2 among the L1; The VC3 discharge, VD2 afterflow, the another part of the I0 among the formation L2.

(9) treat that VC3 discharge finishes, when VC1 was charged to this moment input instantaneous voltage, the voltage that is added on the VF2 was zero.VF2 is open-minded, the VD3 afterflow, and it is constant to keep I0 by the energy storage of L2.At this moment the voltage that is added on the VF2 only is its pressure drop (1.5 volts of less thaies).

(10) finish to the change of current of VF2 by VF1.The energy storage of L1 continues VC1 and C1 charging, until the electric current in the inductance L 1 drops to zero, VC1 and C1 are charged to maximum.Then, C1 discharges through L1, the current reversal among the L1.Design circuit parameter L 1, the resonance frequency of C1 are at 14KHz, and the switching frequency of main IGBT is up to 50KHz; for protecting main IGBT and C1; we only require that the reverse current of L1 has decline by a relatively large margin, and VC1 and C1 are charged to a rational value, the change of current of opening that promptly enters VF1.

(11) open in the process of VF1, at first VC1 discharge forces between the collector and emitter of VF2 and turn-offs voluntarily because of bearing back-pressure, and the while, VD3 also turn-offed because of bearing back-pressure.Respectively provide part conducting electric current by L1 and C1, one makes VC3 charging, VD2 afterflow, the I0 of its two afterflow L2.When the VC1 discharge off, VC2 charges to this moment input instantaneous voltage when being C1 voltage, and VF1 finishes open-minded.

(12) finish to the change of current of VF1 by VF2.The L1 electric current continues to increase, and the C1 discharging current continues to reduce, until the electric current in the inductance L 1 reaches I0, the C1 discharge drops to power-frequency voltage.For the change of current of opening of VF1 is next time prepared.

The soft switch resonance circuit of active nondestructive buffering commutation technique solves exactly from VF1 to VF3, from VF3 to FV1, and from VF1 to VF2, big di/dt in the transient process of four kinds of changes of current from VF2 to FV1 and dv/dt shock problem.Auxiliary IGBT VF2 and VF3 have realized that no-voltage is open-minded, zero-current switching.Main IGBT VF1 also realized less electric current open with no-voltage under shutoff.

With reference to Figure 11, the voltage current waveform of input is sinusoidal wave; With reference to Figure 12, the voltage current waveform of handling through the filtering link also is sinusoidal wave, gives the input voltage and input current waveform of contrast among the figure.As can be seen from Figure 12, the output voltage current waveform is in 0～input voltage and input current waveform middle tone amplitude variationization.

The control signal of the change of current is as follows:

With reference to Figure 13, state A, B, C, D constitute the complete PWM modulating wave cycle of main IGBT VF1.

As shown in figure 13, can be clear that when the power frequency positive half wave VF1, four kinds of states of the change of current control signal between the VF3.State B, D are the transition states of the change of current, and the time is very short, but the key of the soft switch resonance of the active nondestructive buffering change of current, and the change of current of the soft switch resonance of active just nondestructive buffering has significantly reduced the change of current loss of IGBT.State A is the conducting state of VF1.State C is the conducting state of VF3.

When power frequency is born half-wave, can see VF1, four kinds of states of the change of current control signal between the VF2.State B, D are the transition states of the change of current, and the time is very short, but the key of the soft switch resonance of the active really nondestructive buffering change of current, and the change of current of the soft switch resonance of active just nondestructive buffering has significantly reduced the change of current loss of IGBT.State A is the conducting state of VF1.State C is the conducting state of VF2.

The utility model adopts controllable resonant damping LC output filter.

Controllable resonant damping LC output filtering technique is partly adopted in the filtering of present embodiment, and the disturbance harmonic oscillation problem when having prevented unloaded and underloading effectively makes the utility model can no-load running.Traditional LC filter analysis is as follows:

With reference to Fig. 7, assumed load is RL, the inductance L 2 in the system, capacitor C 2, load RL complex impedance is respectively sL2,1/sC2, RL, Figure 12 circuit output voltage to filter before the transfer function of terminal voltage be:

$G\left(s\right)=\frac{\mathrm{Uo}\left(s\right)}{\mathrm{Ui}\left(s\right)}=\frac{1/\mathrm{<figure-callout\; id="2"\; label="s\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}{C}_{}{}_2//R_L}{s{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+(1/\mathrm{<figure-callout\; id="2"\; label="s\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}{C}_{}{}_2//R_L)}=\frac{R_L}{s^2{R}_L{C}_2{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+s{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+R_L}$

Its effective damping ratio $\mathrm{\&xi;}=\sqrt{{<figure-callout\; id="2"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}_2/{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2}/\left(2R_L\right),$ Resonance peak $M_P=1/\left(2\mathrm{\&xi;}\sqrt{1-{\mathrm{\&xi;}}^2}\right).$ As load resistance R _LDuring → ∞, ξ → 0, resonance peak M _P→ ∞.For second-order system, M _PThe relative stability of characterization system is as 1.0＜M _P＜1.4, i.e., 0.4＜ξ＜0.7 o'clock can obtain satisfied mapping; Work as M _P＞1.5 o'clock, overshoot for several times will appear in step response; Common M _PBig more, the transient state overshoot is also big more.Work as M _PWhen very big, if system is subjected to resonance frequency ${\mathrm{\&omega;}}_r={\mathrm{\&omega;}}_n\sqrt{1-2{\mathrm{\&xi;}}^2}$ (when zero load or underloading and undamped natural resonance frequency ω _nVery approaching) locate near interference signal effect, the LC output filter can not effectively suppress and filtering it, and output just has bigger disturbance component, may cause serious consequence.

In fact, transfer function can be expressed as: $G\left(s\right)=\frac{1}{s^2{C}_2{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+\mathrm{<figure-callout\; id="2"\; label="s\; L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}{L}_{}{}_2/R_L+1}$ As load resistance R _LDuring → ∞, abbreviation is: $G\left(s\right)=\frac{1}{s^2{C}_2{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+1}$ Obviously, Here it is undamped LC oscillator,

s ²=(j2 π f _r) ²=-1/ (L ₂C ₂), resonance frequency is $f_r=1/\left(2\mathrm{\&pi;}\sqrt{L_2{C}_2}\right).$ During resonance, very little interference signal input Ui (f is arranged _r), G (f _r) → ∞, resonance peak Uo (f _r) → ∞.

At the defective of Figure 12 circuit, Figure 13 circuit has been proposed, promptly controlled resonance damping LC output filter, assumed load is RL, the inductance L 2 in the system, capacitor C 2, resonance damping resistance R1, resonance damping capacitor C3, load RL complex impedance is respectively sL2,1/sC2, R1,1/sC3, RL, Figure 13 circuit output voltage to filter before the transfer function of terminal voltage be:

The circuit output voltage to filter before the transfer function of terminal voltage be:

$G\left(s\right)=\frac{\mathrm{Uo}\left(s\right)}{\mathrm{Ui}\left(s\right)}=\frac{(1/s{C}_2)//[{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1+(1/s{C}_3)]//R_L}{s{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+(1/s{C}_2)//[{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1+(1/s{C}_3)]//R_L}$

$=\frac{({\mathrm{sR}}_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3+1)}{s^2{C}_2{L}_2[(s{R}_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3+1)+{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3/C_2]+s{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2/R_L(s{R}_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3+1)+(s{R}_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3+1)}$

$=\frac{s+\frac{1}{R_1{C}_3}}{C_2{L}_2[{\mathrm{<figure-callout\; id="3"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^3+(\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{R_1}){\mathrm{<figure-callout\; id="2"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^2+(1+\frac{1}{R_1{R}_L{C}_2{C}_3})s+\frac{1}{R_1{C}_3}]}$

Write out the denominator polynomial equation of s:

${\mathrm{<figure-callout\; id="3"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^3+(\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{R_1}){\mathrm{<figure-callout\; id="2"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^2+(1+\frac{1}{R_1{R}_L{C}_2{C}_3})s+\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}=0$

According to routh stability criterion, polynomial coefficient can be arranged in the row and column (Routh array) of following form:

$\begin{array}{ccc}{\mathrm{<figure-callout\; id="3"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^3& 1& 1+\frac{1}{R_1{R}_L{C}_2{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}\end{array}$

$\begin{array}{ccc}{\mathrm{<figure-callout\; id="2"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^2& \frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1}& \frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}\end{array}$

$\begin{array}{cc}{s}^1& \frac{(\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{R_1})(1+\frac{1}{R_1{R}_L{C}_2{C}_3})-\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}}{\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1}}\end{array}$

$\begin{array}{cc}{s}^0& \frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}\end{array}$

The condition of system stability is that every in Routh array first row is positive sign, thereby $(\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{R_1})(1+\frac{1}{R_1{R}_L{C}_2{C}_3})-\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}>0$ Must set up.The prerequisite that this inequality is set up is, $\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1}>0,$ When zero load, first is zero, and second can not be zero.This condition is permanent to be set up.Another condition of system stability be whole coefficients of denominator multinomial s equation all be on the occasion of.This condition is permanent to be set up.Thereby two conditions in the necessary and sufficient condition of system stability are all permanent to be set up, and all limits of system all are positioned at left half s plane, system stability.From transfer function as seen, system is many zero point of a left half-plane, and root locus is to moving to left, and the stability of a system improves.

Can prove, work as C ₃=C ₂And be former C ₂Half of value, L ₂It is constant, ${\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1=2\sqrt{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2/\left(2C_2\right)}/\mathrm{\&pi;}$ Promptly can obtain satisfied effect.Resonance frequency is $f_n=1/\left(2\mathrm{\&pi;}\sqrt{L_2\left(2C_2\right)}\right),$ If C ₂=C ₃=2.2 μ F, L ₂=300 μ H, then R ₁=5.4 Ω, resonance frequency f _nIf=4380Hz is resonance amplitude voltage effective value U _n, R ₁Loss Suppose U _n=10V can get R ₁Loss is 1.13W; Suppose U _n=15V can get R ₁Loss is 2.5W, visible R ₁Is very big to the loss of resonance frequency with the increase decay of resonance amplitude.Output voltage effective value U=220V, output frequency f _s=50Hz, at this moment R ₁Loss Be about 0.12W, R ₁Loss to available power can be ignored.

In the present embodiment, detect with the driving of auxiliary IGBT as follows:

Report information such as the voltage of this part detection power circuit, electric current, temperature, overload, short circuit are given control microprocessor.Accept the main IGBT deblock signal that control microprocessor sends and carry out relevant action.While this part is the operating state of detection power circuit also, and produces the controlling and driving signal of auxiliary IGBT with this.

The operating state of detection power circuit has adopted a kind of design cleverly, constitutes power circuit servo-actuated detection system, makes detection system both simple and reliable, can truly and apace reflect the operating state of power circuit again.Generate PWM with this devices at full hardware that constructs auxiliary IGBT, simple circuit drives.The reliability and stability of the IGBT change of current have effectively been guaranteed.

Because the main element of PWM operating part is high-power, high voltage, high-frequency device, and main power IGBT is operated in the PWM modulating frequency of 50KHz, the stray parameter (interelectrode capacitance of device relevant with wiring in the high-power circuit with structure, wiring inductance etc.) (do not adopt this technology, must adopt hard switching to cushion commutation technique with the soft switch change of current of active nondestructive buffering of formations such as auxiliary IGBT is the most troubling.At that rate, even adopt state-of-the-art circuit, power consumption also can significantly increase, and filter inductance and electric capacity all must strengthen, and the people is unacceptable the most in addition is that power IGBT must significantly amplify, and reduces the PWM modulating frequency.The consequence of bringing is, product weight increases, and volume increases, and cost increases, and performance declines to a great extent, and finally can't compete with external product), the side reaches the technical staff clenchs one's teeth actually, in the explosive sound repeatedly of power IGBT this technology is broken through and is grasped.LC output filtering technique during by beginning turns to controllable resonant damping LC output filtering technique, and IGBT is burnt in the LC vibration of middle experience to make us hanging back.

In the development process of IGBT sinewave dimmer, the manpower that this part drops into is also very big.Account for the nearly more than 1/4th (mainly being the high-power circuit of debugging) of amount of work.

The circuit output voltage to filter before the transfer function of terminal voltage be:

$G\left(s\right)=\frac{\mathrm{Uo}\left(s\right)}{\mathrm{Ui}\left(s\right)}=\frac{(1/s{C}_2)//[{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1+(1/s{C}_3)]//R_L}{s{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2+(1/s{C}_2)//[{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1+(1/s{C}_3)]//R_L}$

$=\frac{({\mathrm{sR}}_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3+1)}{s^2{C}_2{L}_2[(s{R}_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3+1)+{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3/C_2]+s{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2/R_L(s{R}_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3+1)+(s{R}_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3+1)}$

$=\frac{s+\frac{1}{R_1{C}_3}}{C_2{L}_2[{\mathrm{<figure-callout\; id="3"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^3+(\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{R_1}){\mathrm{<figure-callout\; id="2"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^2+(1+\frac{1}{R_1{R}_L{C}_2{C}_3})s+\frac{1}{R_1{C}_3}]}$

Write out the denominator polynomial equation of s:

${\mathrm{<figure-callout\; id="3"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^3+(\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{R_1}){\mathrm{<figure-callout\; id="2"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^2+(1+\frac{1}{R_1{R}_L{C}_2{C}_3})s+\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}=0$

According to routh stability criterion, polynomial coefficient is arranged in the row and column (Routh array) of following form:

$\begin{array}{ccc}{\mathrm{<figure-callout\; id="3"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^3& 1& 1+\frac{1}{R_1{R}_L{C}_2{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}\end{array}$

$\begin{array}{ccc}{\mathrm{<figure-callout\; id="2"\; label="s"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">s</figure-callout>}}^2& \frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1}& \frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}\end{array}$

$\begin{array}{cc}{s}^1& \frac{(\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{R_1})(1+\frac{1}{R_1{R}_L{C}_2{C}_3})-\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}}{\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1}}\end{array}$

$\begin{array}{cc}{s}^0& \frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}\end{array}$

The condition of system stability is that every in Routh array first row is positive sign, thereby $(\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}+\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{R_1})(1+\frac{1}{R_1{R}_L{C}_2{C}_3})-\frac{1}{R_1{\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">C</figure-callout>}}_3}>0$ Must set up.The prerequisite that this inequality is set up is, $\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="R\; L\; C"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_L{C}_{}{}_2}+\frac{L_2}{{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1}>0,$ When zero load, first is zero, and second can not be zero.This condition is permanent to be set up.

Another condition of system stability be whole coefficients of denominator multinomial s equation all be on the occasion of.This condition is permanent to be set up.

Thereby two conditions in the necessary and sufficient condition of system stability are all permanent to be set up, and all limits of system all are positioned at left half s plane, system stability.

From transfer function as seen, system is many zero point of a left half-plane, and root locus is to moving to left, and the stability of a system improves.

Can prove, work as C ₃=C ₂And be former C ₂Half of value, L ₂It is constant, ${\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">R</figure-callout>}}_1=2\sqrt{{\mathrm{<figure-callout\; id="2"\; label="L"\; filenames="Y20052012022200171.png,Y20052012022200181.png"\; state="\{\{state\}\}">L</figure-callout>}}_2/\left(2C_2\right)}/\mathrm{\&pi;}$ Promptly can obtain satisfied effect.Resonance frequency is $f_n=1/\left(2\mathrm{\&pi;}\sqrt{L_2\left(2C_2\right)}\right),$ If C ₂=C ₃=2.2 μ F, L ₂=300 μ H, then R ₁=5.4 Ω, resonance frequency f _nIf=4380Hz is resonance amplitude voltage effective value U _n, R ₁Loss Suppose U _n=10V can get R ₁Loss is 1.13W; Suppose U _n=15V can get R ₁Loss is 2.5W, visible R ₁Is very big to the loss of resonance frequency with the increase decay of resonance amplitude.Output voltage effective value U=220V, output frequency f _s=50Hz, at this moment R ₁Loss Be about 0.12W, R ₁Loss to available power can be ignored.

Report information such as the voltage of this part detection power circuit, electric current, temperature, overload, short circuit are given control microprocessor.Accept the main IGBT deblock signal that control microprocessor sends and carry out relevant action.While this part is the operating state of detection power circuit also, and produces the controlling and driving signal of auxiliary IGBT with this.

The operating state of detection power circuit has adopted a kind of design cleverly, constitutes power circuit servo-actuated detection system, makes detection system both simple and reliable, can truly and apace reflect the operating state of power circuit again.Generate PWM with this devices at full hardware that constructs auxiliary IGBT, simple circuit drives.The reliability and stability of the IGBT change of current have effectively been guaranteed.

Claims (10)

1, a kind of device for regulating ligth of stage illumination lamp is characterized in that: comprise signal input and processing section (1), control signal generating portion (2) and operating part (3); Signal input processing section (1) comprises signal input unit and signal processing unit, control signal generating portion (2) comprises that microcomputer control unit and feedback unit constitute, and operating part (3) comprises main IGBT unit, auxilliary IGBT unit, filter unit and controlled power unit; The signal input part of control signal generating portion (2) connects the feedback signal input that feedback signal output, feedback signal output that the signal output part of signal input processing section (1), input that control signal output ends connects operating part (3), feedback signal input connect operating part (3) by feedback unit connect signal input and processing section (1).

2, a kind of device for regulating ligth of stage illumination lamp according to claim 1, it is characterized in that: signal input processing section (1) comprises DMX signal input channel (11), keyboard circuit (12), display circuit (13), rotary encoder (14), memory (15) and signal processor (16), DMX signal input channel (11), keyboard circuit (12), display circuit (13), the signal output part of rotary encoder (14) connects a signal input part of signal processor (16) respectively, the signal output part of signal processor (16) connects the signal input part of control generating portion (2), and signal processor (16) is provided with the feedback signal output that a feedback signal input connects control generating portion (2); Described DMX signal input channel (11) can comprise more than one the road or two the tunnel.

3, a kind of device for regulating ligth of stage illumination lamp according to claim 2, it is characterized in that: described DMX signal input channel (11) has two identical electric paths, each electric path is formed by connecting by input signal terminal (110), level shifting circuit (111), photoelectric isolating circuit (112), signal shaping pre-process circuit (113), by the external input signal of input signal terminal (110), connect the signal input part of signal processor (16) by the output of shaping pre-process circuit (113).

4, a kind of device for regulating ligth of stage illumination lamp according to claim 2 is characterized in that: signal processor (16) is made of two sixteen bit microcomputer chips or 32 microcomputer chips and peripheral cell thereof.

5, a kind of device for regulating ligth of stage illumination lamp according to claim 1, it is characterized in that: control generating portion (2) is made of computer control unit and some feedback circuits of built-in Control Software, described feedback circuit comprises short-circuit condition feedback circuit (22), current feedback circuit (23), overload feedback circuit (24), voltage feedback circuit (25), overtemperature feedback circuit (26), the signal input part of described feedback circuit connect the feedback signal output of controlled power model respectively, signal output part connects the feedback signal input of input processing section (1) respectively.

6, a kind of device for regulating ligth of stage illumination lamp according to claim 5 is characterized in that: the computer control unit is made of sixteen bit microcomputer chip or 32 microcomputer chips (20), memory chip (21) and peripheral cell thereof.

7, a kind of device for regulating ligth of stage illumination lamp according to claim 1, it is characterized in that: operating part (3) is by control unit (30), main IGBT unit (31), auxilliary IGBT unit (32), the soft switch of active nondestructive buffering, input LC filter circuit (33) and output LC filter circuit (34), and main IGBT unit (31) is constituted or is made of two IGBT elements by a rectifier bridge and an IGBT element; Auxilliary IGBT unit (32) is made of two IGBT elements; The input that the input connection power frequency power input signal (35) of input LC filter circuit (33), output connect main IGBT unit (31), the output of main IGBT unit (31) connects the input of auxilliary IGBT unit (32), and the output of auxilliary IGBT unit (32) connects the input of controlled power frequency power model (36) by output LC filter circuit (34).

8, a kind of device for regulating ligth of stage illumination lamp according to claim 7 is characterized in that: main IGBT, auxilliary igbt chip are the photoelectric-isolated insulated gate bipolar transistor.

9, a kind of device for regulating ligth of stage illumination lamp according to claim 7, it is characterized in that: current feedback circuit and voltage feedback circuit adopt linear optical coupling respectively; Each feedback loop adopts active lossless or low-loss to cushion soft switch.

10, a kind of device for regulating ligth of stage illumination lamp according to claim 1 is characterized in that: the signal processor (16) of signal input processing section (1) is connected by the microcomputer control unit of serial line interface with control signal generating portion (2); The microcomputer control unit of control signal generating portion (2) is connected with six input LC filter circuits of operating part (3) by six winding displacements.

Images