CN219843608U - Carrier cancellation system based on numerical control passive vector modulator - Google Patents
Carrier cancellation system based on numerical control passive vector modulator Download PDFInfo
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Abstract
The utility model discloses a carrier cancellation system based on a numerical control passive vector modulator, which comprises a transmitter, a power division network, a delay line, a transceiver isolator, an antenna, a carrier cancellation module and a receiver, wherein the transmitter is connected with the power division network; the transmitter is connected with the power division network, the power division network is respectively connected with the delay line, the carrier cancellation module and the transceiver isolator, the transceiver isolator is respectively connected with the antenna and the carrier cancellation module, and the carrier cancellation module is connected with the receiver. The utility model can not only meet the precision of phase and amplitude control, but also reduce the introduction of extra phase noise and amplitude noise, thereby increasing the communication distance of the self-interference system.
Description
Technical Field
The utility model relates to a carrier cancellation system based on a numerical control passive vector modulator, and belongs to the technical field of carrier communication.
Background
Radio frequency identification (Radio Frequency Identification, RFID) is a radio frequency identification technology, which performs non-contact two-way data communication in a radio frequency mode, and reads and writes a recording medium (an electronic tag or a radio frequency card) in a radio frequency mode, so as to achieve the purposes of identification and data exchange.
Carrier leakage in an rfid reader/writer refers to a signal that, in some full duplex wireless communication systems, a single tone signal output from a transmitter enters a receiver due to various non-ideal factors. The carrier leakage signal affects the demodulation of the reflected signal of the tag or object, and the reason for this is mainly three: firstly, the limited isolation of a transceiver isolator, namely a circulator and a directional coupler are commonly used devices for separating transceiver signals, and the commonly used isolation is 25-30 dB; secondly, the echo reflection of the antenna can not realize perfect matching between an antenna port and a receiving and transmitting port, so that echo signals can be formed at the port, and the echo loss of the antenna is only about 15-20 dB generally; third, the amplitude and phase of the reflected signal caused by the environment of the antenna near field change with the environmental change, which is also a main cause of uncertainty of the carrier leakage amplitude and phase. Carrier signals that leak to the receiver are important factors affecting the performance of the receiver. Large carrier leakage can cause active devices in the receive chain to saturate, resulting in the receiver not functioning properly. Even if the amplitude of the carrier leakage is insufficient to cause circuit saturation, its phase noise and amplitude noise raise the noise floor of the receiver and reduce the sensitivity of the receiver. The sensitivity of the receiver decreases (i.e., the sensitivity value increases) with increasing carrier leakage signal from the system, and thus it determines not only the maximum output power of the transmitter but also the minimum signal processing capability of the receiver, thereby defining the maximum transmission distance of the system.
In chinese patent application No. 202111418672.0, a radio frequency cancellation circuit and an anti-interference receiver are disclosed. The radio frequency cancellation circuit provides a carrier cancellation scheme which utilizes a vector modulator, a microprocessor, an ADC, a DAC and other matched circuits to realize self-adaption. However, in this technical solution, the control signal of the vector modulator is generated by the DAC, and because the baseband signal inevitably contains noise, the cancellation signal is synthesized by the mixer, and the noise associated with the DAC inevitably enters the receiving channel, thereby reducing the receiving sensitivity of the receiving link. The modulator itself is also implemented by two multipliers, which include active circuitry that introduces additional noise that is uncorrelated with the noise in the transmitted signal and therefore remains after cancellation and goes to the subsequent modules of the receiver. After entering the subsequent modules of the receiver, the noise floor of the receiver is raised, further exacerbating the deterioration of the sensitivity of the receiver.
Disclosure of Invention
The utility model aims to provide a carrier cancellation system based on a numerical control passive vector modulator.
In order to achieve the technical purpose, the utility model adopts the following technical scheme:
a carrier cancellation system based on a numerical control passive vector modulator comprises a transmitter, a power division network, a delay line, a transceiver isolator, an antenna, a carrier cancellation module and a receiver;
the transmitter is connected with the power division network, the power division network is respectively connected with the delay line, the carrier cancellation module and the transceiver isolator, the transceiver isolator is respectively connected with the antenna and the carrier cancellation module, and the carrier cancellation module is connected with the receiver.
The carrier cancellation module preferably comprises a numerical control passive vector modulator, a cancellation directional coupler, a sampling directional coupler, a quadrature demodulator, a two-way analog-to-digital converter and a field programmable logic array;
the input end of the mixer in the numerical control passive vector modulator is connected with two paths of output ends of the field programmable logic array, and the output end of the combiner in the numerical control passive vector modulator is connected with the input end of the other end of the cancellation directional coupler; one end input end of the cancellation directional coupler is connected with the other end output end of the receiving and transmitting isolator, and the output end of the cancellation directional coupler is connected with the input end of the sampling directional coupler; one end output end of the sampling directional coupler is connected with the other input ends of the 0-degree phase and the 90-degree phase of the quadrature demodulator respectively, and the other end output end of the sampling directional coupler is connected with the input end of the receiver; the 0-degree phase and the 90-degree phase of the quadrature demodulator are respectively connected with the input end of the two-way analog-to-digital converter; the I-path and Q-path output ends of the two-path analog-to-digital converter are respectively connected with two-path input ends of the field programmable logic array.
The numerical control passive vector modulator comprises a mixer, a Q-path inverter, an I Lu Fanxiang device, a Q-path digital modulation attenuator, an I-path digital modulation attenuator and a power combiner; the function and the implementation mode of the Q-channel inverter are the same as those of the I-channel inverter, and the function and the implementation mode of the Q-channel digital modulation attenuator are the same as those of the I-channel digital modulation attenuator;
the 0-degree phase output end of the mixer is connected with the I-path inverter, and the 90-degree phase output end of the mixer is connected with the Q-path inverter; the I-path inverter is connected with the I-path digital modulation attenuator; the Q-channel inverter is connected with the Q-channel digital modulation attenuator; the I-path digital-tuning attenuator and the Q-path digital-tuning attenuator are both connected with the power combiner.
The I-path inverter comprises an input end single-pole double-throw switch, a first interconnection line, a second interconnection line and an output end single-pole double-throw switch;
the first port of the input end single-pole double-throw switch is connected with the 0-degree phase output end of the mixer; the second port of the input end single-pole double-throw switch is connected with one end of the first interconnecting wire; the third port of the input end single-pole double-throw switch is connected with one end of the second interconnecting wire; the other end of the first interconnecting wire is connected with a second port of the output end single-pole double-throw switch; the other end of the second interconnecting wire is connected with a third port of the output end single-pole double-throw switch; the first port of the output end single-pole double-throw switch is connected with the I-path digital-control attenuator.
Compared with the prior art, the carrier cancellation system based on the numerical control passive vector modulator has the core idea that an active circuit is not used in the cancellation signal synthesis process. Specifically, the utility model increases the correlation between the leakage signal and the cancellation signal at the cancellation point by adding the delay feeder on the cancellation signal generation link, so as to increase the output noise suppression bandwidth. The utility model adopts two one-dimensional lookup tables to model the passive vector modulator in a two-dimensional lookup table mode, thereby reducing the requirement of the FPGA algorithm on storage resources. Aiming at the problem that the discrete complex gain deviation of the passive vector modulator is inconsistent, the utility model provides an LMS algorithm based on Euclidean distance judgment to realize dynamic tracking inhibition of carrier leakage. The utility model can not only meet the precision of phase and amplitude control, but also reduce the introduction of extra phase noise and amplitude noise, thereby increasing the communication distance of the self-interference system.
Drawings
Fig. 1 is a schematic circuit diagram of a carrier cancellation system based on a digitally controlled passive vector modulator in an embodiment of the present utility model;
FIG. 2 is a schematic diagram of a digitally controlled passive vector modulator according to an embodiment of the present utility model;
FIG. 3 (a) is a schematic diagram of a test platform according to an embodiment of the present utility model;
FIG. 3 (b) is a flowchart showing a complex gain list testing operation in accordance with one embodiment of the present utility model;
FIG. 3 (c) is a second flowchart illustrating a complex gain list test in accordance with an embodiment of the present utility model;
fig. 4 is a flowchart of a carrier cancellation method based on euclidean distance search decisions in an embodiment of the present utility model.
Detailed Description
The technical contents of the present utility model will be described in detail with reference to the accompanying drawings and specific examples.
< first embodiment >
As shown in fig. 1, a first embodiment of the present utility model discloses a carrier cancellation system based on a digitally controlled passive vector modulator, which at least comprises a transmitter 1, a power division network 2, a delay line 3, a transceiver isolator 4, an antenna 5, a carrier cancellation module 6 and a receiver 7. The transmitter 1 is connected with the power division network 2, the power division network 2 is respectively connected with the delay line 3, the carrier cancellation module 6 and the transceiver isolator 4, the transceiver isolator 4 is respectively connected with the antenna 5 and the carrier cancellation module 6, and the carrier cancellation module 6 is connected with the receiver 7. The specific composition and working principle of the components are described as follows:
in a first embodiment of the utility model, the transmitter 1 comprises a power amplifier 101, a signal source 102. The output end of the signal source 102 is connected to the input end of the power amplifier 101, and the output end of the power amplifier 101 is connected to the input end of the first power divider 201.
Wherein the transmitter 1 is adapted to generate a high power tone signal for:
1) Generating a cancellation signal;
2) Local oscillation required by error signal demodulation;
3) Radiating through the antenna toward the tag or target.
In the first embodiment of the present utility model, the power dividing network 2 includes a first power divider 201 and a second power divider 202. The input end of the first power divider 201 is connected with the output end of the power amplifier 101, one end output end of the first power divider 201 is connected with the input end of the second power divider 202, and the other end output end of the first power divider 201 is connected with one end of the delay line 3; one end output end of the second power divider 202 is connected to one end input end of the transceiver isolator 4, and the other end output end of the second power divider 202 is connected to one end input ends of the quadrature demodulator 604, which are respectively in 0 ° phase and 90 ° phase.
The power division network 2 distributes and outputs the single-tone signal output by the transmitter 1 according to a reasonable proportion, and outputs a part of the signal distributed according to the reasonable proportion to the numerical control passive vector modulator 601 through the delay line 3 by the first power divider 201, and outputs another part of the signal distributed according to the reasonable proportion to the transceiver isolator 4 by the second power divider 202.
In a first embodiment of the utility model the delay line 3 is constituted by a length of coaxial cable.
One end of the delay line 3 is connected with the output end of the other end of the first power divider 201, and the other end of the delay line 3 is connected with the numerical control passive vector modulator 601.
The effect of the delay line 3 is, among other things, to improve the correlation of the cancellation signal and the leakage signal at the cancellation point by reducing the delay deviation. I.e. the correlation of the two signals is proportional to the error signal noise suppression bandwidth and also proportional to the processing bandwidth of the receiver.
In the first embodiment of the present utility model, one end input end of the transceiver isolator 4 is connected to one end output end of the second power divider 202, one end output end of the transceiver isolator 4 is connected to the antenna 5, and the other end output end of the transceiver isolator 4 is connected to one end input end of the cancellation directional coupler 602.
The transceiver isolator 4 is used for separating a transmission signal and a reception signal, and the isolation of the transceiver isolator is generally 25-30 dB. The antenna 5 functions to radiate a transmitted signal and to receive a signal reflected back by a tag (or object).
In a first embodiment of the utility model, the carrier cancellation module 6 comprises a digitally controlled passive vector modulator (Digital Control Passive Vector Modulator, DPVM) 601, a cancellation directional coupler 602, a sampling directional coupler 603, a quadrature demodulator 604, a two-way analog-to-digital converter ADC 605 and a field programmable logic array FPGA 606. The input end of the mixer 607 in the numerical control passive vector modulator 601 is connected with two paths of output ends of the field programmable logic array FPGA 606, and the output end of the combiner 612 in the numerical control passive vector modulator 601 is connected with the input end of the other end of the cancellation directional coupler 602; one end input end of the cancellation directional coupler 602 is connected with the other end output end of the transceiver isolator 4, and the output end of the cancellation directional coupler 602 is connected with the input end of the sampling directional coupler 603; one end output end of the sampling directional coupler 603 is connected with the other input ends of the 0-degree phase and the 90-degree phase of the quadrature demodulator 604 respectively, and the other end output end of the sampling directional coupler 603 is connected with the input end of the receiver 7; the 0-degree phase and the 90-degree phase of the quadrature demodulator 604 are respectively connected with two input ends of the two-way analog-to-digital converter ADC 605; the I-way and Q-way outputs of the two-way analog-to-digital converter ADC 605 are connected to two-way inputs of the field programmable logic array FPGA 606, respectively.
As shown in fig. 2, the digitally controlled passive vector modulator 601 includes a mixer 607, a Q Lu Fanxiang device 608, an I Lu Fanxiang device 609, a Q-way digital attenuator 610, an I-way digital attenuator 611, and a combiner 612. The function and the implementation mode of the Q-channel inverter are the same as those of the I-channel inverter, and the function and the implementation mode of the Q-channel digital modulation attenuator are the same as those of the I-channel digital modulation attenuator.
Wherein the 0 ° phase output of the mixer 607 is connected to the I Lu Fanxiang device 609, and the 90 ° phase output of the mixer 607 is connected to the Q Lu Fanxiang device 608; the I-way inverter 609 is connected with the I-way digital modulation attenuator 611; the Q-way inverter 608 is connected to the Q-way digitally tuned attenuator 610; the I-path digital attenuator 611 and the Q-path digital attenuator 610 are connected to a combiner 612.
The I-way inverter 609 includes an input single pole double throw switch 613, a first interconnect line 0, a second interconnect line 1, and an output single pole double throw switch 614. Wherein the first port 1 of the input single pole double throw switch 613 is connected with the 0 ° phase output of the mixer 607; the second port 2 of the input single pole double throw switch 613 is connected with one end of the first interconnecting line 0; the third port 3 of the input single pole double throw switch 613 is connected with one end of the second interconnecting line 1; the other end of the first interconnecting line 0 is connected with the second port 2 of the output end single-pole double-throw switch 614; the other end of the second interconnecting wire 1 is connected with a third port 3 of the output end single-pole double-throw switch 614; the first port 1 of the output single pole double throw switch 614 is connected to the I-way digitally modulated attenuator 611.
Wherein the digitally controlled passive vector modulator 601 is operative on the digital signal I CW [8:0]And Q CW [8:0]The amplitude and phase of the input signal are changed under control of (a).
The cancellation directional coupler 602 functions, among other things, to vector sum the cancellation signal and the leakage signal and output an error signal.
The sampling directional coupler 603 is used to take a small part of the error signal output by the cancellation directional coupler 602, so as to obtain the amplitude and phase information of the residual leakage signal in the error signal.
The quadrature demodulator 604 is used to convert the error signal output from the cancellation directional coupler 602 into baseband signals, i.e., an in-phase signal I and a quadrature signal Q.
The dual analog-to-digital converter 605 is used to convert the analog I and Q signals into digital signals and output the digital signals to the FGPA.
The FPGA signal processing module 606 is used for implementing an ELMS (minimum mean square error algorithm) based on euclidean distance decision, and solving the I by the I/Q signal of the error signal CW [8:0]And Q CW [8:0]。
< second embodiment >
The second embodiment of the utility model discloses a method for realizing a carrier cancellation system based on a numerical control passive vector modulator, which comprises the following steps:
s1: and constructing a complex gain automatic test hardware platform of the numerical control passive vector modulator (Digital Control Passive Vector Modulator, DPVM).
As shown in fig. 3 (a), the output end of the power divider is respectively connected with one end input end of the numerically controlled passive vector modulator, the sine input end of the quadrature demodulator and the cosine input end of the quadrature demodulator; the output end of the numerical control passive vector modulator is respectively connected with the sine input end of the quadrature demodulator and the cosine input end of the quadrature demodulator; the cosine output end of the quadrature demodulator is connected with the input end of the ADC 1; the sine output end of the quadrature demodulator is connected with the input end of the ADC 2; the output end of the ADC1 and the output end of the ADC2 are connected with a field programmable logic array (FPGA); the output end of the field programmable logic array is connected with the other input end of the numerical control passive vector modulator; the data output end of the field programmable logic array is connected with the upper computer.
S2: for I-path control word I CW And Q-way control word Q CW And (3) testing the complex gain list of the I path and the Q path to obtain a one-dimensional gain list of the I path and the Q path.
As shown in fig. 3 (b) and fig. 3 (c), wherein the specific test method includes:
s21: control word Q of setting Q path CW =0, set control word I of I way CW ＝-255。
The effect of maximizing the Q-way attenuation value is to reduce the impact of the Q-way signal on the I-way test.
S22: judgment control word I CW And 255 or less.
If yes, go to step S23; if not, obtaining a one-dimensional gain list of the I path, wherein the elements are
S23: obtaining the current complex gain A through testing I +jA Q The complex gain is recorded and the process proceeds to step S24.
Wherein A is I Is the real part of the complex gain; a is that Q Is the imaginary part of the complex gain; j is the sign of the imaginary number, which mathematically means-1 radix.
S24: set I CW ＝I CW +1, repeating step S21.
The method for obtaining the one-dimensional gain list of the Q paths is the same as the method for obtaining the one-dimensional gain list of the I paths, and the present utility model is not repeated here.
S3: and generating a cancellation baseband signal at the time n.
Numerical control passive vector modulator is controlled in control word (I CW (n)＝s，Q CW Generating a cancellation baseband signal under the action of (n) =m)
Wherein, the liquid crystal display device comprises a liquid crystal display device,is the real part of the vector modulator gain, +.>Respectively the imaginary part, S of the gain of the vector modulator ref The complex baseband signal of the reference signal is complex constant.
S4: and acquiring an n-moment error complex baseband signal.
The n-time error complex baseband signal is the difference between the n-time leakage complex baseband signal and the n-time cancellation complex baseband signal.
S5: and predicting the complex gain of the vector modulator model of the next clock cycle according to the minimum mean square error principle.
The complex gain of the vector modulator model for the next clock cycle is predicted by the following calculation formula:
wherein a (n) =a I (n)+j*A Q (n) is the internal complex gain; a is that I (n) is the real part, A Q (n) is its imaginary part; the parameter mu is used for controlling loop bandwidth of the ELMS algorithm;predicting complex gain for the next periodic vector modulator model; />For its real part, & gt>Is its imaginary part.
The ELMS algorithm is a minimum mean square error algorithm (Least Mean Square Based on Euclidean Distance, abbreviated as ELMS) based on euclidean distance decision, and is used for realizing cancellation of carrier leakage signals.
S6: calculating an I-path control word I at n moments by using the one-dimensional gain list of the I-path and the Q-path obtained in the step S2 CW And Q-way control word Q CW And complex gains of their respective adjacent control words.
Provided with thisI-path gain control word I CW (n) =s, Q-way gain control word Q CW (n) =m, I-way control word offset l e { -1,0,1}, Q-way control word offset k e { -1,0,1}.
Obtaining complex gain of I path by searching one-dimensional gain list of I pathWhere l.epsilon. -1,0, 1.
Obtaining the complex gain of the Q path by searching the one-dimensional gain list of the Q pathWhere k ε { -1,0,1}.
The complex gains of the I path and the Q path are added to obtain the complex gain of the vector modulator model realized under the action of 9 groups of control words, and the calculation formula is as follows:
s7: and obtaining the offset of the optimal control word through the shortest Euclidean distance searching judgment.
Calculating predicted complex gains with a coordinate-transformed digital calculator (Coordinate Rotation Digital Computer, CORDIC for short)And the above 9 complex gains +.>The Euclidean distance between, where l, k ε { 1,0,1}.
The offset (L, K) of the control word corresponding to the shortest Euclidean distance is obtained by a searching method, and the calculation formula is as follows:
where L is the offset of the I-way control word and K is the offset of the Q-way control word.
S8: the internal complex gain is updated.
The calculation formula for updating the internal complex gain is as follows:
when (L, K) = (0, 0) represents complex gain predicted by searchAnd->The Euclidean distance is the shortest, i.e. the control word of the next cycle will remain unchanged, when the complex gain A (n+1) in the next cycle is set to +.>
When (L, K) + (0, 0) denotes complex gain predicted by searchAnd->The Euclidean distance is the shortest, i.e. the control word of the next cycle will change, when the internal complex gain A (n+1) of the next cycle is set to
S9: updating the control word of the vector modulator, and repeating the steps S3 to S9 until the operation is stopped. The control word of the update vector controller is calculated as follows:
I cw (n+1)＝I cw (n)+L
Q cw (n+1)＝Q cw (n)+K
because the mixer, the numerical control inverse phase shifter, the numerical control attenuator and the power combiner which form the numerical control passive vector modulator DPVM have certain amplitude errors and phase errors, complex gains and control words corresponding to the DPVM cannot be described through a simple mathematical formula. The ideal model is a two-dimensional lookup table, i.e. traversing all possibilities of the control word, and obtaining the complex gain corresponding to the DPVM by testing. The utility model constructs the DPVM model by using the method that two one-dimensional lists approximate to one two-dimensional list, and solves the problems that in the prior art, a large amount of test time is required to be consumed for establishing the model of the control word with the two bits of 9 bits wide, and a large amount of FPGA storage resources are required to be consumed for realizing the lookup table.
Compared with the prior art, the carrier cancellation system based on the numerical control passive vector modulator has the core idea that an active circuit is not used in the cancellation signal synthesis process. Specifically, the utility model increases the correlation between the leakage signal and the cancellation signal at the cancellation point by adding the delay feeder on the cancellation signal generation link, so as to increase the output noise suppression bandwidth. The utility model adopts two one-dimensional lookup tables to model the passive vector modulator in a two-dimensional lookup table mode, thereby reducing the requirement of the FPGA algorithm on storage resources. Aiming at the problem that the discrete complex gain deviation of the passive vector modulator is inconsistent, the utility model provides an LMS algorithm based on Euclidean distance judgment to realize dynamic tracking inhibition of carrier leakage. The utility model can not only meet the precision of phase and amplitude control, but also reduce the introduction of extra phase noise and amplitude noise, thereby increasing the communication distance of the self-interference system.
The carrier cancellation system based on the numerical control passive vector modulator provided by the utility model is described in detail. Any obvious modifications to the present utility model, without departing from the spirit thereof, would constitute an infringement of the patent rights of the utility model and would take on corresponding legal liabilities.
Claims (5)
1. The carrier cancellation system based on the numerical control passive vector modulator is characterized by comprising a transmitter, a power division network, a delay line, a receiving and transmitting isolator, an antenna, a carrier cancellation module and a receiver;
the transmitter is connected with the power division network, the power division network is respectively connected with the delay line, the carrier cancellation module and the transceiver isolator, the transceiver isolator is respectively connected with the antenna and the carrier cancellation module, and the carrier cancellation module is connected with the receiver.
2. The carrier cancellation system of claim 1, wherein: the carrier cancellation module comprises a numerical control passive vector modulator, a cancellation directional coupler, a sampling directional coupler, a quadrature demodulator, a two-way analog-to-digital converter and a field programmable logic array;
the input end of the mixer in the numerical control passive vector modulator is connected with two paths of output ends of the field programmable logic array, and the output end of the combiner in the numerical control passive vector modulator is connected with the input end of the other end of the cancellation directional coupler; one end input end of the cancellation directional coupler is connected with the other end output end of the receiving and transmitting isolator, and the output end of the cancellation directional coupler is connected with the input end of the sampling directional coupler; one end output end of the sampling directional coupler is connected with the other input ends of the 0-degree phase and the 90-degree phase of the quadrature demodulator respectively, and the other end output end of the sampling directional coupler is connected with the input end of the receiver; the 0-degree phase and the 90-degree phase of the quadrature demodulator are respectively connected with the input end of the two-way analog-to-digital converter; the I-path and Q-path output ends of the two-path analog-to-digital converter are respectively connected with two-path input ends of the field programmable logic array.
3. The carrier cancellation system of claim 2, wherein:
the numerical control passive vector modulator comprises a mixer, a Q-path inverter, an I Lu Fanxiang device, a Q-path digital modulation attenuator, an I-path digital modulation attenuator and a power combiner; the function and the implementation mode of the Q-channel inverter are the same as those of the I-channel inverter, and the function and the implementation mode of the Q-channel digital modulation attenuator are the same as those of the I-channel digital modulation attenuator.
4. The carrier cancellation system of claim 3, wherein:
the 0-degree phase output end of the mixer is connected with the I-path inverter, and the 90-degree phase output end of the mixer is connected with the Q-path inverter; the I-path inverter is connected with the I-path digital modulation attenuator; the Q-channel inverter is connected with the Q-channel digital modulation attenuator; the I-path digital-tuning attenuator and the Q-path digital-tuning attenuator are both connected with the power combiner.
5. The carrier cancellation system of claim 4, wherein:
the I-path inverter comprises an input end single-pole double-throw switch, a first interconnection line, a second interconnection line and an output end single-pole double-throw switch; the first port of the input end single-pole double-throw switch is connected with the 0-degree phase output end of the mixer; the second port of the input end single-pole double-throw switch is connected with one end of the first interconnecting wire; the third port of the input end single-pole double-throw switch is connected with one end of the second interconnecting wire; the other end of the first interconnecting wire is connected with a second port of the output end single-pole double-throw switch; the other end of the second interconnecting wire is connected with a third port of the output end single-pole double-throw switch;
the first port of the output end single-pole double-throw switch is connected with the I-path digital-control attenuator.
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