CN218549563U - Current compensation circuit, quasi-resonant power supply and charging device - Google Patents
Current compensation circuit, quasi-resonant power supply and charging device Download PDFInfo
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- CN218549563U CN218549563U CN202222448834.1U CN202222448834U CN218549563U CN 218549563 U CN218549563 U CN 218549563U CN 202222448834 U CN202222448834 U CN 202222448834U CN 218549563 U CN218549563 U CN 218549563U
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/02—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries for charging batteries from ac mains by converters
- H02J7/04—Regulation of charging current or voltage
- H02J7/06—Regulation of charging current or voltage using discharge tubes or semiconductor devices
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The application discloses a current compensation circuit, a quasi-resonant power supply and a charging device, wherein the current compensation circuit comprises a control module and a current providing module, and the control module is connected with a rectifying and filtering circuit and is used for being connected with the output voltage of the rectifying and filtering circuit; the current providing module comprises a resistance value adjustable circuit and a resistance value fixed circuit which are mutually connected in parallel, one parallel end of the resistance value fixed circuit and the resistance value adjustable circuit is used for being connected to the pulse controller, the other parallel end of the resistance value fixed circuit and the resistance value adjustable circuit is grounded, and the resistance value adjustable circuit is also connected with the control module; the control module is used for adjusting the resistance of the resistance value adjustable circuit when the output voltage of the received rectifying and filtering circuit is larger than or equal to the set voltage so as to reduce the current output to the pulse controller by the current providing module. The design can effectively reduce the overall model selection cost of the quasi-resonant power supply.
Description
Technical Field
The application relates to the technical field of power supplies, in particular to a current compensation circuit, a quasi-resonant power supply and a charging device.
Background
With the widespread use of new energy efficiency standards, the efficiency requirements of the switching power supply in the market field are higher and higher. Compared with a linear power supply, the switching power supply has the advantages of easiness in control, high efficiency, small size, good reliability, easiness in protection and the like, and is widely applied to equipment such as television power supplies, mobile phone chargers, industrial instruments, power adapters and the like.
Quasi-resonant power supply is switching power supply's one, and quasi-resonant power supply includes rectifier filter circuit and pulse controller, and quasi-resonant power supply is under the condition of full voltage, and when rectifier filter circuit's output voltage is great, input pulse controller electric current is too big, for making pulse controller can normally work under the condition of heavy current, often can select the pulse controller of nai heavy current, leads to resonant power supply's whole lectotype cost to be on the high side. Therefore, how to effectively reduce the model selection cost of the quasi-resonant power supply has become an urgent problem to be solved.
SUMMERY OF THE UTILITY MODEL
The embodiment of the application provides a current compensation circuit, a quasi-resonant power supply and a charging device, which can effectively reduce the overall model selection cost of the quasi-resonant power supply.
In a first aspect, an embodiment of the present application provides a current compensation circuit of a quasi-resonant power supply, where the quasi-resonant power supply includes a rectification filter circuit and a pulse controller that are connected to each other; the current compensation circuit comprises a control module and a current providing module, wherein the control module is connected with the rectifying and filtering circuit and is used for accessing the output voltage of the rectifying and filtering circuit; the current providing module comprises a resistance value adjustable circuit and a resistance value fixed circuit which are mutually connected in parallel, one parallel end of the resistance value fixed circuit and the resistance value adjustable circuit is used for being connected to the pulse controller, the other parallel end of the resistance value fixed circuit and the resistance value adjustable circuit is grounded, and the resistance value adjustable circuit is also connected with the control module; the control module is used for adjusting the resistance of the resistance value adjustable circuit when the output voltage of the received rectifying and filtering circuit is larger than or equal to the set voltage so as to reduce the current output to the pulse controller by the current providing module.
Based on this application embodiment's current compensation circuit, control module is used for when receiving rectifier filter circuit's output voltage be greater than or equal to the settlement voltage, the resistance of adjustable circuit of adjustment resistance, in order to increase the total resistance that the electric current provided the module, thereby under the unchangeable circumstances of pulse controller's power, reduce the electric current that the electric current provided the module output to pulse controller, pulse controller's undercurrent input under the big voltage circumstances has been realized, the lectotype cost of pulse controller can effectively be reduced, thereby reach the mesh that reduces quasi-resonant power's whole lectotype cost.
In a second aspect, an embodiment of the present application provides a quasi-resonant power supply, which includes a circuit board and the current compensation circuit described above, where the current compensation circuit is fabricated on the circuit board.
Based on quasi-resonance power supply of this application embodiment, because above-mentioned current compensation circuit's design, have above-mentioned current compensation circuit's quasi-resonance power supply, can effectively reduce quasi-resonance power supply's whole lectotype cost. In addition, the quasi-resonant power supply also has the effects of effectively improving the overall efficiency of the full-voltage input power supply and reducing the temperature rise and the electromagnetic interference.
In a third aspect, an embodiment of the present application provides a charging device, where the charging device includes a housing and the quasi-resonant power supply described above, where the housing has an installation space, and the quasi-resonant power supply is disposed in the installation space.
Based on the charging device in the embodiment of the application, the charging device with the quasi-resonant power supply can effectively reduce the overall model selection cost of the charging device.
Drawings
In order to more clearly illustrate the embodiments of the present application or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present application, and other drawings can be obtained by those skilled in the art without creative efforts.
Fig. 1 is a schematic circuit structure diagram of a current compensation module when the number of resistance value adjustable circuits is one in the application embodiment;
fig. 2 is a schematic circuit diagram of a current compensation module according to an embodiment of the present disclosure when the number of resistance adjustable circuits is multiple and the number of control modules is one;
fig. 3 is a schematic circuit diagram of a current compensation module when the number of resistance adjustable circuits is multiple and the number of control modules is multiple according to an embodiment of the present disclosure.
Reference numerals: 10. a current compensation circuit; 11. a resistance value adjustable circuit; q1, a first switching element; r39 and a first resistor; 12. a resistance value fixing circuit; r44, a resistance fixed resistor; 13. a control module; q2, a second switching element; r3, a bias resistor; ZD11, zener diodes; 14. a voltage dividing circuit; r27, a first divider resistor; r41 and a second divider resistor; r62, a third voltage dividing resistor; b1, voltage division nodes; r7 and a second resistor; 20. a rectification filter circuit; v +, output voltage; 30. a pulse controller.
Detailed Description
In order to make the objects, technical solutions and advantages of the present application more clearly understood, the present application is further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the present application and are not intended to limit the present application.
With the widespread use of new energy efficiency standards, the efficiency requirements of the switching power supply in the market field are higher and higher. Compared with a linear power supply, the switching power supply has the advantages of easiness in control, high efficiency, small size, good reliability, easiness in protection realization and the like, and is widely applied to equipment such as a television power supply, a mobile phone charger, an industrial instrument, a power adapter and the like.
The quasi-resonant power supply is one of the switching power supplies, and comprises a rectifying filter circuit and a pulse controller, wherein under the condition that the quasi-resonant power supply is under full voltage (namely wide voltage, the identification range of the general wide voltage is AC: 85V-264V), when the output voltage of the rectifying filter circuit is larger, the current of an input pulse controller is overlarge, so that the pulse controller can normally work under the condition of large current, the pulse controller with high current resistance is often selected, and the integral model selection cost of the quasi-resonant power supply is higher.
Therefore, how to effectively reduce the model selection cost of the quasi-resonant power supply has become an urgent problem to be solved.
In order to solve the above technical problem, please refer to fig. 1, a first aspect of the present application provides a current compensation circuit 10 for a quasi-resonant power supply, which can effectively reduce the overall model selection cost of the quasi-resonant power supply.
The quasi-resonant power supply comprises a rectifying and filtering circuit 20 and a pulse controller 30, a current compensation circuit 10 comprises a control module 13 and a current providing module, the current providing module comprises a resistance value adjustable circuit 11 and a resistance value fixed circuit 12, the control module 13 is used for being connected to an output voltage V + of the rectifying and filtering circuit 20, and when the output voltage V + is larger than or equal to a set voltage, the control module 13 reduces the current output to the pulse controller 30 by the current providing module by adjusting the resistance of the resistance value adjustable circuit 11.
The specific circuit structure of the current compensation circuit 10 of the quasi-resonant power supply is described below with reference to fig. 1 to 3.
As shown in fig. 1, the quasi-resonant power supply includes a rectifying and filtering circuit 20 and a pulse controller 30.
The rectifying and filtering circuit 20 is used for rectifying and filtering the external power supply voltage to form an output voltage V +. The external supply voltage may be understood as a mains voltage. It can be understood that the mains voltages in different regions or different countries are different, so that different mains voltages can form different output voltages V + after being processed by the rectifying and filtering circuit 20.
The primary function of the pulse controller 30 is to output a pulse signal to control the voltage of the primary winding of the quasi-resonant power supply coupled to the secondary winding. For example, the pulse controller 30 may be, but is not limited to, an SC3057.
The rectifying-filtering circuit 20 is connected to the pulse controller 30.
The current compensation circuit 10 includes a control module 13 and a current providing module.
The control module 13 is a circuit structure for controlling the magnitude of the current output from the current providing module to the pulse controller 30 according to the output voltage V + of the rectifying and smoothing circuit 20. The specific circuit configuration of the control module 13 will be described later.
The current providing module is used as a circuit structure for outputting current to the pulse controller 30, and includes a resistance value adjustable circuit 11 and a resistance value fixing circuit 12.
The resistance value of the resistance value adjustable circuit 11 is adjustable, and the control module 13 selectively adjusts the resistance value of the resistance value adjustable circuit 11 according to the output voltage V + of the rectification filter. The specific circuit structure of the resistance value adjustable circuit 11 will be described later.
The resistance value of the resistance value fixing circuit 12 is fixed and unchanged, the resistance value fixing circuit 12 may only include one resistor, and the resistance value of the one resistor is fixed and unchanged (namely, a fixed value resistor), and the resistance value fixing circuit 12 may also include a plurality of resistors, which may be connected in one of a series connection, a parallel connection and a mixed connection to form a resistor with a fixed and unchanged resistance value. The specific circuit configuration of the resistance value fixing circuit 12 will be described later.
As shown in fig. 1 to 3, the resistance value adjustable circuit 11 is connected in parallel with the resistance value fixing circuit 12. It should be noted that the number of the resistance value adjustable circuits 11 may be one or multiple, and when the number of the resistance value adjustable circuits 11 is one, two ends of the resistance value adjustable circuit 11 are respectively connected to two ends of the resistance value fixing circuit 12; when the number of the resistance value adjustable circuits 11 is plural, both ends of each resistance value adjustable circuit 11 are respectively connected to both ends of the resistance value fixing circuit 12.
One parallel end of the resistance value fixing circuit 12 and all the resistance value adjustable circuits 11 is used for being connected to the pulse controller 30 to output current to the pulse controller 30, and the other parallel end of the resistance value fixing circuit 12 and all the resistance value adjustable circuits 11 is grounded.
The control module 13 is configured to be connected to the rectifying and filtering circuit 20 to access the output voltage V +, the control module 13 is further connected to the resistance value adjustable circuit 11, and the control module 13 is configured to adjust the resistance value of the resistance value adjustable circuit 11 when the control module 13 receives that the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, so as to reduce the current output by the current providing module to the pulse controller 30. The voltage corresponding to the overcurrent that affects the normal operation of the pulse controller 30 is the "set voltage".
It will be appreciated that with the power of the pulse controller 30 remaining constant, according to the formula P = I 2 And R, where I is the current output by the current providing module to the pulse controller 30, and R is the total resistance of the current providing module. To reduce the current I output by the current supply circuit to the pulse controller 30, the total resistance R of the current supply module can only be increased. The total resistance of the current providing module is equal to the sum of the resistances of the resistance fixing circuit 12 and the resistance adjustable circuit 11 which are connected in parallel, and the resistance of the resistance fixing circuit 12 is fixed, so that in order to increase the total resistance R, the resistance of the resistance adjustable circuit 11 can be adjusted by directly increasing the resistance of the resistance adjustable circuit 11 to increase the total resistance R, and the resistance of the resistance adjustable circuit 11 can be adjusted by disconnecting the resistance adjustable circuit 11 from the resistance fixing circuit 12 to increase the total resistance R. It should be noted that, if the total resistance R is increased by disconnecting the adjustable resistance circuit 11 from the fixed resistance circuit 12, when the number of the adjustable resistance circuits 11 is one, the adjustable resistance circuit 11 may be directly disconnected from the fixed resistance circuit 12, so that the total resistance R is equal to the resistance of the fixed resistance circuit 12; when the number of the resistance adjustable circuits 11 is multiple, at least part of the resistance adjustable circuits 11 need to be disconnected from the resistance fixing circuit 12 reasonably as long as the resistance of the total resistor R after disconnection is greater than the resistance of the total resistor R before disconnection.
Based on the current compensation circuit 10 in the embodiment of the present application, the control module 13 is configured to adjust the resistance of the resistance value adjustable circuit 11 when the output voltage V + received from the rectifying and filtering circuit 20 is greater than or equal to the set voltage, so as to increase the total resistance of the current providing module, thereby reducing the current output from the current providing module to the pulse controller 30 under the condition that the power of the pulse controller 30 remains unchanged, thereby achieving the small current input of the pulse controller 30 under the condition of a large voltage, and effectively reducing the model selection cost of the pulse controller 30, thereby achieving the purpose of reducing the overall model selection cost of the quasi-resonant power supply.
As shown in fig. 1 to fig. 3, it is understood that the number of the resistance value adjustable circuits 11 may be one or more. When the number of the resistance value adjustable resistors is one, the number of the control modules 13 is one, and the one control module 13 adjusts the resistance of the one resistance value adjustable circuit 11 when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage. When the number of the resistance value adjustable circuits 11 is plural, the number of the control modules 13 may be one or plural. When the number of the control modules 13 is one, the control module 13 simultaneously adjusts the resistances of all the resistance value adjustable circuits 11 when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage; when the number of the control modules 13 is plural, one control module 13 may correspondingly adjust the resistance of one resistance value adjustable circuit 11 when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, or one control module 13 may simultaneously adjust the resistances of a plurality of (not all) resistance value adjustable circuits 11 when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage. For example, when the number of the adjustable resistance circuits 11 is three and the number of the control modules 13 is two, one of the control modules 13 controls the resistors of two adjustable resistance circuits 11 simultaneously when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, and the other control module 13 controls the resistor of the remaining one adjustable resistance circuit 11 when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage. It should be noted that, when there are a plurality of control modules 13, the output voltages V + of the rectifying and filtering circuits 20 received by different control modules 13 may be the same or different, and the setting voltages corresponding to different output voltages V + are also different. For convenience of description, the number of the resistance value adjustable circuits 11 is one, and the number of the control modules 13 is also one for example.
As shown in fig. 1, considering that the resistance of the resistance fixing circuit 12 is fixed and the resistance of the resistance adjustable circuit 11 is selectively changed under the control of the control module 13, in order to make the resistance fixing circuit 12 and the resistance adjustable circuit 11 have corresponding functions, it is designed that in some embodiments, the resistance fixing circuit 12 includes a resistance fixing resistor R44, one end of the resistance fixing resistor R44 is used for connecting to the pulse controller 30, and the other end of the resistance fixing resistor R44 is grounded. The resistance value adjustable circuit 11 includes a first switching element Q1 and a first resistor R39, where the first switching element Q1 has a first input terminal, a first output terminal and a first controlled terminal, the first input terminal is grounded, the first output terminal is used to be connected to the pulse controller 30 through the first resistor R39, and the first controlled terminal is connected to the control module 13. That is, the first switching element Q1 and the first resistor R39 are connected in series to form a series branch, two ends of the resistance fixed resistor R44 are connected in parallel with the series branch, one parallel end of the series branch and one parallel end of the resistance fixed resistor R44 are grounded, the other parallel end of the series branch and the other parallel end of the resistance fixed resistor R44 are used for being connected to the pulse controller 30, and the control module 13 is connected to the first controlled end of the first switching element Q1. When the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, the control module 13 controls the first switching element Q1 to be turned off, so as to increase the total resistance of the current providing module. Specifically, when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, the control module 13 controls the first input terminal of the first switching element Q1 to be disconnected from the first output terminal of the first switching element Q1, so that the first switching element Q1 is in a disconnected state, and the first switching element Q1 is disconnected, so that the first resistor R39 connected in series with the first switching element Q1 is disconnected from the resistance value fixing resistor R44, at this time, the resistance value of the total resistor is the resistance value of the resistance value fixing resistor R44, and the resistance value of the total resistor of the current providing module after the first switching element Q1 is disconnected is increased relative to the resistance value of the total resistor of the current providing module before the first switching element Q1 is disconnected. In the design, the first switch element Q1 is disconnected to disconnect the first resistor R39 and the resistance value fixing resistor R44, at this time, the resistance value of the total resistor of the current providing module is the resistance value of the resistance value fixing resistor R44, and compared with that before the first switch element Q1 is disconnected, the resistance value of the total resistor of the current providing module is increased to some extent, so that the current output to the pulse controller 30 by the current providing module is effectively reduced, the small current input of the pulse controller 30 under the condition of large voltage is realized, the model selection cost of the pulse controller 30 can be effectively reduced, and the purpose of reducing the whole model selection cost of the quasi-resonant power supply is achieved.
As shown in fig. 1, in consideration of the fact that the control module 13 controls the first switching element Q1 to be turned off when the output voltage V + of the rectifying and smoothing circuit 20 is greater than or equal to the set voltage, of course, the control module 13 also needs to control the first switching element Q1 to be turned on when the output voltage V + of the rectifying and smoothing circuit 20 is less than the set voltage, in order to enable the control module 13 to have a corresponding circuit control function, it is designed that in some embodiments, the control module 13 includes a second switching element Q2, a zener diode ZD11 and a bias resistor R3. The second switching element Q2 has a second input terminal, a second output terminal, and a second controlled terminal. The second controlled terminal is used for connecting the output voltage V + of the rectifying and filtering circuit 20, and the second output terminal is connected with the first controlled terminal. The cathode of the zener diode ZD11 is connected to the second input terminal, and the anode of the zener diode ZD11 is grounded. One end of the bias resistor R3 is connected with the second controlled end, and the other end of the bias resistor R3 is connected with the second input end. Specifically, when the output voltage V + of the rectifying and smoothing circuit 20 is greater than or equal to the set voltage, the larger output voltage V + acts on the second controlled terminal of the second switching element Q2, and the larger output voltage V + acts on the cathode of the zener diode ZD11 through the bias resistor R3, so that the voltage acting on the cathode of the zener diode ZD11 is greater than the reverse breakdown voltage of the zener diode ZD11 to make the zener diode ZD11 reverse breakdown, the zener diode ZD11 reverse breakdown pulls down the voltage of the second input terminal of the second switching element Q2, so that the voltage of the second input terminal of the second switching element Q2 is less than the voltage of the second controlled terminal of the second switching element Q2 to turn off the second switching element Q2, the second switching element Q2 turns off to turn off the first switching element Q1, the first switching element Q1 turns off to disconnect the first resistor R39 from the fixed resistance R44, and the resistance of the above-mentioned total resistance R44 is the resistance after the first switching element Q1 turns off to provide the total off current of the first switching element Q1. On the contrary, when the output voltage V + of the rectifying and filtering circuit 20 is less than the set voltage, the smaller output voltage V + acts on the second controlled end of the second switching element Q2, and the smaller output voltage V + acts on the cathode of the zener diode ZD11 through the bias resistor R3, so that the voltage acting on the cathode of the zener diode ZD11 is less than the reverse breakdown voltage of the zener diode ZD11 to make the zener diode ZD11 not be reverse broken down, and the voltage of the second input end of the second switching element Q2 is greater than the voltage of the second controlled end of the second switching element Q2 (and the voltage difference is greater than the conduction threshold of the second switching element Q2) to make the second switching element Q2 conductive, the second switching element Q2 conductive to make the first switching element Q1 conductive, the first switching element Q1 conductive to make the first resistor R39 and the resistance fixed resistor R44 parallel connected, at this time, the resistance of the total resistor R44 is the total resistance after the parallel connection of the first resistor R39, and the total resistance of the first switching element Q1 after providing the total current of the first switching module that is reduced relative to the first switching module. In this design, when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, the second switching element Q2 is turned off to turn off the first switching element Q1, the first switching element Q1 is turned off to turn off the first resistor R39 and the resistance fixing resistor R44, and at this time, the resistance of the total resistor of the current providing module is the resistance of the resistance fixing resistor R44, compared with that before the first switching element Q1 is turned off, the resistance of the total resistor of the current providing module is increased, so that the current output from the current providing module to the pulse controller 30 is effectively reduced, the small current input of the pulse controller 30 under the condition of large voltage is realized, the model selection cost of the pulse controller 30 can be effectively reduced, and the purpose of reducing the overall model selection cost of the quasi-resonant power supply is achieved. When the output voltage V + of the rectifying and filtering circuit 20 is less than the set voltage, the second switching element Q2 is turned on to turn on the first switching element Q1, the first switching element Q1 is turned on to connect the first resistor R39 and the resistance fixing resistor R44 in parallel, and at this time, the resistance of the total resistor of the current providing module is the resistance after the resistance fixing resistor R44 and the first resistor R39 are connected in parallel, compared with the resistance of the total resistor of the current providing module before the first switching element Q1 is turned on, the resistance of the total resistor of the current providing module is reduced, so that the current output from the current providing module to the pulse controller 30 is effectively increased, the pulse controller 30 is input with a proper large current under a small voltage condition, and the normal operation of the pulse controller 30 is ensured.
Further, the control module 13 further includes a voltage dividing circuit 14, one end of the voltage dividing circuit 14 is used for connecting to the output voltage V + of the rectifying and filtering circuit 20, and the other end of the voltage dividing circuit 14 is grounded, the voltage dividing circuit 14 includes at least two voltage dividing resistors connected in series, and the voltage dividing circuit 14 has a voltage dividing node b1 between any two voltage dividing resistors, and the voltage dividing node b1 is connected to the second controlled end. Specifically, the voltage dividing circuit 14 includes a first voltage dividing resistor R27, a second voltage dividing resistor R41, and a third voltage dividing resistor R62, a first end of the first voltage dividing resistor R27 is used for connecting to the output voltage V + of the rectifying and filtering circuit 20, a second end of the first voltage dividing resistor R27 is connected to a first end of the second voltage dividing resistor R41, a second end of the second voltage dividing resistor R41 is connected to a first end of the third voltage dividing resistor R62, a second end of the third voltage dividing resistor R62 is grounded, and a voltage dividing node b1 is located between the second end of the second voltage dividing resistor R41 and the first end of the third voltage dividing resistor R62. In the design, by designing the voltage dividing circuit 14, the output voltage V + of the rectifying and filtering circuit 20 is divided by the voltage dividing circuit 14 and then acts on the second controlled end of the second switching element Q2, so as to protect the second switching element Q2 well.
Further, the control module 13 further includes a second resistor R7, a first end of the second resistor R7 is grounded, and another end of the second resistor R7 is connected to the second output terminal. In the design, the second resistor R7 is designed, the second resistor R7 has a good voltage dividing effect, and when the second switch element Q2 is turned on, the voltage difference between the gate of the first switch element Q1 and the source of the first switch element Q1 is greater than the turn-on threshold of the first switch element Q1, so that the second switch element Q2 is effectively turned on.
As shown in fig. 1, considering that when the output voltage V + of the rectifying and smoothing circuit 20 is equal to or greater than the set voltage, the second switching element Q2 is turned off to turn off the first switching element Q1, and when the output voltage V + of the rectifying and smoothing circuit 20 is less than the set voltage, the second switching element Q2 is turned on to turn on the first switching element Q1, in order to enable the first switching element Q1 and the second switching element Q2 to realize the respective on-off functions, specific expressions regarding the first switching element Q1 and the second switching element Q2 may include, but are not limited to, one or more of the following embodiments.
In the first embodiment, the first switching element Q1 is one of a field effect transistor and a triode. In this design, if the first switching element Q1 is designed as a field effect transistor, when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, the source electrode of the field effect transistor and the gate electrode of the field effect transistor are disconnected, and when the output voltage V + of the rectifying and filtering circuit 20 is less than the set voltage, the source electrode of the field effect transistor and the gate electrode of the field effect transistor are connected; if the first switching element Q1 is designed as a triode, when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, the collector of the triode is disconnected from the emitter of the triode, and when the output voltage V + of the rectifying and filtering circuit 20 is less than the set voltage, the collector of the triode is connected to the emitter of the triode.
In a second embodiment, the second switching element Q2 is one of a field effect transistor and a triode. In this design, if the second switching element Q2 is designed as a field effect transistor, when the output voltage V + of the rectifying and smoothing circuit 20 is greater than or equal to the set voltage, the source of the field effect transistor and the gate of the field effect transistor are disconnected, and when the output voltage V + of the rectifying and smoothing circuit 20 is less than the set voltage, the source of the field effect transistor and the gate of the field effect transistor are connected; if the second switching element Q2 is designed as a triode, when the output voltage V + of the rectifying and filtering circuit 20 is greater than or equal to the set voltage, the collector of the triode is disconnected from the emitter of the triode, and when the output voltage V + of the rectifying and filtering circuit 20 is less than the set voltage, the collector of the triode is connected to the emitter of the triode.
Specifically, the first switching element Q1 is an NPN type field effect transistor, and the second switching element Q2 is a PNP type field effect transistor. A gate of the NPN fet is used as the first controlled terminal of the first switching element Q1, a source of the NPN fet is used as the first input terminal of the first switching element Q1, a drain of the NPN fet is used as the first output terminal of the first switching element Q1, a gate of the PNP fet is used as the second controlled terminal of the second switching element Q2, a source of the PNP fet is used as the second input terminal of the second switching element Q2, and a drain of the PNP fet is used as the second output terminal of the second switching element Q2.
As shown in fig. 1, the operation principle of the current compensation circuit 10 is briefly described as follows:
when the output voltage V + of the rectifying and smoothing circuit 20 is larger, the larger output voltage V + is divided by the first voltage dividing resistor R27 and the second voltage dividing resistor R41, the voltage at the point a is UA, the gate voltage of the second switching element Q2 (PNP fet) is equal to the voltage at the point a, due to the presence of the bias resistor R3, the voltage at the point a acts on the cathode of the zener diode ZD11 through the bias resistor R3, the voltage acting on the cathode of the zener diode ZD11 is greater than the reverse breakdown voltage of the zener diode ZD11 at this time, the zener diode ZD11 reverse breakdown causes the source voltage of the second switching element Q2 to be pulled low, at this time, the second switching element Q2 is disconnected because the source voltage of the second switching element Q2 is less than the gate voltage of the second switching element Q2, the disconnection of the second switching element Q2 causes the first switching element Q1 (NPN fet) to be disconnected, the first switching element Q1 is disconnected so that the first switching element R39 is disconnected from the fixed resistance R44 at this time, the total current of the first switching element Q1 (NPN) is increased according to the formula, the total output current of the first switching element P1, and the total output power module is increased by the total output power module P1, the total output power module 2 R, wherein P is a fixed value, and I is reduced due to the increase of R, so that the current output from the current providing module to the pulse controller 30 is reduced, the low-current input of the pulse controller 30 under the condition of high voltage is realized, the model selection cost of the pulse controller 30 can be effectively reduced, and the purpose of reducing the whole model selection cost of the quasi-resonant power supply is achieved.
When the output voltage V + of the rectifying and filtering circuit 20 is small, the small output voltage V + is divided by the first voltage dividing resistor R27 and the second voltage dividing resistor R41, the voltage at the point a is UA '(UA' < UA), the gate voltage of the second switching element Q2 (PNP fet) is equal to the voltage at the point a, and due to the existence of the bias resistor R3, the voltage at the point a acts on the cathode of the zener diode ZD11 through the bias resistor R3, and at this time, the electricity acting on the cathode of the zener diode ZD11The voltage is smaller than the reverse breakdown voltage of the zener diode ZD11, so that the zener diode ZD11 cannot be reversely broken down, at this time, the source voltage of the second switching element Q2 is greater than the gate voltage of the second switching element Q2, so that the second switching element Q2 is turned on, so that the first switching element Q1 (NPN-type field effect transistor) is turned on, the first switching element Q1 is turned on, so that the first resistor R39 is connected in parallel with the resistance value fixed resistor R44, at this time, the total resistance of the current providing module after the first switching element Q1 is turned on is a resistance after the first resistor R39 is connected in parallel with the resistance value fixed resistor R44, and is reduced compared with the total resistance of the current providing module before the first switching element Q1 is turned on, the output power at the point B is P, and according to the formula P = I 2 R, wherein P is a constant value, and I is increased due to the decrease of R, so that the current output from the current providing module to the pulse controller 30 is increased, and the input of a proper large current to the pulse controller 30 under the condition of a small voltage is realized, thereby ensuring the normal operation of the pulse controller 30.
In a second aspect of the present application, a quasi-resonant power supply is provided, which includes a circuit board and the current compensation circuit 10, where the current compensation circuit 10 is fabricated on the circuit board. In this design, due to the design of the current compensation circuit 10, the quasi-resonant power supply having the current compensation circuit 10 can effectively reduce the overall model selection cost of the quasi-resonant power supply. In addition, the quasi-resonant power supply also has the effects of effectively improving the overall efficiency of the full-voltage input power supply and reducing the temperature rise and the electromagnetic interference.
A third aspect of the present application provides a charging device, which includes a housing (not shown in the figure) and the quasi-resonant power supply mentioned above, the housing having an installation space, and the quasi-resonant power supply being provided in the installation space. Wherein the charging device may include, but is not limited to, a charger. In the design, the charging device with the quasi-resonant power supply can effectively reduce the overall model selection cost of the charging device.
The same or similar reference numerals in the drawings of the present embodiment correspond to the same or similar components; in the description of the present application, it is to be understood that if there is an orientation or positional relationship indicated by the terms "upper", "lower", "left", "right", etc. based on the orientation or positional relationship shown in the drawings, it is only for convenience of description and simplification of description, but it is not intended to indicate or imply that the referred device or element must have a specific orientation, be constructed in a specific orientation, and be operated, and therefore, the terms describing the positional relationship in the drawings are only for illustrative purposes and are not to be construed as limitations of the present patent, and specific meanings of the above terms may be understood by those skilled in the art according to specific situations.
The above description is only exemplary of the present application and should not be taken as limiting the present application, as any modification, equivalent replacement, or improvement made within the spirit and principle of the present application should be included in the protection scope of the present application.
Claims (10)
1. A current compensation circuit of a quasi-resonant power supply, wherein the quasi-resonant power supply comprises a rectifying filter circuit and a pulse controller which are connected with each other, the current compensation circuit comprises:
the control module is connected with the rectifying and filtering circuit and is connected to the output voltage of the rectifying and filtering circuit;
the current providing module comprises a resistance value adjustable circuit and a resistance value fixed circuit which are mutually connected in parallel, one parallel end of the resistance value adjustable circuit and the resistance value fixed circuit is used for being connected to the pulse controller, the other parallel end of the resistance value fixed circuit and the resistance value adjustable circuit is grounded, and the resistance value adjustable circuit is also connected with the control module;
the control module is used for adjusting the resistance of the resistance value adjustable circuit when the output voltage of the rectifying and filtering circuit is larger than or equal to a set voltage, so as to reduce the current output to the pulse controller by the current providing module.
2. The current compensation circuit of claim 1,
the resistance value fixing circuit comprises a resistance value fixing resistor, one end of the resistance value fixing resistor is used for being connected to the pulse controller, and the other end of the resistance value fixing resistor is grounded;
the resistance value adjustable circuit comprises a first switch element and a first resistor, wherein the first switch element is provided with a first input end, a first output end and a first controlled end, the first input end is grounded, the first output end is used for being connected to the pulse controller through the first resistor, and the first controlled end is connected with the control module;
when the output voltage of the rectifying and filtering circuit is greater than or equal to a set voltage, the control module controls the first switching element to be switched off so as to increase the total resistance value of the current providing module.
3. The current compensation circuit of claim 2, wherein the control module comprises:
the second switching element is provided with a second input end, a second output end and a second controlled end, the second controlled end is used for being connected with the output voltage of the rectifying and filtering circuit, and the second output end is connected with the first controlled end;
the cathode of the voltage stabilizing diode is connected with the second input end, and the anode of the voltage stabilizing diode is grounded;
and one end of the bias resistor is connected with the second controlled end, and the other end of the bias resistor is connected with the second input end.
4. The current compensation circuit of claim 3, wherein the control module further comprises:
the voltage division circuit, voltage division circuit's one end is used for the access rectifier filter circuit output voltage, voltage division circuit's other end ground connection, voltage division circuit includes two at least series connection's divider resistance, just voltage division circuit is arbitrary two have the partial pressure node between the divider resistance, the partial pressure node with the second controlled terminal is connected.
5. The current compensation circuit of claim 3,
the first switch element is one of a field effect transistor and a triode; and/or
The second switch element is one of a field effect transistor and a triode.
6. The current compensation circuit of claim 5,
the first switching element includes an NPN-type field effect transistor, and the second switching element includes a PNP-type field effect transistor.
7. The current compensation circuit of claim 3, wherein the control module further comprises:
and one end of the second resistor is grounded, and the other end of the second resistor is connected with the second output end.
8. Current compensation circuit according to one of the claims 1 to 7,
the number of the resistance value adjustable circuits is multiple, and each resistance value adjustable circuit is connected with the resistance value fixed circuit in parallel; the control module is used for adjusting the resistance of at least one resistance value adjustable circuit when the output voltage of the rectifying and filtering circuit is larger than or equal to a set voltage, so as to reduce the current output to the pulse controller by the current providing module.
9. A quasi-resonant power supply, comprising:
a circuit board; and
a current compensation circuit according to any one of claims 1 to 8 which is fabricated on the circuit board.
10. A charging device, comprising:
a housing having an installation space; and
the quasi-resonant power supply of claim 9, disposed in the mounting space.
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202222448834.1U CN218549563U (en) | 2022-09-15 | 2022-09-15 | Current compensation circuit, quasi-resonant power supply and charging device |
| PCT/CN2023/116952 WO2024055869A1 (en) | 2022-09-15 | 2023-09-05 | Current compensation circuit, quasi-resonant power supply, and charging device |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202222448834.1U CN218549563U (en) | 2022-09-15 | 2022-09-15 | Current compensation circuit, quasi-resonant power supply and charging device |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN218549563U true CN218549563U (en) | 2023-02-28 |
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Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202222448834.1U Active CN218549563U (en) | 2022-09-15 | 2022-09-15 | Current compensation circuit, quasi-resonant power supply and charging device |
Country Status (2)
| Country | Link |
|---|---|
| CN (1) | CN218549563U (en) |
| WO (1) | WO2024055869A1 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2024055869A1 (en) * | 2022-09-15 | 2024-03-21 | 安克创新科技股份有限公司 | Current compensation circuit, quasi-resonant power supply, and charging device |
Family Cites Families (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US8373403B1 (en) * | 2008-08-08 | 2013-02-12 | Power-One, Inc. | Circuit for controlling synchronous rectifiers during start-up into pre-biased output voltage |
| JP5822670B2 (en) * | 2011-11-17 | 2015-11-24 | 日立アプライアンス株式会社 | LED lighting device |
| CN214045083U (en) * | 2020-11-06 | 2021-08-24 | Tcl通力电子（惠州）有限公司 | Battery charging control circuit and device |
| CN218549563U (en) * | 2022-09-15 | 2023-02-28 | 安克创新科技股份有限公司 | Current compensation circuit, quasi-resonant power supply and charging device |
-
2022
- 2022-09-15 CN CN202222448834.1U patent/CN218549563U/en active Active
-
2023
- 2023-09-05 WO PCT/CN2023/116952 patent/WO2024055869A1/en unknown
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2024055869A1 (en) * | 2022-09-15 | 2024-03-21 | 安克创新科技股份有限公司 | Current compensation circuit, quasi-resonant power supply, and charging device |
Also Published As
| Publication number | Publication date |
|---|---|
| WO2024055869A1 (en) | 2024-03-21 |
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