CN212969455U - Parallel-connection staggered full-bridge LLC circuit - Google Patents
Parallel-connection staggered full-bridge LLC circuit Download PDFInfo
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- CN212969455U CN212969455U CN202022227715.4U CN202022227715U CN212969455U CN 212969455 U CN212969455 U CN 212969455U CN 202022227715 U CN202022227715 U CN 202022227715U CN 212969455 U CN212969455 U CN 212969455U
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Abstract
The utility model provides a parallel connection staggered full-bridge LLC circuit, in each phase unit, the positive and negative poles at the direct current side of an inversion unit are used as the positive and negative poles of the input end of the phase unit and are connected to the two ends of a corresponding input capacitor module; the input end of the LLC transformer is connected with the alternating current side of the inversion unit; the dotted terminal of the output end of the LLC transformer is connected with the alternating current side of the rectification unit; the different name ends of the output ends of the LLC transformers in each phase unit are connected; the positive and negative electrodes on the direct current side of the rectification unit are used as the positive and negative electrodes of the output end of the phase unit and are connected to the two ends of the output capacitor module in parallel; the input ends of all LLC transformers are not directly connected, the swing amplitude of the LLC transformers is input voltage Vbus, and therefore under the condition that the same power is output, the input end current of the LLC transformers and the current of the parallel units can be reduced to the maximum extent, the loss of the parallel connection staggered full-bridge LLC circuit is reduced, meanwhile, the requirements on MOSFET power devices are reduced, and the applicability is high.
Description
Technical Field
The utility model belongs to the technical field of power electronics, more specifically the theory that says so especially relates to a parallelly connected crisscross full-bridge LLC circuit.
Background
At present, the primary side of a transformer in a high-power interleaved LLC circuit mostly adopts a star connection midpoint mode, and the primary side winding of each transformer is connected with the negative pole connection point of the output end of the corresponding resonant circuit; the midpoints of the star-shaped connections have two connection modes, one is a multiphase bridge type mode formed by suspending the midpoints and is shown in figure 1, the other is a structure formed by connecting the midpoints to the negative pole of a power supply or a plurality of half bridges formed by connecting the midpoints to the negative pole of the power supply or the negative pole of the power supply, and the two connection modes can form a 2-phase, 3-phase or multiphase structure.
In high-power application occasions, the requirements on the loss, the thermal design and the efficiency of a machine are higher; however, the swing utilization rate of the primary side voltage of the transformer with the two structures is not high, one highest swing is 2/3Vbus, the other highest swing is Vbus/2, and Vbus is input voltage; both bring large loss, therefore, both cannot meet the requirement of high power application.
SUMMERY OF THE UTILITY MODEL
In view of this, the present invention provides a parallel-connection staggered full-bridge LLC circuit for reducing the loss of the parallel-connection staggered full-bridge LLC circuit in any application scenario.
The utility model discloses a parallelly connected crisscross full-bridge LLC circuit, include: the device comprises an output capacitor module, at least one input capacitor module and at least two phase units; the phase unit includes: the device comprises an inversion unit, an LLC transformer and a rectification unit; wherein:
the positive electrode and the negative electrode of the input end of each phase unit are respectively connected to the two ends of the corresponding input capacitor module; the positive electrode and the negative electrode of the output end of each phase unit are connected to the two ends of the output capacitor module in parallel;
in the phase unit, the positive electrode and the negative electrode on the direct current side of the inverter unit are used as the positive electrode and the negative electrode of the input end of the phase unit; the input end of the LLC transformer is connected with the alternating current side of the inversion unit; the homonymous end of the output end of the LLC transformer is connected with the alternating current side of the rectification unit; the different name end of the output end of the LLC transformer is connected with the different name end of the output end of the LLC transformer in other phase units; and the positive and negative electrodes on the direct current side of the rectification unit are used as the positive and negative electrodes of the output end of the phase unit.
Optionally, when the number of the input capacitor modules is 1, the input ends of the phase units are respectively connected to two ends of the input capacitor module in parallel.
Optionally, the number of the phase units is odd or even.
Optionally, when the number of the input capacitor modules is N, the connection mode of the N input capacitor modules is one of series connection, parallel connection and series-parallel connection, and N is a positive integer greater than 1:
the input ends of the ith part of the phase units are respectively connected to the two ends of the ith input capacitor module; i is more than or equal to 1 and less than or equal to N.
Optionally, the number of each part of the phase units is M, and M is a positive integer; the total number of all the phase units is M × N.
Optionally, N ═ 2.
Optionally, M is an odd number.
Optionally, when the number of the phase units connected to the same input capacitor module is 3, the driving signals of the phase units connected to the same input capacitor module are respectively staggered by 120 degrees.
Optionally, the inverting unit is of a full-bridge topology structure;
the rectifying unit is of a multiphase bridge type topological structure.
Optionally, the LLC transformer includes: a resonant inductor, a resonant capacitor and a transformer;
one end of the resonance inductor is used as the homonymous end of the input end of the LLC transformer;
the other end of the resonance inductor is connected with one end of the resonance capacitor;
the other end of the resonance capacitor is connected with the dotted end of the primary winding of the transformer;
the synonym end of the primary winding is used as the synonym end of the input end of the LLC transformer;
and the homonymous end of the secondary winding of the transformer is used as the homonymous end of the output end of the LLC transformer, and the synonym end of the secondary winding of the transformer is used as the synonym end of the output end of the LLC transformer.
According to the above technical solution, in the parallel staggered full-bridge LLC circuit provided in the present invention, the positive and negative electrodes of the input end of each phase unit are respectively connected to the two ends of the corresponding input capacitor module; the positive and negative electrodes of the output end of each phase unit are connected in parallel to the two ends of the output capacitor module and are connected with the output capacitor module; in the phase unit, the positive and negative electrodes on the direct current side of the inversion unit are used as the positive and negative electrodes of the input end of the phase unit; the input end of the LLC transformer is connected with the alternating current side of the inversion unit; the dotted terminal of the output end of the LLC transformer is connected with the alternating current side of the rectification unit; the different name end of the output end of the LLC transformer is connected with the different name end of the output end of the LLC transformer in other phase units; the positive and negative poles at the direct current side of the rectification unit are used as the positive and negative poles at the output end of the phase unit; therefore, the input ends of all the LLC transformers are not directly connected, the swing amplitude of the LLC transformers is the input voltage Vbus, and further under the condition of outputting the same power, the input end current of the LLC transformers and the current of the inversion units are reduced to the maximum extent, the loss of the parallel connection staggered full-bridge LLC circuit is reduced, meanwhile, the requirements on MOSFET power devices are reduced, and the applicability is strong.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings needed to be used in the description of the embodiments or the prior art will be briefly described below, and it is obvious that the drawings in the following description are some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to these drawings without creative efforts.
FIG. 1 is a schematic diagram of a high power interleaved LLC circuit provided by the prior art;
FIG. 2 is a schematic diagram of another prior art high power interleaved LLC circuit;
fig. 3 is a schematic diagram of a parallel interleaved full-bridge LLC circuit according to an embodiment of the present invention;
FIG. 4 is a diagram of a primary voltage waveform of a transformer of a high power three-phase interleaved LLC circuit provided by the prior art;
FIG. 5 is a graph of a primary voltage waveform of a transformer of another prior art high power interleaved LLC circuit;
fig. 6 is a diagram of a primary voltage waveform of a transformer according to an embodiment of the present invention;
fig. 7 is a schematic diagram of another parallel interleaved full-bridge LLC circuit according to an embodiment of the present invention;
fig. 8 is a schematic diagram of another parallel interleaved full-bridge LLC circuit according to an embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the embodiments of the present invention clearer, the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings in the embodiments of the present invention, and it is obvious that the described embodiments are some, but not all, embodiments of the present invention. Based on the embodiments in the present invention, all other embodiments obtained by a person skilled in the art without creative work belong to the protection scope of the present invention.
In this application, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
The embodiment of the utility model provides a parallelly connected crisscross full-bridge LLC circuit for solve in the prior art because the swing amplitude utilization ratio of the transformer primary side voltage of two kinds of structures is not high, one is 2/3Vbus, another is Vbus/2; both bring larger loss, therefore, both can not meet the requirement of high power application occasions.
The parallel interleaved full bridge LLC circuit, see fig. 3, includes: an output capacitance module C5, at least one input capacitance module (e.g., C1 shown in fig. 3 and 8 and C1 and C4 shown in fig. 7), and a plurality of phase cells; the phase unit includes: an inverting unit (as shown in fig. 3, taking an inverting unit as an example, which includes switching tubes Q1, Q2, Q3 and Q4), an LLC transformer (as shown in fig. 3 as L1+ C2+ T1, L2+ C3+ T2 or L3+ C4+ T3), and a rectifying unit (as shown in fig. 3 as D1+ D2, D3+ D4 or D5+ D6); wherein:
the positive electrode and the negative electrode of the input end of each phase unit are respectively connected to the two ends of the corresponding input capacitor module; specifically, the positive electrode of the input end of each phase unit is respectively connected with the positive electrode BUS + of the corresponding input capacitor module; the negative poles of the input ends of the phase units are respectively connected with the negative poles BUS-of the corresponding input end capacitor modules. It should be noted that, when the number of the input capacitance modules is greater than 1, if the number of the phase units is equal to the number of the input capacitance modules, each phase unit may be connected to each input capacitance module in a one-to-one correspondence manner; if the number of the phase units is not equal to that of the input capacitor modules, each phase unit is connected to two ends of the corresponding input capacitor module; when the number of the input capacitor modules is 1, the input ends of the phase units are connected in parallel to the two ends of the input capacitor module. The number of the input capacitor modules and the specific connection relationship thereof are not specifically limited herein, and are all within the protection scope of the present application.
The positive and negative electrodes of the output end of each phase unit are connected to the two ends of the output capacitor module C5 in parallel; specifically, the positive electrode of the output end of each phase unit is connected with the positive electrode Vout + of the output capacitor module C5; the negative poles of the output ends of the phase units are respectively connected with the negative pole Vout-of the output capacitor module C5.
In the phase unit, the positive and negative electrodes on the direct current side of the inversion unit are used as the positive and negative electrodes of the input end of the phase unit; specifically, the direct current side positive electrode of the inversion unit is used as the input end positive electrode of the phase unit and is connected with the positive electrode BUS + of the corresponding input capacitor module, and the direct current side negative electrode of the inversion unit is used as the input end negative electrode of the phase unit and is connected with the negative electrode BUS + of the corresponding input capacitor module; the input end of the LLC transformer is connected with the alternating current side of the inversion unit; specifically, the homonymous end of the input end of the LLC transformer is connected with one end of the alternating current side of the inversion unit, and the synonym end of the input end of the LLC transformer is connected with the other end of the alternating current side of the inversion unit; the dotted terminal of the output end of the LLC transformer is connected with the alternating current side of the rectification unit; the different name end of the output end of the LLC transformer is connected with the different name end of the output end of the LLC transformer in other phase units; the positive and negative poles at the direct current side of the rectification unit are used as the positive and negative poles at the output end of the phase unit; specifically, the positive electrode of the direct current side of the rectifying unit is used as the positive electrode of the output end of the phase unit and is connected with the positive electrode Vout + of the output capacitor module C5, and the negative electrode of the direct current side of the rectifying unit is used as the negative electrode of the output end of the phase unit and is connected with the negative electrode Vout-of the output capacitor module C5.
It should be noted that, because the input ends of the LLC transformers are not directly connected, but are connected to the two ends of the corresponding input capacitor modules through the inverter units, the number of the input capacitor modules may be 1 or multiple, and there may be multiple connection combination modes, which are not described herein again one by one, and are all within the protection scope of the present application. The input capacitance module includes at least one input capacitance. The output capacitance module C5 includes at least one output capacitance. The number of capacitors in the input capacitor module and the output capacitor module C5 is not described herein again, and is within the scope of the present application.
In practical application, the inversion unit is of a full-bridge topology structure; specifically, as shown in fig. 3 or fig. 8, a structure composed of switching tubes Q1, Q2, Q3, and Q4 is taken as an example for explanation: one end of the switching tube Q1 is connected with one end of the switching tube Q2, and the connection point is used as the alternating current side end of the inversion unit; the other end of the switch tube Q1 is connected with one end of the switch tube Q3, and the connection point is used as the positive electrode of the direct current side of the inversion unit; the other end of the switch tube Q3 is connected with one end of the switch tube Q4, and the connection point is used as the other end of the alternating current side of the inversion unit; the other end of the switching tube Q4 is connected with the other end of the switching tube Q2, and the connection point is used as a DC side negative electrode of the inverter unit. As shown in fig. 3, the inverter unit formed by the switching tubes Q5, Q6, Q7, and Q8 and the inverter unit formed by the switching tubes Q9, Q10, Q11, and Q12 are the same as the inverter unit formed by the switching tubes Q1, Q2, Q3, and Q4, and therefore, the description thereof is omitted, and the present invention is within the protection scope of the present application.
The rectifying unit is of a multiphase bridge type topological structure; specifically, as shown in fig. 3 or fig. 8, a structure formed by diodes D1 and D2 is taken as an example for explanation: the anode of the diode D1 is connected with the cathode of the diode D2, and the connection point is used as the alternating current side of the rectifying unit; the cathode of the diode D1 is used as the positive electrode of the direct current side of the rectifying unit and is connected with the positive electrode Vout + of the output capacitor module C5; the anode of the diode D2 is used as the cathode of the DC side of the rectifying unit and is connected with the cathode Vout-of the output capacitor module C5. As shown in fig. 3, the rectifying units formed by the diodes D3 and D4 and the rectifying units formed by the diodes D5 and D6 are the same as the rectifying units formed by the diodes D1 and D2, and are not described in detail here and are within the scope of the present application.
Fig. 3 shows by way of example a three-phase parallel staggered full-bridge LLC circuit, fig. 8 shows by way of example a multiphase parallel staggered full-bridge LLC circuit, and parallel staggered full-bridge LLC circuits with other specific phases are not repeated here one by one, and are all within the scope of the present application.
In practical application, when the number of the phase units connected to the same input capacitor module is 3, that is, the structure formed by the input capacitor module and each phase unit connected to the input capacitor module is a 3-phase LLC circuit, the driving signals of the phase units connected to the same input capacitor module are respectively staggered by 120 degrees.
It should be noted that, the inherent characteristic of the LLC structure is that the current ripple on the output capacitor module C5 will be relatively large, and even number interleaving does not perform peak-valley complementation well on the output current ripple, so that the valuable odd-phase LLC structure, such as the most typical 3-phase LLC structure, operates according to a phase difference of 120 degrees to obtain similar 3-phase high-frequency alternating current, and then rectifies to obtain 6 half-wave currents interleaved by 60 degrees. Since the bus current on the rectifying unit is the sum of 6 half waves staggered by 60 degrees, it operates with the advantage of effectively reducing the current ripple on the output capacitor.
The LLC circuit is a gating network when in operation, and the resonant frequencies of the LLC circuit are respectively as follows:
wherein Lm is a primary side excitation inductance of a transformer in the LLC circuit; lr is resonance inductance in the LLC circuit; cr is a resonance capacitor in the LLC circuit. During normal operation, the switching frequency range is designed to be near fr1, so the fundamental frequency of the primary voltage of the transformer is fr 1; while the high frequency components are filtered out because of the gating network. The primary voltage waveforms of the transformers in the two structures of fig. 1 and fig. 2 are subjected to fourier transform, and the amplitudes of the obtained fundamental wave components are equal. The primary voltage waveform of the transformer of the structure of fig. 1 is shown in fig. 4, and the fundamental component thereof is 2 Vin/pi; the primary voltage waveform of the transformer of the structure of fig. 2 is shown in fig. 5, and the fundamental component thereof is 2 Vin/pi; the ordinate shown in fig. 4 and 5 is the coefficient of Vin. Thus, in both configurations, the primary side of the transformer is designed in a half-bridge fashion.
It should be noted that, with the structure shown in fig. 1 and fig. 2, because the swing amplitude is low, if the transformer outputs the same power, the primary side of the transformer will need higher current; the LLC resonant converters are all designed in a ZVS working area, so that the loss of the primary side of the transformer is basically conduction loss; in addition, the LLC resonant converter basically selects a MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor) as a switching device, and when the device such as the MOSFET is turned on, its loss calculation formula is Q ^ I ^2 × Rds, and since the primary side current I and the loss Q are in a square relationship, reducing the primary side current I can very effectively reduce the loss value Q, so if the primary side current of the transformer can be reduced, it will bring a relatively easy thermal design to the product, and it will be easier to improve the product efficiency.
In this embodiment, the input end of each LLC transformer is connected to the corresponding input capacitor module through the corresponding inverter unit, i.e., the primary side of each LLC transformer is designed as multiple independent full bridges; particularly, when each input capacitor module is connected with at least two phase units, the primary side of each LLC transformer is designed into a plurality of independent parallel full bridges, the voltage waveform of the primary side of the transformer is shown in figure 6, and the amplitude of the fundamental voltage component of the structure is 2 times that of the structure shown in figures 1 and 2; therefore, if the LLC transformer transfers the same energy to the rectifying unit, the current of the structure shown in fig. 3 only needs half of the structure shown in fig. 1 and 2, and the input end current of the LLC transformer and the current of the inverting unit can be reduced to the maximum extent; the benefits of loss Q ═ I ^2 ^ R and current 1/2I are that the loss becomes 1/4; the loss of the primary side device is reduced, and the efficiency is improved; it is also beneficial to the latter thermal structure design, especially for high power output applications. The loss of the parallel connection staggered full-bridge LLC circuit is reduced, the requirement on an MOSFET power device is reduced, and the applicability is strong. In addition, the phase control is staggered in each phase unit, for example, three phases are staggered by 120 degrees, so that the current ripple of the output capacitor module C5 is small, and multi-stage output or input multi-bus is easy to expand.
Optionally, the LLC transformer includes: a resonant inductor (e.g., L1, L2, or L3 shown in fig. 3), a resonant capacitor (e.g., C2, C3, or C4 shown in fig. 3), and a transformer (e.g., T1, T2, or T3 shown in fig. 3).
One end of the resonance inductor is used as the homonymous end of the input end of the LLC transformer and is connected with the positive electrode of the output end of the inversion unit; the other end of the resonance inductor is connected with one end of the resonance capacitor; the other end of the resonant capacitor is connected with the dotted terminal of the primary winding of the transformer; the synonym end of the primary winding is used as the synonym end of the input end of the LLC transformer; the homonymous end of the secondary winding of the transformer is used as the homonymous end of the output end of the LLC transformer, and the synonym end of the secondary winding of the transformer is used as the synonym end of the output end of the LLC transformer.
Specifically, as shown in fig. 3, taking the LLC transformer in the phase 1 unit as an example for explanation, one end of the resonant inductor L1 is connected to the connection point between the switching tube Q3 and the switching tube Q4 as the dotted terminal of the input end of the LLC transformer; the other end of the resonant inductor L1 is connected with one end of a resonant capacitor C2; the other end of the resonant capacitor C2 is connected with the dotted terminal of the primary winding of the transformer T1; the synonym terminal of the primary winding of the transformer T1 is used as the synonym terminal of the input terminal of the LLC transformer and is connected with the connection point between the switching tube Q1 and the switching tube Q2. Specific connection relations of LLC transformers in other phase units are not described herein any more, and are all within the scope of protection of the present application.
The secondary windings of the transformers are connected with the rectifying units in a star-shaped mode, meanwhile, the primary windings of the transformers and the inversion units form independent full bridges, when three independent full bridges are formed between the primary windings of the transformers and the inversion units, staggered driving is carried out according to 120-degree phase difference, three-phase currents with 120-degree phase difference are obtained, and therefore current ripples on the output capacitor module C5 are smaller; according to the star connection method of the three-phase windings, one phase of current is equal to the sum of the currents of the other two phases, if any phase of current flows through zero, the currents of the other two phases are necessarily equal, so that the secondary winding of the transformer can realize natural current sharing, and the primary winding of the transformer can also realize natural current sharing according to the transformer principle.
In this embodiment, the primary side of each LLC circuit is an independent full-bridge parallel structure, and the primary windings of each transformer are not directly connected; the secondary windings of the transformers adopt star connection, midpoint suspension and full-bridge rectification modes, so that the phase units are connected in parallel in a staggered mode, the current on each phase unit is small, and the efficiency is high; the secondary windings are connected in a star shape, and automatic current equalization can be realized.
In practical application, as can be seen from the above description, the number of the input capacitor modules is at least one; however, when the number of input capacitance modules is different, the connection relationship of each phase unit is different, and here, the connection relationship of each phase unit when the number of input capacitance modules is different will be described:
(1) when the number of the input capacitor modules is 1, the input ends of the phase units are respectively connected to two ends of the input capacitor modules in parallel.
Specifically, the positive electrode of the input end of each phase unit is connected with the positive electrode of the input capacitor module; and the negative electrode of the input end of each phase unit is connected with the negative electrode of the input capacitor module.
In practical application, the number of the phase units can be an odd number or an even number; the specific value is not specifically limited, and may be determined according to actual conditions, and is within the scope of the present application.
(2) And when the number of the input capacitance modules is N, N is a positive integer greater than 1. The N input capacitance modules are connected in one of series connection, parallel connection and series-parallel connection.
The input ends of the phase units of the 1 st part are respectively connected to the two ends of the 1 st input capacitor module in parallel; the input ends of the ith partial phase units are respectively connected to the two ends of the ith input capacitor module in parallel; 1< i < N; and the input ends of the Nth partial phase units are respectively connected to two ends of the Nth input capacitor module in parallel.
It should be noted that the number of the phase units connected to each input capacitance module may be equal, that is, the number of each partial phase unit is M, where M is a positive integer; the total number of all the phase units is M x N; the number of phase units connected to each input capacitance module may also be unequal. However, in order to ensure the balance of the multi-input capacitor module, the number of phase units connected to each input capacitor module should be equal.
In practical applications, the total number of all phase units may be even or odd. Specifically, when N is 2, that is, in the double-BUS configuration, the total number of all the phase units is an even number, and the number of the phase units connected to each input capacitance module is equal. For example, if it is required to design 2 interleaved LLC circuits, 1 LLC circuit with such a structure is designed for each of the input capacitor module C1 and the input capacitor module C4, and the secondary windings of 2 transformers adopt a similar star connection manner to obtain higher output power. If 4 interleaved LLC circuits need to be designed, 2 LLC circuits with the structure are respectively designed for the input capacitance module C1 and the input capacitance module C4, and 4 transformer outputs adopt a similar star connection mode to obtain higher output power. In the same way, the 6 th phase and the 8 th phase can be designed by the structure shown in the figure 7. In case of a dual BUS design, it is preferable that each input capacitor module is designed with an odd number of LLC, i.e. M is an odd number, most typically 6 interleaved, and each of the input capacitor module C1 and the input capacitor module C4 is designed as a 3-phase LLC circuit.
Of course, if there are only odd phases, it is only possible to arrange on the structure of odd number of input capacitor modules, such as one input capacitor module, as shown in fig. 5, and the design of odd number of phases, such as single phase, 3 phases, 5 phases and 7 phases, is very significant for reducing the current ripple of the output capacitor module C5. The inherent characteristic of the LLC circuit is that the current ripple on the output capacitor module C5 is relatively large, and the odd-number interleaving pair output current ripple can be well peak-to-valley complemented, and therefore, is a relatively valuable structure, most typically a 3-phase LLC circuit.
In the embodiment, a plurality of phase units are connected in parallel in a staggered mode, so that the current of a single LLC transformer is small, and the efficiency is high; meanwhile, the multi-level parallel output scheme of the input multi-bus is easy to expand, the current of a single LLC transformer is further reduced, and the working efficiency is improved.
Features described in the embodiments in the present specification may be replaced with or combined with each other, and the same and similar portions among the embodiments may be referred to each other, and each embodiment is described with emphasis on differences from other embodiments. In particular, the system or system embodiments are substantially similar to the method embodiments and therefore are described in a relatively simple manner, and reference may be made to some of the descriptions of the method embodiments for related points. The above-described system and system embodiments are only illustrative, wherein the units described as separate parts may or may not be physically separate, and the parts displayed as units may or may not be physical units, may be located in one place, or may be distributed on a plurality of network units. Some or all of the modules may be selected according to actual needs to achieve the purpose of the solution of the present embodiment. One of ordinary skill in the art can understand and implement it without inventive effort.
Those of skill would further appreciate that the various illustrative elements and algorithm steps described in connection with the embodiments disclosed herein may be implemented as electronic hardware, computer software, or combinations of both, and that the various illustrative components and steps have been described above generally in terms of their functionality in order to clearly illustrate this interchangeability of hardware and software. Whether such functionality is implemented as hardware or software depends upon the particular application and design constraints imposed on the implementation. Skilled artisans may implement the described functionality in varying ways for each particular application, but such implementation decisions should not be interpreted as causing a departure from the scope of the present invention.
The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.
Claims (10)
1. A parallel interleaved full bridge LLC circuit, comprising: the device comprises an output capacitor module, at least one input capacitor module and at least two phase units; the phase unit includes: the device comprises an inversion unit, an LLC transformer and a rectification unit; wherein:
the positive electrode and the negative electrode of the input end of each phase unit are respectively connected to the two ends of the corresponding input capacitor module; the positive electrode and the negative electrode of the output end of each phase unit are connected to the two ends of the output capacitor module in parallel;
in the phase unit, the positive electrode and the negative electrode on the direct current side of the inverter unit are used as the positive electrode and the negative electrode of the input end of the phase unit; the input end of the LLC transformer is connected with the alternating current side of the inversion unit; the homonymous end of the output end of the LLC transformer is connected with the alternating current side of the rectification unit; the different name end of the output end of the LLC transformer is connected with the different name end of the output end of the LLC transformer in other phase units; and the positive and negative electrodes on the direct current side of the rectification unit are used as the positive and negative electrodes of the output end of the phase unit.
2. The LLC circuit of claim 1, wherein when the number of the input capacitor modules is 1, the input terminals of the phase units are respectively connected in parallel to two ends of the input capacitor modules.
3. The parallel interleaved full bridge LLC circuit according to claim 2, wherein said number of phase units is odd or even.
4. The LLC circuit of claim 1, wherein when the number of input capacitor modules is N, the N input capacitor modules are connected in one of series connection, parallel connection and series-parallel connection, N is a positive integer greater than 1:
the input ends of the ith part of the phase units are respectively connected to the two ends of the ith input capacitor module; i is more than or equal to 1 and less than or equal to N.
5. The LLC circuit of claim 4, wherein the number of phase units in each portion is M, M being a positive integer; the total number of all the phase units is M × N.
6. The parallel-interleaved full-bridge LLC circuit according to claim 5, wherein N-2.
7. The LLC circuit of claim 5, wherein M is an odd number.
8. The LLC circuit according to any of claims 1-6, wherein when the number of phase units connected to a same input capacitor module is 3, the driving signals of the phase units connected to a same input capacitor module are respectively interleaved by 120 degrees.
9. The parallel-interleaved full-bridge LLC circuit according to any of claims 1-6, wherein said inverting unit is of full-bridge topology;
the rectifying unit is of a multiphase bridge type topological structure.
10. The parallel interleaved full bridge LLC circuit according to any of claims 1-6, wherein said LLC transformer comprises: a resonant inductor, a resonant capacitor and a transformer;
one end of the resonance inductor is used as the homonymous end of the input end of the LLC transformer;
the other end of the resonance inductor is connected with one end of the resonance capacitor;
the other end of the resonance capacitor is connected with the dotted end of the primary winding of the transformer;
the synonym end of the primary winding is used as the synonym end of the input end of the LLC transformer;
and the homonymous end of the secondary winding of the transformer is used as the homonymous end of the output end of the LLC transformer, and the synonym end of the secondary winding of the transformer is used as the synonym end of the output end of the LLC transformer.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202022227715.4U CN212969455U (en) | 2020-10-09 | 2020-10-09 | Parallel-connection staggered full-bridge LLC circuit |
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Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112953228A (en) * | 2021-02-10 | 2021-06-11 | 深圳市优优绿能电气有限公司 | Interleaved LLC converter |
| CN113179008A (en) * | 2021-05-12 | 2021-07-27 | 阳光电源股份有限公司 | Multiphase LLC resonance DC/DC circuit |
| WO2023272809A1 (en) * | 2021-06-28 | 2023-01-05 | 天津铁路信号有限责任公司 | Acac alternating-current power supply module for railway signal power supply panel |
| CN115720047A (en) * | 2022-12-06 | 2023-02-28 | 深圳市优优绿能股份有限公司 | Power expansion device for three-phase LLC circuit |
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2020
- 2020-10-09 CN CN202022227715.4U patent/CN212969455U/en active Active
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112953228A (en) * | 2021-02-10 | 2021-06-11 | 深圳市优优绿能电气有限公司 | Interleaved LLC converter |
| CN113179008A (en) * | 2021-05-12 | 2021-07-27 | 阳光电源股份有限公司 | Multiphase LLC resonance DC/DC circuit |
| CN113179008B (en) * | 2021-05-12 | 2024-02-09 | 阳光电源股份有限公司 | Multiphase LLC resonance DC/DC circuit |
| WO2023272809A1 (en) * | 2021-06-28 | 2023-01-05 | 天津铁路信号有限责任公司 | Acac alternating-current power supply module for railway signal power supply panel |
| CN115720047A (en) * | 2022-12-06 | 2023-02-28 | 深圳市优优绿能股份有限公司 | Power expansion device for three-phase LLC circuit |
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