CN211830528U

CN211830528U - Multiphase disc type hybrid excitation flux switching motor

Info

Publication number: CN211830528U
Application number: CN201921874529.0U
Authority: CN
Inventors: 曹瑞武; 张学; 王凯; 王支业; 王业彬; 王秋岭
Original assignee: Xuzhou Dayuan Electromotor Co ltd; Nanjing University of Aeronautics and Astronautics
Current assignee: Xuzhou Dayuan Electromotor Co ltd; Nanjing University of Aeronautics and Astronautics
Priority date: 2019-11-01
Filing date: 2019-11-01
Publication date: 2020-10-30
Anticipated expiration: 2029-11-01

Abstract

The utility model discloses a disk type hybrid excitation magnetic flux switching motor comprises stator core, rotor core, armature winding, excitation winding and permanent magnet. The stator and the rotor are coaxially mounted. And 4 m × k × n stator magnetic conduction teeth are arranged on a single stator iron core, and m × q permanent magnets are arranged on the stator in total and are uniformly embedded outside the excitation slot. The rotor iron core is provided with (2 m k +/-1) n magnetic conduction teeth which are uniformly distributed along the circumference; m is the number of phases of the motor, n is the number of motor units, k is the number of concentrated armature windings in series connection with any one phase of armature winding in each motor unit, and q is a positive integer (ensuring that 4 x k x n/q is a positive integer and is less than 2 x k x n). The motor provides excitation magnetic flux through the permanent magnet and the excitation winding, not only has strong magnetic field regulation capacity, but also has smaller axial size, and is suitable for being applied to occasions requiring thin installation with strict requirements, such as electric automobiles and the like, and requiring wide speed regulation range.

Description

Multiphase disc type hybrid excitation flux switching motor

Technical Field

The utility model relates to a disk type hybrid excitation magnetic flux switching motor belongs to the motor and makes technical field.

Background

With the development of new energy technology, the motor is widely researched and applied as a core component in the fields of rail transit, new energy automobiles and the like. The armature current and the exciting current of the direct current motor can be independently adjusted, so that the speed regulation characteristic of the direct current motor when the direct current motor is used for a motor and the stability of the output voltage when the direct current motor is used as a generator are the most ideal of a plurality of motors. However, the direct current motor has the disadvantages of frequent maintenance, poor reliability and the like due to the existence of the mechanical brush and the commutator, and the application range of the direct current motor is limited. The alternating current induction motor has the advantages of simple structure, no need of electric brushes, convenient maintenance and high reliability, is widely applied to the field of common transmission, but has poor speed regulation performance, low power factor and low efficiency. The traditional permanent magnet brushless alternating current motor has the advantages of high power density, high power factor and the like, and is developed rapidly in recent years. The motor is long in axial direction, and the application occasions with small space are limited.

Therefore, a novel disk type permanent magnet flux switching motor enters the field of vision of people. The motor is short in axial direction, the permanent magnets of the motor are located on the side of the stator, and the rotor only consists of the iron core, so that the complexity of the motor is greatly reduced, the heat dissipation performance of the permanent magnets is effectively enhanced, and the irreversible demagnetization risk of the permanent magnets is reduced. The magnetic field of the motor is not adjustable, and when the motor runs at a high speed, a weak magnetic control technology needs to be adopted to realize the high-speed running, which undoubtedly increases the complexity and the cost of the system.

In recent years, a disc type hybrid excitation flux switching motor is researched that permanent magnets and excitation are both positioned on the stator side, has certain magnetic regulation capacity, and is suitable for high-speed operation. Research shows that the adjacent permanent magnets of the traditional disk type hybrid excitation flux switching motor oppositely magnetize, the direction of the magnetic field of the concentrated excitation winding in the same slot with the permanent magnet is the same as or opposite to the direction of the magnetic field of the permanent magnet, and the excitation efficiency of the concentrated excitation winding is influenced to a certain extent. And the more permanent magnets, the poorer the magnetic regulation capability, and when the exciting current is zero, the positioning torque exists in the motor.

Disclosure of Invention

Utility model purpose:

the utility model aims at providing a transfer strong, the speed governing can be good, the operation is reliable, brushless, concentrate armature winding, concentrate excitation winding and permanent magnet and all arrange the stator in and can independent control, simple structure and with low costs, efficient disk hybrid excitation magnetic flow switching motor. The excitation magnetic field of the motor can be controlled by controlling the current of the direct current concentrated excitation winding, so that the motor has higher efficiency in a wider rotating speed range when being used as a motor, and can have a wider voltage regulation range when being used as a generator; in addition, because the magnetizing direction of the permanent magnet is along the circumferential tangent direction, when the exciting current is zero, the permanent magnet magnetic field only forms a closed loop at the stator side, the total magnetic flux of each phase of winding is zero at the moment, and the cogging torque is zero.

The technical scheme is as follows:

in order to realize the functions, the utility model provides an improved disk type hybrid excitation flux switching motor, which consists of a stator, a rotor, a concentrated armature winding, a concentrated excitation winding and a permanent magnet; the stator and the rotor are both made of magnetic conductive materials, an air gap is formed between the stator and the rotor, stator magnetic guide teeth are arranged on the stator, grooves are formed among the stator magnetic guide teeth, permanent magnets are arranged in part of the grooves, and concentrated armature windings and concentrated excitation windings are arranged on the stator magnetic guide teeth.

The number of the magnetic conduction teeth of the stator is Ns (4 × m × k × n); the concentrated armature windings are sleeved on two adjacent stator magnetic conduction teeth, the adjacent concentrated armature windings share one groove, and the groove provided with the concentrated armature windings is called an armature groove; concentrated excitation windings are sequentially arranged in the other 2 m k n slots, each concentrated excitation winding is sleeved with two adjacent stator magnetic conduction teeth, two adjacent concentrated excitation windings share or are separated by one slot, and the slots in which the concentrated excitation windings are arranged are called excitation slots; the stator is provided with m × q permanent magnets in total, and the permanent magnets are uniformly embedded at the bottom of the excitation slot; concentrated excitation windings in the slots are distributed on the outer side of the permanent magnet in the axial direction; the permanent magnets are uniformly distributed, and 4 x k x n/q stator magnetic conduction teeth are arranged between every two permanent magnets at intervals;

the rotor is of a tooth-groove-shaped structure and is made of magnetic conduction materials, and the number of the magnetic conduction teeth of the rotor is Nr (2 x m k +/-1) n;

wherein m is the number of phases of the motor, n is the number of motor units, k is the number of concentrated armature windings in series connection with any one phase of concentrated armature windings in each motor unit, and q is a positive integer less than 2 x k x n.

Furthermore, any phase of concentrated armature winding in each motor unit is formed by connecting k pairs of concentrated armature windings in series, k continuously placed concentrated armature windings are set to be the same phase from the first concentrated armature winding of any phase, and then k concentrated armature windings belonging to adjacent phases are sequentially setSequentially arranging according to the arrangement mode until all the motor units are arranged; 2k concentrated armature windings belonging to the same phase form k pairs of complementary concentrated armature windings, wherein the relative positions of two concentrated armature windings in any pair of concentrated armature windings and the rotor are different by half of the rotor pole pitch tau_sCorresponding to 180-degree electrical angle, the n motor units are sequentially arranged, and the concentrated armature windings belonging to the same phase in different motor units are connected in series or in parallel.

When every two concentrated excitation windings of the motor are separated by one slot, the directions of magnetic fields generated by the concentrated excitation windings are the same; when each two concentrated excitation windings share one slot, the directions of magnetic fields generated by the two adjacent concentrated excitation windings are opposite; concentrated excitation windings in each motor unit are connected in series to form a concentrated excitation winding unit, and concentrated excitation winding units in the n motor units are connected in series or in parallel.

Furthermore, the magnetizing directions of all the permanent magnets of the motor are along the same circumferential tangential direction; the magnetizing direction of each permanent magnet is opposite to the magnetic field direction of the concentrated excitation winding positioned at the axial outer side of the permanent magnet. When the exciting current introduced into the concentrated exciting winding is zero, only a permanent magnetic field exists in the motor, the permanent magnetic field only forms an annular closed magnetic circuit on the stator part, the annular closed magnetic circuit cannot penetrate through the air gap and the rotor, and the total magnetic flux in the concentrated armature winding is zero.

Preferably, the concentrated armature winding and the concentrated excitation winding are made of copper or a superconducting material, and the permanent magnet is made of a rare earth material such as ferrite or aluminum-iron-boron.

Preferably, the disk type hybrid excitation flux switching motor may be operated as a motor or a generator.

The technical effects are as follows:

the utility model provides a pair of disk hybrid excitation magnetic flux switching motor, it concentrates armature winding, concentrates excitation winding and permanent magnet and all is located the stator side, and the rotor is the tooth's socket type structure that comprises magnetic materials, simple structure, and the reliability is high. The concentrated armature winding and the concentrated excitation winding can be controlled independently, the excitation magnetic field of the motor can be controlled by controlling the current of the direct current concentrated excitation winding, the characteristics of the motor can be adapted in a wide rotating speed range, the maximum rotating speed of the motor can be improved when the concentrated armature winding and the concentrated excitation winding are used in the field of electric automobiles, and the high efficiency of the motor in the wide range is realized; the permanent magnet can weaken the magnetic field of the stator yoke part of the motor, reduce the magnetic field saturation degree of the motor, increase the magnetic flux passing through the three-phase concentrated armature winding and effectively improve the utilization rate of the concentrated excitation winding and the motor efficiency; the magnetizing directions of all permanent magnets in the motor are along the same circumferential tangential direction, when the exciting current is zero, the permanent magnetic field only forms a closed loop at the side of the stator, the total magnetic flux of the three-phase concentrated armature winding is zero, and the cogging torque is zero, so that when the motor is in no-load, the exciting current is cut off, and the torque pulsation can be effectively reduced. The magnetic field regulating device is used as a motor, the magnetic field regulating range of the motor is wide, and the magnetic field regulating device is suitable for application occasions with wide speed regulating range, such as electric automobiles.

Drawings

The invention will be further described with reference to the following figures and examples:

fig. 1 is a schematic view of a three-dimensional structure of a motor according to embodiment 1 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 2 is a schematic view of an axial structure of a motor stator of an embodiment 1 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 3 is a plane development view of a motor according to embodiment 1 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 4 is a schematic view of a three-dimensional structure of a motor according to embodiment 2 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 5 is a schematic view of an axial structure of a motor stator of embodiment 2 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 6 is a plane development view of a disc-type hybrid excitation flux switching motor according to embodiment 2 of the present invention;

fig. 7 is a schematic view of a three-dimensional structure of a motor according to embodiment 3 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 8 is a schematic view of an axial structure of a motor stator in embodiment 3 of a disc-type hybrid excitation flux switching motor according to the present invention;

fig. 9 is a plane development view of a motor according to embodiment 3 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 10 is a schematic view of a three-dimensional structure of a motor according to embodiment 4 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 11 is a schematic view of an axial structure of a motor stator of embodiment 4 of a disc-type hybrid excitation flux switching motor according to the present invention;

fig. 12 is a planar expanded view of a motor according to embodiment 4 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 13 is a schematic view of a three-dimensional structure of a motor according to embodiment 5 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 14 is a schematic view of an axial structure of a stator of a motor according to embodiment 5 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 15 is a planar expanded view of a motor according to embodiment 5 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 16 is a schematic view of a three-dimensional structure of a motor according to embodiment 6 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 17 is a planar expanded view of a motor according to embodiment 6 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 18 is a schematic view of a three-dimensional structure of a motor according to embodiment 7 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 19 is a planar expanded view of a motor according to embodiment 7 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 20 is a schematic view of a three-dimensional structure of a motor according to an embodiment 8 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 21 is a planar expanded view of a motor according to embodiment 8 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 22 is a schematic view of a three-dimensional structure of a motor according to embodiment 9 of a disc-type hybrid excitation flux switching motor of the present invention;

fig. 23 is a planar expanded view of a motor according to embodiment 9 of a disc-type hybrid excitation flux switching motor of the present invention;

the permanent magnet synchronous motor comprises a rotor 10, a stator 11, a magnetic conduction tooth 110, a concentrated armature winding 111, a concentrated excitation winding 112 and a permanent magnet 113.

Detailed Description

The utility model provides a disk type hybrid excitation magnetic flux switching motor, for making the utility model discloses a purpose, technical scheme and effect are clearer, and are clear and definite to and refer to the drawing and it is right to lift the example the utility model discloses further detailed description. It should be understood that the specific embodiments described herein are for purposes of illustration only and are not intended to limit the invention.

Example 1

Referring to fig. 1, the disk hybrid excitation flux switching motor of the present invention is composed of a stator 11, a rotor 10, a concentrated armature winding 111, a concentrated excitation winding 112 and a permanent magnet 113; the stator 11 and the rotor 10 are both made of magnetic conductive materials and have air gaps; the stator 11 is provided with stator magnetic conduction teeth 110, slots are formed between the stator magnetic conduction teeth 110, permanent magnets 113 are arranged in part of the slots, and concentrated armature windings 111 and concentrated excitation windings 112 are alternately arranged on the stator magnetic conduction teeth 110. In the motor of the present embodiment, m is 3, n is 1, k is 1, and q is 1, where m is the number of phases of the motor, n is the number of motor units, k is the number of concentrated armature windings 111 in each stator motor unit, q is a coefficient determining the number of permanent magnets, and q is a positive integer such that 4 × k × n/q is taken. That is, the motor is a three-phase motor, has A, B, C three phases, and includes 1 motor unit, where k is 1 pair of concentrated armature windings in each motor unit, and the number of magnetic conductive teeth 110 of the stator 11 is Ns 4 m n k 12; the magnetic conduction teeth are sequentially provided with concentrated armature windings 111, the number of the concentrated armature windings 111 is 2 × m × n × k ═ 6, each concentrated armature winding 111 spans two magnetic conduction teeth 110, and adjacent concentrated armature windings 111 share one groove; 2 × m × k × n-6 concentrated excitation windings 112 are sequentially arranged in the other 2 × m × k × n-6 slots, each concentrated excitation winding 112 spans two adjacent magnetic conduction teeth 110, each two concentrated excitation windings 112 share one slot, and the directions of magnetic fields generated by the two adjacent concentrated excitation windings 112 are opposite; the number of the permanent magnets 113 on the stator 11 is m × q ═ 3, the permanent magnets are uniformly embedded inside the axial direction of the excitation slot, 4 × k × n/q ═ 4 stator magnetic conduction teeth 110 are arranged between every two permanent magnets, the magnetizing directions of all the permanent magnets 113 are along the same circumferential tangential direction, and the magnetizing directions are opposite to the directions of the magnetic fields generated by the concentrated excitation windings in the excitation slot. The rotor 10 is a tooth-slot type, the number of the rotor magnetic conduction teeth is Nr (2 × m × k ± 1) n, when k is 1, m is 3, and n is 1, Nr may be 5 or 7, and in this embodiment, Nr is 5; since k is 1 and n is 1 in this embodiment, the number of pairs of concentrated armature windings 111 connected in series with any phase winding in a motor unit is k is 1 (as shown in the schematic diagram of the axial structure of the stator shown in fig. 2, a1 and a2 in the motor), from the first concentrated armature winding of any phase (as shown in a 1), there are k 1 concentrated armature windings adjacently placed to belong to the same phase, and then k is 1 concentrated armature windings 111 (i.e., B1 and C1 in fig. 3) belonging to the adjacent phases are sequentially arranged, according to the above arrangement, the three-phase concentrated armature windings in the motor are arranged in the following manner: A1-B1-C1-A2-B2-C2. The relative positions of the same-phase k-1 concentrated armature winding 111 and the secondary phase are different by half the rotor pole pitch, corresponding to 180 degrees of electrical angle, as shown in fig. 3, i.e. a-phase two concentrated armature windings a1 and a 2. At this time, the concentrated armature winding a1 crosses over two magnetic conducting teeth, the central line of which is opposite to the central line of the teeth of the rotor 10, and the central line of the concentrated armature winding a2 is opposite to the central line of the slots of the rotor 10, and the relative positions of the two windings and the rotor 10 are different by half the rotor pole pitch and are spatially different by 180 electrical degrees.

If the influence of the permanent magnet 113 is not considered, because the directions of the magnetic fields generated by the adjacent concentrated excitation windings 112 are opposite, the winding mode of reasonably arranging the concentrated armature windings a1 and a2 on the stator 11 can enable counter electromotive forces generated in the windings to be mutually superposed and present complementarity; during one electrical cycle of rotor 10 rotation (i.e., one stator 10 pole pitch rotation), there is a difference in magnetic circuit between concentrated armature windings a1 and a 2; in the position shown in fig. 3, assuming that the flux linkage in concentrated armature winding a1 is approximately zero at this time, the position is referred to as a first equilibrium position, and the positions of concentrated armature winding a2 and a1 relative to the rotor are different by half the pole pitch of rotor 10, the flux linkage in concentrated armature winding a2 is also approximately zero at this time, and the position is referred to as a second equilibrium position. During one electrical cycle of rotor 10 rotating counterclockwise (rotor 10 from left to right in fig. 3), the flux linkage amplitude change in concentrated armature winding a1 is as follows: first equilibrium location-positive maximum amplitude-second equilibrium location-negative maximum amplitude-first equilibrium location; and the flux linkage amplitude change process in the concentrated armature winding A2 is as follows: second equilibrium position-positive maximum amplitude-first equilibrium position-negative maximum amplitude-second equilibrium position. The trends of flux linkage change in the concentrated armature winding 111 of a1 and a2 are symmetrically complementary. After concentrated armature windings A1 and A2 are connected in series to form an A-phase winding, harmonic components of counter potentials generated by the concentrated armature windings A1 and A2 are mutually offset, and the obtained counter potentials have better sine. The sine performance is better, so that the torque fluctuation is reduced, and the method is very suitable for brushless alternating current (BLAC) control; the two phases B and C also have the characteristics of the phase A, and the phases of the three phases are different from each other by 120 degrees in electrical angle.

If the current passed through the concentrated excitation winding 112 is zero, only considering the action of the permanent magnets 113, the magnetizing directions of all the permanent magnets 113 are along the same circumferential tangential direction, and the permanent magnetic field only forms a closed magnetic circuit at the stator 11 and cannot pass through the air gap and the rotor 10, so that the electromagnetic torque cannot be generated. As shown in fig. 3, due to the existence of the yoke, most of the magnetic circuit of the motor is the yoke passing through the slot where the permanent magnet 113 is located, and taking PM1 as an example, the magnetic circuit of the permanent magnet magnetic field can be described as follows: PM 1-stator flux guide tooth adjacent to PM 1-yoke-another stator tooth adjacent to PM 1-returns to PM 1. Since the magnetizing direction of the permanent magnet 113 is magnetized in the circumferential direction, taking the permanent magnet PM1 as a reference, a small part of the permanent magnet magnetic circuit can be described as: PM 1-stator flux guide tooth adjacent to PM 1-yoke-stator flux guide tooth adjacent to PM 2-PM 2-stator flux guide tooth adjacent to PM 2-yoke-stator flux guide tooth adjacent to PM 3-PM 3-stator flux guide tooth adjacent to PM 3-yoke-returns to PM1, eventually forming a closed magnetic circuit. When passing through the permanent magnet 113, the permanent magnetic field inevitably passes through the concentrated armature winding 111 on the periphery of the permanent magnet 113, for example, when passing through the PM2, the permanent magnetic field inevitably passes through the concentrated armature winding a2, but because the air gap reluctance is large, the permanent magnetic field does not enter the rotor 10 through the air gap, so the permanent magnetic fields passing through and out of the concentrated armature winding a2 are the same, and finally, the permanent magnetic flux linkage in the concentrated armature winding a2 is zero; for the other concentrated armature winding a1 of phase a, the permanent magnet flux linkage is also zero because it only passes through the stator yoke outside the winding and does not pass into or out of the concentrated armature winding a 1. This phenomenon does not change with the rotation of the rotor 10, and therefore the flux linkage of the a phase is always zero during the rotation of the rotor 10, and no opposite potential is generated. Because the permanent magnets 113 are uniformly distributed and three phases are symmetrical, B, C two phases also have the characteristic of A phase, and the characteristic effectively overcomes the defect that the traditional mixed excitation flux switching motor cannot be completely de-energized to cause overlarge short-circuit current when short-circuit fault occurs.

When the magnetic fields generated by the permanent magnet 113 and the concentrated excitation winding 112 are considered at the same time, the magnetization direction of the permanent magnet 113 is opposite to the direction of the magnetic field generated by the concentrated excitation winding 112 located at the radial outer side, which is specifically expressed as follows: on one hand, the directions of the permanent magnetic field and the electric excitation magnetic field are opposite at the yoke part of the stator, and when the saturation degree of the magnetic field of the stator 11 is too high, the saturation degree of the magnetic field of the yoke part of the stator can be effectively reduced by the permanent magnetic field, and the iron loss of the motor is effectively reduced; on the other hand, the permanent magnetic field can reduce the magnetic field saturation degree of the stator magnetic conduction teeth 110, so that the excitation flux linkage in the three-phase winding is indirectly improved, and therefore, the back electromotive force of the three-phase winding can be effectively improved.

When the motor needs to operate at a large torque, the size of the direct current exciting current is increased, so that the exciting magnetic field intensity of the motor is enhanced, and the exciting efficiency of the motor can be improved; when the torque is small, the direct current exciting current can be increased, the torque is reduced, and the efficiency of the motor is improved.

Example 2

Fig. 4 shows a disk-type hybrid excitation flux switching motor. In this embodiment, m is 3, n is 2, k is 1, and q is 1. The motor of the present embodiment is different from the motor of embodiment 1 in that the number n of motor units on the stator 11 is 2. That is, the motor is a three-phase motor, has A, B, C three phases, and includes 2 motor units, each of which has k equal to 1 pairs of concentrated armature windings, and the number of the magnetic conductive teeth 110 of the stator 11 is Ns equal to 4 equal to m equal to n equal to 24; the magnetic conduction teeth are sequentially provided with concentrated armature windings 111, the number of the concentrated armature windings 111 is 2 × m × n × k ═ 12, each concentrated armature winding 111 spans two magnetic conduction teeth 110, and adjacent concentrated armature windings 111 share one groove; 2 × m × k × n-12 concentrated excitation windings 112 are sequentially arranged in the other 12 slots, each concentrated excitation winding 112 spans two adjacent magnetic conduction teeth 110, each two concentrated excitation windings 112 share one slot, and the magnetic fields generated by the two adjacent concentrated excitation windings 112 are opposite in direction; concentrated excitation windings in a first motor unit in the stator 11 are connected in series to form a first concentrated excitation winding unit, and the first concentrated excitation winding unit and a second concentrated excitation winding unit can be connected in series or in parallel to form a concentrated excitation winding; the number of the permanent magnets 113 on the stator 11 is m × q ═ 3, the permanent magnets are uniformly embedded inside the axial direction of the excitation slot, 4 × k × n/q ═ 8 stator magnetic conduction teeth 110 are arranged between every two permanent magnets, the magnetizing directions of all the permanent magnets 113 are along the same circumferential tangential direction, and the magnetizing directions are opposite to the directions of the magnetic fields generated by the concentrated excitation windings in the excitation slot. The rotor 10 is a tooth-slot type, the number of the rotor magnetic conduction teeth is Nr (2 × m × k ± 1) n, when k is 1, m is 3, and n is 2, Nr may be 10, 14, in this embodiment, Nr is 14;

since in this embodiment, k is 1 and n is 2, the number of pairs of concentrated armature windings 111 in series connected to any phase winding in the motor unit is k is 1 (as shown in fig. 5, a1 and a2 in the first motor unit or A3 and a4 in the second motor unit), from the first concentrated armature winding of any phase (as shown in fig. 1), there are k 1 concentrated armature windings adjacently placed in the same phase, and thereafter, k is 1 concentrated armature windings 111 (i.e., B1 and C1 in fig. 6) belonging to adjacent phases are sequentially disposed, according to the above arrangement, the three-phase concentrated armature windings in the first motor unit are arranged in the following manner: A1-B1-C1-A2-B2-C2. The relative positions of the 2 k-2 concentrated armature windings 111 belonging to the same phase and the secondary phase are different by half the rotor pole pitch, corresponding to 180 degrees of electrical angle, and in fig. 6, the a-phase two concentrated armature windings a1 and a 2. At this time, the concentrated armature winding a1 crosses over two magnetic conducting teeth, the central line of which is opposite to the central line of the teeth of the rotor 10, and the central line of the concentrated armature winding a2 is opposite to the central line of the slots of the rotor 10, and the relative positions of the two windings and the rotor 10 are different by half the rotor pole pitch and are spatially different by 180 electrical degrees.

If the influence of the permanent magnet 113 is not considered, because the directions of the magnetic fields generated by the adjacent concentrated excitation windings 112 are opposite, the winding mode of reasonably arranging the concentrated armature windings a1 and a2 on the stator 11 can enable counter electromotive forces generated in the windings to be mutually superposed and present complementarity; during one electrical cycle of rotor 10 rotation (i.e., one stator 10 pole pitch rotation), there is a difference in magnetic circuit between concentrated armature windings a1 and a 2; assuming that the flux linkage in concentrated armature winding a1 is approximately zero at this time, the position shown in fig. 3 is referred to as the first equilibrium position, and the positions of concentrated armature windings a2 and a1 relative to the rotor are different by half the pole pitch of rotor 10, the flux linkage in concentrated armature winding a2 is also approximately zero at this time, and therefore, the position is referred to as the second equilibrium position. During one electrical cycle of rotor 10 rotating counterclockwise (rotor 10 from left to right in fig. 6), the flux linkage amplitude change in concentrated armature winding a1 is as follows: first equilibrium location-positive maximum amplitude-second equilibrium location-negative maximum amplitude-first equilibrium location; and the flux linkage amplitude change process in the concentrated armature winding A2 is as follows: second equilibrium position-positive maximum amplitude-first equilibrium position-negative maximum amplitude-second equilibrium position. The trend of flux linkage change in the A1 and A2 two-part concentrated armature winding is symmetrically complementary. After concentrated armature windings A1 and A2 are connected in series to form an A-phase winding, harmonic components of counter potentials generated by the concentrated armature windings A1 and A2 are mutually offset, and the obtained counter potentials have better sine. Likewise, the concentrated armature windings A3, a4 in the second motor unit also have the characteristics of the first motor unit, and therefore, the concentrated armature windings A3, a4 also have complementary characteristics therebetween. When concentrated armature windings A1, A2, A3 and A4 in two motor units are connected in series to form an A-phase winding of the stator 11, counter potential higher harmonics generated in the concentrated windings are mutually offset and have better sine property, so that torque fluctuation is reduced, and the brushless alternating current (BLAC) motor is very suitable for brushless alternating current (BLAC) control; the two phases B and C also have the characteristics of the phase A, and the phases of the three phases are different from each other by 120 degrees in electrical angle.

If the current passed through the concentrated excitation winding 112 is zero, only considering the action of the permanent magnets 113, the magnetizing directions of all the permanent magnets 113 are along the same circumferential tangential direction, and the permanent magnetic field only forms a closed magnetic circuit at the stator 11 and cannot pass through the air gap and the rotor 10, so that the electromagnetic torque cannot be generated. As shown in fig. 6, due to the existence of the yoke, most of the magnetic circuit of the motor is the yoke passing through the slot where the permanent magnet 113 is located, and taking PM1 as an example, the magnetic circuit of the permanent magnet magnetic field can be described as follows: PM 1-stator tooth adjacent to PM 1-stator yoke-another stator tooth adjacent to PM 1-is returned to PM 1. Since the permanent magnets are magnetized in the same circumferential tangential direction, a part of the magnetic circuit forms a loop along the circumference of the yoke part of the stator 11, and if the PM1 is taken as a reference, the magnetic circuit of the permanent magnet magnetic field can be described as follows: PM1, stator magnetic conduction teeth, stator yokes and stator magnetic conduction teeth, wherein the stator magnetic conduction teeth are adjacent to PM1, the stator magnetic conduction teeth are adjacent to PM2, PM2, stator magnetic conduction teeth, stator yokes and stator magnetic conduction teeth, which are adjacent to PM2, PM3, PM3, permanent magnets, which are adjacent to PM3, stator magnetic conduction teeth, stator yokes and PM1, return to PM1, and sequentially pass through the rest permanent magnets 113 according to the path, and finally a closed magnetic circuit is formed. When passing through the permanent magnet 113, the permanent magnetic field inevitably passes through the concentrated armature winding 111 on the periphery of the permanent magnet 113, for example, when passing through the PM2, the permanent magnetic field inevitably passes through the concentrated armature winding a12, but because the air gap reluctance is large, the permanent magnetic field does not enter the rotor 10 through the air gap, so the permanent magnetic fields passing through and out of the concentrated armature winding a2 are the same, and finally, the permanent magnetic flux linkage in the concentrated armature winding a2 is almost zero; for the other concentrated armature windings a1, A3 and a4 of the a phase, the permanent magnet flux linkages are zero because they pass only through the stator yoke outside the windings and do not pass into or out of the concentrated armature windings a1, A3 and a 4. This phenomenon does not change with the rotation of the rotor 10, and therefore the flux linkage of the a phase is always zero during the rotation of the rotor 10, and no opposite potential is generated. Because the permanent magnets 113 are uniformly distributed and three phases are symmetrical, B, C two phases also have the characteristics of A phase. This embodiment has the same characteristics as embodiment 1.

Example 3

Fig. 7 shows a disk-type hybrid excitation flux switching motor. In this embodiment, m is 3, n is 2, k is 1, and q is 2. The difference from the motor of embodiment 2 is that the number m × q of the permanent magnets 113 on the stator 11 of this embodiment is 6, and the permanent magnets are uniformly embedded inside the axial direction of the excitation slot, and 4 stator magnetic guide teeth 110 are spaced between every two permanent magnets by 4 × k × n/q. The magnetizing directions of all the permanent magnets 113 are along the same circumferential tangential direction and are opposite to the magnetic field direction generated by the concentrated excitation winding in the excitation slot.

In this embodiment, as shown in fig. 8, the number and arrangement of the motor windings are the same as those of embodiment 2, and the flux linkage change and the back electromotive force in the three-phase winding have the same characteristics as those of embodiment 2. The number of the permanent magnet blocks is doubled relative to the motor in embodiment 2, and m × q on the stator 11 is equal to 6 permanent magnets which are uniformly distributed and symmetrical with each other. Since the magnetizing direction of the permanent magnet 113 in the motor of this embodiment has the same characteristics as the motor of embodiment 1, as shown in fig. 9, most of the magnetic field passes through the yoke due to the presence of the slot yoke where the permanent magnet is located, which can be described as PM1 by way of example: the PM1, PM1 adjacent to the stator flux guide teeth 110, yoke portion, PM1 adjacent to the other stator flux guide teeth 110, PM1, and the magnetic circuit of the other permanent magnets 113 is similar to that of PM 1. A portion of the magnetic path of the permanent magnetic field can still be described as: the PM1, the stator magnet guiding tooth 110 adjacent to the PM1, the stator yoke, the stator magnet guiding tooth 110 adjacent to the PM2, and the permanent magnet PM2 sequentially pass through the rest of the permanent magnets 113 according to the path, and finally form a closed magnetic circuit. When passing through the permanent magnet 113, the permanent magnetic field necessarily passes through the concentrated armature winding 111 on the periphery of the permanent magnet 113, for example, when passing through PM1 or PM4, the permanent magnetic field necessarily passes through the concentrated armature winding B1 or B3, but because the air gap reluctance is large, the permanent magnetic field does not enter the rotor 10 through the air gap, so the permanent magnetic fields passing through and out of the concentrated armature winding B1 or B3 are the same, and finally, the permanent magnetic flux linkage in the concentrated armature winding B1 or B3 is almost zero; for the other concentrated armature windings B2 and B4 of the B phase, the permanent magnet flux linkages are zero because they pass only through the stator yoke outside the windings and do not pass into or out of the concentrated armature windings B2 and B4. This phenomenon does not change with the rotation of the rotor 10, and the flux linkage of the a phase is always zero during the rotation of the rotor 10, and no opposite potential is generated. Since the permanent magnets 113 are uniformly distributed and three phases are symmetrical, A, C two phases also have the characteristics of B phase. This embodiment has the same characteristics as embodiment 2.

Example 4

Fig. 10 shows a disk-type hybrid excitation flux switching motor. In this embodiment, m is 3, n is 1, k is 2, and q is 1. The difference from the motor of embodiment 1 is that the number k of concentrated armature windings 111 connected in series with each phase of concentrated armature winding in each motor unit is 2 in this embodiment. That is, the motor is a three-phase motor, has A, B, C three phases, and includes 1 motor unit, where k is 2 pairs of concentrated armature windings in each motor unit, and the number of magnetic conductive teeth 110 of the stator 11 is Ns 4 m n k 24; the magnetic conduction teeth are sequentially provided with concentrated armature windings 111, the number of the concentrated armature windings 111 is 2 × m × n × k ═ 12, each concentrated armature winding 111 spans two magnetic conduction teeth 110, and adjacent concentrated armature windings 111 share one groove; 2 × m × k × n-12 concentrated excitation windings 112 are sequentially arranged in the other 12 slots, each concentrated excitation winding 112 spans two adjacent magnetic conduction teeth 110, each two concentrated excitation windings 112 share one slot, and the magnetic fields generated by the two adjacent concentrated excitation windings 112 are opposite in direction; concentrated excitation windings in a first motor unit in the stator 11 are connected in series to form a first concentrated excitation winding unit, and the first concentrated excitation winding unit and a second concentrated excitation winding unit can be connected in series or in parallel to form a concentrated excitation winding; the number of the permanent magnets 113 on the stator 11 is m × q ═ 3, the permanent magnets are uniformly embedded inside the axial direction of the excitation slot, every two permanent magnets are spaced by 4 × k × n/q ═ 8 stator magnetic conduction teeth 110, the magnetizing directions of all the permanent magnets 113 are along the same circumferential tangential direction, and the magnetizing directions are opposite to the magnetic field directions generated by the concentrated excitation windings 112 in the excitation slot. The rotor 10 is a tooth-groove type, the number of the rotor magnetic conduction teeth is Nr (2 × m × k ± 1) n, when k is 1, m is 3, and n is 2, Nr may be 11 or 13, and in this embodiment, Nr is 13.

Since k is 2 and n is 1 in this embodiment, the number of pairs of concentrated armature windings 111 connected in series with any phase winding in the motor unit is k is 2 (as shown in the schematic diagram of the axial structure of the stator shown in fig. 11, a11 and a22 in the motor unit), from the first concentrated armature winding of any phase (as shown in a 11), there are k 2 concentrated armature windings adjacently placed to belong to the same phase, and then k is 2 concentrated armature windings 111 (i.e., B11 and C12 in fig. 12) belonging to adjacent phases are sequentially arranged, according to the above arrangement, the arrangement of the three-phase concentrated armature windings in the motor unit is: A11-A12-B11-B12-C11-C12-A21-A22-B21-B22-C21-C22. The relative positions of the 4 concentrated armature windings 111 and the secondary winding belonging to the same phase are different by half the rotor pole pitch, corresponding to 180 degrees of electrical angle, as shown in fig. 3, i.e. a-phase two concentrated armature windings a11 and a 21. At this time, the concentrated armature winding a11 crosses over two magnetic conducting teeth, the central line of which is opposite to the central line of the teeth of the rotor 10, and the central line of the concentrated armature winding a21 is opposite to the central line of the slots of the rotor 10, and the relative positions of the two windings and the rotor 10 are different by half the rotor pole pitch and are spatially different by 180 electrical degrees. Due to the fact that the relative positions of A11 and A12 and A21 and A22 are close to the relative position of the rotor 10, when the concentrated windings A11, A12, A21 and A22 are connected in series to form an A-phase winding, the amplitude of counter potential of the A-phase winding is slightly smaller than four times of the amplitude of fundamental waves of the concentrated windings A11, A12, A21 and A22. The B-phase winding and the C-phase winding have the same characteristics. This embodiment has the same characteristics as embodiment 1.

Example 5

Fig. 13 is also a disk type hybrid excitation flux switching motor. In this embodiment, m is 5, n is 1, k is 1, and q is 1, that is, the motor is a five-phase motor, the stator 11 includes 1 motor unit, there are k is 1 pair of concentrated armature windings in each motor unit, and the number of the magnetic conductive teeth 110 on the stator 11 is Ns is 4 m is n is 20; the magnetic conduction teeth are sequentially provided with concentrated armature windings 111, the number of the concentrated armature windings 111 is 2 × m × n × k ═ 10, each concentrated armature winding 111 spans two magnetic conduction teeth 110, and adjacent concentrated armature windings 111 share one groove; 2 × m × k × n is sequentially arranged in the remaining 10 slots, 10 concentrated excitation windings 112 are arranged in each slot, each concentrated excitation winding 112 spans two adjacent magnetic conduction teeth 110, each two concentrated excitation windings 112 share one slot, and the directions of magnetic fields generated by two adjacent concentrated excitation windings 112 are opposite; concentrated excitation windings in a first motor unit in the stator 11 are connected in series to form a first concentrated excitation winding unit, and the first concentrated excitation winding unit and a second concentrated excitation winding unit can be connected in series or in parallel to form a concentrated excitation winding; the number of the permanent magnets 113 of the stator 11 is m × q ═ 5, the permanent magnets are uniformly embedded in the inner side of the excitation slot axis, 4 × k × n/q ═ 4 stator magnetic conduction teeth 110 are arranged between every two permanent magnets, the magnetizing directions of all the permanent magnets 113 are along the same circumferential tangential direction, and the magnetizing directions are opposite to the magnetic field directions generated by the concentrated excitation windings in the excitation slots. The rotor 10 is a slot-type structure made of a magnetic conductive material, the number of the rotor magnetic conductive teeth is Nr (2 × m × k ± 1) n, when k is 1, m is 5, and n is 1, Nr may be 9 or 11, and in this embodiment, Nr is 11. In the motor of the present embodiment, the number of pairs of concentrated armature windings 111 connected in series to any one phase winding is set to "k" 1. As shown in fig. 14, the concentrated armature winding of phase a is composed of two concentrated armature windings a1, a2 connected in series, the concentrated armature winding a1 crosses over two magnetic conductive teeth 110, the central line of which is opposite to the central line of the teeth of the rotor 10, and the central line of the concentrated armature winding a2 is opposite to the central line of the slots of the rotor 10, and the relative positions of the two windings and the rotor 10 are different by half the rotor pole pitch and are different by 180 degrees in space. Therefore, the motor also has the complementary characteristic of a magnetic circuit, counter potential higher harmonics generated in each phase of winding are mutually counteracted, and finally the obtained counter potential has better sine.

The magnetizing direction of the permanent magnet 113 in the motor of the embodiment is the same as that of the motor of the embodiment 1, and the permanent magnet magnetic field forms a closed magnetic circuit only in the stator 11. As shown in fig. 15, due to the existence of the yoke of the slot where the permanent magnet 113 is located, the magnetic path of most of the permanent magnet 113 only passes through the adjacent magnetically conducting teeth 110 and the yoke of the slot where the permanent magnet 113 is located, and taking PM1 as an example, it can be described as: PM 1-PM 1 is adjacent to stator magnetically conducting tooth 110-yoke part-PM 1 is adjacent to another magnetically conducting tooth-PM 1. A small portion of the magnetic path of the permanent magnetic field can still be described as: PM 1-stator magnetic conduction teeth adjacent to PM 1-stator yoke-stator magnetic conduction teeth adjacent to PM 2-PM 2, and passes through the rest of the permanent magnets in sequence according to the path, and finally a closed magnetic circuit is formed. The permanent magnetic field penetrates through the permanent magnet PM1 and simultaneously necessarily penetrates through the concentrated armature winding B1, but because the air gap magnetic resistance is large, the permanent magnetic field cannot enter the rotor 10 through the air gap, so that the permanent magnetic fields penetrating into and out of the concentrated armature winding B11 are the same, and finally, the permanent magnetic flux linkage in the concentrated armature winding B11 is almost zero; for the other concentrated armature winding B2 of phase B, the permanent magnet flux linkage is zero because it only passes through the yoke of the stator 11 outside the winding and does not pass into or out of the concentrated armature winding a 2. This phenomenon does not change with the rotation of the rotor 10, and the flux linkage of the a phase is always zero during the rotation of the rotor 10, and no opposite potential is generated. B, C, D, E has the same characteristics of phase A due to the uniform distribution of the permanent magnets 113. Therefore this embodiment motor possesses equally the utility model discloses the characteristics of motor.

Example 6

Fig. 16 shows a disk-type double-stator hybrid excitation flux switching motor, which is obtained by symmetry along the outer end surface of the rotor 10 in embodiment 2, and is a magnetic circuit parallel hybrid excitation flux switching motor, in which two stators 11 of the motor can work independently, or work in parallel or work in series. In the present embodiment, m is 3, n is 2, k is 1, and q is 1, and the number of motor units n is 2 on a single stator 11. That is, the motor is a three-phase motor, has A, B, C three phases, and includes 2 motor units, each of which has k equal to 1 pairs of concentrated armature windings, and the number of the magnetic conductive teeth 110 of a single stator 11 is Ns equal to 4 equal to m equal to n equal to 24; the magnetic conduction teeth are sequentially provided with concentrated armature windings 111, the number of the concentrated armature windings 111 is 2 × m × n × k ═ 12, each concentrated armature winding 111 spans two magnetic conduction teeth 110, and adjacent concentrated armature windings 111 share one groove; 2 × m × k × n-12 concentrated excitation windings 112 are sequentially arranged in the other 12 slots, each concentrated excitation winding 112 spans two adjacent magnetic conduction teeth 110, each two concentrated excitation windings 112 share one slot, and the magnetic fields generated by the two adjacent concentrated excitation windings 112 are opposite in direction; concentrated excitation windings in a first motor unit in the single stator 11 are connected in series to form a first concentrated excitation winding unit, and the first concentrated excitation winding unit and a second concentrated excitation winding unit can be connected in series or in parallel to form a concentrated excitation winding; the excitation units on the two stators can be connected in parallel or in series, and can also be controlled independently; the number of the permanent magnets 113 on the single stator 11 is m × q ═ 3, the permanent magnets are uniformly embedded in the axial inner side of the excitation slot, 4 × k × n/q ═ 8 stator magnetic conduction teeth 110 are arranged between every two permanent magnets, the magnetizing directions of all the permanent magnets 113 are along the same circumferential tangential direction, and the magnetizing directions are opposite to the magnetic field directions generated by the concentrated excitation windings in the excitation slot. The rotor 10 is a tooth-slot type, the number of the rotor magnetic conduction teeth is Nr (2 × m × k ± 1) n, when k is 1, m is 3, and n is 2, Nr may be 10, 14, in this embodiment, Nr is 14; because the embodiment is obtained by symmetry of the embodiment 2, the characteristics of the motor are not changed, the two stator 11 units can be controlled independently, and the same-phase concentrated armature winding 111 can also be controlled by connecting in series or in parallel to form a phase winding.

When the field current is zero, the magnetic field in the motor is the same as that in embodiment 2, and a loop is formed only on the stator 11 side. Regardless of the influence of the permanent magnets 113, if the concentrated excitation windings 112 of the two stators 11 are supplied with positive current, it can be concluded that the magnetic paths of the two stators 11 in the rotor 10 are opposite. In order to improve the efficiency of the motor, the concentrated field winding 112 of the stator 11 obtained symmetrically is supplied with a negative field current, and the direction of the magnetic field of the permanent magnet 113 is opposite to that of the concentrated field winding of the same slot, so the magnetizing directions of the permanent magnets 113 on the stator 11 obtained symmetrically are the same, as shown in fig. 17. Because the two stators can work independently or in series or parallel, the number of the permanent magnets 113 on the stator 11 obtained symmetrically can be the same as or different from that of the original stator 11, and the core lies in ensuring that the direction of the permanent magnetic field is opposite to that of the excitation field of the slot where the permanent magnetic field is located, and ensuring that 4 x n x k/q is a positive integer.

Example 7

Fig. 18 shows a double-stator hybrid excitation flux switching motor, which is a magnetic circuit series hybrid excitation flux switching motor in the present embodiment, which is symmetrical along the outer end surface of the rotor in embodiment 2, and is different from embodiment 6 in that the rotor 10 has no yoke portion, and the permanent magnet 113 has a magnetizing direction opposite to that of the primary stator 11 in order to satisfy the condition that the permanent magnet 113 has a magnetizing direction opposite to that of the same slot excitation field, as shown in fig. 19. When the excitation current is zero, the permanent magnetic field has the same characteristics as those of embodiments 2 and 6. When the field current is supplied, the field magnetic circuit forms a loop through the two stators 11 and the rotor 10 unlike embodiment 6, and forms a loop between a single stator 11 and the rotor 10 unlike embodiment 6, and thus is called a series magnetic circuit type hybrid field flux switching motor. The magnetic circuit series motor generally operates on both sides simultaneously. The number of the permanent magnets 113 on the stators 11 on both sides may be the same or different, and the core is to ensure that the direction of the permanent magnetic field is opposite to that of the excitation field of the slot where the permanent magnetic field is located, and ensure that 4 × n × k/q is a positive integer.

Example 8

Fig. 20 shows a double-rotor hybrid excitation flux switching motor obtained by symmetry along the outer end surface of the stator 11 in example 2. As shown in fig. 21, the magnetic field direction in the stator 11 is the same by changing the current direction of the concentrated field winding 112 on the side where the symmetry is obtained so that the magnetic field direction generated in the yoke portion of the stator 11 is the same, and in this case, the magnetic circuit parallel type hybrid field flux switching motor is used. The directions of the concentrated armature winding 111 and the permanent magnet 113 are kept unchanged. The single-sided motor having the same characteristics as in embodiment 2, and the two-sided concentrated armature windings can be operated in series or in parallel, has the same characteristics as in embodiment 2. When the excitation current in the motor is zero, due to the existence of the stator yoke, taking PM1 as an example, the permanent magnet circuit in the motor can be described as follows: PM 1-PM 1 adjacent magnetically permeable tooth 110-yoke-PM 1 Another adjacent magnetically permeable tooth 110-returns to PM 1. Since the magnetization directions of the permanent magnets 113 are along the same circumferential direction, there is a portion of the permanent magnetic circuit that can be described as: PM 1-PM 1 adjacent to magnet guiding tooth 110-yoke-PM 2 adjacent to magnet guiding tooth-PM 2-PM 2 another adjacent magnet guiding tooth 110-yoke-PM 3 adjacent to magnet guiding tooth 110-PM 3-PM 3 another magnet guiding tooth-yoke-PM 1 another magnet guiding tooth-and back to PM 1. This embodiment has the same characteristics as embodiment 2.

Example 9

Fig. 22 shows a double-rotor hybrid excitation flux switching motor obtained by symmetry along the outer end surface of the stator 11 in example 2. As shown in fig. 23, the magnetic series hybrid excitation flux switching motor is provided. The symmetrical winding structure is the same as that of the primary stator 11, and the magnetizing direction of the permanent magnet 113 is opposite in order to satisfy the condition that the magnetic field direction of the permanent magnet 113 is opposite to the exciting magnetic field direction of the slot where the permanent magnet is located. Because the magnetic circuits of the upper part and the lower part of the motor are connected in series, the horizontal component of the magnetic field in the stator 11 is small, and therefore all the slots can be removed. When the current passed by the concentrated excitation winding 112 is zero, the permanent magnet magnetic circuits on the upper and lower sides are connected in series, taking PM3 and PM6 as examples, which can be described as follows: PM 3-the adjacent magnetic conductive tooth 110 of PM 3-PM 6-the adjacent magnetic conductive tooth 110 of PM 6-returns to PM. When the concentrated excitation winding 112 is supplied with a forward current, the magnetic circuit of the excitation magnetic field enters the stator through the upper and lower rotors and the air gap, regardless of the influence of the permanent magnet 113, which can be described as follows: the stator magnetic guiding teeth 110, the upper side air gap, the upper side rotor, the upper side air gap, the other stator magnetic guiding teeth 110, the lower side air gap, the lower side rotor, the lower side air gap return to the stator magnetic guiding teeth. This embodiment has the same characteristics as embodiment 2.

The basic principles and the main features of the invention and the advantages of the invention have been shown and described above. It will be understood by those skilled in the art that the present invention is not limited to the above embodiments, and that the foregoing embodiments and descriptions are provided only to illustrate the principles of the present invention without departing from the spirit and scope of the present invention. The scope of the invention is defined by the appended claims and equivalents thereof.

Claims

1. A multi-phase disc type hybrid excitation flux switching motor is characterized by comprising a stator (11), a rotor (10), a concentrated armature winding (111), a concentrated excitation winding (112) and a permanent magnet (113); the stator (11) and the rotor (10) are both made of magnetic conductive materials, an air gap is formed between the stator and the rotor, stator magnetic guide teeth (110) are arranged on the stator (11), grooves are formed between the stator magnetic guide teeth (110), permanent magnets (113) are arranged in part of the grooves, and concentrated armature windings (111) and concentrated excitation windings (112) are arranged on the stator magnetic guide teeth (110); the number of the magnetic conduction teeth (110) on the stator (11) is all Ns (4 x m k n); 2 m x k x n concentrated armature windings (111) are sequentially wound on the magnetic conduction teeth (110) of the stator (11), each concentrated armature winding (111) is sleeved on two adjacent magnetic conduction teeth (110), the adjacent concentrated armature windings (111) share one groove, and the groove provided with the concentrated armature winding (111) is called an armature groove; concentrated excitation windings (112) are sequentially arranged in the other 2 m k n slots, each concentrated excitation winding (112) is sleeved with two adjacent stator magnetic conduction teeth (110), two adjacent concentrated excitation windings (112) share or are separated by one slot, and the slots provided with the concentrated excitation windings (112) are called excitation slots; the stator (11) is provided with m × q permanent magnets (113) which are uniformly embedded outside the excitation slot; concentrated excitation windings (112) in the slots are distributed on the axial outer side of the permanent magnet (113); the permanent magnets (113) are uniformly distributed, and 4 x k x n/q stator magnetic conduction teeth (110) are arranged between every two permanent magnets (113); the rotor (10) is of a tooth groove type structure formed by magnetic conducting materials, and the number of the magnetic conducting teeth of the rotor is Nr ═ (2 × m × k ± 1) n;

the motor comprises a motor, a plurality of concentrated armature windings (111), a plurality of motor units and a plurality of motor units, wherein m is the number of phases of the motor, n is the number of the motor units, k is the logarithm of the concentrated armature windings (111) which are connected in series with any one phase of the concentrated armature windings in each motor unit, m, n, k and q are positive integers, and q is a positive integer smaller than 2 x n x k.

2. The multi-phase disc type hybrid excitation flux switching motor according to claim 1, wherein any one phase concentrated armature winding in each motor unit is formed by connecting k pairs of concentrated armature windings (111) in series, from the first concentrated armature winding (111) of any one phase, k continuously placed concentrated armature windings (111) are arranged as the same phase, and then k concentrated armature windings (111) belonging to adjacent phases are sequentially arranged according to the arrangement mode until all the motor units are arranged; 2k concentrated armature windings (111) belonging to the same phase form k pairs of complementary concentrated armature windings, wherein the relative positions of two concentrated armature windings (111) in any pair of concentrated armature windings and the rotor (10) are different by half of the rotor pole pitch tau_sCorresponding to 180-degree electrical angle, the n motor units are sequentially arranged, and concentrated armature windings (111) belonging to the same phase in different motor units are connected in series or in parallel.

3. A multi-phase disc type hybrid excitation flux switching motor according to claim 1, wherein when every two concentrated excitation windings (112) are separated by one slot, the directions of magnetic fields generated by the concentrated excitation windings (112) are the same; when each two concentrated excitation windings (112) share one slot, the directions of the magnetic fields generated by the two adjacent concentrated excitation windings (112) are opposite; concentrated excitation windings (112) in each motor unit are connected in series to form a concentrated excitation winding unit, and concentrated excitation winding (112) units in the n motor units are connected in series or in parallel.

4. The multiphase disc type hybrid excitation flux switching motor according to claim 1, wherein the magnetization directions of all the permanent magnets (113) are along the same circumferential tangential direction; the magnetizing direction of each permanent magnet (113) is opposite to the magnetic field direction of the concentrated excitation winding (112) in the same slot; when the exciting current introduced into the concentrated exciting winding (112) is zero, only a permanent magnetic field exists in the motor, the permanent magnetic field only forms a ring-shaped closed magnetic circuit at the stator (11) part and cannot penetrate through an air gap and the rotor (10), and the total magnetic flux of the concentrated armature winding (111) is zero.

5. A multiphase disc hybrid excitation flux switching machine according to claim 1, wherein the concentrated excitation winding (112) and concentrated armature winding (111) are copper or superconducting material.

6. The multiphase disc type hybrid excitation flux switching motor according to claim 1, wherein the permanent magnet is a rare earth material such as ferrite, aluminum-iron-boron, and the like.

7. The multiphase disc type hybrid excitation flux switching motor according to claim 1, wherein a magnetic circuit parallel type double rotor disc type hybrid excitation flux switching motor is obtained by using an outer end surface of a stator (11) as a mirror surface, a yoke portion of a stator slot is removed, a motor magnetic circuit passes through two rotors (10) and the stator (11), and the motor is a magnetic circuit series type hybrid excitation flux switching motor.

8. The multiphase disc type hybrid excitation flux switching motor according to claim 1, wherein the outermost end face of the rotor (10) is used as a mirror image surface to obtain a magnetic circuit parallel type double-stator disc type hybrid excitation flux switching motor, a yoke part of the rotor (10) is removed, and a motor magnetic circuit passes through two stators (11) and the rotor to obtain a magnetic circuit series type double-stator disc type hybrid excitation flux switching motor.

9. The multiphase disc type hybrid excitation flux switching electric machine according to any one of claims 1 to 8, wherein the disc type hybrid excitation flux switching electric machine is an electric motor or a generator.