CN211830528U - Multiphase disc type hybrid excitation flux switching motor - Google Patents

Abstract

The utility model discloses a disk-type hybrid excitation magnetic flux switching motor, which is composed of a stator iron core, a rotor iron core, an armature winding, an excitation winding and a permanent magnet. The stator and the rotor are installed coaxially. There are 4*m*k*n stator magnetic conductive teeth on a single stator core, and m*q permanent magnets are arranged on the stator, which are evenly embedded outside the excitation slot. The rotor core has (2*m*k±1)*n magnetic conductive teeth evenly distributed along the circumference; m is the number of phases of the motor, n is the number of motor units, and k is any phase armature winding in each motor unit The number of pairs of concentrated armature windings in series, q is a positive integer (guaranteed that 4*k*n/q is a positive integer and less than 2*k*n). The motor provides excitation magnetic flux through permanent magnets and excitation windings. It not only has strong magnetic field adjustment ability, but also has a small axial size of the motor, which is suitable for applications in strict requirements for thin installations, such as electric vehicles, which require a wide speed regulation range. occasion.

Description

A multi-phase disc hybrid excitation flux switching motor

technical field

The utility model relates to a disk-type hybrid excitation magnetic flux switching motor, which belongs to the technical field of motor manufacturing.

Background technique

With the development of new energy technology, motors have been widely researched and applied as core components in rail transit, new energy vehicles and other fields. Since the armature current and the excitation current of the DC motor can be independently adjusted, the speed regulation characteristics when used as a motor and the output voltage stability when running as a generator are the most ideal among many motors. However, due to the existence of mechanical brushes and commutators in the structure of the DC motor, it has disadvantages such as frequent maintenance and poor reliability, which limits its application range. The AC induction motor has a simple structure, no brushes, easy maintenance, and high reliability. It is widely used in the field of general transmission, but the motor has poor speed regulation performance, low power factor and efficiency. The traditional permanent magnet brushless AC motor has developed rapidly in recent years due to the advantages of high power density and high power factor. The motor shaft is long, which limits applications in small spaces.

Therefore, a new type of disk-type permanent magnet flux switching motor has entered people's field of vision. The axial direction of this motor is short, the permanent magnets of the motor are all located on the stator side, and the rotor is only composed of iron cores, which not only greatly reduces the complexity of the motor, but also effectively enhances the heat dissipation of the permanent magnets, reducing the Risk of irreversible demagnetization of permanent magnets. The magnetic field of the motor cannot be adjusted, and the field weakening control technology is required to achieve high-speed operation during high-speed operation, which undoubtedly increases the complexity and cost of the system.

In recent years, many studies on disk-type hybrid excitation flux-switching motors have been carried out. The permanent magnets and the excitation are located on the stator side, which has a certain ability to adjust the magnetic field and is suitable for high-speed operation. Studies have shown that the magnetic field direction of the concentrated excitation winding in the same slot as the permanent magnet is the same or opposite to the magnetic field direction of the permanent magnet when the adjacent permanent magnets of the traditional disk-type hybrid excitation flux switching motor are oppositely magnetized, which affects the magnetic field direction to a certain extent. The excitation efficiency of the concentrated field winding. Moreover, the more permanent magnets, the worse the magnetic adjustment ability. When the excitation current is zero, the motor has a positioning torque.

SUMMARY OF THE INVENTION

Purpose of the utility model:

In view of the deficiencies existing in the prior art, the purpose of this utility model is to provide a kind of strong magnetic regulation ability, good speed regulation performance, reliable operation, no brushes, concentrated armature windings, concentrated excitation windings and permanent magnets all placed in the stator And can be independently controlled, the structure is simple, the cost is low, and the high-efficiency disk-type hybrid excitation magnetic flux switching motor is provided. By controlling the current of the DC concentrated excitation winding, the excitation magnetic field of the motor can be controlled, so as to ensure that the motor operates as a motor with high efficiency in a wide speed range, and as a generator, it can have a wider voltage regulation range; , since the magnetizing direction of the permanent magnet is along the tangential direction of the circumference, when the excitation current is zero, the permanent magnet magnetic field only forms a closed loop on the stator side, and the total magnetic flux of each phase winding is zero at this time, and the cogging torque is zero.

Technical solutions:

In order to achieve the above functions, the present utility model provides an improved disc type hybrid excitation magnetic flux switching motor, which is composed of a stator, a rotor, a concentrated armature winding, a concentrated excitation winding and a permanent magnet; The stator is composed of magnetic materials and has an air gap between them. The stator is provided with stator magnetic conductive teeth, slots between the stator magnetic conductive teeth, permanent magnets in some of the slots, and concentrated armatures on the stator magnetic conductive teeth. windings and concentrated field windings.

The number of magnetic conductive teeth of the stator is Ns=4*m*k*n; wherein, 2*m*k*n concentrated armature windings are wound on the stator magnetic conductive teeth in turn, and each concentrated armature winding is sleeved With two adjacent stator magnetic conductive teeth, the adjacent concentrated armature windings share a slot, and the slot where the concentrated armature windings are arranged is called the armature slot; the other 2*m*k*n slots are sequentially set with concentrated excitation Windings, each concentrated excitation winding is covered with two adjacent stator magnetic conductive teeth, and two adjacent concentrated excitation windings share or are separated by a slot, and the slot where the concentrated excitation winding is arranged is called the excitation slot; the stator is provided with a total of m*q permanent magnets are evenly embedded at the bottom of the excitation slot; the concentrated excitation windings in the slot are distributed on the axial outer side of the permanent magnet; the permanent magnets are evenly distributed, and the interval between every two permanent magnets is 4*k*n/q stator magnetic teeth;

The rotor has a cogged structure and is composed of magnetic conductive materials, and the number of magnetic conductive teeth of the rotor is Nr=(2*m*k±1)n;

Among them, m is the number of phases of the motor, n is the number of motor units, k is the number of concentrated armature winding pairs connected in series with any one phase concentrated armature winding in each motor unit, and q is a positive integer less than 2*k*n.

Further, any one-phase concentrated armature winding in each of the above-mentioned motor units is composed of k pairs of concentrated armature windings in series. From the first concentrated armature winding of any phase, k consecutively placed concentrated armature windings. Set to the same phase, then set k concentrated armature windings belonging to adjacent phases in turn, and arrange them in sequence according to the above arrangement, until all the motor units are arranged; 2k concentrated armature windings belonging to the same phase form k pairs of complementary concentrated power armature windings, in which the relative positions of the two concentrated armature windings in any pair of concentrated armature windings and the rotor differ by half the rotor pole pitch τ _s , corresponding to an electrical angle of 180 degrees, n motor units are arranged in sequence, different motor units The concentrated armature windings belonging to the same phase are connected in series or in parallel.

When every two concentrated excitation windings of the above-mentioned motor are separated by a slot, the magnetic fields generated by the concentrated excitation windings are in the same direction; when every two concentrated excitation windings share a slot, the magnetic fields generated by the adjacent two concentrated excitation windings are in opposite directions; each motor The concentrated excitation windings in the unit are connected in series to form a concentrated excitation winding unit, and the concentrated excitation winding units in the n motor units are connected in series or in parallel.

Further, the magnetization directions of all permanent magnets of the above-mentioned motor are along the same circumferential tangential direction; the magnetization direction of each permanent magnet is opposite to the magnetic field direction of the concentrated excitation winding located on its axial outer side. When the excitation current in the concentrated excitation winding is zero, there is only a permanent magnetic field in the motor, and the permanent magnetic field only forms an annular closed magnetic circuit in the stator part, and will not pass through the air gap and the rotor. The total magnetic flux is zero.

As a preference, the concentrated armature winding and the concentrated excitation winding are made of copper or superconducting materials, and the permanent magnets are made of rare earth materials such as ferrite or aluminum iron boron.

As a preference, the above-mentioned disk-type hybrid excitation magnetic flux switching motor can be operated as a motor or a generator.

Technical effect:

The utility model provides a disk-type hybrid excitation magnetic flux switching motor, wherein the concentrated armature winding, the concentrated excitation winding and the permanent magnet are all located on the stator side, and the rotor is a cogged structure composed of magnetically conductive materials, which is simple in structure and reliable. Sex is high. The concentrated armature winding and the concentrated excitation winding can be controlled separately, and the excitation magnetic field of the motor can be controlled by controlling the current of the DC concentrated excitation winding, which can adapt to the characteristics of the motor in a wide speed range, and can be used in the field of electric vehicles. speed, the motor can achieve high efficiency in a wide range; the permanent magnet can weaken the magnetic field of the motor stator yoke, reduce the magnetic field saturation of the motor, and increase the magnetic flux through the three-phase concentrated armature winding, effectively improving the concentrated excitation winding. Utilization and motor efficiency; the magnetizing direction of all permanent magnets in the motor is along the same circular tangent direction, when the excitation current is zero, the permanent magnetic field only forms a closed loop on the stator side, and the total magnetic flux of the three-phase concentrated armature windings is zero, the cogging torque is zero, so when the motor has no load, the excitation current is cut off, which can effectively reduce the torque ripple. Used as a motor, the motor has a wide range of magnetic field regulation, and is suitable for applications with a wide speed regulation range, such as electric vehicles.

Description of drawings

Below in conjunction with accompanying drawing and embodiment, the utility model is further described:

1 is a schematic diagram of the three-dimensional structure of the motor in Embodiment 1 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

2 is a schematic diagram of the axial structure of the motor stator of Embodiment 1 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

Fig. 3 is a flat-panel expanded view of the motor in Embodiment 1 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

4 is a schematic diagram of the three-dimensional structure of the motor in Embodiment 2 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

5 is a schematic diagram of the axial structure of the motor stator in Embodiment 2 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

FIG. 6 is an expanded view of the motor in Embodiment 2 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

7 is a schematic diagram of the three-dimensional structure of the motor in Embodiment 3 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

8 is a schematic diagram of the axial structure of the motor stator in Embodiment 3 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

FIG. 9 is a plane development view of the motor in Embodiment 3 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

10 is a schematic three-dimensional structure diagram of the motor in Embodiment 4 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

11 is a schematic diagram of the axial structure of the motor stator of Embodiment 4 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

Fig. 12 is a flat expanded view of the motor in Embodiment 4 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

13 is a schematic three-dimensional structure diagram of the motor in Embodiment 5 of a disk-type hybrid excitation magnetic flux switching motor according to the present invention;

14 is a schematic diagram of the axial structure of the motor stator in Embodiment 5 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

Fig. 15 is a plane development view of the motor in Embodiment 5 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

16 is a schematic three-dimensional structural diagram of the motor in Embodiment 6 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

Fig. 17 is a flat-panel expanded view of the motor in Embodiment 6 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

18 is a schematic three-dimensional structure diagram of a disk-type hybrid excitation magnetic flux switching motor according to Embodiment 7 of the present invention;

Fig. 19 is a flat-panel expanded view of the motor in Embodiment 7 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

20 is a schematic three-dimensional structure diagram of the motor in Embodiment 8 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

Fig. 21 is a flat-panel expanded view of the motor in Embodiment 8 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

22 is a schematic three-dimensional structure diagram of the motor in Embodiment 9 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

Figure 23 is a flat-panel expanded view of the motor in Embodiment 9 of a disk-type hybrid excitation magnetic flux switching motor of the present invention;

Among them, 10-rotor, 11-stator, 110-magnetic conductive teeth, 111-concentrated armature winding, 112-concentrated excitation winding, 113-permanent magnet.

Detailed ways

The utility model provides a disk-type hybrid excitation magnetic flux switching motor. In order to make the purpose, technical scheme and effect of the utility model clearer and clearer, the utility model is further described in detail with reference to the accompanying drawings and examples. It should be understood that the specific implementations described herein are only used to explain the present invention, but not to limit the present invention.

Example 1

Referring to FIG. 1 , a disk-type hybrid excitation magnetic flux switching motor of the present invention is composed of a stator 11, a rotor 10, a concentrated armature winding 111, a concentrated excitation winding 112 and a permanent magnet 113; the stator 11 and the rotor 10 are both It is made of magnetic conductive material and has an air gap; the stator 11 is provided with stator magnetic conductive teeth 110, there are slots between the stator magnetic conductive teeth 110, and permanent magnets 113 are arranged in part of the slots, and the stator magnetic conductive teeth 110 are arranged alternately. Concentrated armature winding 111 and concentrated field winding 112 . In the motor of this embodiment, m=3, n=1, k=1, q=1, where m is the number of phases of the motor, n is the number of motor units, and k is the concentrated armature of one phase in each stator motor unit The logarithm of the concentrated armature windings 111 connected in series with the windings, q is a coefficient that determines the number of permanent magnets, and the value of q needs to make 4*k*n/q a positive integer. That is, the motor is a three-phase motor with three phases A, B, and C, and includes one motor unit. Each motor unit has k=1 pair of concentrated armature windings, and the number of magnetic conductive teeth 110 of the stator 11 is Ns =4*m*n*k=12; the number of concentrated armature windings 111 provided with the magnetic conductive teeth in turn is 2*m*n*k=6, and each concentrated armature winding 111 spans two magnetic conductive teeth 110 , the adjacent concentrated armature windings 111 share one slot; the remaining 2*m*k*n=6 slots are sequentially set with 2*m*k*n=6 concentrated excitation windings 112, and each concentrated excitation winding 112 spans The adjacent two magnetic conductive teeth 110 share a slot for each two concentrated excitation windings 112, and the magnetic fields generated by the adjacent two concentrated excitation windings 112 are in opposite directions; the number of permanent magnets 113 on the stator 11 is m*q= 3. It is evenly embedded in the axial inner side of the excitation slot. The interval between every two permanent magnets is 4*k*n/q=4 stator magnetic conductive teeth 110. And the direction of the magnetic field generated by the concentrated excitation winding in the excitation slot is opposite. The rotor 10 is of cogging type, and the number of rotor magnetic conductive teeth is Nr=(2*m*k±1)n, when k=1, m=3, n=1, Nr can be 5, 7, the present The embodiment takes Nr=5; since k=1 and n=1 in this embodiment, the logarithm of the concentrated armature winding 111 connected in series with any phase winding in the motor unit is k=1 (as shown in FIG. 2 , the stator shaft In the schematic diagram of the structure, A1 and A2 in the motor, starting from the first concentrated armature winding of any phase (such as from A1), there are k=1 adjacent concentrated armature windings belonging to the same phase. Then, k=1 concentrated armature windings 111 belonging to adjacent phases (ie B1 and C1 in Fig. 3) are set in sequence. According to the above arrangement, the arrangement of the three-phase concentrated armature windings in the motor is: A1-B1 -C1-A2-B2-C2. The relative positions of k=1 concentrated armature windings 111 belonging to the same phase and the secondary differ by half the rotor pole pitch, which corresponds to an electrical angle of 180 degrees, as shown in Figure 3 with the two concentrated armature windings A1 and A2 in phase A. At this time, the concentrated armature winding A1 spans two magnetic conductive teeth, and its center line is facing the center line of the rotor 10 teeth, while the center line of the concentrated armature winding A2 is facing the center line of the rotor 10 slot. The relative position of the rotor 10 is different by half the rotor pole pitch, which is 180 degrees electrical angle in space.

If the influence of the permanent magnets 113 is not considered, since the magnetic fields generated by the adjacent concentrated excitation windings 112 are in opposite directions, rationally setting the winding methods of the concentrated armature windings A1 and A2 on the stator 11 can make the back electromotive force generated in the windings superimposed on each other, and Complementarity is exhibited; in the process of rotating the rotor 10 for one electrical cycle (ie, rotating one pole pitch of the stator 10), the concentrated armature windings A1 and A2 have differences on the magnetic circuit; in the position shown in Figure 3, if it is assumed that this time The flux linkage in the concentrated armature winding A1 is approximately zero, which is called the first equilibrium position, while the position of the concentrated armature winding A2 and A1 relative to the rotor is different, with a difference of half the rotor 10 pole pitch. At this time, in the concentrated armature winding A2 The flux linkage of is also approximately zero, so this position is called the second equilibrium position. When the rotor 10 rotates counterclockwise (in FIG. 3 , the rotor 10 is from left to right) for one electrical cycle, the flux linkage amplitude variation process in the concentrated armature winding A1 is: the first equilibrium position—the positive maximum amplitude ——The second equilibrium position——the negative maximum amplitude value——the first equilibrium position; and the change process of the flux linkage amplitude in the concentrated armature winding A2 is: the second equilibrium position——the positive maximum amplitude value——the first equilibrium position - Negative Maximum Amplitude - Second Equilibrium Position. The changing trends of the flux linkages in the concentrated armature windings 111 of A1 and A2 are symmetrical and complementary. After the concentrated armature windings A1 and A2 are connected in series to form an A-phase winding, the harmonic components of the counter-EMF generated by them cancel each other out, and the obtained counter-EMF has good sinusoidality. It has good sine, thus reducing the torque ripple, and is very suitable for brushless AC (BLAC) control; B and C two phases also have the characteristics of A phase, and the phase difference between the three phases is 120° electrical angle.

If the current flowing into the concentrated excitation winding 112 is zero, and only the action of the permanent magnets 113 is considered, since the magnetization directions of all the permanent magnets 113 are along the same circumferential tangent direction, the permanent magnet magnetic field only forms a closed magnetic circuit in the stator 11 . , does not pass through the air gap and the rotor 10, so no electromagnetic torque is generated. As shown in Figure 3, due to the existence of the yoke, most of the magnetic circuit of the motor passes through the yoke of the slot where the permanent magnet 113 is located. Taking PM1 as an example, the magnetic circuit of the permanent magnetic field can be described as: PM1—PM1 adjacent The stator magnetic conductive teeth of the yoke part - the other stator tooth adjacent to PM1 - return to PM1. Since the magnetization direction of the permanent magnet 113 is magnetized in the circumferential direction, taking the permanent magnet PM1 as a reference, a small part of the permanent magnet magnetic circuit can be described as: PM1—the stator magnetic conductive teeth adjacent to PM1—yoke part— The stator magnetic conductive teeth adjacent to PM2 - PM2 - the stator magnetic conductive teeth adjacent to PM2 - the yoke part - the stator magnetic conductive teeth adjacent to PM3 - PM3 - the stator magnetic conductive teeth adjacent to PM3 The magnetic teeth - the yokes - go back to PM1 and finally form a closed magnetic circuit. When the permanent magnet magnetic field passes through the permanent magnet 113, it will inevitably pass through the concentrated armature winding 111 around the permanent magnet 113. For example, when the permanent magnetic field passes through PM2, it will inevitably pass through the concentrated armature winding A2, but due to the air gap The magnetic resistance is large, and the permanent magnet magnetic field will not enter the rotor 10 through the air gap, so the permanent magnetic field passing through and passing through the concentrated armature winding A2 is the same, and finally the permanent magnet flux linkage in the concentrated armature winding A2 is zero; For other concentrated armature winding A1 of phase A, since the permanent magnetic flux linkage only passes through the stator yoke outside the winding, it will not penetrate or exit the concentrated armature winding A1, and its permanent magnetic flux linkage is also zero. . This phenomenon does not change with the rotation of the rotor 10 , so the flux linkage of the A-phase is always zero during the rotation of the rotor 10 , and no opposite potential is generated. Due to the uniform distribution of the permanent magnets 113 and the symmetry of the three phases, the B and C phases also have the characteristics of the A phase, which effectively eliminates the fact that the traditional hybrid excitation flux switching motor cannot be completely demagnetized when a short-circuit fault occurs, resulting in excessive short-circuit current. big disadvantage.

When considering the magnetic field generated by the permanent magnet 113 and the concentrated excitation winding 112 at the same time, since the direction of magnetization of the permanent magnet 113 is opposite to the direction of the magnetic field generated by the concentrated excitation winding 112 located on the outer side of the permanent magnet, the specific performance is as follows: on the one hand, in the stator In the yoke, the permanent magnetic field and the electric excitation magnetic field are in opposite directions. When the magnetic field saturation of the stator 11 is too high, the permanent magnetic field can effectively reduce the magnetic field saturation of the stator yoke and effectively reduce the iron loss of the motor. The magnetic field can reduce the saturation degree of the magnetic field of the stator magnetic conductive teeth 110 , thereby indirectly increasing the excitation flux linkage in the three-phase winding, and therefore, can effectively improve the back EMF of the three-phase winding.

When the motor needs to run at high torque, increase the magnitude of the DC excitation current, thereby enhancing the excitation magnetic field strength of the motor, which can improve the excitation efficiency of the motor; when the torque is small, the DC excitation current can be increased, reducing the torque and improving the efficiency of the motor .

Example 2

Figure 4 shows a disk-type hybrid excitation flux switching motor. In this embodiment, m=3, n=2, k=1, and q=1. The difference from the motor of the first embodiment is that the number of motor units on the stator 11 of this embodiment is n=2. That is, the motor is a three-phase motor with three phases A, B, and C, including two motor units, each motor unit has k=1 pair of concentrated armature windings, and the number of magnetic conductive teeth 110 of the stator 11 is Ns =4*m*n*k=24; the number of concentrated armature windings 111 provided with the magnetic conductive teeth in turn is 2*m*n*k=12, and each concentrated armature winding 111 spans two magnetic conductive teeth 110 , the adjacent concentrated armature windings 111 share one slot; the remaining 2*m*k*n=12 slots are sequentially set with 2*m*k*n=12 concentrated excitation windings 112, and each concentrated excitation winding 112 spans The adjacent two magnetic conductive teeth 110 share one slot for each two concentrated excitation windings 112, and the magnetic fields generated by the adjacent two concentrated excitation windings 112 are opposite in direction; the concentrated excitation windings in the first motor unit in the stator 11 are connected in series to form the first motor. A concentrated excitation winding unit, the first concentrated excitation winding unit and the second concentrated excitation winding unit can be connected in series or in parallel to form a concentrated excitation winding; the number of permanent magnets 113 on the stator 11 is m*q=3, which are evenly embedded in the excitation On the inner side of the slot axis, the interval between every two permanent magnets is 4*k*n/q=8 stator magnetic conductive teeth 110. The magnetization directions of all permanent magnets 113 are along the same circumferential tangential direction, and are in line with the excitation slot where they are located. The magnetic field produced by the concentrated field winding in the The rotor 10 is of cogging type, and the number of rotor magnetic conductive teeth is Nr=(2*m*k±1)n, when k=1, m=3, n=2, Nr can be 10, 14, the present The embodiment takes Nr=14;

Since k=1 and n=2 in this embodiment, the logarithm of the concentrated armature windings 111 connected in series with any phase winding in the motor unit is k=1 (as shown in the schematic diagram of the axial structure of the stator in FIG. 5 , the first motor A1 and A2 in the unit or A3 and A4 in the second motor unit), from the first concentrated armature winding of any phase (such as from A1), there are k = 1 adjacent concentrated armatures The windings belong to the same phase, and then k=1 concentrated armature windings 111 belonging to adjacent phases (ie B1 and C1 in FIG. 6 ) are arranged in sequence. According to the above arrangement, the three-phase concentrated armatures in the first motor unit are The winding arrangement is: A1-B1-C1-A2-B2-C2. The relative positions of the 2k=2 concentrated armature windings 111 belonging to the same phase and the secondary differ by half the rotor pole pitch, corresponding to an electrical angle of 180 degrees. At this time, the concentrated armature winding A1 spans two magnetic conductive teeth, and its center line is facing the center line of the rotor 10 teeth, while the center line of the concentrated armature winding A2 is facing the center line of the rotor 10 slot. The relative position of the rotor 10 is different by half the rotor pole pitch, which is 180 degrees electrical angle in space.

If the influence of the permanent magnets 113 is not considered, since the magnetic fields generated by the adjacent concentrated excitation windings 112 are in opposite directions, rationally setting the winding methods of the concentrated armature windings A1 and A2 on the stator 11 can make the back electromotive force generated in the windings superimposed on each other, and Complementarity is exhibited; in the process of rotating the rotor 10 for one electrical cycle (ie, rotating one pole pitch of the stator 10), the concentrated armature windings A1 and A2 have differences on the magnetic circuit; in the position shown in Figure 3, if it is assumed that this time The flux linkage in the concentrated armature winding A1 is approximately zero, which is called the first equilibrium position, while the positions of the concentrated armature winding A2 and A1 relative to the rotor are different, with a difference of half the rotor 10-pole distance. The flux linkage is also approximately zero, so this position is called the second equilibrium position. During the counterclockwise rotation of the rotor 10 (in FIG. 6 , the rotor 10 is from left to right) for one electrical cycle, the change process of the flux linkage amplitude in the concentrated armature winding A1 is: the first equilibrium position—the positive maximum amplitude ——The second equilibrium position——the negative maximum amplitude value——the first equilibrium position; and the change process of the flux linkage amplitude in the concentrated armature winding A2 is: the second equilibrium position——the positive maximum amplitude value——the first equilibrium position - Negative Maximum Amplitude - Second Equilibrium Position. The changing trends of the flux linkages in the concentrated armature windings of A1 and A2 are symmetrical and complementary. After the concentrated armature windings A1 and A2 are connected in series to form an A-phase winding, the harmonic components of the counter-EMF generated by them cancel each other out, and the obtained counter-EMF has good sinusoidality. Similarly, the concentrated armature windings A3 and A4 in the second motor unit also have the characteristics of the first motor unit. Therefore, the concentrated armature windings A3 and A4 also have complementary characteristics. When the concentrated armature windings A1, A2, A3 and A4 in the two motor units are connected in series to form the A-phase winding of the stator 11, the high-order harmonics of the back EMF generated in the concentrated windings cancel each other out and have good sine, so The torque ripple is reduced, and it is very suitable for brushless AC (BLAC) control; the B and C phases also have the characteristics of the A phase, and the phase difference between the three phases is 120° electrical angle.

If the current flowing into the concentrated excitation winding 112 is zero, and only the action of the permanent magnets 113 is considered, since the magnetization directions of all the permanent magnets 113 are along the same circumferential tangent direction, the permanent magnet magnetic field only forms a closed magnetic circuit in the stator 11 . , does not pass through the air gap and the rotor 10, so no electromagnetic torque is generated. As shown in Figure 6, due to the existence of the yoke, most of the magnetic circuit of the motor passes through the yoke of the slot where the permanent magnet 113 is located. Taking PM1 as an example, the magnetic circuit of the permanent magnetic field can be described as: PM1—PM1 adjacent The stator tooth - the stator yoke - the other stator tooth adjacent to PM1 - back to PM1. Since the permanent magnets are magnetized along the tangential direction of the same circumference, a part of the magnetic circuit forms a loop along the circumference of the yoke of the stator 11. If PM1 is used as a reference, the magnetic circuit of the permanent magnetic field can be described as: PM1—the stator adjacent to PM1 Magnetic teeth - stator yoke - stator magnetic teeth adjacent to PM2 - PM2 - stator magnetic teeth adjacent to PM2 - stator yoke - stator magnetic teeth adjacent to PM3 - PM3 - The stator magnetic conductive teeth adjacent to PM3 - the stator yoke - the permanent magnets adjacent to PM1 - return to PM1, and pass through the remaining permanent magnets 113 in sequence according to this path, finally forming a closed magnetic circuit. When the permanent magnet magnetic field passes through the permanent magnet 113, it will inevitably pass through the concentrated armature winding 111 around the permanent magnet 113. For example, when the permanent magnetic field passes through PM2, it will inevitably pass through the concentrated armature winding A12, but due to the air gap The magnetic resistance is large, and the permanent magnet magnetic field will not enter the rotor 10 through the air gap, so the permanent magnetic field passing through and passing through the concentrated armature winding A2 is the same, and finally the permanent magnetic flux linkage in the concentrated armature winding A2 is almost zero; For the other concentrated armature windings A1, A3 and A4 of phase A, since the permanent magnet flux only passes through the stator yoke outside the winding, it will not penetrate or exit the concentrated armature windings A1, A3 and A4. Their permanent magnetic flux linkage is also zero. This phenomenon does not change with the rotation of the rotor 10 , so the flux linkage of the A-phase is always zero during the rotation of the rotor 10 , and no opposite potential is generated. Since the permanent magnets 113 are evenly distributed and the three phases are symmetrical, the B and C phases also have the characteristics of the A phase. Therefore, the present embodiment has the same characteristics as the first embodiment.

Example 3

Figure 7 shows a disk-type hybrid excitation flux switching motor. In this embodiment, m=3, n=2, k=1, and q=2. The difference from the motor in Embodiment 2 is that the number of permanent magnets 113 on the stator 11 of this embodiment is m*q=6, which are evenly embedded in the axial interior of the excitation slot, and the interval between every two permanent magnets is 4*k* n/q=4 stator magnetic conductive teeth 110 . The magnetization directions of all the permanent magnets 113 are along the same circumferential tangent direction, and are opposite to the magnetic field directions generated by the concentrated excitation windings in the excitation slots where they are located.

In this embodiment, as shown in FIG. 8 , the number and arrangement of the motor windings are the same as those of the second embodiment, and the flux linkage change and back electromotive force in the three-phase windings have the same characteristics as those of the second embodiment. The number of permanent magnet blocks is doubled compared to that of the motor in Example 2, and m*q=6 permanent magnets on the stator 11 are evenly distributed and symmetrical to each other. Since the magnetizing direction of the permanent magnets 113 in the motor of this embodiment has the same characteristics as that of the motor of Embodiment 1, as shown in FIG. 9 , due to the existence of the slot yoke where the permanent magnets are located, most of the magnetic field passes through the yoke to PM1 For example, it can be described as: PM1—PM1 is adjacent to stator magnetic conductive teeth 110—yoke part—PM1 is adjacent to another stator magnetic conductive tooth 110—PM1. The magnetic circuits of other permanent magnets 113 are similar to PM1. A part of the magnetic circuit of the permanent magnetic field can still be described as: PM1 - stator magnetic conductive teeth 110 adjacent to PM1 - stator yoke - stator magnetic conductive teeth 110 adjacent to PM2 - permanent magnet PM2, and according to This path passes through the remaining permanent magnets 113 in turn, and finally forms a closed magnetic circuit. When the permanent magnet magnetic field passes through the permanent magnet 113, it will inevitably pass through the concentrated armature winding 111 around the permanent magnet 113. For example, when the permanent magnetic field passes through PM1 or PM4, it will inevitably pass through the concentrated armature winding B1 or B3. However, due to the large air-gap reluctance, the permanent magnet magnetic field will not enter the rotor 10 through the air gap, so the permanent magnetic field passing through and passing through the concentrated armature winding B1 or B3 is the same, and the final concentrated armature winding B1 or B3 will have the same permanent magnetic field. The permanent magnetic flux linkage is almost zero; for the other concentrated armature windings B2 and B4 of phase B, since the permanent magnetic flux linkage only passes through the stator yoke part outside the winding, it will not penetrate into or out of the concentrated armature winding. B2 and B4, their permanent magnet flux linkages are also zero. This phenomenon does not change with the rotation of the rotor 10. During the rotation of the rotor 10, the flux linkage of the A-phase is always zero, and no opposite potential is generated. Since the permanent magnets 113 are evenly distributed and the three phases are symmetrical, the A and C phases also have the characteristics of the B phase. Therefore, the present embodiment has the same characteristics as the second embodiment.

Example 4

Figure 10 shows a disk-type hybrid excitation flux switching motor. In this embodiment, m=3, n=1, k=2, and q=1. The difference from the motor in Embodiment 1 is that in this embodiment, the number of pairs of concentrated armature windings 111 connected in series with each phase of concentrated armature windings in each motor unit is k=2. That is, the motor is a three-phase motor with three phases of A, B, and C, including one motor unit, each motor unit has k=2 pairs of concentrated armature windings, and the number of magnetic conductive teeth 110 of the stator 11 is Ns =4*m*n*k=24; the number of concentrated armature windings 111 provided with the magnetic conductive teeth in turn is 2*m*n*k=12, and each concentrated armature winding 111 spans two magnetic conductive teeth 110 , the adjacent concentrated armature windings 111 share one slot; the remaining 2*m*k*n=12 slots are sequentially set with 2*m*k*n=12 concentrated excitation windings 112, and each concentrated excitation winding 112 spans The adjacent two magnetic conductive teeth 110 share one slot for each two concentrated excitation windings 112, and the magnetic fields generated by the adjacent two concentrated excitation windings 112 are opposite in direction; the concentrated excitation windings in the first motor unit in the stator 11 are connected in series to form the first motor. A concentrated excitation winding unit, the first concentrated excitation winding unit and the second concentrated excitation winding unit can be connected in series or in parallel to form a concentrated excitation winding; the number of permanent magnets 113 on the stator 11 is m*q=3, which are evenly embedded in the excitation On the inner side of the slot axis, the interval between every two permanent magnets is 4*k*n/q=8 stator magnetic conductive teeth 110. The magnetization directions of all permanent magnets 113 are along the same circumferential tangential direction, and are in line with the excitation slot where they are located. The direction of the magnetic field generated by the concentrated excitation winding 112 is opposite. The rotor 10 is of cogging type, and the number of rotor magnetic conductive teeth is Nr=(2*m*k±1)n, when k=1, m=3, n=2, Nr can be 11, 13, the present In the embodiment, Nr=13.

Since k=2 and n=1 in this embodiment, the logarithm of the concentrated armature windings 111 connected in series with any phase winding in the motor unit is k=2 (as shown in the schematic diagram of the axial structure of the stator as shown in FIG. A11 and A22), starting from the first concentrated armature winding of any phase (such as from A11), there are k=2 adjacent concentrated armature windings belonging to the same phase, and then set in turn to belong to the adjacent Phase k=2 concentrated armature windings 111 (ie B11 and C12 in Figure 12), according to the above arrangement, the arrangement of the three-phase concentrated armature windings in the motor unit is: A11-A12-B11-B12- C11-C12-A21-A22-B21-B22-C21-C22. The relative positions of the 2k=4 concentrated armature windings 111 belonging to the same phase and the secondary differ by half the rotor pole pitch, corresponding to an electrical angle of 180 degrees, as shown in Fig. At this time, the concentrated armature winding A11 spans the two magnetic conductive teeth, and its center line is facing the center line of the rotor 10 teeth, while the center line of the concentrated armature winding A21 is facing the center line of the rotor 10 slot. The relative position of the rotor 10 is different by half the rotor pole pitch, which is 180 degrees electrical angle in space. Since the relative positions of A11 and A12, A21 and A22 and the rotor 10 are relatively close, when the concentrated windings A11, A12, A21 and A22 are connected in series to form the A-phase winding, the amplitude of the back EMF of the A-phase winding is slightly smaller than that of the concentrated windings A11, A12, A21 and A22. Four times the amplitude of the A22 fundamental. The B-phase and C-phase windings have the same characteristics. Therefore, the present embodiment has the same characteristics as the first embodiment.

Example 5

Figure 13 is also a disk-type hybrid excitation flux switching motor. In this embodiment, m=5, n=1, k=1, q=1, that is, the motor is a five-phase motor, the stator 11 includes one motor unit, and each motor unit has k=1 pair of centralized power For the armature winding, the number of magnetic conductive teeth 110 on the stator 11 is Ns=4*m*n*k=20; the number of concentrated armature windings 111 on the magnetic conductive teeth is 2*m*n*k=10 , each concentrated armature winding 111 straddles two magnetic conductive teeth 110, and the adjacent concentrated armature windings 111 share a slot; the remaining 2*m*k*n=10 slots are sequentially set with 2*m*k*n =10 concentrated excitation windings 112, each concentrated excitation winding 112 spans two adjacent magnetic conductive teeth 110, every two concentrated excitation windings 112 share a slot, and the magnetic fields generated by the adjacent two concentrated excitation windings 112 are opposite in direction; the stator In 11, the concentrated excitation windings in the first motor unit are connected in series to form a first concentrated excitation winding unit, and the first concentrated excitation winding unit and the second concentrated excitation winding unit can be connected in series or in parallel to form a concentrated excitation winding; the stator 11 permanent magnet 113 The number of blocks is m*q=5, which are evenly embedded in the axial inner side of the excitation slot, and the interval between each two permanent magnets is 4*k*n/q=4 stator magnetic conductive teeth 110. All permanent magnets 113 are magnetized The directions are all along the same circular tangent direction, and are opposite to the magnetic field direction generated by the concentrated excitation winding in the excitation slot. The rotor 10 is a cogged structure composed of magnetic conductive materials, and the number of magnetic conductive teeth of the rotor is Nr=(2*m*k±1)n. When k=1, m=5, and n=1, Nr can be are 9 and 11, and Nr=11 is taken in this embodiment. The logarithm of the concentrated armature windings 111 connected in series to any phase winding in the motor in this embodiment is k=1. As shown in Figure 14, the concentrated armature winding of phase A is composed of two concentrated armature windings A1 and A2 connected in series. The concentrated armature winding A1 spans the two magnetic conductive teeth 110, and its center line is facing the center of the rotor 10 teeth. The center line of the concentrated armature winding A2 is directly opposite to the center line of the rotor 10 slot, and the relative position between the two and the rotor 10 differs by half the rotor pole pitch, which is 180 degrees electrical angle in space. Therefore, the motor also has the characteristics of complementary magnetic circuits, and the high-order harmonics of the back EMF generated in the windings of each phase cancel each other out, and the final opposite EMF obtained has a good sine.

The magnetization direction of the permanent magnets 113 in the motor of this embodiment also has the same characteristics as the motor of the first embodiment, and the permanent magnet magnetic field only forms a closed magnetic circuit in the stator 11 . As shown in FIG. 15 , due to the existence of the yoke of the slot where the permanent magnet 113 is located, most of the magnetic circuits of the permanent magnet 113 only pass through the adjacent magnetic guide teeth 110 and the yoke of the slot where the permanent magnet 113 is located. Taking PM1 as an example, It can be described as: PM1—PM1 adjacent stator magnetic conductive teeth 110—yoke portion—PM1 adjacent to another magnetic conductive tooth—PM1. A small part of the magnetic circuit of the permanent magnetic field can still be described as: PM1 - stator magnetic conductive teeth adjacent to PM1 - stator yoke - stator magnetic conductive teeth adjacent to PM2 - PM2, and follow this path in turn Through the remaining permanent magnets, a closed magnetic circuit is finally formed. When the permanent magnet magnetic field passes through the permanent magnet PM1, it will inevitably pass through the concentrated armature winding B1. However, due to the large reluctance of the air gap, the permanent magnetic field will not enter the rotor 10 through the air gap, so it penetrates into and out of the concentrated armature. The permanent magnetic field of winding B11 is the same, and the permanent magnetic flux linkage in the final concentrated armature winding B11 is almost zero; for other concentrated armature windings B2 of phase B, since the permanent magnetic flux linkage only passes through the stator outside the winding 11 The yoke part does not penetrate into or out of the concentrated armature winding A2, and their permanent magnet flux linkage is also zero. This phenomenon does not change with the rotation of the rotor 10. During the rotation of the rotor 10, the flux linkage of the A-phase is always zero, and no opposite potential is generated. Due to the uniform distribution of the permanent magnets 113, the B, C, D, and E phases also have the characteristics of the A phase. Therefore, the motor of this embodiment also has the characteristics of the motor of the present invention.

Example 6

Fig. 16 is a disk-type dual-stator hybrid excitation flux switching motor. This embodiment is obtained symmetrically along the outer end face of the rotor 10 from Example 2. It is a magnetic circuit parallel type hybrid excitation flux switching motor. The two stators 11 of the motor can be independently It can also work in parallel or in series. In this embodiment, m=3, n=2, k=1, q=1, and the number of motor units on a single stator 11 in this embodiment is n=2. That is, the motor is a three-phase motor with three phases of A, B, and C, including two motor units, each motor unit has k=1 pair of concentrated armature windings, and the number of magnetic conductive teeth 110 of a single stator 11 is Ns=4*m*n*k=24; the number of concentrated armature windings 111 provided with the magnetic conductive teeth in turn is 2*m*n*k=12, and each concentrated armature winding 111 spans two magnetic conductive teeth 110, the adjacent concentrated armature windings 111 share one slot; the remaining 2*m*k*n=12 slots are sequentially set with 2*m*k*n=12 concentrated excitation windings 112, and each concentrated excitation winding 112 Across two adjacent magnetic conductive teeth 110, every two concentrated excitation windings 112 share a slot, and the magnetic fields generated by the adjacent two concentrated excitation windings 112 are opposite in direction; the concentrated excitation windings in the first motor unit in a single stator 11 are connected in series The first concentrated excitation winding unit is formed, and the first concentrated excitation winding unit and the second concentrated excitation winding unit can be connected in series or in parallel to form a concentrated excitation winding; the excitation units on the two stators can be connected in parallel or in series, or can be controlled independently; the single The number of permanent magnets 113 on the stator 11 is m*q=3, which are evenly embedded in the axial inner side of the excitation slot, and the interval between every two permanent magnets is 4*k*n/q=8 stator magnetic conductive teeth 110, all the The magnetization directions of the permanent magnets 113 are all along the same circumferential tangent direction, and are opposite to the magnetic field direction generated by the concentrated excitation windings in the excitation slots where they are located. The rotor 10 is of cogging type, and the number of rotor magnetic conductive teeth is Nr=(2*m*k±1)n, when k=1, m=3, n=2, Nr can be 10, 14, the present The embodiment takes Nr=14; since this embodiment is obtained symmetrically in Embodiment 2, the characteristics of the motor have not changed, the two stator 11 units can be controlled independently, and the in-phase concentrated armature winding 111 can also be connected in series or in parallel. Form a phase winding to control.

When the excitation current is zero, the magnetic field in the motor is the same as that in Embodiment 2, and a loop is formed only on the stator 11 side. Regardless of the influence of the permanent magnets 113 , if both the concentrated excitation windings 112 of the two stators 11 are supplied with positive currents, it can be concluded that the magnetic circuits of the two stators 11 in the rotor 10 are opposite. In order to improve the efficiency of the motor, a negative excitation current is introduced into the concentrated excitation winding 112 in the symmetrically obtained stator 11. Since the magnetic field directions of the permanent magnets 113 and the concentrated excitation windings in the same slot are opposite, the symmetrically obtained permanent magnets on the stator 11 The magnetization direction on 113 is the same, as shown in Figure 17. Since the two stators can work alone or in series or in parallel, the number of permanent magnets 113 on the stator 11 obtained by symmetry can be the same as or different from the original stator 11. The direction of the slot excitation magnetic field is opposite, and 4*n*k/q is guaranteed to be a positive integer.

Example 7

Figure 18 shows a dual-stator hybrid excitation flux switching motor. This embodiment is symmetrical along the outer end surface of the rotor from Embodiment 2. It is a magnetic circuit series-type hybrid excitation flux switching motor. The difference from Embodiment 6 is that the rotor 10 Without the yoke, in order to satisfy the direction of the excitation magnetic field of the permanent magnet 113 and the same slot opposite, the magnetization direction of the permanent magnet 113 is opposite to the magnetization direction of the original stator 11, as shown in FIG. 19 . When the excitation current is zero, the permanent magnet magnetic field has the same characteristics as those of Embodiment 2 and Embodiment 6. When the excitation current is applied, the excitation magnetic circuit is different from the embodiment 6, and the excitation magnetic circuit forms a loop through the two stators 11 and the rotor 10, which is different from the embodiment 6, which forms a loop between a single stator 11 and the rotor 10, so it is called It is a series magnetic circuit type hybrid excitation flux switching motor. Magnetic circuit series motors generally work on both sides at the same time. The number of permanent magnets 113 on the stators 11 on both sides can be the same or different. The core is to ensure that the direction of the permanent magnet magnetic field is opposite to the direction of the excitation magnetic field of the slot where it is located, and to ensure that 4*n*k/q is a positive integer.

Example 8

FIG. 20 shows a dual-rotor hybrid excitation magnetic flux switching motor, which is obtained symmetrically along the outer end face of the stator 11 from the second embodiment. As shown in Fig. 21, in order to make the magnetic field direction generated in the yoke part of the stator 11 the same, the current direction of the concentrated excitation winding 112 on one side is changed to be symmetrical, so that the magnetic field direction of the stator 11 is the same, at this time, the magnetic circuit parallel type is used. Hybrid excitation flux switching motor. The directions of the concentrated armature windings 111 and the permanent magnets 113 remain unchanged. The single-sided motor has the same characteristics as the second embodiment, and the concentrated armature windings on both sides can be operated in series or in parallel. The motor has the same characteristics as the second embodiment. When the excitation current in the motor is zero, due to the existence of the stator yoke, taking PM1 as an example, the permanent magnet magnetic circuit in the motor can be described as: PM1—PM1 The adjacent magnetic conductive teeth 110—yoke—PM1 Another An adjacent magnetic conductive tooth 110 - back to PM1. Since the magnetization direction of the permanent magnets 113 is along the same circumferential direction, a part of the permanent magnet magnetic circuit can be described as: PM1 - PM1 adjacent magnetic conductive teeth 110 - yoke part - PM2 adjacent magnetic conductive teeth - PM2 - -PM2 another adjacent magnetic conductive tooth 110 - yoke - PM3 adjacent magnetic conductive tooth 110 - PM3 - PM3 another magnetic conductive tooth - yoke - PM1 another magnetic conductive tooth - back PM1. Therefore, the present embodiment has the same characteristics as the second embodiment.

Example 9

FIG. 22 is a dual-rotor hybrid excitation magnetic flux switching motor, which is obtained symmetrically along the outer end surface of the stator 11 from the second embodiment. As shown in Figure 23, it is a magnetic series-type hybrid excitation flux switching motor. The symmetrically obtained winding structure is the same as that of the original stator 11. In order to satisfy the fact that the magnetic field direction of the permanent magnet 113 is opposite to the direction of the excitation magnetic field of the slot, the magnetizing direction of the symmetrically obtained permanent magnet 113 is opposite. Since the magnetic circuits of the upper and lower parts of the motor are connected in series, the horizontal component of the magnetic field in the stator 11 is very small, so the yokes of all the slots can be removed. When the current passing through the concentrated excitation winding 112 is zero, the permanent magnet magnetic circuits on the upper and lower sides are connected in series. Taking PM3 and PM6 as examples, it can be described as: PM3—the magnetic conductive teeth 110 adjacent to PM3—PM6— PM6 Adjacent Magnetic Conductive Teeth 110 - Back to PM. When a forward current is passed into the concentrated excitation winding 112, regardless of the influence of the permanent magnets 113, the magnetic circuit of the excitation magnetic field enters the stator through the upper and lower rotors and the air gap, which can be described as: stator magnetic conductive teeth 110—upper air Gap - upper rotor - upper air gap - another stator magnetic conductive tooth 110 - lower air gap - lower rotor - lower air gap - back to the stator magnetic conductive tooth. Therefore, the present embodiment has the same characteristics as the second embodiment.

The basic principles and main features of the present invention and the advantages of the present invention are shown and described above. It should be understood by those skilled in the art that the present invention is not limited by the above-mentioned embodiments. The above-mentioned embodiments and descriptions only illustrate the principle of the present invention. Without departing from the spirit and scope of the present invention, the present invention The new model will also have various changes and improvements, which all fall within the scope of the claimed invention. The claimed scope of the present invention is defined by the appended claims and their equivalents.

Claims (9)

1. A multi-phase disc type hybrid excitation flux switching motor is characterized by comprising a stator (11), a rotor (10), a concentrated armature winding (111), a concentrated excitation winding (112) and a permanent magnet (113); the stator (11) and the rotor (10) are both made of magnetic conductive materials, an air gap is formed between the stator and the rotor, stator magnetic guide teeth (110) are arranged on the stator (11), grooves are formed between the stator magnetic guide teeth (110), permanent magnets (113) are arranged in part of the grooves, and concentrated armature windings (111) and concentrated excitation windings (112) are arranged on the stator magnetic guide teeth (110); the number of the magnetic conduction teeth (110) on the stator (11) is all Ns (4 x m k n); 2 m x k x n concentrated armature windings (111) are sequentially wound on the magnetic conduction teeth (110) of the stator (11), each concentrated armature winding (111) is sleeved on two adjacent magnetic conduction teeth (110), the adjacent concentrated armature windings (111) share one groove, and the groove provided with the concentrated armature winding (111) is called an armature groove; concentrated excitation windings (112) are sequentially arranged in the other 2 m k n slots, each concentrated excitation winding (112) is sleeved with two adjacent stator magnetic conduction teeth (110), two adjacent concentrated excitation windings (112) share or are separated by one slot, and the slots provided with the concentrated excitation windings (112) are called excitation slots; the stator (11) is provided with m × q permanent magnets (113) which are uniformly embedded outside the excitation slot; concentrated excitation windings (112) in the slots are distributed on the axial outer side of the permanent magnet (113); the permanent magnets (113) are uniformly distributed, and 4 x k x n/q stator magnetic conduction teeth (110) are arranged between every two permanent magnets (113); the rotor (10) is of a tooth groove type structure formed by magnetic conducting materials, and the number of the magnetic conducting teeth of the rotor is Nr ═ (2 × m × k ± 1) n;

the motor comprises a motor, a plurality of concentrated armature windings (111), a plurality of motor units and a plurality of motor units, wherein m is the number of phases of the motor, n is the number of the motor units, k is the logarithm of the concentrated armature windings (111) which are connected in series with any one phase of the concentrated armature windings in each motor unit, m, n, k and q are positive integers, and q is a positive integer smaller than 2 x n x k.

2. The multi-phase disc type hybrid excitation flux switching motor according to claim 1, wherein any one phase concentrated armature winding in each motor unit is formed by connecting k pairs of concentrated armature windings (111) in series, from the first concentrated armature winding (111) of any one phase, k continuously placed concentrated armature windings (111) are arranged as the same phase, and then k concentrated armature windings (111) belonging to adjacent phases are sequentially arranged according to the arrangement mode until all the motor units are arranged; 2k concentrated armature windings (111) belonging to the same phase form k pairs of complementary concentrated armature windings, wherein the relative positions of two concentrated armature windings (111) in any pair of concentrated armature windings and the rotor (10) are different by half of the rotor pole pitch tau_sCorresponding to 180-degree electrical angle, the n motor units are sequentially arranged, and concentrated armature windings (111) belonging to the same phase in different motor units are connected in series or in parallel.

3. A multi-phase disc type hybrid excitation flux switching motor according to claim 1, wherein when every two concentrated excitation windings (112) are separated by one slot, the directions of magnetic fields generated by the concentrated excitation windings (112) are the same; when each two concentrated excitation windings (112) share one slot, the directions of the magnetic fields generated by the two adjacent concentrated excitation windings (112) are opposite; concentrated excitation windings (112) in each motor unit are connected in series to form a concentrated excitation winding unit, and concentrated excitation winding (112) units in the n motor units are connected in series or in parallel.

4. The multiphase disc type hybrid excitation flux switching motor according to claim 1, wherein the magnetization directions of all the permanent magnets (113) are along the same circumferential tangential direction; the magnetizing direction of each permanent magnet (113) is opposite to the magnetic field direction of the concentrated excitation winding (112) in the same slot; when the exciting current introduced into the concentrated exciting winding (112) is zero, only a permanent magnetic field exists in the motor, the permanent magnetic field only forms a ring-shaped closed magnetic circuit at the stator (11) part and cannot penetrate through an air gap and the rotor (10), and the total magnetic flux of the concentrated armature winding (111) is zero.

5. A multiphase disc hybrid excitation flux switching machine according to claim 1, wherein the concentrated excitation winding (112) and concentrated armature winding (111) are copper or superconducting material.

6. The multiphase disc type hybrid excitation flux switching motor according to claim 1, wherein the permanent magnet is a rare earth material such as ferrite, aluminum-iron-boron, and the like.

7. The multiphase disc type hybrid excitation flux switching motor according to claim 1, wherein a magnetic circuit parallel type double rotor disc type hybrid excitation flux switching motor is obtained by using an outer end surface of a stator (11) as a mirror surface, a yoke portion of a stator slot is removed, a motor magnetic circuit passes through two rotors (10) and the stator (11), and the motor is a magnetic circuit series type hybrid excitation flux switching motor.

8. The multiphase disc type hybrid excitation flux switching motor according to claim 1, wherein the outermost end face of the rotor (10) is used as a mirror image surface to obtain a magnetic circuit parallel type double-stator disc type hybrid excitation flux switching motor, a yoke part of the rotor (10) is removed, and a motor magnetic circuit passes through two stators (11) and the rotor to obtain a magnetic circuit series type double-stator disc type hybrid excitation flux switching motor.

9. The multiphase disc type hybrid excitation flux switching electric machine according to any one of claims 1 to 8, wherein the disc type hybrid excitation flux switching electric machine is an electric motor or a generator.

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