CN210007624U - high transformation ratio bidirectional half-bridge current-doubling converter - Google Patents
high transformation ratio bidirectional half-bridge current-doubling converter Download PDFInfo
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- CN210007624U CN210007624U CN201920712251.0U CN201920712251U CN210007624U CN 210007624 U CN210007624 U CN 210007624U CN 201920712251 U CN201920712251 U CN 201920712251U CN 210007624 U CN210007624 U CN 210007624U
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Abstract
The utility model provides an two-way half-bridge current doubler of high transformation ratio in power electronics field, including low voltage power V1, 0 high voltage power V2, high frequency transformer Tx, electric capacity C3, dc blocking electric capacity Cb, current doubler rectifier circuit, half-bridge circuit and half-bridge voltage divider circuit, the number of turns on the primary side of high frequency transformer Tx is Np, the number of turns on the secondary side of high frequency transformer Tx is Ns, low voltage power V1, electric capacity C3 and current doubler rectifier circuit are parallelly connected each other, current doubler rectifier circuit and high frequency transformer Tx's primary side are connected, high voltage power V2, half-bridge circuit and half-bridge voltage divider circuit are parallelly connected each other, the end of dc blocking electric capacity Cb is connected with the C end of the secondary side of high frequency transformer Tx, in addition end and half-bridge voltage divider circuit are connected.
Description
Technical Field
The utility model relates to a power electronics field indicates bidirectional half-bridge double current converters of high transformation ratio very much.
Background
Compared with other topologies, the topology utilizes the transformer to carry out energy bidirectional transmission, can realize high-energy-ratio bidirectional conversion between a low-voltage end and a high-voltage end, and has the characteristics of easy realization of soft switching of a switch tube of a main circuit, low power consumption, high efficiency, small volume and the like, so that is widely applied to the field of power electronic products such as a switching power supply and the like.
Conventional converters include three types:
is a non-isolated unidirectional parallel DC/DC converter which is composed of two or more unidirectional DC/DC converters connected in parallel, the converter has the advantages that the power can be connected in parallel to be large, but the converter has the defects that the number of the parallel unidirectional DC/DC converters is large, the design cost is high, the size is large, the control method is complex, the input and the output are not isolated, the safety is low, the load is greatly damaged after the power supply is abnormal, and the converter is not suitable for application occasions with high safety.
The isolated voltage type bidirectional DC/DC converter has the advantages that voltage is controlled through groups of electrical isolation transformers, two groups of high-frequency rectifying/inverting units are arranged, the converter is high in response speed, but the converter has the following defects that a switching tube has voltage drop, the voltage on a low-voltage side cannot be too low, an input end is not provided with an inductance structure and only has an energy storage capacitor, and the converter is not suitable for occasions with large voltage transformation ratio and small current ripples required by the input end.
The phase-shift control bidirectional DC/DC converter comprises groups of electrical isolation transformers, groups of inductance units and two groups of high-frequency rectifying/inverting units, and has the advantages that the phase difference of switching signals at two sides is controlled by phase shift, energy can be transferred from the side to the other side, the converter is provided with a soft switching mode, the working efficiency is high, but the converter has the following defects that the control method is complex, switching tubes at two sides work, a circuit has large circulation current, and the current stress of the switching tubes is large.
Therefore, it is problems to be solved in an urgent need to provide converters with small current ripple, small stress of the switching tube, high safety, high transformation ratio, simple structure and simple control method.
Disclosure of Invention
The to-be-solved technical problem of the utility model lies in providing kinds of high transformation ratio two-way half-bridge current-multiplying converters, realizes reducing current ripple and switch tube stress, promotes the security and the transformation ratio of converter, and simple structure, control method are simple.
The utility model discloses a two-way half-bridge current doubler of high transformation ratio that realize like this, including low voltage power V1, 0 high voltage power V2, high frequency transformer Tx, electric capacity C3, dc blocking electric capacity Cb, current doubler rectifier circuit, half-bridge circuit and half-bridge voltage dividing circuit, the number of turns on the primary side of high frequency transformer Tx is Np, the number of turns on the secondary side of high frequency transformer Tx is Ns, low voltage power V1, electric capacity C3 and current doubler rectifier circuit are parallelly connected each other, current doubler rectifier circuit and high frequency transformer Tx's primary side are connected, high voltage power V2, half-bridge circuit and half-bridge voltage dividing circuit are parallelly connected each other, the end of dc blocking electric capacity Cb is connected with the C end on the secondary side of high frequency transformer Tx, end is connected with half-bridge voltage dividing circuit in addition, the d end of the secondary.
, the current doubler rectification circuit comprises a inductor L1, a inductor L2, a switching diode M1 and a switching diode M2, a end of the inductor L1 is connected with the anode of the low-voltage power supply V1, the other end of the inductor L1 is connected with the switching diode M1 and the a end of the primary side of the high-frequency transformer Tx, a end of the inductor L2 is connected with the anode of the low-voltage power supply V1, the other end of the inductor L2 is connected with the switching diode M2 and the b end of the primary side of the high-frequency transformer Tx, and the switching diode M1 and the switching diode M2 are both connected with the cathode of the low-voltage power supply V1.
, the half-bridge circuit comprises a switching diode M3 and a switching diode M4, wherein the end of the switching diode M3 is connected with the anode of a high-voltage power supply V2, the other end of the switching diode M is connected with the DC blocking capacitor Cb and a switching diode M4, and the switching diode M4 is connected with the cathode of the high-voltage power supply V2.
Furthermore , the half-bridge voltage division circuit comprises a capacitor C1 and a capacitor C2, wherein a end of the capacitor C1 is connected with the anode of a high-voltage power supply V2, another end of the capacitor C2 is connected with a d end of a secondary side of the high-frequency transformer Tx, and the capacitor C2 is connected with the cathode of the high-voltage power supply V2.
The utility model has the advantages that:
1. through setting inductance L1 and inductance L2 shunt the electric current, have realized sharing the electric current ripple, and then have reached the effect that reduces the electric current ripple, reduces inductance L1 and inductance L2's copper decreases.
2. The voltage is divided by arranging the switching diode M1 and the switching diode M2 on the primary side of the high-frequency transformer Tx, and the voltage is divided by arranging the switching diode M3 and the switching diode M4 on the secondary side of the high-frequency transformer Tx, so that the stress of each switching diode is reduced.
3. The circuit structure is simple because only high-frequency transformers Tx are arranged, and the input and the output are isolated through the high-frequency transformers Tx, so that the safety is improved.
4. The high-transformation-ratio bidirectional half-bridge current-doubling converters can be controlled by controlling the on-off of the switching diode M1, the switching diode M2, the switching diode M3 and the switching diode M4, and the control method is simple.
5. The high transformation ratio of the high-frequency transformer Tx is realized by arranging the switching diode M1 and the switching diode M2 to divide the voltage, reducing the voltage drop of a single switching diode, and arranging the inductor L1 and the inductor L2.
Drawings
The present invention will now be described in connection with the following examples with reference to the accompanying drawings.
Fig. 1 is a circuit diagram of kinds of high transformation ratio bidirectional half-bridge current-doubling converters of the present invention.
Fig. 2 is a circuit diagram of stage 1 of the buck mode of the present invention.
Fig. 3 is a circuit diagram of stage 2 of the buck mode of the present invention.
Fig. 4 is a circuit diagram of stage 3 of the buck mode of the present invention.
Fig. 5 is a circuit diagram of stage 4 of the buck mode of the present invention.
Fig. 6 is a schematic diagram of voltage and current waveforms in the voltage reduction mode of the present invention.
Fig. 7 is a circuit diagram of stage 1 of the boost mode of the present invention.
Fig. 8 is a circuit diagram of stage 2 of the boost mode of the present invention.
Fig. 9 is a circuit diagram of stage 3 of the boost mode of the present invention.
Fig. 10 is a circuit diagram of stage 4 of the boost mode of the present invention.
Fig. 11 is a schematic diagram of the voltage and current waveforms in the boost mode of the present invention.
Fig. 12 is a schematic block circuit diagram of a conventional non-isolated unidirectional parallel DC/DC converter.
Fig. 13 is a schematic block circuit diagram of a conventional isolated voltage type bidirectional DC/DC converter.
FIG. 14 is a schematic block circuit diagram of a conventional phase-shift controlled bi-directional DC/DC converter.
Detailed Description
Referring to fig. 1 to 14, the high-transformation-ratio bidirectional half-bridge current-doubling converter according to the present invention includes a low-voltage power supply V1, 0 high-voltage power supply V2, 1 high-frequency transformer Tx, capacitors C3, dc blocking capacitors Cb, current-doubling rectifying circuits, half-bridge circuits, and half-bridge voltage-dividing circuits, wherein the primary side of the high-frequency transformer Tx has Np turns, the secondary side of the high-frequency transformer Tx has Ns turns, the low-voltage power supply V1, capacitor C3, and current-doubling rectifying circuits are connected in parallel, the current-doubling rectifying circuits are connected to the primary side of the high-frequency transformer Tx, the high-voltage power supply V2, the half-bridge voltage-dividing circuits and the half-bridge voltage-dividing circuits are connected in parallel, a terminal of the dc blocking capacitor Cb is connected to a C terminal of the secondary side of the high-frequency transformer, another terminal is connected to the high-frequency transformer Tx, a d terminal of the secondary side of the high-frequency transformer Tx, the dc blocking capacitor Cb is used for isolating the high-frequency transformer from the high-frequency transformer, and the high-frequency transformer Tx is provided with a high-frequency transformer for simple.
The current-doubling rectifying circuit comprises switching diodes M2, wherein an end of an inductor L1 is connected with the anode of a low-voltage power supply V1, the other end of the inductor L1 is connected with the switching diode M1 and the primary side a end of a high-frequency transformer Tx, a 1 end of the inductor L1 is connected with the anode of the low-voltage power supply V1, the other 1 end of the inductor L1 is connected with the switching diode M1 and the primary side b end of the high-frequency transformer Tx, the switching diode M1 and the switching diode M1 are both connected with the cathode of the low-voltage power supply V1, current is shunted by the inductor L1 and the inductor L1, current ripple is divided, the effect of reducing the current sharing, the effect of reducing the copper losses of the inductor L1 and the inductor L1 is achieved, the voltage division of the single switching diode M1 and the high-frequency transformer Tx ratio of the inductor L1 is reduced, and the voltage drop ratio of the inductor L1 is reduced, and the high-frequency transformer Tx is achieved.
The half-bridge circuit comprises switching diodes M3 and switching diodes M4, wherein a end of each switching diode M3 is connected with the anode of a high-voltage power supply V2, the other end of each switching diode M3 is connected with the DC blocking capacitor Cb and the switching diode M4, the switching diode M4 is connected with the cathode of the high-voltage power supply V2, the primary side of the high-frequency transformer Tx is provided with the switching diode M1 and the switching diode M2 to divide voltage, the secondary side of the high-frequency transformer Tx is provided with the switching diode M3 and the switching diode M4 to divide voltage, stress of each switching diode is reduced, the high-transformation ratio bidirectional half-bridge current-doubling converter can be controlled by controlling the on and off of the switching diodes M1, M2, M3 and M4, and the control method is simple.
The half-bridge voltage division circuit comprises capacitors C1 and capacitor C2, wherein a end of the capacitor C1 is connected with the anode of a high-voltage power supply V2, another end of the capacitor C1 is connected with the capacitor C2 and the d end of the secondary side of the high-frequency transformer Tx, and the capacitor C2 is connected with the cathode of the high-voltage power supply V2.
The utility model discloses the theory of operation:
the utility model discloses a two-way half-bridge current doubler converter of high transformation ratio have the buck mode and two kinds of mode of step up, and the buck mode is about to the energy transfer of high-voltage end for the low-voltage end, and the mode of step up is about to the energy transfer of low-voltage end for the high-voltage end.
The buck mode has 4 phases in switching cycles as follows:
stage 1[ t0, t 1): the switching diode M1 is disconnected, the switching diode M2 is connected, the switching diode M3 is connected, and the switching diode M4 is disconnected; at the moment, the voltage at two ends of the switching diode M4 is V2, the voltage of the secondary side of the high-frequency transformer Tx is V2/2, and the end c of the secondary side of the high-frequency transformer Tx is a positive electrode; a current i2 flows through the switching diode M3 and the secondary side of the high-frequency transformer Tx to charge the capacitor C2; the secondary side of the high frequency transformer Tx induces a voltage to the primary side, a current iNpThe current i flows out of the primary side a end of the high-frequency transformer Tx, returns to the primary side b end of the high-frequency transformer Tx after sequentially passing through an inductor L1, a capacitor C3 and a switching diode M2L1Is linearly increased in magnitude, current iL2Is linearly decreased, the current i through the switching diode M2M2＝iL1+iL2. The circuit diagram is shown in fig. 2.
Stage 2[ t1, t 2): the switching diode M1 is switched on, the switching diode M2 is switched on, the switching diode M3 is switched off, and the switching diode M4 is switched off; at the moment, the switching diode M3 and the switching diode M4 at the high-voltage end are both disconnected, energy cannot be transferred through the high-frequency transformer Tx, and the high-voltage power supply V2 charges the capacitor C1 and the capacitor C2; the current flowing through the inductor L1 reaches the maximum value at the moment when the switching diode M3 is switched off, then the current direction is kept unchanged, the magnitude of the current is linearly reduced, and the low-voltage power supply V1 is charged through the switching diode M1 and the inductor L1 which are conducted in the reverse direction; the current flowing through the inductor L2 keeps the current direction unchanged and the magnitude linearly decreases, and the low-voltage power supply V1 is charged through the reverse conducting switching diode M2 and the inductor L2. The circuit diagram is shown in fig. 3.
Stage 3[ t2, t 3): the switching diode M1 is switched on, the switching diode M2 is switched off, the switching diode M3 is switched off, and the switching diode M4 is switched on; at the moment, the voltage at two ends of the switching diode M3 is V2, the voltage of the secondary side of the high-frequency transformer Tx is V2/2, and the end d of the secondary side of the high-frequency transformer Tx is a positive electrode; current i2The current flows through a switching diode M4 and the secondary side of the high-frequency transformer Tx to charge a capacitor C1; current ic1And ic2D end flowing to secondary side of high frequency transformer Tx; the secondary side of the high frequency transformer Tx induces a voltage to the primary side, a current iNpThe current i flows out of the b end of the primary side of the high-frequency transformer Tx, returns to the a end of the primary side of the high-frequency transformer Tx after sequentially passing through an inductor L2, a capacitor C3 and a switching diode M1L2Is linearly increased in magnitude, current iL1Is linearly decreased, the current i through the switching diode M1M1＝iL1+iL2. The circuit diagram is shown in fig. 4.
Stage 4[ t3, t 4): the switching diode M1 is switched on, the switching diode M2 is switched on, the switching diode M3 is switched off, and the switching diode M4 is switched off; this phase is the same as phase 2, current iL2Is changed from linear rising to linear falling, and the current iL1The magnitude of (c) decreases linearly. The circuit diagram is shown in fig. 5.
FIG. 6 shows the transformer voltage U at stage 1 to stage 4 in the buck modeNpTransformer current iNsInductor current iL1Inductor current iL2And a waveform diagram of the output current iout.
The boost mode has 4 phases within switching cycles as follows:
stage 1[ t0, t 1): the switching diode M1 is disconnected, the switching diode M2 is connected, the switching diode M3 is connected, and the switching diode M4 is disconnected; at this time, the voltage of the low voltage source V1 is applied to the two ends of the inductor L2, and the current i on the inductor L2L2Gradually, graduallyIncrease of iL1Flows from the low-voltage power supply V1 and the inductor L1 to the primary side a end i of the high-frequency transformer TxNp＝iL1And i isL1The current ripple on the inductor L2 and the inductor L1 have the effect of mutual cancellation when the current ripple begins to decrease; the voltage on the primary side of the high-frequency transformer Tx is the sum of the voltages across the low-voltage power supply V1 and the inductor L1, and the potential en on the secondary side of the high-frequency transformer Tx is NS (V1+ L1 di)L1dt)/Np ═ V2/2, where diL1The value of/dt represents the current iL1Rate of change in unit time, current iNsThe voltage flows out from the end C of the secondary side of the high-frequency transformer Tx and then charges a capacitor C1 through a switching diode M3. The circuit diagram is shown in fig. 7.
Stage 2[ t1, t 2): the switching diode M1 is switched on, the switching diode M2 is switched on, the switching diode M3 is switched off, and the switching diode M4 is switched off; a low-voltage power supply V1 for storing energy in inductor L1 and inductor L2 at two ends of inductor L1 and inductor L2, iL1From decreasing to increasing, iL2Continue to increase i1The relationship between the voltage and the current in the inductor at this time is increased to V1 ═ L1 × diL1/dt，V1＝L2*diL2And dt, the voltage of the secondary side of the high-frequency transformer Tx is zero, and the capacitor C1 and the capacitor C2 supply power to the high-voltage power supply V2. The circuit diagram is shown in fig. 8.
Stage 3[ t2, t 3): the switching diode M1 is switched on, the switching diode M2 is switched off, the switching diode M3 is switched off, and the switching diode M4 is switched on; at this time, the voltage of the low voltage source V1 is applied to the two ends of the inductor L1, and the current i on the inductor L1L1Gradually increase iL2Flows from the low-voltage power supply V1 and the inductor L2 to the primary side b terminal of the high-frequency transformer Tx, i.e. iNp＝iL2And i isL2The current ripple on the inductor L2 and the inductor L1 have the effect of mutual cancellation when the current ripple begins to decrease; the voltage on the primary side of the high-frequency transformer Tx is the sum of the voltages across the low-voltage power supply V1 and the inductor L2, and the potential en on the secondary side of the high-frequency transformer Tx is NS (V1+ L2 di)L1dt)/Np ═ V2/2, where diL1The value of/dt represents the current iL1Rate of change in unit time, current iNsThe voltage flows out from the end d of the secondary side of the high-frequency transformer Tx and then charges a capacitor C2 through a switching diode M4. The circuit diagram is shown in fig. 9.
Stage 4[ t3, t 4): the switching diode M1 is switched on, the switching diode M2 is switched on, the switching diode M3 is switched off, and the switching diode M4 is switched off; this phase is the same as phase 2, current iL1Is continuously increased in magnitude, the current i1The increase continues. The circuit diagram is shown in fig. 10.
FIG. 11 shows the transformer voltage U from stage 1 to stage 4 in boost modeNpTransformer current iNsInductor current iL1Inductor current iL2And a waveform diagram of the output current iout.
The dashed lines in fig. 2-5 and 7-10 indicate that the line is not energized after the switching diode is turned off.
To sum up, the utility model has the advantages that:
1. through setting inductance L1 and inductance L2 shunt the electric current, have realized sharing the electric current ripple, and then have reached the effect that reduces the electric current ripple, reduces inductance L1 and inductance L2's copper decreases.
2. The voltage is divided by arranging the switching diode M1 and the switching diode M2 on the primary side of the high-frequency transformer Tx, and the voltage is divided by arranging the switching diode M3 and the switching diode M4 on the secondary side of the high-frequency transformer Tx, so that the stress of each switching diode is reduced.
3. The circuit structure is simple because only high-frequency transformers Tx are arranged, and the input and the output are isolated through the high-frequency transformers Tx, so that the safety is improved.
4. The high-transformation-ratio bidirectional half-bridge current-doubling converters can be controlled by controlling the on-off of the switching diode M1, the switching diode M2, the switching diode M3 and the switching diode M4, and the control method is simple.
5. The high transformation ratio of the high-frequency transformer Tx is realized by arranging the switching diode M1 and the switching diode M2 to divide the voltage, reducing the voltage drop of a single switching diode, and arranging the inductor L1 and the inductor L2.
Although specific embodiments of the present invention have been described, it will be understood by those skilled in the art that the specific embodiments described are illustrative only and are not limiting upon the scope of the invention, and that equivalent modifications and variations can be made by those skilled in the art without departing from the spirit of the invention, which is to be limited only by the claims appended hereto.
Claims (4)
- The high-transformation-ratio bidirectional half-bridge current-doubling converter is characterized by comprising low-voltage power supplies V1 and V2 and high-voltage power supplies V2 and V high-frequency transformers Tx and , capacitors C3 and Cb and current-doubling rectifying circuits, half-bridge circuits and half-bridge voltage dividing circuits, wherein the number of turns of the primary side of the high-frequency transformer Tx is Np, the number of turns of the secondary side of the high-frequency transformer Tx is Ns, the low-voltage power supplies V1 and C3 and the current-doubling rectifying circuits are connected in parallel, the current-doubling rectifying circuits are connected with the primary side of the high-frequency transformer Tx, the high-voltage power supplies V2 and half-bridge circuit and half-bridge voltage dividing circuits are connected in parallel, the Cb end of the current-blocking capacitor Cb is connected with the C end of the secondary side of the high-frequency transformer Tx, the other .
- 2. The high-transformation-ratio bidirectional half-bridge current-doubling converter as claimed in claim 1, wherein said current-doubling rectifying circuit includes inductor L1, inductor L2, switching diode M1 and switching diode M2, said inductor L1 has its terminal connected to the positive terminal of the low-voltage source V1 and its terminal connected to said switching diode M1 and the a terminal of the primary side of the high-frequency transformer Tx, said inductor L2 has its terminal connected to the positive terminal of the low-voltage source V1 and its terminal connected to said switching diode M2 and the b terminal of the primary side of the high-frequency transformer Tx, and said switching diode M1 and switching diode M2 are connected to the negative terminal of the low-voltage source V1.
- 3. The kinds of high transformation ratio bidirectional half-bridge current doubler converter as claimed in claim 1, wherein said half-bridge circuit includes switching diode M3 and switching diode M4, the terminal of said switching diode M3 is connected to the positive pole of the high voltage power supply V2, the other terminal is connected to said DC blocking capacitor Cb and switching diode M4, and said switching diode M4 is connected to the negative pole of the high voltage power supply V2.
- 4. The high-transformation-ratio bidirectional half-bridge current-doubling converters as claimed in claim 1, wherein the half-bridge voltage-dividing circuit includes capacitors C1 and capacitors C2, the end of the capacitor C1 is connected to the positive pole of a high-voltage power supply V2, the other end is connected to the capacitor C2 and the d-end of the secondary side of the high-frequency transformer Tx, and the capacitor C2 is connected to the negative pole of the high-voltage power supply V2.
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110212768A (en) * | 2019-05-17 | 2019-09-06 | 福建星云电子股份有限公司 | A kind of high no-load voltage ratio bi-directional half bridge times current converter |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN110212768A (en) * | 2019-05-17 | 2019-09-06 | 福建星云电子股份有限公司 | A kind of high no-load voltage ratio bi-directional half bridge times current converter |
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Denomination of utility model: High-transformation-ratio bidirectional half-bridge current-doubling converter Effective date of registration: 20200703 Granted publication date: 20200131 Pledgee: China Exim Bank Fujian branch Pledgor: FUJIAN NEBULA ELECTRONICS Co.,Ltd. Registration number: Y2020980003784 |