CN207530785U - It can be applied to the automatic gain control circuit of burst trans-impedance amplifier - Google Patents
It can be applied to the automatic gain control circuit of burst trans-impedance amplifier Download PDFInfo
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- CN207530785U CN207530785U CN201820091170.9U CN201820091170U CN207530785U CN 207530785 U CN207530785 U CN 207530785U CN 201820091170 U CN201820091170 U CN 201820091170U CN 207530785 U CN207530785 U CN 207530785U
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Abstract
The utility model provides the automatic gain control circuit that can be applied to burst trans-impedance amplifier, wherein switching tube is in parallel with the feedback resistance of trans-impedance amplifier, and the output end vo ut of the input terminal Iin of the drain electrode connection trans-impedance amplifier of switching tube, source electrode connection trans-impedance amplifier；The input terminal of the common-source amplifier is connected to the output end vo ut of trans-impedance amplifier, and output terminal is connected to the grid of switching tube；When the input current of trans-impedance amplifier is zero, switching tube is off state；When the input current of trans-impedance amplifier incrementally increases, the output voltage of trans-impedance amplifier gradually declines, and the output voltage of the common-source amplifier gradually rises；So that the gate source voltage of switching tube incrementally increases, switching tube is opened, the resistance decrease of switching tube and feedback resistance parallel equivalent feedback resistance so that the output voltage of trans-impedance amplifier is no longer as the increase of input current continues to decline.Foregoing circuit without special processes, can be realized using conventional device.
Description
Technical field
The utility model is related to optical fiber telecommunications system more particularly to trans-impedance amplifiers.
Background technology
In Modern High-Speed optical fiber telecommunications system, trans-impedance amplifier TIA (Trans-Impedance Amplifier) plays the part of
It and the faint photo-signal that photodiode generates is converted and is enlarged into voltage signal, and export and carried out to subsequent circuit
Processing.Therefore TIA is in receiving terminal forefront, is the core devices of optical communication system receiving terminal, noise, sensitivity, dynamic
The core index such as range, sensitivity determine the entire performance for receiving system substantially.
Typical trans-impedance amplifier circuit structure as shown in Figure 1, its core index across resistance ZT, bandwidth f-3dB, equivalent inpnt makes an uproar
Sound InIt can be derived as：
In addition to this, input dynamic range is also an important indicator, is defined as saturation input optical power and sensitivity
Difference.Saturation input optical power and sensitivity are respectively defined as minimum and maximum defeated in the range of certain permissible bit error rate
Optical power.Sensitivity is mainly determined that equivalent input noise is smaller by equivalent input noise, then sensitivity index is higher；And satisfy
It is mainly determined with input optical power by factors such as the pulse-width distortions of output signal.It can be seen that, to obtain better from above-mentioned formula
Good sensitivity index is needed under the premise of bandwidth allows, and will be R across resistanceFValue is done greatly as possible, and bigger across hindering, then saturation
Input optical power is then smaller.
Usually automatic growth control (Automatic Gain can be all added in the trans-impedance amplifier of practical application
Control, AGC) circuit solves the problems, such as this.I.e. in smaller input optical power, keep greatly across resistance；In larger input light work(
During rate, automatic adjustment reduces across resistance so that output signal will not generate excessive pulse-width distortion, so as to widen dynamic range.
AGC functions generally use one adjustable active pull-up is in parallel with feedback resistance to be realized to the adjusting across resistance.Have
Two kinds of common methods cause output to generate excessive pulse-width distortion to detect whether excessive attend the meeting of input optical power, first, detection
The exchange output amplitude of TIA；Second is that the output DC level variation of detection TIA.
Two methods are required for adding in low-pass filter in the feedback loop to filter out high fdrequency component, to keep across the steady of resistance
It is fixed, reduce output signal shake.Generally for acceptable jittering characteristic is ensured, the low-frequency cut-off frequency needs of AGC loop are low
To tens KHz.Since AGC loop is there are low-frequency cut-off frequency, and low-frequency cut-off frequency is again relatively low, thus AGC loop need compared with
The long stable convergence time, usually in tens us or so.Therefore both agc circuits are only applicable in continuous communication mode.
And in passive optical network (Passive Optical Network, PON) system, in OLT (Optical Line
Terminal) hold, receiving terminal receive signal be happen suddenly (Burst Mode) signal, i.e., the ONU (Optical of tens
Network Unit) local side sends a signal to OLT in turn according to certain time-division, luminous power that each ONU is sent, transmitting range
Differ, therefore the optical signal that OLT terminations receive has the characteristics that sequential burst, luminous power mutation, as shown in Figure 2.
PON is broadly divided into GPON and EPON, wherein due to using nrz encoding and tightened up timing requirements, GPON's
Realize that difficulty is much larger than EPON.Illustrate by taking GPON as an example herein, a typical GPON burst packet is as shown in Figure 6.One
A burst packet by lead code (36ns), define symbol (16ns), valid data (nrz encoding), safety clearance area (26ns) structure
Into.When the burst receiving system of OLT receives a burst packet, entire burst receiving system is needed in lead code sequential
It is interior, i.e. stable working condition is established in 36ns, correctly to handle subsequent valid data signal.
So if using traditional AGC methods, it is desirable that AGC loop restrains stabilization in 36ns, then AGC feedback control loops
Low-frequency cut-off frequency cannot be made too low, and theoretical calculation cannot be below 5MHz.And since the Signal coding of GPON is NRZ codes,
Longest line code (consequential identical digit, CID) is up to 72bit, when transmitting this encoded signal, AGC
The low-frequency cut-off frequency of loop must be sufficiently low, could reduce dc shift (DC Wandering) effect, reduces shake.Therefore
The presence of this contradiction causes traditional AGC control loops that can not be suitable in the GPON reception systems of burst mode.
In order to overcome above-mentioned contradiction, general burst AGC control circuits sample mode as shown in Figure 4 to realize, utilize one
A diode clamps down on the output amplitude of TIA, i.e., when input current greatly to a certain extent, TIA output node voltages decline, and cause
The pressure drop of feedback resistance increases to so that diode is opened, and part input current is fallen in feedback resistance Rf on diodes in parallel, shunting,
So that the output amplitude of TIA no longer increased dramatically, so as to which TIA output amplitudes be clamped down in a certain range.
But this mode has one disadvantage in that, the cut-in voltage of typical diode is 0.7V or so, even if using deep sub-micro
Rice MOS FET are as diode, and threshold value is substantially also all in more than 0.4V.And general TIA output amplitudes are only in 0.2Vpp
Within will not just generate apparent distortion, therefore, generally realized using special Low threshold (low threshold) device,
The cost done so is that process costs rise, and technique is needed especially to support, many commercial process do not support this special device
The process option of part.
Utility model content
Technical problem underlying to be solved in the utility model be to provide it is a kind of can be applied to burst trans-impedance amplifier from
Dynamic gain control circuit, can realize without the support of special processes, and using conventional device.
The utility model additionally provide it is a kind of can be applied to burst trans-impedance amplifier automatic gain control circuit, including across
Impedance amplifier, common-source amplifier, switching tube；
Wherein switching tube is in parallel with the feedback resistance of trans-impedance amplifier, and the drain electrode connection trans-impedance amplifier of switching tube
The output end vo ut of input terminal Iin, source electrode connection trans-impedance amplifier；The input terminal of the common-source amplifier is connected to be amplified across resistance
The output end vo ut of device, output terminal are connected to the grid of switching tube；
When the input current of trans-impedance amplifier is zero, switching tube is off state；When the input electricity of trans-impedance amplifier
When stream incrementally increases, the output voltage of trans-impedance amplifier gradually declines, and the output voltage of the common-source amplifier gradually rises；Make
The gate source voltage for obtaining switching tube incrementally increases；When the gate source voltage of switching tube increases above Vth, switching tube is opened, switch
The resistance decrease of pipe and feedback resistance parallel equivalent feedback resistance so that the output voltage of trans-impedance amplifier is no longer with input electricity
The increase of stream continues to decline.
In a preferred embodiment：The common-source amplifier includes NMOS tube M2 and resistance R1；The grid of the NMOS tube M2
The extremely input terminal of common-source amplifier, the drain electrode of NMOS tube M2 are the output terminal of common-source amplifier；The resistance R1 is connected to
Between the drain electrode of NMOS tube M2 and supply voltage Vdd.
In a preferred embodiment：The common-source amplifier is common source difference amplifier；It includes NOMS pipes M4, NMOS tube
M5, resistance R2, resistance R3 and constant-current source I1；
Wherein, the grid of NOMS pipes M4 is the input terminal of common source difference amplifier amplifier, and the grid of NOMS pipes M5 is inclined
It puts in a fixed reference voltage Vref；Output terminal of the drain electrode of NOMS pipes M4 as common source difference amplifier；
Described resistance R2, R3 are connected between NOMS pipes M4, the drain electrode of NMOS tube M5 and supply voltage Vdd；It is described
NOMS pipes M4, NMOS tube M5 source electrode be connected and pass through current source I1 ground connection.
In a preferred embodiment：The switching tube is NMOS tube M3.
In a preferred embodiment：The trans-impedance amplifier includes feedback resistance R2, common source and common grid amplifier.
In a preferred embodiment：The common source and common grid amplifier, including NMOS tube M1, NMOS tube M0 and resistance R0,
The grid of middle NMOS tube M1 is the input terminal Iin of trans-impedance amplifier, and the grid of NMOS tube M0 is connected to bias voltage Vbia；It is described
The drain electrode of NMOS tube M1 is connected to the source electrode of NMOS tube M0, the source electrode ground connection of NMOS tube M1；The feedback resistance R2 is connected to
Between the drain electrode of the grid and NMOS tube M0 of NMOS tube M1；The resistance R0 is connected to drain electrode and the supply voltage of NMOS tube M0
Between Vdd.
Compared to the prior art, the technical solution of the utility model has following advantageous effect：
The utility model provides a kind of auto gain control method and circuit that can be applied to burst trans-impedance amplifier, leads to
It the output voltage of detection trans-impedance amplifier is crossed, and removes after level-one is reversely amplified the grid of control switching tube, so as to control
Whether the unlatching of the switching tube in parallel with feedback resistance.In this way, the output of trans-impedance amplifier, in other words feedback resistance
Smaller pressure drop is only needed, after common-source amplifier reversely amplifies, the grid of switching tube will increase, Simultaneous Switching pipe
Source voltage is as the output voltage of trans-impedance amplifier declines and declines, so that the gate source voltage of switching tube is increased to and is enough
So that switching tube opens conducting, so as to which the output voltage swing of trans-impedance amplifier be limited in a certain range.Due to increasing common source
The reversed amplification of amplifier, in this structure, switching tube only needs with conventional normality threshold NMOS tube, to greatly reduce
Process costs increase the flexibility of process choice.
In addition, in this configuration, eliminating the low-pass filtering link of AGC control loops, prolong so as to fulfill supper-fast, nothing
When gain control；And it realizes and is controlled by bit, so as to which the dc shift generated when encountering long CID codes be avoided to imitate
It should.
Description of the drawings
Fig. 1 is typical trans-impedance amplifier circuit structure diagram；
Fig. 2 is the exemplary plot of burst packet；
Fig. 3 is typical GPON burst packets structure chart；
Fig. 4 is the circuit diagram for reaching automatic growth control using diode clamp width in the prior art；
Fig. 5 is the circuit diagram of the preferred embodiment in the utility model 1；
Fig. 6 is the circuit diagram of the preferred embodiment in the utility model 2.
Specific embodiment
The utility model is described in further detail in the following with reference to the drawings and specific embodiments, but the utility model
Therefore embodiment is not defined in following embodiment.
A kind of auto gain control method that can be applied to burst trans-impedance amplifier, in the feedback resistance two of trans-impedance amplifier
An end switching tube in parallel controls the gate source voltage of switching tube by detecting the output voltage of trans-impedance amplifier, and after reversely amplifying；
When the input current increase of trans-impedance amplifier, trans-impedance amplifier output voltage declines, the source voltage of switching tube
Decline therewith；Trans-impedance amplifier output voltage declines after reversely amplification so that the grid voltage of switching tube rises；So that
The gate source voltage increase of trans-impedance amplifier, switching tube conducting；A part of input current is flowed through from switching tube, so as to reduce stream
Cross the electric current across resistance.
By detecting the output voltage of trans-impedance amplifier, and the grid of control switching tube is removed after level-one is reversely amplified,
So as to come whether controlling the unlatching of the switching tube in parallel with feedback resistance.In this way, the output of trans-impedance amplifier or
Say that feedback resistance only needs smaller pressure drop, after common-source amplifier reversely amplifies, the grid of switching tube will increase, together
When switching tube source voltage with trans-impedance amplifier output voltage decline and decline so that the gate source voltage of switching tube
It increases to and switching tube is sufficient to make to open conducting, so as to which the output voltage swing of trans-impedance amplifier be limited in a certain range.Due to
Increasing the reversed amplification of common-source amplifier, in this structure, switching tube is only needed with conventional normality threshold NMOS tube,
Process costs are greatly reduced, increase the flexibility of process choice.
In order to realize above-mentioned control method, the utility model provides two kinds of embodiments.
Embodiment 1
With reference to figure 5, it is a kind of can be applied to burst trans-impedance amplifier automatic gain control circuit, including trans-impedance amplifier,
Common-source amplifier, NMOS tube M3；
The trans-impedance amplifier includes feedback resistance R2, common source and common grid amplifier.The common source and common grid amplifier, including
NMOS tube M1, NMOS tube M0 and resistance R0, the wherein grid of NMOS tube M1 are input terminal the I in, NMOS tube M0 of trans-impedance amplifier
Grid be connected to bias voltage Vbia；The drain electrode of the NMOS tube M1 is connected to the source electrode of NMOS tube M0, the source of NMOS tube M1
Pole is grounded；The feedback resistance R2 is connected between the drain electrode of grid and NMOS tube M0 of NMOS tube M1；The resistance R0 connections
Between the drain electrode of NMOS tube M0 and supply voltage Vdd.As the simple replacement of the present embodiment, common source and common grid amplifier can be with
Using other structures, the realization of the present embodiment is not interfered with, belongs to the simple replacement of the present embodiment.
The common-source amplifier includes NMOS tube M2 and resistance R1；The grid of the NMOS tube M2 is defeated for common-source amplifier
Enter end, the drain electrode of NMOS tube M2 is the output terminal of common-source amplifier；The resistance R1 is connected to drain electrode and the power supply of NMOS tube M2
Between voltage Vdd.
The NMOS tube M3 is in parallel with the feedback resistance R2 of trans-impedance amplifier, and the drain electrode connection of NMOS tube M3 is put across resistance
The input terminal Iin of big device, the output end vo ut of source electrode connection trans-impedance amplifier；The input terminal of the common-source amplifier be connected to across
The output end vo ut of impedance amplifier, output terminal are connected to the grid of NMOS tube M3；
When the input current of trans-impedance amplifier is zero, by the parameter for reasonably setting each device so that NMOS tube
M3 is off state；When the input current of trans-impedance amplifier incrementally increases, the output voltage of trans-impedance amplifier gradually declines,
So that the source voltage of NMOS tube M3 declines therewith；Due to trans-impedance amplifier output terminal be common-source amplifier input terminal,
Therefore, after the reversed amplification of common-source amplifier, the output voltage of the common-source amplifier gradually rises so that NMOS tube M3
Grid voltage rise therewith；Therefore, the gate source voltage of NMOS tube M3 incrementally increases；When the gate source voltage of NMOS tube M3 increases to
During more than Vth, NMOS tube M3 is opened, and NMOS tube M3 and the resistance decrease that feedback resistance R2 parallel equivalents are feedback resistance R2 make
The output voltage of trans-impedance amplifier is obtained no longer as the increase of input current continues to decline, so as to which the output of trans-impedance amplifier be put
Width limits in a certain range.
Embodiment 2
Difference lies in the present embodiment, the common-source amplifier is common source differential amplification to the present embodiment with embodiment 1
Device；It includes NOMS pipes M4, NMOS tube M5, resistance R2, resistance R3 and constant-current source I1；
Wherein, the grid of NOMS pipes M4 is the input terminal of common source difference amplifier amplifier, and the grid of NOMS pipes M5 is inclined
It puts in a fixed reference voltage Vref；Output terminal of the drain electrode of NOMS pipes M4 as common source difference amplifier；
Described resistance R2, R3 are connected between NOMS pipes M4, the drain electrode of NMOS tube M5 and supply voltage Vdd；It is described
NOMS pipes M4, NMOS tube M5 source electrode be connected and pass through current source I1 ground connection.
When the input current of trans-impedance amplifier is zero, by reasonably setting the parameter of each device, by reasonably
The parameter of each device is set so that NMOS tube M3 is off state；When the input current of trans-impedance amplifier incrementally increases,
So that the source voltage of NMOS tube M3 declines therewith；Due to trans-impedance amplifier output terminal be common-source amplifier input terminal,
Therefore, after the reversed amplification of common-source amplifier, the output voltage of the common-source amplifier gradually rises so that NMOS tube M3
Grid voltage rise therewith；Therefore, the gate source voltage of NMOS tube M3 incrementally increases；When the gate source voltage of NMOS tube M3 increases to
During more than Vth, NMOS tube M3 is opened, and NMOS tube M3 and the resistance decrease that feedback resistance R2 parallel equivalents are feedback resistance R2 make
The output voltage of trans-impedance amplifier is obtained no longer as the increase of input current continues to decline, so as to which the output of trans-impedance amplifier be put
Width limits in a certain range.
By using common source difference amplifier in this present embodiment, and the grid of the NOMS pipes M5 of common source difference amplifier is inclined
It puts in a fixed reference voltage Vref, compared to embodiment 1, is easier so corresponding when precisely setting NMOS tube M3 is opened
Input current threshold value.Rest part and embodiment 1 are all identical, repeat no more.
Above-described embodiment of the utility model is only intended to clearly illustrate the utility model example, and is not
Restriction to the embodiment of the utility model.It is all made within the design of the utility model and technical solution any repair
Change, equivalent replacement and improvement etc., should be included within the utility model scope of the claims.
Claims (6)
1. a kind of automatic gain control circuit that can be applied to burst trans-impedance amplifier, it is characterised in that：Including trans-impedance amplifier,
Common-source amplifier, switching tube；
Wherein switching tube is in parallel with the feedback resistance of trans-impedance amplifier, and the input of the drain electrode connection trans-impedance amplifier of switching tube
Hold the output end vo ut of Iin, source electrode connection trans-impedance amplifier；The input terminal of the common-source amplifier is connected to trans-impedance amplifier
Output end vo ut, output terminal are connected to the grid of switching tube；
When the input current of trans-impedance amplifier is zero, switching tube is off state；When trans-impedance amplifier input current by
During step increase, the output voltage of trans-impedance amplifier gradually declines, and the output voltage of the common-source amplifier gradually rises；So that it opens
The gate source voltage for closing pipe incrementally increases；When the gate source voltage of switching tube increases above Vth, switching tube open, switching tube with
The resistance decrease of feedback resistance parallel equivalent feedback resistance so that the output voltage of trans-impedance amplifier is no longer with input current
Increase continues to decline.
2. a kind of automatic gain control circuit that can be applied to burst trans-impedance amplifier according to claim 1, feature
It is：The common-source amplifier includes NMOS tube M2 and resistance R1；The grid of the NMOS tube M2 is the input of common-source amplifier
End, the drain electrode of NMOS tube M2 are the output terminal of common-source amplifier；The resistance R1 is connected to the drain electrode of NMOS tube M2 and power supply electricity
Between pressure Vdd.
3. a kind of automatic gain control circuit that can be applied to burst trans-impedance amplifier according to claim 1, feature
It is：The common-source amplifier is common source difference amplifier；It includes NOMS pipes M4, NMOS tube M5, resistance R2, resistance R3 and perseverance
Stream source I1；
Wherein, the grid of NOMS pipes M4 is the input terminal of common source difference amplifier amplifier, and the grid of NOMS pipes M5 is biased in
One fixed reference voltage Vref；Output terminal of the drain electrode of NOMS pipes M4 as common source difference amplifier；
Described resistance R2, R3 are connected between NOMS pipes M4, the drain electrode of NMOS tube M5 and supply voltage Vdd；The NOMS
Pipe M4, NMOS tube M5 source electrode be connected and pass through current source I1 ground connection.
4. a kind of automatic gain control circuit that can be applied to burst trans-impedance amplifier according to Claims 2 or 3, special
Sign is：The switching tube is NMOS tube M3.
5. a kind of automatic gain control circuit that can be applied to burst trans-impedance amplifier according to claim 4, feature
It is：The trans-impedance amplifier includes feedback resistance R2, common source and common grid amplifier.
6. a kind of automatic gain control circuit that can be applied to burst trans-impedance amplifier according to claim 5, feature
It is：The common source and common grid amplifier, including NMOS tube M1, NMOS tube M0 and resistance R0, wherein the grid of NMOS tube M1 be across
The grid of the input terminal Iin of impedance amplifier, NMOS tube M0 are connected to bias voltage Vbia；The drain electrode of the NMOS tube M1 is connected to
The source electrode of NMOS tube M0, the source electrode ground connection of NMOS tube M1；The feedback resistance R2 is connected to the grid and NMOS tube of NMOS tube M1
Between the drain electrode of M0；The resistance R0 is connected between the drain electrode of NMOS tube M0 and supply voltage Vdd.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201820091170.9U CN207530785U (en) | 2018-01-19 | 2018-01-19 | It can be applied to the automatic gain control circuit of burst trans-impedance amplifier |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201820091170.9U CN207530785U (en) | 2018-01-19 | 2018-01-19 | It can be applied to the automatic gain control circuit of burst trans-impedance amplifier |
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| Publication Number | Publication Date |
|---|---|
| CN207530785U true CN207530785U (en) | 2018-06-22 |
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ID=62576775
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201820091170.9U Active CN207530785U (en) | 2018-01-19 | 2018-01-19 | It can be applied to the automatic gain control circuit of burst trans-impedance amplifier |
Country Status (1)
| Country | Link |
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| CN (1) | CN207530785U (en) |
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2018
- 2018-01-19 CN CN201820091170.9U patent/CN207530785U/en active Active
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