CN204597808U - Based on the single-phase high frequency inverter of SCC-LCL-T resonant network - Google Patents

Abstract

The utility model discloses a kind of constant-current source type single-phase high frequency inverter based on SCC-LCL-T resonant network, the described constant-current source type single-phase high frequency inverter based on SCC-LCL-T resonant network comprises interconnective semi-bridge inversion unit X and SCC-LCL-T resonant network unit Y, and described SCC-LCL-T resonant network unit Y has gate-controlled switch electric capacity SCC; The resonant inductance L of described LCL-T resonant network, the first inductance L _a, the first resonant capacitance C _sform T-shaped structure, gate-controlled switch electric capacity SCC is connected on the capacitive branch of LCL-T network, comprises the 3rd switching tube S of two differential concatenations ₃with the 4th switching tube S ₄.It is convenient that the utility model has control, is easy to realize, and can conveniently realize ZVS Sofe Switch, switching loss is little, and conversion efficiency is high, and the use of controlled capacitance can compensate the impact of input voltage fluctuation and component parameters error, ensures the advantages such as constant current output.

Description

Based on the single-phase high frequency inverter of SCC-LCL-T resonant network

Technical field

The utility model relates to a kind of high-frequency ac distribution (HFAC PDS) technology, particularly a kind of single-phase high frequency inverter based on SCC-LCL-T resonant network.

Background technology

High-frequency ac distribution (HFAC PDS) mode is compared with DC distribution (DC PDS) mode, there is voltage transitions convenience and power density advantages of higher, both can be applicable to small-power, the computer of short-distance transmission and communication equipment, can be applicable to again mid power, the electric automobile of long range propagation and micro-capacitance sensor field.Single-phase high frequency inverter is responsible for effect direct current being converted to high-frequency alternating current, is then fed to high-frequency ac current bus.At present, conventional high-frequency ac inverter as current source to high-frequency ac current bus feed time, the size of output current is responsive to input voltage fluctuation, cannot eliminate the impact that component error causes, and converter self lacks effective controlled means, be difficult to provide constant output current.The utility model is intended to the deficiency overcome in prior art, proposes a kind of constant-current source type single-phase high frequency inverter based on SCC-LCL-T resonant network.

Utility model content

The purpose of this utility model is that the shortcoming overcoming prior art is with not enough, a kind of single-phase high frequency inverter based on SCC-LCL-T resonant network is provided, this single-phase high frequency inverter is applicable to high-frequency ac field of power distribution, is applied particularly to and direct voltage source is converted to single-phase high frequency constant-current source.

The purpose of this utility model is achieved through the following technical solutions: a kind of single-phase high frequency inverter based on SCC-LCL-T resonant network, comprise: interconnective semi-bridge inversion unit X and SCC-LCL-T resonant network unit Y, described SCC-LCL-T resonant network unit Y has gate-controlled switch electric capacity SCC;

Described semi-bridge inversion unit X comprises: the first switching tube S ₁, second switch pipe S ₂, the first diode VD ₁, the second diode VD ₂, the first electric capacity C ₁with the second electric capacity C ₂; Wherein, the first switching tube S ₁drain electrode and the first diode VD ₁positive pole all with the first electric capacity C ₁positive pole be connected; First switching tube S ₁source electrode, the first diode VD ₁negative electrode and the first electric capacity C ₁negative pole all with second switch pipe S ₂drain electrode be connected, described second switch pipe S ₂drain electrode and the second diode VD ₂positive pole all with the second electric capacity C ₂positive pole be connected; Second switch pipe S ₂source electrode and the second diode VD ₂negative electrode all with the second electric capacity C ₂negative pole be connected;

Described SCC-LCL-T resonant network unit Y comprises resonant inductance L, the first inductance L _a, the first resonant capacitance C _swith gate-controlled switch electric capacity SCC; The end of described resonant inductance L, the first inductance L _ahead end all with the first resonant capacitance C _spositive pole be connected; The 3rd diode VD in described gate-controlled switch electric capacity SCC ₃positive pole, the 3rd switching tube S ₃drain electrode and the second resonant capacitance C ₃positive pole all with the first resonant capacitance C _snegative pole be connected; The 3rd diode VD in gate-controlled switch electric capacity SCC ₃negative pole, the 3rd switching tube S ₃source electrode, the second resonant capacitance C ₃negative pole all with the 4th diode VD ₄negative pole be connected, described 4th diode VD ₄negative pole and the 4th switching tube S ₄source electrode all with the 3rd resonant capacitance C ₄positive pole be connected; 4th diode VD ₄positive pole, the 4th switching tube S ₄drain electrode all with the 3rd resonant capacitance C ₄negative pole be connected; 4th diode VD ₄positive pole and the first switching tube S ₁source electrode be connected;

Produced the square-wave voltage of fixed frequency and 50% duty ratio by described semi-bridge inversion unit X, by SCC-LCL-T resonant network unit Y, filtering is carried out to described square-wave voltage, export the sinusoidal current of constant amplitude and phase place.

The inductance value of described resonant inductance L is greater than the first inductance L _ainductance value, to realize half-bridge circuit ZVS.

Described SCC-LCL-T resonant network unit Y adopts gate-controlled switch electric capacity SCCZ, and described gate-controlled switch electric capacity SCC comprises the 3rd diode VD ₃, the 4th diode VD ₄, the 3rd switching tube S ₃, the 4th switching tube S ₄, the second resonant capacitance C ₃with the 3rd resonant capacitance C ₄;

3rd diode VD ₃positive pole, the 3rd switching tube S ₃drain electrode and the second resonant capacitance C ₃positive pole all with the first resonant capacitance C _snegative pole be connected; Described 3rd diode VD ₃negative pole, the 3rd switching tube S ₃source electrode, the second resonant capacitance C ₃negative pole all with the 4th diode VD ₄negative pole be connected; Described 4th diode VD ₄negative pole, the 4th switching tube S ₄source electrode all with the 3rd resonant capacitance C ₄positive pole be connected; Described 4th diode VD ₄positive pole, the 4th switching tube S ₄drain electrode all with the 3rd resonant capacitance C ₄negative pole be connected; 4th diode VD ₄positive pole and the first switching tube S ₁source electrode be connected; Described second resonant capacitance C ₃capacitance and the 3rd resonant capacitance C ₄capacitance equal, described 3rd switching tube S ₃with the 4th switching tube S ₄all adopt phase shifting control, described phase shifting control phase angle is the drive singal relative to semi-bridge inversion unit X, and the computing formula of the equivalent capacitance value of described gate-controlled switch electric capacity SCC is:

$C_{eq\_sw}=\frac{C_3}{\[1-(\mathrm{\α}+\sin 2\mathrm{\α})\]/\mathrm{\π}},$

Wherein, C ₃be the capacitance of the second resonant capacitance, α is phase-shift control angle.

The drive singal of described gate-controlled switch electric capacity SCC regulates equivalent capacity C by changing phase shifting angle α _eqvalue, to compensate the disturbance of input voltage fluctuation and component error, the excursion of described phase shifting angle α is 90 ° ~ 180 °, and the ratio H of the described output current of SCC-LCL-T resonant network unit Y output and the input voltage of semi-bridge inversion unit X input is:

$H=\frac{I_o}{V_{in}}=\frac{V_o/R_o}{V_{in}}=\frac{\sqrt{2}/\mathrm{\π}}{2Z_n\·\{\frac{1}{Q}(1-{\mathrm{\ω}}_n^2)+j\[(1+\mathrm{\λ}){\mathrm{\ω}}_n-{\mathrm{\λ\ω}}_n^3\]\}},$

Wherein, Q is quality factor, ω _nfor normalized radian frequency, λ is resonant inductance ratio, Z _nfor characteristic impedance.

The drive singal of described semi-bridge inversion unit X adopts the type of drive of fixed frequency fixed duty cycle, and gate-controlled switch electric capacity SCC adopts the phase shifting control relative to half-bridge circuit.

There is resonance in described SCC-LCL-T resonant network unit Y, realize constant current output under switching frequency; Described switching capacity adopts shifts to control, duty ratio D=0.5 relative to half-bridge driven.Along with the difference of phase shift angle, the equivalent capacitance value of capacitive branch can change, to overcome the impact of input voltage fluctuation and component parameters error.

The drive singal of described semi-bridge inversion unit X adopts the type of drive of fixed frequency fixed duty cycle, and gate-controlled switch electric capacity SCC adopts the phase shifting control relative to half-bridge circuit, and its control circuit is simple, is easy to realize, easy to operate.

The utility model has following advantage and effect relative to prior art:

(1) the utility model adopts SCC-LCL-T resonant network unit Y to realize exporting square wave filtering to half-bridge inversion circuit, and make to export as sinusoidal current, output current does not change with the variation of load, realizes constant current output.

(2) the utility model is based on gate-controlled switch electric capacity SCC that SCC-LCL-T resonant network unit Y capacitance branch road is connected, the value changing equivalent capacity is regulated by the phase shift relative to half-bridge driven, thus the value of regulation output electric current, the impact that compensation input voltage fluctuation and component error cause.

(3) switching tube that in the utility model, semi-bridge inversion unit X and gate-controlled switch electric capacity SCC uses all can realize Sofe Switch, and switching loss is little, and conversion efficiency is high.

(4) in the utility model, semi-bridge inversion unit X drives the type of drive adopting fixed frequency fixed duty cycle, and switching capacity adopts the phase shifting control relative to half-bridge circuit, and control circuit is simple, is easy to realize, easy to operate.

Accompanying drawing explanation

Fig. 1 is the constant-current source type single-phase high frequency inverter structure figure based on SCC-LCL-T resonant network.

Fig. 2 is the equivalent circuit diagram of the constant-current source type single-phase high frequency inverter based on SCC-LCL-T resonant network.

Fig. 3 is the Vital Voltage current waveform figure of the constant-current source type single-phase high frequency inverter based on SCC-LCL-T resonant network.

Fig. 4 is the simple equivalent circuit figure of the constant-current source type single-phase high frequency inverter resonant network based on SCC-LCL-T resonant network.

Embodiment

Below in conjunction with embodiment and accompanying drawing, the utility model is described in further detail, but execution mode of the present utility model is not limited thereto.

Embodiment

As shown in Figure 1, be the structure chart of the constant-current source type single-phase high frequency inverter based on SCC-LCL-T resonant network described in the utility model.The described constant-current source type single-phase high frequency inverter based on SCC-LCL-T resonant network is by interconnective semi-bridge inversion unit X and SCC-LCL-T resonant network unit Y, and described SCC-LCL-T resonant network unit Y has gate-controlled switch electric capacity SCC Z.Described semi-bridge inversion unit X comprises the first switching tube S ₁, second switch pipe S ₂, the first diode VD ₁, the second diode VD ₂, the first electric capacity C ₁, the second electric capacity C ₂; Wherein, the first switching tube S ₁drain electrode and the first diode VD ₁positive pole all with the first electric capacity C ₁positive pole be connected; First switching tube S ₁source electrode and the first diode VD ₁negative electrode and the first electric capacity C ₁negative pole all with second switch pipe S ₂drain electrode and the second diode VD ₂positive pole and the second electric capacity C ₂positive pole be connected; Second switch pipe S ₂source electrode and the second diode VD ₂negative electrode all with the second electric capacity C ₂negative pole be connected; First diode VD ₁with the second diode VD ₂two ends respectively the first equivalent electric capacity C in parallel ₁with the second electric capacity C ₂, the first switching tube S ₁with second switch pipe S ₂adopt the type of drive of complementary fixed frequency fixed duty cycle, duty ratio D=0.5, conveniently realizes Sofe Switch; Described SCC-LCL-T resonant network unit Y comprises resonant inductance L, the first inductance L _a, the first resonant capacitance C _swith gate-controlled switch electric capacity SCC Z, draw together resonant inductance L, the first inductance L _awith the first resonant capacitance C _sform T-shaped structure, gate-controlled switch electric capacity SCC Z is series at the capacitive branch of SCC-LCL-T resonant network unit Y, comprises the 3rd switching tube S of two differential concatenations ₃4th switching tube S ₄, the 3rd switching tube S ₃4th switching tube S ₄drain electrode respectively with the 3rd diode VD ₃, the 4th diode VD ₄negative electrode connect, source electrode respectively with the 3rd diode VD ₃, the 4th diode VD ₄anode be connected, the 3rd diode VD ₃, the 4th diode VD ₄two ends respectively the second equivalent resonant capacitance C in parallel ₃, the 3rd resonant capacitance C ₄, there is resonance in SCC-LCL-T resonant network unit Y, realize constant current output under switching frequency; Described switching capacity adopts shifts to control, duty ratio D=0.5 relative to half-bridge driven.Along with the difference of phase shift angle, the equivalent capacitance value of capacitive branch can change, to overcome the impact of input voltage fluctuation and component parameters error.After SCC-LCL-T resonant network unit Y filtering, produce sinusoidal high-frequency ac current, and be fed to high-frequency ac current bus HFAC BUS.

Below with the equivalent electric circuit shown in Fig. 2 for object, the mains voltage current waveform figure shown in composition graphs 3 and the simple equivalent circuit figure shown in Fig. 4 illustrate specific works principle of the present utility model.

First do to give a definition, resonance angular frequency: normalized radian frequency: switching angle frequency: w=2 π f _s, characteristic impedance: quality factor: wherein R _ofor output load resistance, f _shalf-bridge switch frequency, C _eqfor the equivalent capacity of capacitive branch.

At the first switching tube S ₁, second switch pipe S ₂grid source electrode between to apply complementary frequency be f _s, the drive singal U of duty ratio D=0.5 _gs1, U _gs2, obtaining frequency at AB point-to-point transmission is f _s, the square-wave voltage v of Symmetrical _a.Because resonant network is very large to the impedance of high order harmonic component, therefore ignore v _ahigh order harmonic component and only consider fundametal compoment, can be obtained by Fig. 2 equivalent electric circuit, the first-harmonic input impedance Z of SCC-LCL-T resonant network unit Y _infor:

$Z_{in}=\frac{w_{o}L\{(1-w_n^2)+jQ\[(1+\frac{L_a}{L})w_n-\frac{L_a}{L}{w}_n^3\]\}}{Q(1-\frac{L_a}{L}{w}_n^2)+{\mathrm{jw}}_n},---\left(1\right)$

Flow through the current i on resonant inductance L _lwith v _afundametal compoment v _a1phase difference be:

Work as ω _nwhen=1, have choose the first inductance L _abe slightly less than resonant inductance L, have i.e. v _a1be ahead of i _l, create necessary condition for realizing half-bridge circuit ZVS.

Then, by v _aintroduce SCC-LCL-T resonant network unit Y, the drive singal U of gate-controlled switch electric capacity SCC Z _gs3, U _gs4lag behind half-bridge circuit drive singal U respectively _gs1, U _gs2α angle, primary variables oscillogram as shown in Figure 3, has following formula:

$i_c={\hat{U}}_{eq}{\mathrm{wC}}_{eq}cos\left(wt\right),---\left(3\right)$

Wherein, for C _eqon crest voltage

$U_{eq\_sw}=\frac{1}{C_{3,4}}{\∫}_{\mathrm{\δ}-\frac{\mathrm{\π}}{2}}^t{i}_{c}dt=\frac{1}{C_{3,4}}{\∫}_{\mathrm{\δ}-\frac{\mathrm{\π}}{2}}^t{\hat{U}}_{eq}{\mathrm{wC}}_{eq}cos\left(wt\right)dt,---\left(4\right)$

Definition U _{eq_sw}zero crossing be θ ₁, θ ₂, capacitive branch current i _cadvanced v _afundametal compoment v _a1angle be δ, then have θ ₁=δ-pi/2, θ ₂=π-θ ₁=3 pi/2-δ.

Based on above equation, Fourier decomposition is carried out to (4) formula and obtains U _{eq_sw}fundametal compoment:

$U_{eq\_sw1}=\frac{i_c}{{\mathrm{wC}}_{3,4}}\[2-\frac{1}{\mathrm{\π}}(2\mathrm{\δ}-sin2\mathrm{\δ})\]sin\left(wt\right),---\left(5\right)$

Obtained by geometric knowledge: $\mathrm{\δ}=\frac{\mathrm{\α}+\mathrm{\π}}{2},---\left(6\right)$

Simultaneous (3), (5) and (6) namely obtain switching capacity size:

$C_{eq\_sw}=\frac{C_3}{2-\frac{1}{\mathrm{\π}}(2\mathrm{\δ}-sin2\mathrm{\δ})}=\frac{C_3}{\[1-(\mathrm{\α}+sin2\mathrm{\α})\]/\mathrm{\π}},---\left(7\right)$

Then the equivalent capacity of capacitive branch is:

$C_{eq}=C_s//C_{eq\_sw}=\frac{C_s\frac{C_3}{\[1-\left(\mathrm{\α}+\sin 2\mathrm{\α}\right)\]/\mathrm{\π}}}{C_s+\frac{C_3}{\[1-\left(\mathrm{\α}+\sin 2\mathrm{\α}\right)\]/\mathrm{\π}}},---\left(8\right)$

Can be adjusted the value of equivalent capacity by the size changing phase shifting angle α.As shown in Figure 4, be the simple equivalent circuit figure of the SCC-LCL-T resonant network of described inverter, the ratio that application steady-state circuit analytic approach can obtain output current and input voltage is:

$H=\frac{I_o}{V_{in}}=\frac{V_o/R_o}{V_{in}}=\frac{\sqrt{2}/\mathrm{\π}}{2Z_n\·\{\frac{1}{Q}(1-{\mathrm{\ω}}_n^2)+j\[(1+\mathrm{\λ}){\mathrm{\ω}}_n-{\mathrm{\λ\ω}}_n^3\]\}},---\left(9\right)$

Wherein, $\mathrm{\λ}=\frac{L_a}{L}.$

Work as ω _nwhen=1, H is a steady state value, realizes constant current output characteristic; When error appears in input voltage fluctuation or component parameters, by regulating phase shifting angle α 90 ° to 180 ° changes, ω can be regulated _nvalue, thus realize the adjustment of H, for the impact compensating input voltage fluctuation and component error provides a kind of effective approach.

Above-described embodiment is the utility model preferably execution mode; but execution mode of the present utility model is not restricted to the described embodiments; change, the modification done under other any does not deviate from Spirit Essence of the present utility model and principle, substitute, combine, simplify; all should be the substitute mode of equivalence, be included within protection range of the present utility model.

Claims (2)

1. the single-phase high frequency inverter based on SCC-LCL-T resonant network, it is characterized in that, comprise: interconnective semi-bridge inversion unit (X) and SCC-LCL-T resonant network unit (Y), described SCC-LCL-T resonant network unit (Y) has gate-controlled switch electric capacity SCC (Z);

Described semi-bridge inversion unit (X) comprising: the first switching tube (S ₁), second switch pipe (S ₂), the first diode (VD ₁), the second diode (VD ₂), the first electric capacity (C ₁) and the second electric capacity (C ₂); Wherein, the first switching tube (S ₁) drain electrode and the first diode (VD ₁) positive pole all with the first electric capacity (C ₁) positive pole be connected; First switching tube (S ₁) source electrode, the first diode (VD ₁) negative electrode and the first electric capacity (C ₁) negative pole all with second switch pipe (S ₂) drain electrode be connected, described second switch pipe (S ₂) drain electrode and the second diode (VD ₂) positive pole all with the second electric capacity (C ₂) positive pole be connected; Second switch pipe (S ₂) source electrode and the second diode (VD ₂) negative electrode all with the second electric capacity (C ₂) negative pole be connected;

Described SCC-LCL-T resonant network unit (Y) comprises resonant inductance (L), the first inductance (L _a), the first resonant capacitance (C _s) and gate-controlled switch electric capacity SCC (Z); The end of described resonant inductance (L), the first inductance (L _a) head end all with the first resonant capacitance (C _s) positive pole be connected; The 3rd diode (VD in described gate-controlled switch electric capacity SCC (Z) ₃) positive pole, the 3rd switching tube (S ₃) drain electrode and the second resonant capacitance (C ₃) positive pole all with the first resonant capacitance (C _s) negative pole be connected; The 3rd diode (VD in gate-controlled switch electric capacity SCC (Z) ₃) negative pole, the 3rd switching tube (S ₃) source electrode, the second resonant capacitance (C ₃) negative pole all with the 4th diode (VD ₄) negative pole be connected, described 4th diode (VD ₄) negative pole and the 4th switching tube (S ₄) source electrode all with the 3rd resonant capacitance (C ₄) positive pole be connected; 4th diode (VD ₄) positive pole, the 4th switching tube (S ₄) drain electrode all with the 3rd resonant capacitance (C ₄) negative pole be connected; 4th diode (VD ₄) positive pole and the first switching tube (S ₁) source electrode be connected.

2. the single-phase high frequency inverter based on SCC-LCL-T resonant network according to claim 1, it is characterized in that, described SCC-LCL-T resonant network unit (Y) adopts gate-controlled switch electric capacity SCC (Z), and described gate-controlled switch electric capacity SCC (Z) comprises the 3rd diode (VD ₃), the 4th diode (VD ₄), the 3rd switching tube (S ₃), the 4th switching tube (S ₄), the second resonant capacitance (C ₃) and the 3rd resonant capacitance (C ₄);

3rd diode (VD ₃) positive pole, the 3rd switching tube (S ₃) drain electrode and the second resonant capacitance (C ₃) positive pole all with the first resonant capacitance (C _s) negative pole be connected; Described 3rd diode (VD ₃) negative pole, the 3rd switching tube (S ₃) source electrode, the second resonant capacitance (C ₃) negative pole all with the 4th diode (VD ₄) negative pole be connected; Described 4th diode (VD ₄) negative pole, the 4th switching tube (S ₄) source electrode all with the 3rd resonant capacitance (C ₄) positive pole be connected; Described 4th diode (VD ₄) positive pole, the 4th switching tube (S ₄) drain electrode all with the 3rd resonant capacitance (C ₄) negative pole be connected; 4th diode (VD ₄) positive pole and the first switching tube (S ₁) source electrode be connected; Described second resonant capacitance (C ₃) capacitance and the 3rd resonant capacitance (C ₄) capacitance equal.