CN201197211Y - Output current compensation circuit of LED driving circuit - Google Patents

Abstract

The utility model discloses an output current compensation circuit for an LED drive circuit, which comprises a threshold set module, a comparison module, a drive module, a switch module and a compensation module, wherein the threshold set module sets a threshold voltage; the comparison module compares the threshold voltage which is set by the threshold set module and a sampling voltage of the LED drive circuit; an output voltage of the comparison module performs signal enhancement through the drive module, controls the on-off of the switch module and then adjusts the threshold voltage which is set by the threshold set module; and the compensation module adjusts the threshold voltage of the LED drive circuit and compensates the influence of variation of an external input voltage Vin and/or an external LED output voltage on an output current of an LED.

Description

The output current compensating circuit of led drive circuit

Technical field

The utility model relates to the led drive circuit field, relates in particular to the output current compensation technique of the led drive circuit under the ring control model that stagnates.

Background technology

At present, at led drive circuit, particularly extensively adopt the led drive circuit of the ring control model that stagnates in the high-power LED drive circuit, its control loop is simple, need not slope compensation and frequency compensation, required peripheral component are few, make things convenient for the client to use.

Fig. 1 is the part-structure figure of the led drive circuit of the present stagnant ring control model that adopts, and comprises threshold setting module (10), comparison module (11), driver module (12) and switch module (13), wherein:

Described threshold setting module (10) comprises voltage follow module and the some resistance that is made of operational amplifier A 1 and NMOS pipe M3, the positive input termination led drive circuit internal reference voltage VREF of A1, the negative input end of A1 connects the source electrode of M3, the grid of the output termination M3 of A1, described some resistance comprise resistance R 1, R2 and R4, the drain electrode of R1 one termination M3, the other end is as the Vin port of led drive circuit, R2 connects the source electrode of M3, other end series connection R4, R4 ground connection;

Described comparison module (11) comprises comparator A2, and the negative input end of A2 connects the drain electrode of M3, and the positive input terminal of A2 is as the CS port of led drive circuit;

Described driver module (12) comprises driver A3, the output of the input termination A2 of A3;

Described switch module (13) comprises NMOS pipe M1 and M2, and the grid of M1 and M2 all is connected the output of A3, the source grounding of M1 and M2, and the drain electrode of M2 is connected between R2 and the R4, and the drain electrode of M1 is as the SW port of led drive circuit;

The led drive circuit shortcoming of above-mentioned stagnant ring control model is: because the influence of internal logic time-delay, comparator rising time-delay and the time-delay that descends, when the load of led drive circuit driving LED, its input voltage vin is or/and external LED output voltage V out when changing, the big young pathbreaker of average current Iavg of LED load changes, and makes the stabilized current characteristic of led drive circuit relatively poor.Adopt the led drive circuit of stagnant ring control model shown in Figure 1, generally when 6～30V input voltage changed, output current had 5%～15% variation, made the electric current of LED load wayward on the one hand, influenced luminous stability; On the other hand, the output current of led drive circuit will become greatly when input voltage vin and output voltage V out change, and can have a strong impact on the life-span of LED load when surpassing the rated current of LED load.

Summary of the invention

To be solved in the utility model is to stagnate to encircle the deficiency that the led drive circuit under the control model exists, and the output current compensating circuit of the led drive circuit under the ring control model that stagnates being provided.

The output current compensating circuit of led drive circuit is characterised in that to comprise threshold setting module, comparison module, driver module, switch module and compensating module:

Described threshold setting module inserts the external input voltage Vin of led drive circuit by the Vin port of led drive circuit, while threshold setting module ground connection, make the threshold setting module after led drive circuit powers on, continue conducting, described threshold setting module comprises the voltage follow module, and the internal reference voltage VREF of described voltage follow module access led drive circuit and the output voltage of voltage follow module remain and equal internal reference voltage VREF;

The size of the sampled voltage of described comparison module compare threshold setting module preset threshold voltage and led drive circuit, the sampled voltage of led drive circuit is by CS port input comparison module, sampled voltage is the pressure reduction of Vin and CS port, and threshold voltage is the pressure reduction of Vin and threshold setting module output voltage.When the sampled voltage of led drive circuit during less than threshold voltage, the output voltage of comparison module carries out signal by driver module and strengthens back starting switch module, when the sampled voltage of led drive circuit during greater than threshold voltage, the output voltage of comparison module carries out signal by driver module and strengthens back stopcock module;

Described switch module is regulated the electric current of threshold setting module by the conducting or the shutoff of switch module simultaneously, thereby is regulated the threshold voltage of threshold setting module settings by the break-make of the external led circuit of the SW port controlling led drive circuit of led drive circuit.

Described a kind of compensating module is connected to the Vin port of led drive circuit, when led drive circuit inserts external input voltage Vin, compensating module is regulated the threshold voltage of the threshold setting module output of led drive circuit, and the variation of compensation external input voltage Vin is to the influence of external LED output current.

Described another compensating module is connected to the CS port and the SNS port of led drive circuit, when led drive circuit CS port and SNS port are connected to LED two ends in the external led circuit of led drive circuit (LED output voltage), compensating module is adjusted the threshold voltage of the threshold setting module output of led drive circuit, and the variation of the output voltage of the external LED that the compensation LED drive circuit is driven is to the influence of LED output current.

Wherein, described threshold setting module comprises voltage follow module and some resistance: described voltage follow module is made of operational amplifier A 1 and metal-oxide-semiconductor M3, the positive input termination led drive circuit internal reference voltage VREF of A1, the negative input end of A1 connects the source electrode of metal-oxide-semiconductor M3, the grid of the output termination M3 of A1; Described some resistance comprises resistance R 1, R2 and R4, the drain electrode of R1 one termination metal-oxide-semiconductor M3, and the other end is as the Vin port of led drive circuit, and R2 connects the source electrode of M3, other end series connection R4, R4 ground connection;

Wherein, described comparison module comprises comparator A2, and the negative input end of A2 connects the drain electrode of M3, and the positive input terminal of A2 is as the CS port of led drive circuit;

Wherein, described driver module comprises driver A3, the output of the input termination A2 of A3;

Wherein, described switch module comprises metal-oxide-semiconductor M1 and M2, and the grid of M1 and M2 all is connected the output of A3, the source grounding of M1 and M2, and the drain electrode of M2 is connected between R2 and the R4, and the drain electrode of M1 is as the SW port of led drive circuit;

Wherein, described metal-oxide-semiconductor M1, M2 and M3 can be N channel enhancement metal-oxide-semiconductor; Also described metal-oxide-semiconductor M1, M2 and M3 can be replaced with NPN type triode.

Can adopt compensating resistance for first kind of compensating module;

Wherein, the connected mode of described compensating resistance is: the Vin port of the described led drive circuit of compensating resistance R3 cross-over connection and the source electrode of metal-oxide-semiconductor M3.

Wherein, the connected mode of described compensating resistance can also for: draw the output port of a port as the led drive circuit of band output current compensation from the source electrode of described metal-oxide-semiconductor M3, compensating resistance R3 is at this output port of outside cross-over connection of led drive circuit and the Vin port of led drive circuit.

Can also adopt the current mirror module for first kind of compensating module;

Wherein, described current mirror module comprises: current mirror circuit 1, current mirror circuit 2 and resistance R 5;

Wherein, described current mirror circuit 1 is made of two common emitters, grounded base triode Q3 and Q4, the emitter of two pipes all links to each other with power supply VCC, the base stage of triode Q3 links to each other with the collector electrode of self, and the collector electrode of triode Q4 links to each other with the source electrode of metal-oxide-semiconductor M3 in the described led drive circuit;

Wherein, described current mirror circuit 2 is made of two common emitters, grounded base triode Q1 and Q2, the equal ground connection of the emitter of two pipes, the base stage of triode Q1 links to each other with the collector electrode of self, and the collector electrode of triode Q2 links to each other with the collector electrode of triode Q3 in the described current mirror circuit 1;

Wherein, the collector electrode of the triode Q1 of current mirror circuit 1 in described resistance R 5 cross-over connection input voltage vin and the described current mirror module.

Wherein, described triode Q3 and Q4 are the positive-negative-positive triode, and triode Q1 and Q2 are NPN type triode;

Wherein, described triode Q3 and Q4 also can replace with the P channel MOS tube, and its corresponding connected mode in like manner;

Wherein, described triode Q1 and Q2 also can replace with the N-channel MOS pipe, and its corresponding connected mode in like manner.

Can adopt sampling mirror image module for second kind of compensating module;

Wherein, described sampling mirror image module comprises output voltage sampling circuit and current mirror circuit 3;

Wherein, described output voltage sampling circuit is by common emitter, grounded base triode Q5 and Q6, and triode Q7 and resistance R 6 compositions; The emitter-base bandgap grading that Q5 links to each other with Q6 is connected to the CS end of led drive circuit, and the collector electrode of Q6 links to each other with the base stage of self, makes Q5 and Q6 form current mirror; The emitter of triode Q7 links to each other with the collector electrode of Q5, and the base stage of Q7 is connected to the negative pole of LED load as the SNS port of described led drive circuit; The base stage of resistance R 6 cross-over connection Q7 and the collector electrode of Q6;

Wherein, described current mirror circuit 3 constitutes the source ground that M4 links to each other with M5 by metal-oxide-semiconductor M4 and the M5 that common gate, common source connect; The drain electrode of M5 links to each other with the grid of self, and links to each other with the drain electrode of metal-oxide-semiconductor Q7 in the described output voltage sampling circuit; The drain electrode of M5 links to each other with the source electrode of metal-oxide-semiconductor M3 in the described led drive circuit.

Wherein, described triode Q5, Q6, Q7 are the positive-negative-positive triode, and described metal-oxide-semiconductor M4, M5 are the N-channel MOS pipe;

Wherein, described triode Q5, Q6, Q7 can replace with the P channel MOS tube, and its corresponding connected mode in like manner;

Wherein, described metal-oxide-semiconductor M4, M5 can replace with NPN type triode, and its corresponding connected mode in like manner.

The utility model can also be with compensating resistance, current mirror module, three kinds of compensating module combinations of sampling mirror image module, as compensating resistance is made up with sampling mirror image module, perhaps the current mirror module is made up with sampling mirror image module, the output current compensating circuit compensation external input voltage Vin that realizes led drive circuit change the influence of LED output current in the external led circuit that led drive circuit drove or/and the variation of the external LED output voltage that the compensation LED drive circuit is driven to the influence of LED output current.

The utility model beneficial effect is: by the LED output current that led drive circuit drove is compensated, greatly improved the constant-current characteristics of the output current of led drive circuit, the output current that makes the LED load of compensation back for the external input voltage Vin of led drive circuit or/and the variation of the output voltage V out of external LED is no longer responsive, thereby make the LED load can be operated in the LED load input voltage of broad or/and under the LED load output voltage.

Description of drawings:

Fig. 1 stagnates to encircle the led drive circuit part-structure figure of control model at present.

Fig. 2 is the system construction drawing that the partial circuit of stagnant at present ring control model led drive circuit links to each other with external led circuit.

Fig. 3 flows through the current waveform figure of external led circuit inductance in the ideal case for the ring control model led drive circuit that stagnates.

Fig. 4 flows through the actual current oscillogram of external led circuit inductance for the ring control model led drive circuit that stagnates.

Fig. 5 is the output current compensating circuit structure chart of the led drive circuit of first kind of compensation way of employing.

Fig. 6 is the output current compensating circuit structure chart of the led drive circuit of second kind of compensation way of employing.

Fig. 7 is the output current compensating circuit structure chart of the led drive circuit of employing compensating resistance.

Fig. 8 is the output current compensating circuit structure chart of the led drive circuit of employing current mirror module.

Fig. 9 is the output current compensating circuit structure chart of the led drive circuit of employing current mirror module.

Figure 10 adopts the change curve of the output current of compensating resistance or current mirror module for compensating front and back led drive circuit to input voltage vin.

Figure 11 is the output current compensating circuit structure chart of the led drive circuit of employing sampling mirror image module.

Figure 12 is the output current compensating circuit structure chart of the led drive circuit of employing sampling mirror image module.

Figure 13 adopts the change curve of the output current of sampling mirror image module for compensating front and back led drive circuit to output voltage

Figure 14 is the output current compensating circuit combination assumption diagram of several led drive circuits.

The external led circuit of output current compensating circuit 2-led drive circuit 3-of the present invention of 1-led drive circuit of the present invention

The led drive circuit that 4-is traditional

Embodiment

Below in conjunction with accompanying drawing content of the present invention is further specified.

Led drive circuit as shown in Figure 1 (partial circuit structure) is when the driving LED load, led drive circuit link to each other to constitute the led drive circuit system with external led circuit, its system configuration as shown in Figure 2: described external led circuit comprises sampling resistor Rsense, LED load, inductance and the Schottky diode D1 of serial connection; The Vin port and the CS port of described sampling resistor Rsense cross-over connection led drive circuit; The positive pole of described LED load connects the CS port of led drive circuit, and negative pole connects an end of described inductance, the SW port of another termination led drive circuit of described inductance; The Vin port and the SW port of the described led drive circuit of described Schottky diode D1 cross-over connection, its PN junction forward is to the Vin port from the SW port;

Led drive circuit system works principle shown in Figure 2 is: when system initially powers on, set up led drive circuit system input voltage vin and led drive circuit internal reference voltage VREF, the A1 output HIGH voltage is to the grid of M3, Vin applies forward voltage through R1 in the drain electrode of M3 simultaneously, make the M3 conducting, voltage follower of the common formation of A1 and M3 makes the source voltage V1 of M3 keep the equal and opposite in direction with reference voltage V REF always.Simultaneously, the branch road conducting that Vin and R1, M3, R2, R4 arrive ground, because I2=I1, the pressure drop on the R1 at this moment is

So the negative input end voltage of comparator A2 is

The positive input terminal voltage of comparator A2 is Vin.Operation principle according to comparator A2: when the difference of the positive input terminal voltage of comparator and negative input end voltage greater than 0 the time, comparator output high level; When the difference of the positive input terminal voltage of comparator and negative input end voltage less than 0 the time, the comparator output low level.Therefore, initially powering on afterwards, positive input and the negative input end pressure reduction of comparator A2 are

Numerical value is greater than zero, and comparator A2 exports high level, through driver A3, makes M1 and M2 conducting simultaneously.

After the M1 conducting, Vin process Rsense, LED, L1, M1 is to the branch road conducting on ground, and this branch road has electric current I _LOccur, because inductance L 1 is an energy-storage travelling wave tube, I _LBe an electric current that increases gradually from small to large, this moment, the voltage of A2 positive input terminal was Vin-Rsense * I _LM2 conducting simultaneously makes R4 by short circuit, and the pressure drop on the R1 raises and is

So the negative input end voltage of A2 is At this moment, the voltage difference of A2 positive input terminal and negative input end is

According to the comparator operation principle, when

Greater than 0 o'clock, A2 kept high level output; When $\frac{\mathrm{VREF}\×R1}{R2}-\mathrm{Rsense}\×I_L$ Less than 0 o'clock, A2 was with output low level.

Along with electric current I on the inductance L 1 _LRising,

Value reduce gradually, when less than 0 the time, comparator A2 output low level realizes upset, by driver A3, M1 and M2 is ended simultaneously.

After M1 ended, the electric energy that inductance L 1 stores still had the electric current I that reduces gradually by Schottky diode D1 afterflow _LBy the loop that L1, D1, Rsense and LED form, this moment, the anode input voltage of A2 was Vin-Rsense * I _LEnding of M2 makes R4 add R1 again simultaneously, M1, and the conductive path of R2, the negative terminal input voltage of A2 is reduced to

The positive-negative input end pressure reduction of A2 is

Consumption and discharging current I along with the L1 energy storage _LReduce gradually, this pressure reduction will be greater than 0, comparator A2 exports high level, realizes upset once more, conducting M1 and M2.Led drive circuit system Automatic Cycle said process is realized the stagnant ring of load LED is driven.

The led drive circuit of above-mentioned stagnant ring control model, its weak point is: because the influence of internal logic time-delay, comparator rising time-delay and the time-delay that descends, at system's input voltage vin and output voltage V out (being the pressure drop at LED load two ends) when changing, the average current Iavg size to the LED load of output can change, and makes the stabilized current characteristic of led drive circuit relatively poor.

Make a concrete analysis of as follows:

According to the operation principle of above-mentioned circuit, inductive current I as can be known _LSize is clamped between two threshold current: maximum Imax and the minimum value Imin, and its size is:

$I\max =\frac{V_H}{R_{\mathrm{SENSE}}}=\frac{\mathrm{<figure-callout\; id="2"\; label="VREF\; R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">VREF</figure-callout>}}{R}\&times;\frac{R1}{R_{\mathrm{SENSE}}}---\left(1\right)$

$I\min =\frac{V_L}{R_{\mathrm{SENSE}}}=\frac{\mathrm{<figure-callout\; id="2"\; label="VREF\; R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">VREF</figure-callout>}}{R}\&times;\frac{R1}{R_{\mathrm{SENSE}}}---\left(2\right)$

Wherein, V _HBe the threshold voltage peak of comparator A2, V _LThreshold voltage minimum for comparator A2;

Under the perfect condition, the average current Iavg of inductive current promptly flows through the output current of LED, its waveform as shown in Figure 3, the average current size is:

$\mathrm{Iavg}=\frac{1}{2}(I\max +I\min )---\left(3\right)$

In the real work, because the time-delay of comparator and whole system causes the variation of average current, as shown in Figure 4.Tdly1 represents electric current rising delay time among Fig. 4, Tdly2 represents electric current decline delay time, the Idly1 delaying current added value of representing to rise, the Idly2 delaying current added value of representing to descend can see that rise time-delay and the time-delay that descends have all caused the variation of peak current.

Upper limit current Imax is because the influence of time-delay becomes Imax ', and lower current Imin is because the influence of time-delay becomes Imin ' time, and its value is:

$I\max \&prime;=I\max +\frac{\mathrm{Vin}-\mathrm{Vout}}{L}\&times;\mathrm{Tdly}1---\left(4\right)$

$I\min \&prime;=I\min -\frac{\mathrm{Vout}}{L}\&times;\mathrm{Tdly}2---\left(5\right)$

$\mathrm{Iavg}=\frac{1}{2}(I\max \&prime;+I\min \&prime;)=\frac{1}{2}[I\max +I\min +\frac{\mathrm{Vin}}{L}\&times;\mathrm{Tdly}1-\frac{\mathrm{Vout}}{L}\&times;(\mathrm{<figure-callout\; id="1"\; label="Tdly"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Tdly</figure-callout>}1+\mathrm{Tdly}2)]---\left(6\right)$

Can obtain, because the output current that time-delay causes is changed to:

$\mathrm{\&Delta;Iavg}=\frac{\mathrm{Vin}}{2L}\&times;\mathrm{Tdly}1-\frac{\mathrm{Vout}}{2L}\&times;(\mathrm{<figure-callout\; id="1"\; label="Tdly"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Tdly</figure-callout>}1+\mathrm{Tdly}2)---\left(7\right)$

In the time of can deriving Vin variation and Vout variation by formula (7), the variable quantity of average current:

During input voltage changes delta Vin, the output average current changes:

$\mathrm{\&Delta;<figure-callout\; id="1"\; label="Iavg"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Iavg</figure-callout>}1=\frac{\mathrm{\&Delta;Vin}}{2L}\&times;\mathrm{Tdly}1---\left(8\right)$

During output voltage changes delta Vout, the output average current changes:

$\mathrm{\&Delta;<figure-callout\; id="2"\; label="Iavg"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Iavg</figure-callout>}2=-\frac{\mathrm{\&Delta;Vout}}{2L}\&times;(\mathrm{<figure-callout\; id="1"\; label="Tdly"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Tdly</figure-callout>}1+\mathrm{Tdly}2)---\left(9\right)$

By formula (8) (9) as can be known, input voltage and output voltage change all can have certain influence to the size of output average current, makes the stabilized current characteristic variation of led drive circuit.

Practical test result has also confirmed this shortcoming: adopt the led drive circuit of hysteresis control method thereof at present, generally output current has 5%～15% variation when 6～30V input voltage changes.The variation of output current has adverse influence to led circuit: make the electric current of LED load wayward on the one hand, influence luminous stability; On the other hand, if output current becomes big during the input and output change in voltage, can have a strong impact on the life-span of LED when surpassing the rated current of LED.

For addressing the above problem, the utility model provide led drive circuit first kind of compensation way of output current compensating circuit circuit structure as shown in Figure 5, comprise threshold setting module (10), comparison module (11), driver module (12), switch module (13) and compensating module: wherein

Described threshold setting module (10) inserts the external input voltage Vin of led drive circuit by the Vin port of led drive circuit, while threshold setting module (10) ground connection, make threshold setting module (10) after led drive circuit powers on, continue conducting, described threshold setting module (10) comprises voltage follow module (101), and the internal reference voltage VREF of described voltage follow module (101) access led drive circuit and the output voltage of voltage follow module (101) remain and equal internal reference voltage VREF;

The size of the sampled voltage of described comparison module (11) compare threshold setting module (10) preset threshold voltage and led drive circuit, the sampled voltage of led drive circuit is by CS port input comparison module, sampled voltage is the pressure reduction of VIN and CS port, and threshold voltage is the pressure reduction of the output voltage of VIN and threshold setting module.When the sampled voltage of led drive circuit during less than threshold voltage, the output voltage of comparison module (11) carries out signal by driver module (12) and strengthens back starting switch module (13), when the sampled voltage of led drive circuit during greater than threshold voltage, the output voltage of comparison module (11) carries out signal by driver module (12) and strengthens back stopcock module (13);

Described switch module (13) is by the break-make of the external led circuit of the SW port controlling led drive circuit of led drive circuit, regulate the electric current of threshold setting module (10) by the conducting or the shutoff of switch module (13) simultaneously, thereby regulate the threshold voltage of threshold setting module settings.。

Described compensating module (14-1) is connected to the Vin port of led drive circuit, when led drive circuit inserts external input voltage Vin, compensating module (14-1) is regulated threshold setting module (10) the preset threshold voltage of led drive circuit, and compensation external input voltage Vin changes the influence to external LED output current.

The circuit structure of another compensation way as shown in Figure 6, described compensating module (14-2) is connected to the CS port and the SNS port of led drive circuit, when led drive circuit CS port and SNS port are connected to the LED two ends that led drive circuit drives (LED output voltage), compensating module is adjusted threshold setting module (10) the preset threshold voltage of led drive circuit, and the external LED output voltage that the compensation LED drive circuit is driven changes the influence to the LED output current.

Wherein, described threshold setting module (10) comprises voltage follow module (101) and some resistance: described voltage follow module (101) is made of operational amplifier A 1 and metal-oxide-semiconductor M3, the positive input termination led drive circuit internal reference voltage VREF of A1, the negative input end of A1 connects the source electrode of metal-oxide-semiconductor M3, the grid of the output termination M3 of A1; Described some resistance comprises resistance R 1, R2 and R4, the drain electrode of R1 one termination metal-oxide-semiconductor M3, and the other end is as the Vin port of led drive circuit, and R2 connects the source electrode of M3, other end series connection R4, R4 ground connection;

Wherein, described comparison module (11) comprises comparator A2, and the negative input end of A2 connects the drain electrode of M3, and the positive input terminal of A2 is as the CS port of led drive circuit;

Wherein, described driver module (12) comprises driver A3, the output of the input termination A2 of A3;

Wherein, described switch module (13) comprises metal-oxide-semiconductor M1 and M2, and the grid of M1 and M2 all is connected the output of A3, the source grounding of M1 and M2, and the drain electrode of M2 is connected between R2 and the R4, and the drain electrode of M1 is as the SW port of led drive circuit;

Wherein, described metal-oxide-semiconductor M1, M2 and M3 can be N channel enhancement metal-oxide-semiconductor, also described metal-oxide-semiconductor M1, M2 and M3 can be replaced with NPN type triode;

Because the threshold setting module (10) of described led drive circuit clamps down on the source voltage V1 size of described metal-oxide-semiconductor M3 for being constantly equal to led drive circuit internal reference voltage VREF, so at M2 on off state one regularly, the electric current I 2 that flows through resistance R 2 is definite value.

Can adopt compensating resistance (14-1) for first kind of compensating module (14-1), as shown in Figure 7, the connected mode of compensating resistance (14-1) is: the Vin port of the described led drive circuit of compensating resistance R3 cross-over connection and the source electrode of metal-oxide-semiconductor M3.

The connected mode of described compensating resistance (14-1) can also for: draw a port from the source electrode of described metal-oxide-semiconductor M3, compensating resistance R3 is at this port of outside cross-over connection of led drive circuit and the Vin port of led drive circuit.

Circuit as shown in Figure 7, its compensation principle that increases compensating resistance (14-1) is as follows:

Because among Fig. 7, I1 is the electric current that flows through on the R1, I2 is the electric current that flows through on the R2, and I3 is the electric current that flows through on the R3, and follower output voltage V 1 equals VREF.Increase after the R3 resistance, when Vin voltage raises, because VREF is constant, the pressure reduction at R3 two ends increases, and the electric current I 3 that flows through R3 increases, and regularly electric current is constant because I2 is at M2 on off state one, and I1=I2-I3, the electric current I 1 that flows through R1 reduces, and current threshold Imax and Imin are reduced.When because the value that the average current that Imax and Imim reduce to cause reduces and Vin increase the value of the average current increase that causes when equating, the value that output current changes with Vin levels off to zero, and select the R3 resistance of suitable size can obtain good compensation characteristic this moment.R3 resistance value size is calculated as follows:

During switch M2 conducting state,

$I1=I2-I3=\frac{\mathrm{VREF}}{R2}-\frac{\mathrm{Vin}-\mathrm{<figure-callout\; id="3"\; label="VREF\; R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">VREF</figure-callout>}}{R},$

Like this, upper limit current Imax becomes Imax3 by (1) formula,

$I\max 3=(\frac{\mathrm{VREF}}{R2}-\frac{\mathrm{Vin}-\mathrm{VREF}}{R3})\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}---\left(10\right)$

In like manner can get, when switch M2 turn-offed, Imin was by the corresponding Imin3 that becomes of (2) formula:

$I\mathrm{<figure-callout\; id="3"\; label="min"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">min</figure-callout>}3=(\frac{\mathrm{<figure-callout\; id="2"\; label="VREF\; R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">VREF</figure-callout>}}{R}-\frac{\mathrm{Vin}-\mathrm{VREF}}{R3})\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}---\left(11\right)$

When Vin changes delta Vin, I3, I1, the variable quantity of Imax3 and Imin3 is

$\mathrm{\&Delta;I}3=\frac{\mathrm{\&Delta;Vin}}{R3}---\left(12\right)$

$\mathrm{\&Delta;I}1=-\frac{\mathrm{\&Delta;Vin}}{R3}---\left(13\right)$

$\mathrm{\&Delta;}I\max 3=-\frac{\mathrm{\&Delta;<figure-callout\; id="3"\; label="Vin\; R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Vin</figure-callout>}}{R}\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}---\left(14\right)$

$\mathrm{\&Delta;}I\mathrm{<figure-callout\; id="3"\; label="min"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">min</figure-callout>}3=-\frac{\mathrm{\&Delta;<figure-callout\; id="3"\; label="Vin\; R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Vin</figure-callout>}}{R}\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}---\left(15\right)$

When Vin changed, the electrorheological that the R3 compensation causes turned to:

$\mathrm{\&Delta;<figure-callout\; id="3"\; label="Iavg"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Iavg</figure-callout>}3=\frac{1}{2}(\mathrm{\&Delta;}I\max 3+\mathrm{\&Delta;}I\min 3)=-\frac{\mathrm{\&Delta;<figure-callout\; id="3"\; label="Vin\; R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Vin</figure-callout>}}{R}\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}---\left(16\right)$

By (8) Shi Kede, when Vin changed, the electrorheological that Tdly1 causes turned to:

$\mathrm{\&Delta;<figure-callout\; id="1"\; label="Iavg"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Iavg</figure-callout>}1=\frac{1}{2}\frac{\mathrm{\&Delta;Vin}}{L}\&times;\mathrm{Tdly}1---\left(17\right)$

If Δ Iavg3=-Δ Iavg1 (18)

Vin changes the average current variation that causes can be adjusted to zero.

With (16) and (17) substitutions (18) formula, can get:

$\frac{\mathrm{\&Delta;<figure-callout\; id="3"\; label="Vin\; R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Vin</figure-callout>}}{R}\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}=\frac{1}{2}\frac{\mathrm{\&Delta;Vin}}{L}\&times;\mathrm{Tdly}1---\left(19\right)$

Therefore, can obtain the relation of R3 and R1:

$\mathrm{<figure-callout\; id="3"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">R</figure-callout>}3=\frac{2L}{\mathrm{Rsense}\&times;\mathrm{<figure-callout\; id="1"\; label="Tdly"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Tdly</figure-callout>}1}\&times;R1---\left(20\right)$

Like this, in circuit, add resistance value and the proportional R3 resistance of R1, can well compensate the variation that Vin changes the average current that causes.For example: L is 47uH in the supposing the system, and Rsense is 0.5 ohm, and Tdly1 is 100ns, and the value of R3 can be set to 1880 * R1.

When sampling resistor Rsense not simultaneously, if the R3 resistance sizes is certain, the size of corresponding adjustment inductance L can compensate the variation of Vin under the various output currents.

Wherein, draw the output port of a port when adopting as the led drive circuit of band output current compensation from the source electrode of described metal-oxide-semiconductor M3, compensating resistance R3 is when the connected mode of the Vin port of this output port of outside cross-over connection of led drive circuit and led drive circuit, and resistance R 3 can be regulated according to peripheral environment.

Wherein, when the connected mode of the source electrode of Vin port that adopts the described led drive circuit of compensating resistance R3 cross-over connection as shown in Figure 7 and metal-oxide-semiconductor M3, resistance R 3 becomes several thousand times ratio with R1, R1 is generally several kilohms in line design, so the value of R3 is about tens megohms, if adopt integrated circuit, the area that R3 occupies led drive circuit is very big, is unfavorable for saving cost.

Can also adopt current mirror module (14-1) for first kind of compensating module (14-1), as shown in Figure 8, it is characterized in that: described current mirror module (14-1) comprises current mirror circuit 1, current mirror circuit 2 and resistance R 5;

Wherein, described current mirror circuit 1 is made of two common emitters, grounded base triode Q3 and Q4, the emitter of two pipes all links to each other with power supply VCC, the base stage of triode Q3 links to each other with the collector electrode of self, and the collector electrode of triode Q4 links to each other with the source electrode of metal-oxide-semiconductor M3 in the described led drive circuit;

Wherein, described current mirror circuit 2 is made of two common emitters, grounded base triode Q1 and Q2, the equal ground connection of the emitter of two pipes, the base stage of triode Q1 links to each other with the collector electrode of self, and the collector electrode of triode Q2 links to each other with the collector electrode of triode Q3 in the described current mirror circuit 1;

Wherein, the collector electrode of the triode Q1 of current mirror circuit 1 in described resistance R 5 cross-over connection input voltage vin and the described current mirror module;

Wherein, described triode Q3 and Q4 are the positive-negative-positive triode, and triode Q1 and Q2 are NPN type triode;

The compensation principle of current mirror circuit module (14-1) shown in Figure 8 is: by Q1, Q2 forms image current, and Q3, Q4 forms image current, reduces electric current step by step, flows through the electric current I 5 of I5 with increase, R5 resistance is reduced, thereby reduce the resistor area of led drive circuit.

Adjust Q1, Q2 and Q3, the area size of Q4 makes SQ1:SQ2=K1, SQ3:SQ4=K2, and K1 * K2=K3, SQ1, SQ2, SQ3, SQ4 are Q1, Q2, Q3, the area of Q4.

Like this, electric current $I4=\frac{I5}{\mathrm{<figure-callout\; id="3"\; label="K"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">K</figure-callout>}3},$ That is:

$I4=\frac{\mathrm{Vin}-\mathrm{<figure-callout\; id="3"\; label="Vbe\; K"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Vbe</figure-callout>}}{K}---\left(21\right)$

During Vin changes delta Vin, because Vbe (base stage-emitter voltage of Q1 is poor) changes not quite, can ignore, the I4 electrorheological turns to:

$\mathrm{\&Delta;}I4=\frac{\mathrm{\&Delta;<figure-callout\; id="3"\; label="Vin\; K"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Vin</figure-callout>}}{K}---\left(22\right)$

Formula (22) is compared with formula (12), many COEFFICIENT K 3, through and first kind of derivation that compensation method is identical, can obtain the relation of R5 and R1:

$\mathrm{<figure-callout\; id="5"\; label="R"\; filenames="Y200820083015E00202.png"\; state="\{\{state\}\}">R</figure-callout>}5=\frac{2L}{\mathrm{Rsense}\&times;\mathrm{<figure-callout\; id="1"\; label="Tdly"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Tdly</figure-callout>}1\&times;\mathrm{<figure-callout\; id="3"\; label="K"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">K</figure-callout>}3}\&times;R1---\left(23\right)$

Like this, setting the K3 value is 10 or 20 resistance R 5 can be reduced to 1/10 or 1/20 of original R3.

Wherein, described triode Q3 and Q4 also can replace with P channel MOS tube M8 and M9, and correspondence connects as shown in Figure 9, the same Fig. 8 of its compensation principle.

Current compensation circuit as Fig. 7, Fig. 8, led drive circuit shown in Figure 9, under the situation that led drive circuit internal delay time, sampling resistor and inductance are determined, when the led drive circuit input voltage changes, can be by regulating the threshold voltage of comparator A2, threshold current to LED load in the external led circuit of led drive circuit compensates, thereby output current is compensated.If sampling resistor changes, can adjust the inductance size, make degree of compensation the same.

Figure 10 compensates front and back for adopting Fig. 7 of the present invention, Fig. 8, current mirror circuit shown in Figure 9, the simulation waveform figure that output current changes input voltage, and among Figure 10, Iavg is an output current, in 6～30V scope, electric current changes 25mA.Iavg3 can see that for the later current average of compensation after the compensation, output current changes very little with input voltage, about about 1mA.

Can adopt sampling mirror image module (14-2) for the second kind of compensating module (14-2) among Fig. 6, as shown in figure 11, it is characterized in that described sampling mirror image module (14-2) comprises output voltage sampling circuit and current mirror circuit 3;

Wherein, described output voltage sampling circuit is by common emitter, grounded base triode Q5 and Q6, and triode Q7 and resistance R 6 compositions; The emitter-base bandgap grading that Q5 links to each other with Q6 is connected to the CS end of led drive circuit, and the collector electrode of Q6 links to each other with the base stage of self, makes Q5 and Q6 form current mirror; The emitter of triode Q7 links to each other with the collector electrode of Q5, and the base stage of Q7 is connected to the negative pole of LED load as the SNS port of described led drive circuit; The base stage of resistance R 6 cross-over connection Q7 and the collector electrode of Q6;

Wherein, described current mirror circuit 3 constitutes the source ground that M4 links to each other with M5 by metal-oxide-semiconductor M4 and the M5 that common gate, common source connect; The drain electrode of M5 links to each other with the grid of self, and links to each other with the drain electrode of metal-oxide-semiconductor Q7 in the described output voltage sampling circuit; The drain electrode of M5 links to each other with the source electrode of metal-oxide-semiconductor M3 in the described led drive circuit;

Wherein, described triode Q5, Q6, Q7 are the positive-negative-positive triode, and described metal-oxide-semiconductor M4, M5 are the N-channel MOS pipe.

The compensation principle of current mirror circuit module (14-2) as shown in figure 11 is:

Because the described output voltage sampling circuit size that can gather the output voltage V out at load LED two ends, and be reflected on the electric current I 6 of the resistance R 6 of flowing through, convert electric current to by the output of Q5 mirror image with the form of electric current.M4 and M5 form current mirror circuit.Electric current I 8 on the M5 is proportional with I6, thereby changes the threshold value of output current, makes a concrete analysis of as follows:

$I6=\frac{\mathrm{Vout}-\mathrm{Vbe}}{R6}---\left(24\right)$

$I8=\frac{I6}{K4}---\left(25\right)$

K is Q6 and Q5, the product of the area ratio coefficient of M4 and M5.

I1＝I2+I8 (26)

Vout changes the I8 that causes, the changing value of I1 and threshold current Imax and Imin is:

$\mathrm{\&Delta;I}8=\frac{\mathrm{\&Delta;<figure-callout\; id="4"\; label="Vout\; K"\; filenames="Y200820083015E00181.png"\; state="\{\{state\}\}">Vout</figure-callout>}}{K}---\left(27\right)$

$\mathrm{\&Delta;I}1=\mathrm{\&Delta;I}8=\frac{\mathrm{\&Delta;<figure-callout\; id="4"\; label="Vout\; K"\; filenames="Y200820083015E00181.png"\; state="\{\{state\}\}">Vout</figure-callout>}}{K}---\left(28\right)$

$\mathrm{\&Delta;}I\max 6=\frac{\mathrm{\&Delta;<figure-callout\; id="4"\; label="Vout\; K"\; filenames="Y200820083015E00181.png"\; state="\{\{state\}\}">Vout</figure-callout>}}{K}\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}---\left(29\right)$

$\mathrm{\&Delta;}I\min 6=\frac{\mathrm{\&Delta;<figure-callout\; id="4"\; label="Vout\; K"\; filenames="Y200820083015E00181.png"\; state="\{\{state\}\}">Vout</figure-callout>}}{K}\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}---\left(30\right)$

Δ Im ax6 and Δ Im in6 are for adding the later threshold current changing value of compensation.

During Vout changes delta Vout, the electric current that the R6 compensation causes changes size and is:

$\mathrm{\&Delta;Iavg}6=\frac{1}{2}(\mathrm{\&Delta;}I\max 6+\mathrm{\&Delta;}I\min 6)=\frac{\mathrm{\&Delta;Vout}}{R6}\&times;\frac{\mathrm{<figure-callout\; id="1"\; label="R"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">R</figure-callout>}1}{\mathrm{Rsense}}---\left(31\right)$

Obtained by (9) formula, during Vout changes delta Vout, time-delay Tdly1, the electric current that Tdly2 causes change size and are:

$\mathrm{\&Delta;<figure-callout\; id="2"\; label="Iavg"\; filenames="Y200820083015E00201.png,Y200820083015E00202.png"\; state="\{\{state\}\}">Iavg</figure-callout>}2=-\frac{\mathrm{\&Delta;Vout}}{2L}\&times;(\mathrm{<figure-callout\; id="1"\; label="Tdly"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Tdly</figure-callout>}1+\mathrm{Tdly}2)---\left(32\right)$

Make Δ Iavg6=-Δ Iavg2, like this, the variation of the output current that time-delay causes is by full remuneration.

(31) and (32) formula substitution is obtained:

$R6=\frac{2L}{(\mathrm{<figure-callout\; id="1"\; label="Tdly"\; filenames="Y200820083015E00201.png,Y200820083015E00212.png"\; state="\{\{state\}\}">Tdly</figure-callout>}1+\mathrm{Tdly}2)\&times;\mathrm{Rsense}\&times;\mathrm{<figure-callout\; id="4"\; label="K"\; filenames="Y200820083015E00181.png"\; state="\{\{state\}\}">K</figure-callout>}4}\&times;R1---\left(33\right)$

Therefore, the current compensation circuit of led drive circuit as shown in figure 11, under the situation that led drive circuit internal delay time, sampling resistor and inductance are determined, when the external LED output voltage of led drive circuit changes, by regulating the threshold voltage of comparator A2, threshold current to the external LED load of led drive circuit compensates, thereby the LED output current is compensated.If sampling resistor changes, can adjust the inductance size, make degree of compensation identical.

Wherein, described triode Q5, Q6, Q7 can replace with the P channel MOS tube, and its corresponding connected mode in like manner;

Wherein, described metal-oxide-semiconductor M4, M5 can replace with NPN type triode, corresponding connected mode such as Figure 12, the same Figure 11 of its compensation principle.

Figure 11, embodiment illustrated in fig. 12 in, suppose that L is 47uH in the external led circuit, Rsense is 0.5 ohm, Tdly1, Tdly2 is approximately 100ns, K4 is set to 10, obtains the value of R6 after can calculating by formula (33).Computation structure according to R6 is carried out emulation, simulation waveform as shown in figure 13, the waveform that Iavg changes with output voltage for output current before the compensation among Figure 13, Iavg6 is the waveform of output current after compensating, can see the variation of having eliminated output current when output voltage changes after the compensation dry straightly.

The utility model can also as compensating resistance is made up with sampling mirror image module, perhaps make up with the current mirror module compensating resistance, current mirror module, three kinds of compensating module combinations of sampling mirror image module, as shown in figure 14 with sampling mirror image module.Combined compensation circuit as shown in figure 14, when input voltage changes, the same Fig. 8 of compensation principle; When output voltage changes, the same Figure 11 of compensation principle, the current compensation circuit compensation external input voltage Vin that realizes led drive circuit change influence to the LED output current that led drive circuit drove or/and the external LED output voltage that the compensation LED drive circuit is driven changes the influence to the LED output current.

Output current compensating circuit as led drive circuit described in the utility model, need to know the time of delay of the output current compensating circuit of led drive circuit in the practical application, according to the parameter size of the size decision compensating circuit element of external inductance of the output current compensating circuit of led drive circuit and sampling resistor.If compensation is certain, when sampling resistor changes, can regulates external inductance, thereby circuit is better compensated.

The utility model discloses the output current compensating circuit of led drive circuit under the ring control model that stagnates, and describe embodiment of the present utility model and effect with reference to the accompanying drawings.What should be understood that is: the foregoing description is just to explanation of the present utility model; rather than to restriction of the present utility model; any innovation and creation that do not exceed in the utility model connotation scope; include but not limited to modification to the composition mode of sample circuit and mirror image; to the change of the local structure of circuit (as utilize those skilled in the art thinkable technical method replace comparison module in the utility model; to replacing being connected of M1 and M2 etc.); to the replacement of the type or the model of components and parts (as with M1; M2; M3 replaces with NPN type triode etc. respectively); and the replacement of other unsubstantialities or modification, all fall within the utility model protection range.

Claims (17)

1.LED the output current compensating circuit of drive circuit is characterized in that comprising threshold setting module, comparison module, driver module, switch module and compensating module, wherein:

Described threshold setting module inserts the external input voltage Vin of led drive circuit by the Vin port of led drive circuit, while threshold setting module ground connection, make the threshold setting module after led drive circuit powers on, continue conducting, described threshold setting module comprises the voltage follow module, and the internal reference voltage VREF of described voltage follow module access led drive circuit and the output voltage of voltage follow module remain and equal internal reference voltage VREF;

The size of the sampled voltage of described comparison module compare threshold setting module preset threshold voltage and led drive circuit, the sampled voltage of led drive circuit is by CS port input comparison module, sampled voltage is the pressure reduction of Vin and CS port, threshold voltage is the pressure reduction of Vin and threshold setting module output voltage, when the sampled voltage of led drive circuit during less than threshold voltage, the output voltage of comparison module carries out signal by driver module and strengthens back starting switch module, when the sampled voltage of led drive circuit during greater than threshold voltage, the output voltage of comparison module carries out signal by driver module and strengthens back stopcock module;

Described switch module is regulated the electric current of threshold setting module by the conducting or the shutoff of switch module simultaneously, thereby is regulated the threshold voltage of threshold setting module settings by the break-make of the external led circuit of the SW port controlling led drive circuit of led drive circuit.

2. the output current compensating circuit of led drive circuit as claimed in claim 1, it is characterized in that described compensating module is connected to the Vin port of led drive circuit, when led drive circuit inserts external input voltage Vin, compensating module is regulated the threshold voltage of the threshold setting module of led drive circuit, and the variation of compensation external input voltage Vin is to the influence of LED output current in the external led circuit that led drive circuit drove.

3. the output current compensating circuit of led drive circuit as claimed in claim 1, it is characterized in that described compensating module is connected to the CS port and the SNS port of led drive circuit, when led drive circuit CS port and SNS port are connected to LED two ends in the external led circuit of led drive circuit (LED output voltage), compensating module is adjusted the threshold voltage of the threshold setting module of led drive circuit, and the variation of the external LED output voltage that the compensation LED drive circuit is driven is to the influence of external LED output current.

4. as the output current compensating circuit of claim 2 or 3 described led drive circuits, it is characterized in that:

Described threshold setting module comprises voltage follow module and some resistance: described voltage follow module is made of operational amplifier A 1 and metal-oxide-semiconductor M3, the positive input termination led drive circuit internal reference voltage VREF of A1, the negative input end of A1 connects the source electrode of metal-oxide-semiconductor M3, the grid of the output termination M3 of A1; Described some resistance comprises resistance R 1, R2 and R4, the drain electrode of R1 one termination metal-oxide-semiconductor M3, and the other end is as the Vin port of led drive circuit, the source electrode of R2 cross-over connection M3 and the drain electrode of M2, drain electrode and the source electrode of R4 cross-over connection M2;

Described comparison module comprises comparator A2, and the negative input end of A2 connects the drain electrode of M3, and the positive input terminal of A2 is as the CS port of led drive circuit;

Described driver module comprises driver A3, the output of the input termination A2 of A3;

Described switch module comprises metal-oxide-semiconductor M1 and M2, and the grid of M1 and M2 all is connected the output of A3, the source grounding of M1 and M2, and the drain electrode of M1 is as the SW port of led drive circuit;

Described metal-oxide-semiconductor M1, M2 and M3 can be N channel enhancement metal-oxide-semiconductor.

5. the output current compensating circuit of led drive circuit as claimed in claim 2 is characterized in that described compensating module can adopt compensating resistance.

6. the output current compensating circuit of led drive circuit as claimed in claim 5 is characterized in that the connected mode of described compensating resistance is: the Vin port of the described led drive circuit of compensating resistance R3 cross-over connection and the source electrode of metal-oxide-semiconductor M3.

7. the output current compensating circuit of led drive circuit as claimed in claim 5, the connected mode that it is characterized in that described compensating resistance is: draw the output port of a port as the led drive circuit of band output current compensation from the source electrode of described metal-oxide-semiconductor M3, compensating resistance R3 is at this output port of outside cross-over connection of led drive circuit and the Vin port of led drive circuit.

8. the output current compensating circuit of led drive circuit as claimed in claim 2 is characterized in that described compensating module can adopt the current mirror module.

9. the output current compensating circuit of led drive circuit as claimed in claim 8 is characterized in that described current mirror module comprises: current mirror circuit 1, current mirror circuit 2 and resistance R 5; Wherein:

Described current mirror circuit 1 is made of two common emitters, grounded base triode Q3 and Q4, the emitter of two pipes all links to each other with power supply VCC, the base stage of triode Q3 links to each other with the collector electrode of self, and the collector electrode of triode Q4 links to each other with the source electrode of metal-oxide-semiconductor M3 in the described led drive circuit;

Described current mirror circuit 2 is made of two common emitters, grounded base triode Q1 and Q2, the equal ground connection of the emitter of two pipes, the base stage of triode Q1 links to each other with the collector electrode of self, and the collector electrode of triode Q2 links to each other with the collector electrode of triode Q3 in the described current mirror circuit 1;

The collector electrode of the triode Q1 of current mirror circuit 1 in described resistance R 5 cross-over connection input voltage vin and the described current mirror module.

10. the output current compensating circuit of led drive circuit as claimed in claim 9 is characterized in that described triode Q3 and Q4 are the positive-negative-positive triode, and triode Q1 and Q2 are NPN type triode.

11. the output current compensating circuit of led drive circuit as claimed in claim 9 is characterized in that described triode Q3 and Q4 also can replace with the P channel MOS tube, its corresponding connected mode in like manner.

12. the output current compensating circuit of led drive circuit as claimed in claim 9 is characterized in that described triode Q1 and Q2 also can replace with the N-channel MOS pipe, its corresponding connected mode in like manner.

13. the output current compensating circuit of led drive circuit as claimed in claim 4 is characterized in that described compensating module can adopt sampling mirror image module.

14. the output current compensating circuit of led drive circuit as claimed in claim 13 is characterized in that described sampling mirror image module comprises output voltage sampling circuit and current mirror circuit 3;

Described output voltage sampling circuit is by common emitter, grounded base triode Q5 and Q6, and triode Q7 and resistance R 6 compositions; The emitter-base bandgap grading that Q5 links to each other with Q6 is connected to the CS end of led drive circuit, and the collector electrode of Q6 links to each other with the base stage of self, makes Q5 and Q6 form current mirror; The emitter of triode Q7 links to each other with the collector electrode of Q5, and the base stage of Q7 is connected to the negative pole of LED load as the SNS port of described led drive circuit; The base stage of resistance R 6 cross-over connection Q7 and the collector electrode of Q6;

Described current mirror circuit 3 constitutes the source ground that M4 links to each other with M5 by metal-oxide-semiconductor M4 and the M5 that common gate, common source connect; The drain electrode of M5 links to each other with the grid of self, and links to each other with the drain electrode of metal-oxide-semiconductor Q7 in the described output voltage sampling circuit; The drain electrode of M5 links to each other with the source electrode of metal-oxide-semiconductor M3 in the described led drive circuit.

15. the output current compensating circuit of led drive circuit as claimed in claim 14 is characterized in that described triode Q5, Q6, Q7 are the positive-negative-positive triode, described metal-oxide-semiconductor M4, M5 are the N-channel MOS pipe.

16. the output current compensating circuit of led drive circuit as claimed in claim 15 is characterized in that described triode Q5, Q6, Q7 can replace with the P channel MOS tube, its corresponding connected mode in like manner.

17. the output current compensating circuit of led drive circuit as claimed in claim 15 is characterized in that described metal-oxide-semiconductor M4, M5 can replace with NPN type triode, its corresponding connected mode in like manner.

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