CN1917394A - Method and system for sending sequence of pilot freqency in system of multiple antenna and carriers - Google Patents

Abstract

The method comprises: determining the pilot frequency carrier numbers M and grouping the pilot frequency carrier; M is not less than the product of all transmitting antenna numbers and multi path numbers, and is even times of all transmitting antenna numbers; the pilot frequency carrier numbers in each group is two times of all transmitting antenna numbers; the pilot frequency carrier in each group is distributed in equal interval; all transmitting antenna transmits pilot frequency sequence on same transmitting symbol and pilot frequency; wherein, the pilot frequency sequences of different transmitting antenna are distributed in equipower and have phase quadrature each other. The invention also reveals pilot frequency transmitting device and receive thereof.

Description

Pilot frequency sequence sending method and system in the multiple antenna and carrier system

Technical field

The present invention relates to the multi-antenna multi-carrier-wave technical field, more particularly, the present invention relates to pilot frequency sequence sending method and system in the multiple antenna and carrier system.

Background technology

The development trend of future mobile communications business is the multimedia service of high-quality, and the requirement of cell throughout will be brought up to 100Mbps～1Gbps.Industry is anticipated the business that can realize two-forty like this in the period of the 2012-2015, but rapidly increase with service rate conflictingly be: the resource of frequency spectrum is limited.In order to realize the message transmission of two-forty on limited frequency spectrum resources, feasible way is exactly the higher new air interface technologies of the exploitation availability of frequency spectrum.Multiple-input and multiple-output (MIMO) technology (being multi-antenna technology) can greatly improve spectrum efficiency, thereby raising radio system capacity, but when it and the Wideband Code Division Multiple Access (WCDMA) (WCDMA) of present 3-G (Generation Three mobile communication system) (3G) when air interface combines, it is handled complexity and becomes cubic relationship with system bandwidth, and this design to receiver brings great difficulty.

Multi-antenna technology combines with multi-transceiver technology, not only can realize the extensibility of system bandwidth, and its processing complexity is only linear with system bandwidth.Therefore receive increasing concern on the world in recent years, and will become the core technology of next generation wireless communication system physical layer.In the receiver of multiple antenna and carrier system, before carrying out diversity merging, coherent detection and decoding, must the precognition channel parameter.The quality of precision of channel estimation is most important for the follow-up work of treatment of receiver.In addition, different with a single aerial system is, because all transmitting antennas send signal simultaneously continuously, what receive on reception antenna is aliasing from the signal of all transmitting antennas, and this has brought bigger difficulty to channel estimating.

At present, the method for channel estimating blind estimation is arranged usually, based on the estimation of targeting sequencing with based on the estimation of frequency pilot sign.Method of estimation based on frequency pilot sign can be followed the tracks of channel state variations and the low advantage of expense fast owing to having, and is fit to more be applied in the fast-changing wireless propagation environment.In real system, for fear of the zone of roll-offing of filter frequency domain response signal is caused distortion, usually that the part carrier wave of transmission bandwidth is vacant as the protection frequency band.

Up to the present, the sequence of pilot symbols at the multiple antenna and carrier system that the protection frequency band is arranged obviously is short of.Though proposed several pilot frequency sequences at present, as the sequence of pilot symbols of even distribution phase quadrature and the sequence of pilot symbols of non-uniform Distribution, these sequence of pilot symbols all have corresponding shortcoming.

Equally distributed sequence of pilot symbols is under the prerequisite that all subcarriers are all supposed to use, and satisfies the long sequence of quadrature between antenna.Owing to do not consider the protection frequency band that exists in the real system,, only be suitable for that all carrier waves of system all are used, the situation of unprotect frequency band so it only be the pilot frequency sequence of optimum in theory.In the time of in it being applied in the real system that has the protection frequency band,, just can not guarantee channel estimated accuracy such as in the environment of the low signal-to-noise ratio or the high speed of a motor vehicle.

The sequence of pilot symbols of non-uniform Distribution can improve the lower bound of minimum pilot overhead, and need pass through a large amount of calculating by the distribution that the gradient iterative algorithm is found the solution pilot power, how searches on the optimum pilot frequency carrier wave problem simultaneously to be still waiting deeply.

Summary of the invention

In view of this, main purpose of the present invention is the pilot frequency sequence sending method that proposes in a kind of multiple antenna and carrier system, to reduce the influence of protection frequency band to the pilot frequency sequence orthogonality.

Another object of the present invention is the pilot frequency sequence transmitting system that proposes in a kind of multiple antenna and carrier system, to reduce the influence of protection frequency band to the pilot frequency sequence orthogonality.

Another object of the present invention is to propose a kind of transmitter, to reduce the influence of protection frequency band to the pilot frequency sequence orthogonality.

A further object of the present invention is to propose a kind of receiver, to reduce the influence of protection frequency band to the pilot frequency sequence orthogonality.

For achieving the above object, technical scheme of the present invention is achieved in that

A kind of pilot frequency sequence sending method of multiple antenna and carrier system, this method comprises:

Determine the pilot frequency carrier wave number M and pilot frequency carrier wave is divided into groups, total number of transmit antennas that is no less than M multiply by the long-pending of channel multi-path number, and M is the even-multiple of total number of transmit antennas, and the number of every group of interior pilot frequency carrier wave is the twice of total number of transmit antennas, and the pilot frequency carrier wave intersection is spacedly distributed in every group;

All transmitting antennas send pilot frequency sequence on identical transmission symbol and pilot frequency carrier wave, wherein the pilot frequency sequence of different transmit antennas each other constant power distribute and quadrature in phase.

Described pilot frequency carrier wave grouping is comprised: with pilot frequency carrier wave be divided into G '= ^M/ _2NtGroup; The number 2N of pilot frequency carrier wave in every group _t, be designated { k _0+g2Nt, k _1+g2Nt..., k _2Nt-2+g2Nt, k _2Nt-1+g2Nt, g=0,1 ..., G '; The pilot frequency carrier wave intersection is spacedly distributed in every group, satisfies $k_{N_t+g2N_t}-{\mathrm{<figure-callout\; id="0"\; label="k"\; filenames="A20061012686400182.png,A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_{0+g2N_t}=\&CenterDot;\&CenterDot;\&CenterDot;=k_{2N_t-1+g2N_t}-k_{N_t-1+g2N_t}=\frac{N}{2D},$ Wherein total number of transmit antennas is N _t, the total carrier wave number of system is N, D is the parameter that the decision pilot carrier position detects.

The value of described D makes function $F\left(D\right)=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}(2+2\cos \mathrm{\&pi;}\frac{d}{D})$ The value minimum, wherein L is the channel multi-path number.The k of any two transmit antennas s, p _iThe phase difference of the frequency pilot sign on the individual pilot frequency carrier wave is θ _i ^Sp, wherein ${\mathrm{\&theta;}}_i^{\mathrm{sp}}=\frac{2\mathrm{\&pi;i}(s-p)}{N_t},$ Total number of transmit antennas is N _t

A kind of pilot frequency sequence transmitting system of multiple antenna and carrier system, this system comprises:

The pilot frequency carrier wave number is determined and grouped element, be used for determining the pilot frequency carrier wave number M, and pilot frequency carrier wave divided into groups, total number of transmit antennas that is no less than M multiply by the long-pending of channel multi-path number, and M is the even-multiple of total number of transmit antennas, the number of pilot frequency carrier wave is the twice of total number of transmit antennas in every group, and the pilot frequency carrier wave intersection is spacedly distributed in every group;

Transmitting antenna is used for sending pilot frequency sequence on identical transmission symbol and carrier wave, wherein the pilot frequency sequence of different transmit antennas each other constant power distribute and quadrature in phase.

Described pilot frequency carrier wave number determines and grouped element, be used for pilot frequency carrier wave be divided into G '= ^M/ _2NtGroup, the number 2N of every group of interior pilot frequency carrier wave _t, be designated { k _0+g2Nt, k _1+g2Nt..., k _2Nt-2+g2Nt, k _2Nt-1+g2Nt, g=0,1 ..., G '; Wherein total number of transmit antennas is N _t, the total carrier wave number of system is N; And

The pilot frequency carrier wave intersection is spacedly distributed in every group, satisfies $k_{N_t+g2N_t}-{\mathrm{<figure-callout\; id="0"\; label="k"\; filenames="A20061012686400182.png,A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_{0+g2N_t}=\&CenterDot;\&CenterDot;\&CenterDot;=k_{2N_t-1+g2N_t}-k_{N_t-1+g2N_t}=\frac{N}{2D},$ Wherein D is the parameter that the decision pilot carrier position detects.

The value of described D makes function $F\left(D\right)=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}(2+2\cos \mathrm{\&pi;}\frac{d}{D})$ The value minimum, wherein L is the channel multi-path number.

The k of any two transmit antennas s, p _iThe phase difference of the frequency pilot sign on the individual pilot frequency carrier wave is θ _i ^Sp, wherein ${\mathrm{\&theta;}}_i^{\mathrm{sp}}=\frac{2\mathrm{\&pi;i}(s-p)}{N_t},$ Total number of transmit antennas is N _t

A kind of transmitter, this transmitter comprise as above each described pilot frequency sequence transmitting system.

A kind of receiver is used to receive the pilot frequency sequence that is sent by as above each described pilot frequency sequence transmitting system.

From technique scheme as can be seen, in the present invention, at first determine the pilot frequency carrier wave number M and pilot frequency carrier wave is divided into groups, wherein M is no less than total number of transmit antennas and multiply by the long-pending of channel multi-path number, and M is the even-multiple of total number of transmit antennas, the number of pilot frequency carrier wave is the twice of total number of transmit antennas in every group, and the pilot frequency carrier wave intersection is spacedly distributed in every group; All transmitting antennas send pilot frequency sequence on identical transmission symbol and pilot frequency carrier wave then, and the pilot frequency sequence of different transmit antennas constant power each other distributes and quadrature in phase.This shows that use after the present invention, frequency band can be avoided protecting in the position of each group pilot frequency carrier wave, reasonable distribution is protected the influence of frequency band to the pilot frequency sequence orthogonality thereby reduced flexibly.

In addition, the present invention can suitably choose rational pilot-frequency expense according to the requirement of system design in actual applications, and the performance that makes system is near ideal communication channel estimation performance lower bound.

Description of drawings

Fig. 1 is the pilot frequency sequence sending method schematic flow sheet in the multiple antenna and carrier system of the present invention.

Fig. 2 is frequency domain transmission OFDM (OFDM) the symbolic construction schematic diagram of the one exemplary embodiment according to the present invention.

Fig. 3 is the structural representation according to the pilot frequency sequence transmitting system in the multiple antenna and carrier system of the present invention.

Fig. 4 is one exemplary embodiment according to the present invention, in the ofdm system of two transmitting antennas, two reception antennas, adopts bit error rate (BER) performance map of space-time/frequency block code (SFBC), turbine (Turbo) coding.

Embodiment

For making the purpose, technical solutions and advantages of the present invention express clearlyer, the present invention is further described in more detail below in conjunction with drawings and the specific embodiments.

At first algorithm of the present invention is elaborated:

At first statement:

The pseudoinverse of representing matrix A; A ^HThe conjugate transpose of representing matrix A; A ^*The conjugation of representing matrix A; The mark of tr (A) representing matrix A; ‖ A ‖ _FThe Frobenius norm of representing matrix A; The min function representation is got minimum value;

Total number of transmit antennas of supposing multiple antenna and carrier system is N _t, the channel multi-path number is L, the total carrier wave number of system is N, and the number M of pilot frequency carrier wave, P is a gross power of distributing to pilot frequency sequence, and is as follows according to the principle of pilot frequency sequence of the present invention:

The pilot signal that receives on every antenna is $Y_{M\&times;1}=A_{M{\&times;N}_{t}L}{h}_{N_{t}L\&times;1}+w_{\mathrm{noise}},$ Wherein: h _{NtL * 1}It is the time domain channel response of corresponding all transmitting antennas; $A_{M\&times;N_{t}L}=[{X_{M\&times;M}}^1{F}_{M\&times;L},\&CenterDot;\&CenterDot;\&CenterDot;,{X_{M\&times;M}}^{N_t}{F}_{M\&times;L}]$ It is the matrix that the pilot signal by all transmitting antennas constitutes;

X _{M * M} ⁱThe diagonal matrix of representing the frequency pilot sign formation of i antenna;

F _{M * L}Expression Fourier transform battle array.

According to time domain LS algorithm, have only as M 〉=N _tL, promptly during A array full rank, its pseudoinverse just exists, and therefore obtains channel estimating ${\hat{H}}_{\mathrm{estimated}}=A^{+}Y,$ So the number M of pilot frequency carrier wave must not be less than N _tL.

Time domain LS algorithm $\mathrm{MSE}=\frac{{\mathrm{\&sigma;}}_{\mathrm{<figure-callout\; id="2"\; label="w"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">w</figure-callout>}}^2}{{\mathrm{LN}}_t}\mathrm{tr}\left\{{\left(\begin{array}{cc}{A}^H& A\end{array}\right)}^{-1}\right\},$ When $\begin{array}{cc}{A}^H& A\end{array}=\stackrel{\&OverBar;}{P}{I}_{L{N}_t}$ The time, can obtain minMSE, wherein MSE represents mean square deviation.

Then

$F^H{X}^{p^H}{X}^{s}F=\left\{\begin{array}{ccc}\stackrel{\&OverBar;}{P}{I}_L& \mathrm{if}& p=s\\ 0_{L\&times;L}& \mathrm{if}& p\&NotEqual;s\end{array}\right.---\left(2\right)$

With F ^HX ^PHX ^sF launches and can get:

X wherein _i ^pRepresent that the p transmit antennas is at k _iFrequency pilot sign on the individual pilot frequency carrier wave;

{ τ ₀..., τ _L-1Each time delay directly of expression channel;

Order $x_i^p=\sqrt{P_i^p}{e}^{j{\mathrm{\&phi;}}_i^p},x_i^s=\sqrt{P_i^s}{e}^{j{\mathrm{\&phi;}}_i^s}$

When p ≠ s, $F^H{X}^{p^H}{X}^{s}F=0_{L\&times;L},$ Promptly for  a, b ∈ 0 ..., L-1} has

$\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}{x}_i^{p^{*}}{x}_i^{\mathrm{<figure-callout\; id="2"\; label="s\; e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">s</figure-callout>}}{e}^j{\frac{2\mathrm{\&pi;}{k}_i}{N}({\mathrm{\&tau;}}_a-{\mathrm{\&tau;}}_b)}^{}=\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}\sqrt{P_i^s{P}_i^p}{e}^{j({\mathrm{\&phi;}}_i^s-{\mathrm{\&phi;}}_i^p)}{e}^{\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;}{k}_i}{N}({\mathrm{\&tau;}}_a-{\mathrm{\&tau;}}_b)}=0---\left(4\right)$

When p=s, $F^H{X}^{p^H}{X}^{s}F=\stackrel{\&OverBar;}{P}{I}_L,$ Promptly for  a, b ∈ 0 ..., L-1}, (6) formula obviously satisfies.

$\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}{x}_i^{s^{*}}{x}_i^{\mathrm{<figure-callout\; id="2"\; label="s\; e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">s</figure-callout>}}{e}^j{\frac{2\mathrm{\&pi;}{k}_i}{N}({\mathrm{\&tau;}}_a-{\mathrm{\&tau;}}_b)}^{}=\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}{P}_i^{\mathrm{<figure-callout\; id="2"\; label="s\; e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">s</figure-callout>}}{e}^j{\frac{2\mathrm{\&pi;}{k}_i}{N}({\mathrm{\&tau;}}_a-{\mathrm{\&tau;}}_b)}^{}=0,a\&NotEqual;b---\left(5\right)$

$\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}{P}_i^s=\stackrel{\&OverBar;}{P},a=b---\left(6\right)$

Consider the situation that the pilot tone constant power distributes, promptly for  i, j ∈ 0,1 ..., M-1} has $P_i^s=P_j^s$ And  p, s ∈ 1,2 ..., N _tHave $P_i^s=P_i^p.$ Order ${\mathrm{\&phi;}}_i^s-{\mathrm{\&phi;}}_i^p={\mathrm{\&theta;}}_i^{\mathrm{sp}},$ τ _a-τ _b=d, then (4) formula and (5) formula can be reduced to:

$\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}{e}^{j[{\mathrm{\&theta;}}_i^{\mathrm{sp}}+\frac{2\mathrm{\&pi;}{k}_i}{N}d]}=0,d\&Element;\{-L+1,\&CenterDot;\&CenterDot;\&CenterDot;,0,\&CenterDot;\&CenterDot;\&CenterDot;,L-1\}---\left(7\right)$

$\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j=0,d\&Element;\{-L+1,\&CenterDot;\&CenterDot;\&CenterDot;,-\mathrm{1,1},\&CenterDot;\&CenterDot;\&CenterDot;,L-1\}---\left(8\right)$

For (7) formula, when d=0, when M is N _tIntegral multiple the time, make G= ^M/ _Nt, θ _i ^SpSatisfy (9) formula:

${\mathrm{\&theta;}}_i^{\mathrm{sp}}=\frac{2\mathrm{\&pi;i}(s-p)}{N_t},i\&Element;\{0+g{N}_t,1+g{N}_t,\&CenterDot;\&CenterDot;\&CenterDot;,N_t-1+g{N}_t\},g=\mathrm{0,1},\&CenterDot;\&CenterDot;\&CenterDot;,G-1---\left(9\right)$

Can obtain $\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}{e}^{j{\mathrm{\&theta;}}_i^{\mathrm{sp}}}=\frac{M}{N_t}\underset{i=0}{\overset{N_t-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j=0;$

During d in (7) ≠ 0, (9) formula substitution formula (7) can be got:

$\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{e}^{j[2\mathrm{\&pi;g}(s-p)+\frac{2\mathrm{\&pi;d}{k}_{g{N}_t}}{N}]}+\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{e}^{j[\frac{2\mathrm{\&pi;}(1+g\left(p\right)N_t)}{N_t}+\frac{2\mathrm{\&pi;d}{k}_{g{N}_t+1}}{N}]}+\&CenterDot;\&CenterDot;\&CenterDot;+\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{e}^{j[\frac{2\mathrm{\&pi;}(N_t-1+g(s-p)N_t)}{N_t}+\frac{2\mathrm{\&pi;d}{k}_{N_t-1+g{N}_t}}{N}]}$

$=\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+e^{\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;}}{N_t}}{\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+\&CenterDot;\&CenterDot;\&CenterDot;+{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j,\&ForAll;d\&Element;\{-L+1,\&CenterDot;\&CenterDot;\&CenterDot;-\mathrm{1,1},\&CenterDot;\&CenterDot;\&CenterDot;,L-1\}---\left(10\right)$

Then (8) formula can be write as

$\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+{\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+\&CenterDot;\&CenterDot;\&CenterDot;+\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j,\&ForAll;d\&Element;\{-L+1,\&CenterDot;\&CenterDot;\&CenterDot;-\mathrm{1,1},\&CenterDot;\&CenterDot;\&CenterDot;,L-1\};$

When all equatioies in (11) formula were set up simultaneously, (8) formula and (10) formula can be set up simultaneously as can be seen.

$\left\{\begin{array}{c}\underset{g=0}{\overset{G^{\&prime;}-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j=0\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ \underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j=0\end{array}\right.---\left(11\right);$

If do not consider to protect earlier frequency band, need only so

$\left\{\begin{array}{c}\frac{d{k}_{g{N}_t}}{N}=\frac{g}{G}+{\mathrm{\&upsi;}}_0\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ \frac{d{k}_{N_t-1+g{N}_t}}{N}=\frac{g}{G}+{\mathrm{\&upsi;}}_{N_t-1}\end{array}\right.,{\mathrm{\&upsi;}}_0,\&CenterDot;\&CenterDot;\&CenterDot;{\mathrm{\&upsi;}}_{N_t-1}\&Element;[0,1),$

(11) just can set up, that is:

$\left\{\begin{array}{c}{k}_{N_t}-{\mathrm{<figure-callout\; id="0"\; label="k"\; filenames="A20061012686400182.png,A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_0=k_{2N_t}-k_{N_t}=k_{g{N}_t}-k_{(g-1)N_t}=\frac{N_{t}N}{\mathrm{Md}}\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ k_{2N_t-1}-k_{N_t-1}=k_{3N_t-1}-k_{2N_t-1}=k_{N_t-1+g{N}_t}-k_{g{N}_t-1}=\frac{N_{t}N}{\mathrm{Md}}\end{array}\right.---\left(12\right)$

The pilot sub-carrier that is spacedly distributed that is proposed, i.e. k ₁-k ₀=k ₂-k ₁=...=k _M-1-k _M-2= ^N/ _M(13) be exactly a kind of situation of (12).

When the number of system protection frequency band less than ^NtN/ _MdThe time, can arrange the position of pilot sub-carrier according to the rule of formula (13), but consider system the protection frequency band width generally all greater than ^NtN/ _Md(such as the downlink OFDMA system parameters that defines among the 3GPP TR25.814, for the situation of 10M bandwidth, total carrier number N is 1024, and the protection frequency band number is 423, if N _t=2, M=12, d=1, the protection frequency band number much larger than ^NtN/ _Md), so will rethink the arrangement of pilot sub-carrier position.

So, if all equatioies are all set up in the solemnity (11), if M is 2N _tIntegral multiple, make G '= ^M/ _2Nt, then formula (11) can be write as following form:

$\left\{\begin{array}{c}\underset{g=0}{\overset{G^{\&prime;}-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+e^{\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;d}{k}_{(2_8+1)N_t}}{N}}=0\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ \underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+e^{\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;d}{k}_{N_t-1+(2_8+1)N_t}}{N}}=0\end{array}\right.\&DoubleRightArrow;\left\{\begin{array}{c}\frac{2\mathrm{\&pi;d}{k}_{(2_8+1)N_t}}{N}=\mathrm{\&pi;}+\frac{2\mathrm{\&pi;<figure-callout\; id="2"\; label="d\; k"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">d</figure-callout>}{k}_{}{}_{2_8{N}_t}}{N}\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ \frac{2\mathrm{\&pi;d}{k}_{(2_8+2)N_t-1}}{N}=\mathrm{\&pi;}+\frac{2\mathrm{\&pi;d}{k}_{(2_8+1)N_t-1}}{N}\end{array}\right.$

$\&DoubleRightArrow;\left\{\begin{array}{c}{k}_{(2_8+1)N_t}-{\mathrm{<figure-callout\; id="2"\; label="k"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_{2_8{N}_t}=\mathrm{\&Delta;}{f}_{\mathrm{pc}}=\frac{\mathrm{<figure-callout\; id="2"\; label="N"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">N</figure-callout>}}{2\left|d\right|}\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ k_{(2_8+2)N_t-1}-k_{(2_8+1)N_t-1}=\mathrm{\&Delta;}{f}_{\mathrm{pc}}=\frac{\mathrm{<figure-callout\; id="2"\; label="N"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">N</figure-callout>}}{2\left|d\right|}\end{array}\right.\&ForAll;\left|d\right|\&Element;\{1,\&CenterDot;\&CenterDot;\&CenterDot;,L-1\},g=\mathrm{0,1},\&CenterDot;\&CenterDot;\&CenterDot;,G^{\&prime;}-1---\left(14\right)$

In formula (4), formula (9), formula (10) substitution formula (3), can get F ^HX ^PHX ^sElement on the F leading diagonal is:

$P\underset{i=0}{\overset{M-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j---\left(15\right)$

Other locational element values are:

$P(\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+e^{\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;}}{N_t}}\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+\&CenterDot;\&CenterDot;\&CenterDot;+{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j\underset{g=0}{\overset{G-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j)---\left(16\right)$

P=wherein ^P/ _MPower for frequency pilot sign on each pilot sub-carrier.

F as can be seen ^HX ^PHX ^sThe value of d is all inequality at each each row of row among the F, but the interval delta f between the pilot sub-carrier _PcMust be a definite value, order

$\mathrm{\&Delta;}{f}_{\mathrm{pc}}=\frac{N}{2D}---\left(17\right)$

Choosing suitable D makes $\min F\left(D\right)={\left|\right|A^{H}A-P{I}_{L{N}_t}\left|\right|}_2,$ Minimize the destruction of protection frequency band for the pilot frequency sequence orthogonality.

$F\left(D\right)={\left|\right|A^{H}A-\stackrel{\&OverBar;}{P}{I}_{L{N}_t}\left|\right|}_2$

$={\mathrm{<figure-callout\; id="2"\; label="N\; t"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">N</figure-callout>}}_t^{}\sqrt{2P}\sqrt{\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}{|\underset{g=0}{\overset{G^{\&prime;}-1}{\mathrm{\&Sigma;}}}({\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+e^{\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;d}({\mathrm{<figure-callout\; id="2"\; label="k"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_{2_8{N}_t}+\frac{N}{2D})}{N}})+\&CenterDot;\&CenterDot;\&CenterDot;e^{\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;}(N_t-1)}{N_t}}\underset{g=0}{\overset{G^{\&prime;}-1}{\mathrm{\&Sigma;}}}({\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+e^{\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;d}(k_{(2_8+1)N_t-1}+\frac{N}{2D})}{N}})|}^2}$

$={\mathrm{<figure-callout\; id="2"\; label="N\; t"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">N</figure-callout>}}_t^{}\sqrt{2P}\sqrt{\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}{{|1+e^{\mathrm{j\&pi;}\frac{d}{D}}|}^2|\underset{g=0}{\overset{G^{\&prime;}-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+\&CenterDot;\&CenterDot;\&CenterDot;+{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j\underset{g=0}{\overset{G^{\&prime;}-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j|}^2},D\&Element;[1,L-1]---\left(18\right)$

Usually L less than N (L＜N), therefore for  d ∈ [1, L-1], can with $|\underset{g=0}{\overset{G^{\&prime;}-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j+\&CenterDot;\&CenterDot;\&CenterDot;+{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j\underset{g=0}{\overset{G^{\&prime;}-1}{\mathrm{\&Sigma;}}}{\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">e</figure-callout>}}^j|$ Be similar to and regard a constant C as, then

$F\left(D\right)={\mathrm{<figure-callout\; id="2"\; label="N\; t"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">N</figure-callout>}}_t^{}\sqrt{2P}C\sqrt{\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}{|1+e^{\mathrm{j\&pi;}\frac{d}{D}}|}^2}---\left(19\right)$

As long as find D to make as can be seen

$\min F_1\left(D\right)=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}{|1+e^{\mathrm{j\&pi;}\frac{d}{d}}|}^2=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}(2+2\cos \mathrm{\&pi;}\frac{d}{D})---\left(20\right)$

Just can obtain $\min F\left(D\right)={\left|\right|A^{H}A-P{I}_{L{N}_t}\left|\right|}_2.$

The D that satisfies (20) formula can easily find by variety of way, seeks such as going by Computer Simulation.

Based on above-mentioned analysis, below pilot frequency sequence sending method of the present invention is elaborated.

Fig. 1 is the pilot frequency sequence sending method schematic flow sheet according to multiple antenna and carrier system of the present invention.As shown in Figure 1, this method comprises:

Step 101: determine the pilot frequency carrier wave number M and pilot frequency carrier wave is divided into groups, total number of transmit antennas that is no less than M multiply by the long-pending of channel multi-path number, and M is the even-multiple of total number of transmit antennas, the number of pilot frequency carrier wave is the twice of total number of transmit antennas in every group, and the pilot frequency carrier wave intersection is spacedly distributed in every group;

Wherein, pilot frequency carrier wave can be divided into G '= ^M/ _2NtGroup; The number 2N of pilot frequency carrier wave in every group _t, be designated { k _0+g2Nt, k _1+g2Nt..., k _2Nt-2+g2Nt, k _2Nt-1+g2Nt, g=0,1 ..., G ';

The pilot frequency carrier wave intersection is spacedly distributed in every group, satisfies $k_{N_t+g2N_t}-{\mathrm{<figure-callout\; id="0"\; label="k"\; filenames="A20061012686400182.png,A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_{0+g2N_t}=\&CenterDot;\&CenterDot;\&CenterDot;=k_{2N_t-1+g2N_t}-k_{N_t-1+g2N_t}=\frac{N}{2D},$ Wherein total number of transmit antennas is N _t, the total carrier wave number of system is N, D is the parameter that the decision pilot carrier position detects.

In addition, preferably, the value of D makes function $F\left(D\right)=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}(2+2\cos \mathrm{\&pi;}\frac{d}{D})$ The value minimum, wherein L is the channel multi-path number.

Step 102: all transmitting antennas send pilot frequency sequence on identical transmission symbol and pilot frequency carrier wave, wherein the pilot frequency sequence of different transmit antennas each other constant power distribute and quadrature in phase.

Here, preferably, for the k of any two transmit antennas s, p _iThe phase difference of the frequency pilot sign on the individual pilot frequency carrier wave is θ _i ^Sp, wherein ${\mathrm{\&theta;}}_i^{\mathrm{sp}}=\frac{2\mathrm{\&pi;i}(s-p)}{N_t},$ Total number of transmit antennas is N _t

Pilot frequency sequence sending method proposed by the invention had both gone for OFDM (OFDM) system, also can be applicable to the OFDMA system based on OFDM.With the ofdm system be below example invention has been described, but it will be appreciated by those of skill in the art that the present invention is suitable equally for other multi-carrier communications systems.With OFDM is that example only describes to exemplary, and is not used in and limits the invention.

Fig. 2 is the frequency domain transmission OFDM symbol structural representation of the one exemplary embodiment according to the present invention.

Based on OFDM symbol shown in Figure 2, suppose that total number of transmit antennas is N _t, the channel multi-path number is L, the number M of pilot frequency carrier wave must not be less than N _tL, and M is necessary for N _tEven-multiple, promptly $\left\{\begin{array}{c}M\&GreaterEqual;N_{t}L\\ M=2G^{\&prime;}{N}_t\end{array}\right..$ For all transmitting antennas, on all pilot frequency carrier waves, the power of frequency pilot sign equates that the power on each frequency pilot sign is P= ^P/ _M, P is a gross power of distributing to pilot frequency sequence, promptly in Fig. 2, antenna 0 and antenna 1 are at pilot frequency carrier wave { k ₀, k ₁..., k ₁₀, k ₁₁On the phase difference of frequency pilot sign be 0, π ..., 0, π }.

The k of any two transmitting antenna s, p _iThe phase difference of the frequency pilot sign on the individual pilot frequency carrier wave is

${\mathrm{\&theta;}}_i^{\mathrm{sp}}=\frac{2\mathrm{\&pi;i}(s-p)}{N_t}.$

The total carrier wave number of supposing the system is that (N does not need to be necessary for 2 to N ⁿForm), with pilot frequency carrier wave be divided into G '= ^M/ _2NtGroup, the number 2N of every group of interior pilot frequency carrier wave _t, be designated { k _0+g2Nt, k _1+g2Nt..., k _2Nt-2+g2Nt, k _2Nt-1+g2Nt, g=0,1 ..., G '; The pilot sub-carrier intersection is spacedly distributed in every group, satisfies $k_{N_t+g2N_t}-{\mathrm{<figure-callout\; id="0"\; label="k"\; filenames="A20061012686400182.png,A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_{0+g2N_t}=\&CenterDot;\&CenterDot;\&CenterDot;=k_{2N_t-1+g2N_t}-k_{N_t-1+g2N_t}=\frac{N}{2D},$ Wherein D is a decision pilot carrier position parameter at interval, and the value of D will make function $F\left(D\right)=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}(2+2\cos \mathrm{\&pi;}\frac{d}{D})$ The value minimum.

Promptly in Fig. 2, { k ₀, k ₁, k ₂, k ₃Be one group of pilot frequency carrier wave, wherein $k_2-{\mathrm{<figure-callout\; id="0"\; label="k"\; filenames="A20061012686400182.png,A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_0=k_3-{\mathrm{<figure-callout\; id="1"\; label="k"\; filenames="A20061012686400182.png"\; state="\{\{state\}\}">k</figure-callout>}}_1=\frac{N}{2D}.$ Equally, { k ₄, k ₅, k ₆, k ₇, { k ₈, k ₉, k ₁₀, k ₁₁Be other two groups of pilot frequency carrier waves, and $k_6-{\mathrm{<figure-callout\; id="4"\; label="k"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_4=k_7-k_5=\frac{N}{2D},$

$k_{11}-k_9=k_{10}-{\mathrm{<figure-callout\; id="8"\; label="k"\; filenames="A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_8=\frac{N}{2D}.$

The flexible reasonable distribution of frequency band can be avoided protecting in the position of each group pilot frequency carrier wave.To be inserted on the part carrier wave of transmission symbol according to the resulting sequence of pilot symbols of above step, data symbol uses other carrier wave, on all transmitting antennas, send then, carry out channel estimating at receiving terminal then and carry out equalizing demodulation after obtaining channel condition information.

Fig. 3 is the structural representation according to the pilot frequency sequence transmitting system of multiple antenna and carrier system of the present invention.As shown in Figure 3, this system comprises:

The pilot frequency carrier wave number is determined and grouped element 301, be used for determining the pilot frequency carrier wave number M, and pilot frequency carrier wave divided into groups, total number of transmit antennas that is no less than M multiply by the long-pending of channel multi-path number, and M is the even-multiple of total number of transmit antennas, the number of pilot frequency carrier wave is the twice of total number of transmit antennas in every group, and the pilot frequency carrier wave intersection is spacedly distributed in every group;

Transmitting antenna 302 is used for sending pilot frequency sequence on identical transmission symbol and carrier wave, wherein the pilot frequency sequence of different transmit antennas each other constant power distribute and quadrature in phase.

Preferably, described pilot frequency carrier wave number determines and grouped element 301, be used for pilot frequency carrier wave be divided into G '= ^M/ _2NtGroup, the number 2N of every group of interior pilot frequency carrier wave _t, be designated { k _0+g2Nt, k _1+g2Nt..., k _2Nt-2+g2Nt, k _2Nt-1+g2Nt, g=0,1 ..., G '; Wherein total number of transmit antennas is N _t, the total carrier wave number of system is N; And

The pilot frequency carrier wave intersection is spacedly distributed in every group, satisfies $k_{N_t+g2N_t}-{\mathrm{<figure-callout\; id="0"\; label="k"\; filenames="A20061012686400182.png,A20061012686400192.png"\; state="\{\{state\}\}">k</figure-callout>}}_{0+g2N_t}=\&CenterDot;\&CenterDot;\&CenterDot;=k_{2N_t-1+g2N_t}-k_{N_t-1+g2N_t}=\frac{N}{2D},$ Wherein D is the parameter that the decision pilot carrier position detects.

More preferably, the value of wherein said D makes function $F\left(D\right)=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}(2+2\cos \mathrm{\&pi;}\frac{d}{D})$ The value minimum, wherein L is the channel multi-path number.

The k of any two transmit antennas s, p _iThe phase difference of the frequency pilot sign on the individual pilot frequency carrier wave is θ _i ^Sp, wherein ${\mathrm{\&theta;}}_i^{\mathrm{sp}}=\frac{2\mathrm{\&pi;i}(s-p)}{N_t},$ Total number of transmit antennas is N _t

The sequence of pilot symbols that uses the present invention to propose carries out channel estimating to multiple antenna and carrier system, can not be subjected to the influence of protection frequency band in the system, have flexibility and practicality concurrently, and implementation complexity is low.Under lower pilot-frequency expense, when the high speed of a motor vehicle, still can guarantee channel estimated accuracy.

The present invention can also be applied in the transmitter and receiver of communication system.To those skilled in the art, except sequence of pilot symbols emission system proposed by the invention, the remainder of transmitter and receiver is mature technology.

Below in conjunction with example so that high efficiency of the present invention, reliability and practicality to be described.

Fig. 4 is one exemplary embodiment according to the present invention, in the ofdm system of two transmitting antennas, two reception antennas, adopts the BER performance map of SFBC, Turbo coding.

Wherein simulated conditions is: carrier frequency 2GHz, system bandwidth 10MHz, carrier wave add up to 1024, protection frequency band carriers number is 423, the pilot frequency carrier wave number is 12, and channel model is that typical urban district (TypicalUrban), the speed of a motor vehicle are that 120km/h, footpath number L=6 and pedestrian (Pedestrian) B, walking speed are 3km/h, footpath number L=6.

As seen from Figure 4, this embodiment is under the condition of pilot-frequency expense 2% (minimum pilot overhead), and the highest signal to noise ratio 16dB that needs, the BER of system can be reached for zero, and than equally distributed pilot frequency sequence, under the prerequisite of equal expense, performance improves 4～8dB.

In addition, can suitably choose rational pilot-frequency expense according to the requirement of system design in actual applications, the performance that makes system is near ideal communication channel estimation performance lower bound.

The above is preferred embodiment of the present invention only, is not to be used to limit protection scope of the present invention.Within the spirit and principles in the present invention all, any modification of being done, be equal to replacement, improvement etc., all should be included within protection scope of the present invention.

Claims (10)

1, a kind of pilot frequency sequence sending method of multiple antenna and carrier system is characterized in that, this method comprises:

Determine the pilot frequency carrier wave number M and pilot frequency carrier wave is divided into groups, total number of transmit antennas that is no less than M multiply by the long-pending of channel multi-path number, and M is the even-multiple of total number of transmit antennas, and the number of every group of interior pilot frequency carrier wave is the twice of total number of transmit antennas, and the pilot frequency carrier wave intersection is spacedly distributed in every group;

All transmitting antennas send pilot frequency sequence on identical transmission symbol and pilot frequency carrier wave, wherein the pilot frequency sequence of different transmit antennas each other constant power distribute and quadrature in phase.

2, the pilot frequency sequence sending method of multiple antenna and carrier system according to claim 1 is characterized in that, described pilot frequency carrier wave grouping is comprised: pilot frequency carrier wave is divided into G '=M/2N _tGroup; The number 2N of pilot frequency carrier wave in every group _t, be designated { k _0+g2Nt, k _1+g2Nt..., k _2Nt-2+g2Nt, k _2Nt-1+g2Nt, g=0,1 ... G '; The pilot frequency carrier wave intersection is spacedly distributed in every group, satisfies $k_{N_t+g2N_t}-k_{0+g2N_t}=...=k_{{2N}_t-1+g2N_t}-k_{N_t-1+g2N_t}=\frac{N}{2D},$ Wherein total number of transmit antennas is N _t, the total carrier wave number of system is N, D is the parameter that the decision pilot carrier position detects.

3, the pilot frequency sequence sending method of multiple antenna and carrier system according to claim 2 is characterized in that, the value of described D makes function $F\left(D\right)=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}(2+2\cos \mathrm{\&pi;}\frac{d}{D})$ The value minimum, wherein L is the channel multi-path number.

4, the pilot frequency sequence sending method of multiple antenna and carrier system according to claim 1 is characterized in that, the k of any two transmit antennas s, p _iThe phase difference of the frequency pilot sign on the individual pilot frequency carrier wave is θ _i ^Sp, wherein ${\mathrm{\&theta;}}_i^{\mathrm{sp}}=\frac{2\mathrm{\&pi;i}(s-p)}{N_t},$ Total number of transmit antennas is N _t

5, a kind of pilot frequency sequence transmitting system of multiple antenna and carrier system is characterized in that, this system comprises:

The pilot frequency carrier wave number is determined and grouped element, be used for determining the pilot frequency carrier wave number M, and pilot frequency carrier wave divided into groups, total number of transmit antennas that is no less than M multiply by the long-pending of channel multi-path number, and M is the even-multiple of total number of transmit antennas, the number of pilot frequency carrier wave is the twice of total number of transmit antennas in every group, and the pilot frequency carrier wave intersection is spacedly distributed in every group;

A plurality of transmitting antennas are used for sending pilot frequency sequence on identical transmission symbol and carrier wave, wherein the pilot frequency sequence of different transmit antennas each other constant power distribute and quadrature in phase.

6, the pilot frequency sequence transmitting system of multiple antenna and carrier system according to claim 5 is characterized in that,

Described pilot frequency carrier wave number is determined and grouped element, is used for pilot frequency carrier wave is divided into G '=M/2N _tGroup, the number 2N of every group of interior pilot frequency carrier wave _t, be designated { k _0+g2Nt, k _1+g2Nt..., k _2Nt-2+g2Nt, k _2Nt-1+g2Nt, g=0,1 ..., G '; Wherein total number of transmit antennas is N _t, the total carrier wave number of system is N; And

The pilot frequency carrier wave intersection is spacedly distributed in every group, satisfies

$k_{N_t+g2N_t}-k_{0+g+2N_t}=...=k_{2N_t-1+g{2N}_t}-k_{N_t-1+g{2N}_t}=\frac{N}{2D},$ Wherein D is the parameter that the decision pilot carrier position detects.

7, the pilot frequency sequence transmitting system of multiple antenna and carrier system according to claim 6 is characterized in that, the value of described D makes function $F\left(D\right)=\underset{d=1}{\overset{L-1}{\mathrm{\&Sigma;}}}(2+2\cos \mathrm{\&pi;}\frac{d}{D})$ The value minimum, wherein L is the channel multi-path number.

8, the pilot frequency sequence transmitting system of multiple antenna and carrier system according to claim 6 is characterized in that,

The k of any two transmit antennas s, p _iThe phase difference of the frequency pilot sign on the individual pilot frequency carrier wave is θ _i ^Sp, wherein ${\mathrm{\&theta;}}_i^{\mathrm{sp}}=\frac{2\mathrm{\&pi;i}(s-p)}{N_t},$ Total number of transmit antennas is N _t

9, a kind of transmitter is characterized in that, this transmitter comprises as each described pilot frequency sequence transmitting system among the claim 5-8.

10, a kind of receiver is characterized in that, is used for receiving the pilot frequency sequence that is sent by each described pilot frequency sequence transmitting system of claim 5-8.

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