CN1908740A - Converter controller having feedforward compensation, converting system and method for controlling same - Google Patents
Converter controller having feedforward compensation, converting system and method for controlling same Download PDFInfo
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- CN1908740A CN1908740A CN 200510088073 CN200510088073A CN1908740A CN 1908740 A CN1908740 A CN 1908740A CN 200510088073 CN200510088073 CN 200510088073 CN 200510088073 A CN200510088073 A CN 200510088073A CN 1908740 A CN1908740 A CN 1908740A
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Abstract
The provided conversion controller with forward compensation comprises: an error amplifier to receive reference signal and feedback signal and output error signal, a pulse generator to output signal to a driver, and an oscillator between the power and ground to output an oscillation signal with amplitude proportioned with power to control duty cycle of. Pulse signal. This invention can avoid effect from power variation.
Description
Technical field
The present invention relates to a kind of display device, particularly relate to a kind of converter controller and control method thereof of controlling the backlight of display device power supply.
Background technology
Discharge lamp as cold-cathode fluorescence lamp (CCFL), is widely used in the LCDs (LCD) of device such as portable computer, televisor light source as a setting.CCFL is started by a DC/AC converter, and this converter changes direct current signal into AC signal, and input voltage is converted to the required high voltage of CCFL.Usually, use a controller to regulate the variation of input voltage, with the electric current of control CCFL.One of them method of regulating input voltage is to use pulse-length modulation (PWM) technology, and wherein the electric current of CCFL is modulated by a pwm control signal in the backfeed loop.
United States Patent (USP) the 6th, 876 has disclosed a kind of PWM of employing technology for No. 157 and has regulated the CCFL converter controller that the CCFL input voltage changes.The feedback signal of an expression CCFL electric current is input to an input end of error amplifier, and another input end of error amplifier receives the signal of an expression CCFL reference brightness.Error amplifier compares error amplification signal of back output to feedback signal and reference signal.A compensation condenser is connected between the output and ground of error amplifier, and controls pwm circuit based on pwm voltage signal of output generation of error amplifier.Be the electric current of control CCFL, error signal can change with the variation of input voltage.When input voltage raise, the value of error signal reduced; When input voltage reduced, the value of error signal raise.Therefore, error amplifier need discharge and recharge compensation condenser, that is to say, controller needs a period of time that the input voltage of transient change is responded, so it is slower that this controller is regulated the speed of input voltage variation, can not be in the instantaneous CCFL electric current be controlled of input voltage variation.In addition, because error signal can change with the variation of input voltage, error signal also can change the time that compensation condenser discharges and recharges.Therefore, when using low frequency PWM dim signal to regulate CCFL brightness, the dutycycle of the pwm signal of pwm circuit output also changes thereupon, thereby influences the brightness of CCFL.
The technology that another kind of CCFL converter controller adopts the input voltage to CCFL to carry out feedforward compensation is regulated the electric current of CCFL.Sort controller comprises an error amplifier, is used for receiving the current deviation signal that is inversely proportional to input voltage, to realize the feedforward compensation of input voltage.Yet, in integrated circuit, be difficult to the Control current deviation and become accurate ratio with input voltage, that is to say that can not accurately compensate input voltage, therefore, this kind controller feedforward compensation performance is not good.In addition, it is complicated that circuit also will become, thereby increase cost.
Summary of the invention
The object of the present invention is to provide a kind of converter controller that has feedforward compensation, this controller can carry out feedforward compensation accurately to the power supply of powering load, the instantaneous of power source change load current is controlled.
Another object of the present invention is to provide a kind of the power supply of powering load is carried out the method for accurate feedforward compensation, thereby avoid load current to change with the variation of power supply.
For achieving the above object, the present invention has feedforward compensation and comprises error amplifier, pulse signal producer and the driver that is connected in series with the converter controller of control load electric current; And be connected the power supply of powering load and the oscillator between the earth terminal.Amplitude of oscillator output and the relevant oscillator signal of described power supply size.Error amplifier receives the feedback signal of a reference signal and an expression load current and exports an error signal.Described error signal is input to the first input end of pulse signal generator, and the oscillator signal of described oscillator is input to second input end of pulse signal generator.Pulse signal generator is exported a pulse signal to described driver according to described error signal and oscillator signal, and the amplitude of described oscillator signal is controlled the dutycycle of described pulse signal, thereby realizes the feedforward compensation of described power supply.
The converter controller that has feedforward compensation with the control load electric current of the present invention, the amplitude of described oscillator signal is directly proportional with described power supply size.
The converter controller that has feedforward compensation with the control load electric current of the present invention, described converter controller also comprises the time component that is connected between described power supply and the earth terminal.
The converter controller that has feedforward compensation with the control load electric current of the present invention, described time component comprises resistor and the capacitor that is connected in series, the contact between this resistor and the capacitor is connected to the output terminal of described oscillator.
The converter controller that has feedforward compensation with the control load electric current of the present invention, described oscillator signal is the sawtooth wave with fixed frequency.
The converter controller that has feedforward compensation with the control load electric current of the present invention, described converter controller also comprise a compensation condenser between the output and ground that is connected described error amplifier.
The converter controller that has feedforward compensation with the control load electric current of the present invention, described power supply is a direct voltage source.
The present invention also provides a kind of converting system that has feedforward compensation with the control load electric current, comprising: power-switching circuit, and it connects the power supply of most described electric, and is the required signal of load with this power source conversion; Controller with the described power-switching circuit of control, comprise the error amplifier that is connected in series, pulse signal producer and driver, be connected the oscillator between described power supply and the earth terminal, error amplifier receives the feedback signal of a reference signal and an expression load current, and according to this reference signal and error signal of feedback signal output, described error signal is input to the first input end of pulse signal generator, the oscillator signal of oscillator output is input to second input end of pulse signal generator, pulse signal generator is according to described error signal and pulse signal of oscillator signal output, described pulse signal is via the output of the described power-switching circuit of described driver control, the amplitude of described oscillator signal changes with described power supply size, thereby regulates the feedforward compensation of the dutycycle of described pulse signal with the realization power supply.
The converting system that has feedforward compensation with the control load electric current of the present invention, the amplitude of described oscillator signal is directly proportional with described power supply size.
The converting system that has feedforward compensation with the control load electric current of the present invention, described controller comprises the time component that is connected between described power supply and the earth terminal.
The converting system that has feedforward compensation with the control load electric current of the present invention, described time component comprises resistor and the capacitor that is connected in series, the contact between this resistor and the capacitor is connected to the output terminal of described oscillator.
The converting system that has feedforward compensation with the control load electric current of the present invention, described oscillator signal is the sawtooth wave with fixed frequency.
The converting system that has feedforward compensation with the control load electric current of the present invention, described power supply is a direct voltage source.
The converting system that has feedforward compensation with the control load electric current of the present invention, described power-switching circuit is converted to the required alternating voltage of described load based on described pulse signal with described direct voltage source.
The converting system that has feedforward compensation with the control load electric current of the present invention, described controller comprise a compensation condenser between the output and ground that is connected described error amplifier.
The present invention comprises: produce the oscillator signal that an amplitude and described power supply are in proportion the method for the power supply realization feedforward compensation of powering load; Produce the feedback signal of an expression load current; Described feedback signal and a reference signal are relatively produced an error signal in the back; And produce the pulse signal of a dutycycle behind more described error signal and the described oscillator signal with described oscillator signal amplitude variations, to control the electric current of described load.
Of the present invention to realize the method for feedforward compensation to the power supply of lamp source power supply, produce the low-frequency pulse width modulated dim signal of a described error signal of control, to regulate the electric current in described lamp source.
Compared with prior art, during mains voltage variations, realize feedforward control by the amplitude that changes the oscillator signal that oscillator produces, this is equivalent to the dutycycle that changes pulse signal along with supply voltage, and error signal is remained unchanged.Therefore, the present invention have the converter controller of feedforward compensation can be when supply voltage changes the accurate dutycycle of regulating impulse signal immediately, thereby the influence of avoiding mains voltage variations to bring, and supply voltage can have the scope of broad.
Description of drawings
Fig. 1 is the circuit block diagram that comprises the converting system of converter controller of the present invention;
Fig. 2 is the circuit diagram of the high frequency oscillator in the converter controller of the present invention;
Fig. 3 is when high frequency oscillator is in normal mode of operation, the reduced graph of circuit shown in Figure 2;
Fig. 4 is the sequential chart of unlike signal waveform in Fig. 1 converter controller;
Fig. 5 is another sequential chart of unlike signal waveform in Fig. 1 converter controller.
Embodiment
Fig. 1 is the circuit block diagram of converting system 100 of the present invention.This system 100 comprises the converter controller 110 of power-switching circuit 160 and these power-switching circuit 160 outputs of control.Power-switching circuit 160 is DC/DC or DC/AC circuit that power supply is provided for the lamp source.In the present embodiment, this lamp source is at least one cold-cathode fluorescence lamp (CCFL) 170, change-over circuit 160 is the DC/AC circuit that direct voltage source VIN are converted to the required alternating voltage of cold-cathode fluorescence lamp 170, for example, full-bridge, half-bridge, recommends and/or Class D type change-over circuit.In one embodiment, change-over circuit 160 is converted to sinusoidal voltage with direct voltage source VIN and is transferred to cold-cathode fluorescence lamp 170.
Converter controller 110 of the present invention comprises that 120, one of error amplifiers have the high frequency oscillator 130 of feedforward compensation, a comparer 140 and a driver 150 that drives CCFL change-over circuit 160 that produces the PWM drive signal.Error amplifier 120, comparer 140, driver 150 and change-over circuit 160 are connected in series.The normal phase input end of error amplifier 120 receives a reference signal, the voltage reference signal VREF that for example represents CCFL expectation brightness, its inverting input receives one via a feedback circuit 180 and crosses the voltage feedback signal VFB that the electric current of CCFL is directly proportional with actual flow.Produce an error signal CMP at its output terminal after error amplifier 120 more described reference signals and the feedback signal.The normal phase input end of this error signal CMP input comparator 140.Between the output and ground GND of error amplifier 120, be connected with a compensation condenser 11.High frequency oscillator 130 is connected between the direct voltage source VIN and earth terminal into 170 power supplies of described cold-cathode fluorescence lamp, and its output terminal is connected to the contact 123 of 13 of the external resistor 12 that is connected in series between direct voltage source VIN and the earth terminal and external capacitors.This resistor 12 and capacitor 13 are time components of the oscillator signal RTCT frequency of determining that high frequency oscillator 130 is exported under normal mode of operation.High frequency oscillator 130 inputs to the inverting input of comparer 140 at the oscillator signal RTCT of its output terminal output.Comparer 140 is according to described error signal CMP and PWM drive signal of oscillator signal RTCT output.Driver 150 receives the output of described PWM drive signal and control transformation circuit 160.Error amplifier 120, high frequency oscillator 130, comparer 140 and driver 150 can be integrated in on the chip piece.
Fig. 2 is shown to be the circuit diagram of the high frequency oscillator 130 in the converter controller 110 of the present invention.High frequency oscillator 130 comprises a resitstance voltage divider that is connected between direct voltage source VIN and the earth terminal, and this resitstance voltage divider comprises first resistance 21 and second resistance 22 that is connected in series.Between direct voltage source VIN and contact 123, be provided with the resistance 32 and the switch 34,36 that are connected in series.Switch 34,36 is a N channel enhancement metal-oxide-semiconductor in one embodiment.High frequency oscillator 130 also comprises first comparer 23 and second comparer 24.Contact CTIN between the switch 34 and 36 is connected to the normal phase input end of first comparer 23 and the inverting input of second comparer 24.First comparer 23 compares the signal and the direct voltage source VIN at contact CTIN place after the resitstance voltage divider dividing potential drop at the first reference voltage VRH of contact 212 places acquisition, VRH is obtained by following formula: VRH=VIN * (R2/ (R1+R2)); Wherein R1 and R2 represent the resistance of first resistance 21 and second resistance 22 respectively.This shows that the first reference voltage VRH is directly proportional with direct voltage source VIN.In one embodiment, the scope of direct voltage source VIN is generally 6 to 30 volts, and first resistance 21 and second resistance 22 by selecting suitable size make the first reference voltage VRH be set to 1/8 to 1/10 of direct voltage source VIN.Simultaneously, this second comparer 24 compares the signal and the second reference voltage VRL at contact CTIN place.The second reference voltage VRL is a voltage signal that does not change and have fixed value with direct voltage source VIN, and its size preferably is chosen as the value that approaches no-voltage, as 0.1 volt.High frequency oscillator 130 also comprises a trigger 26 that is used for receiving first comparer 23 and 24 outputs of second comparer.In the present embodiment, this trigger 26 is rest-set flip-flops, obviously also can select the trigger of other types for use.High frequency oscillator 130 further comprises a switch 25 that is connected capacitor 13 two ends, that is to say, between contact 123 and earth terminal, the conducting state of this switch 25 is controlled by the output of trigger 26.In one embodiment, switch 25 is a N channel enhancement metal-oxide-semiconductor, can certainly select the transistor of other types for use.Running according to the high frequency oscillator 130 of this embodiment will be described in more detail below.
Light detection signal LOB and the conducting state of the enable signal POFF gauge tap 34,36 of whether working with control cold-cathode fluorescence lamp 170 from converting system 100 external circuits by the lamp whether lighted of expression cold-cathode fluorescence lamp 170, can make high frequency oscillator 130 work in following three different modes: CCFL starter pattern, CCFL normal mode of operation and standby mode.Enable signal POFF controls by the conducting state of 38 pairs of switches 36 of phase inverter.When cold-cathode fluorescence lamp 170 is in the starter pattern, enable signal POFF is a low level, and detection signal LOB is a high level, with gauge tap 34,36 equal conductings.Be in normal mode of operation after cold-cathode fluorescence lamp 170 is lighted, enable signal POFF is a low level, with gauge tap 36 conductings; Simultaneously, detection signal LOB is a low level, thus cut-off switch 34.At standby mode, enable signal POFF is a high level, and switch 36 is disconnected, and high frequency oscillator 130 is not worked, thereby turn-offs the electric current of entire circuit, leaks so can reduce electric current, reduces power consumption, thereby under standby mode, can reach purpose of power saving.The running of high frequency oscillator 130 under normal mode of operation and starter pattern will be described in more detail below.
When high frequency oscillator 130 is in normal mode of operation, enable signal POFF and lamp are lighted detection signal LOB and are low level, thereby gauge tap 34 disconnects, switch 36 conductings.Because switch 36 is equivalent to short circuit under conducting state, promptly contact CTIN overlaps with contact 123, and at this moment, the circuit of high frequency oscillator 130 when operate as normal can be represented by circuit shown in Figure 3.Below with reference to Fig. 3 the running of high frequency oscillator 130 when the normal mode of operation described.Thereby direct voltage source VIN charges via 12 pairs of capacitors 13 of resistor and produces voltage signal RTCT at contact 123.Voltage signal RTCT compares by first comparer 23 and the first reference voltage VRH.The output of first comparer 23 keeps low level to equal the first reference voltage VRH up to voltage signal RTCT.Simultaneously, second comparer 24 compares this voltage signal RTCT and the second reference voltage VRL.The output of second comparer 24 keep low level up to voltage signal RTCT less than the second reference voltage VRL.When voltage signal RTCT equals the first reference voltage VRH, the output of first comparer 23 becomes high level by low level, the output of second comparer 24 still remains low level, at this moment rest-set flip-flop 26 is output as high level with gauge tap 25 conductings, and switch 25 conductings are the electric charge on the releasing capacitor 13 just.When discharging into, capacitor 13 make voltage signal RTCT less than the second reference voltage VRL, the output of first comparer 23 becomes low level again, the output of second comparer 24 becomes high level, at this moment the output of rest-set flip-flop 26 becomes low level and disconnects with gauge tap 25, makes power supply VIN continue charging to capacitor 13.This shows that the voltage signal RTCT at contact 123 places is an oscillator signal.Oscillation frequency f under the normal mode of operation is obtained by following formula:
Wherein, R represents the resistance value of external resistor 12, and C represents the capacitance of external capacitor 13.
Please continue with reference to Fig. 2, when high frequency oscillator 130 is in the starter pattern, enable signal POFF is a low level, and it is the LOB high level that lamp is lighted detection signal, thereby makes switch 34,36 equal conductings.At this moment, except as shown in Figure 3 from direct voltage source VIN via external resistor 12 to first current branch of contact 123, also have one from direct voltage source VIN via the extra current branch road of resistance 32 to contact 123.Direct voltage source VIN charges via external resistor 12 and 32 pairs of capacitors 13 of resistance, thereby produces voltage signal RTCT at contact 123.Because switch 36 is equivalent to short circuit under conducting state, promptly contact CTIN overlaps with contact 123.Therefore, the signal of contact CTIN is consistent with the voltage signal RTCT of contact 123.Compare with Fig. 3, except that having increased an extra current branch road charges to capacitor 13, the running of high frequency oscillator 130 is consistent with the description among above-mentioned Fig. 3, for avoiding giving unnecessary details, so in this omission.Oscillation frequency f ' under the starter pattern is obtained by following formula:
Wherein, the resistance value after R ' expression external resistor 12 and resistance 32 parallel connections, C represents the capacitance of external capacitor 13.This shows that the oscillation frequency under the starter pattern is greater than the frequency under the normal mode of operation.By the resistance 32 of selecting suitable size, make the starter frequency ratio normal working frequency of cold-cathode fluorescence lamp 170 increase by 30 percent, thereby realize normal starter.
As Fig. 4 and shown in Figure 5, the oscillator signal RTCT43 of oscillator 130 is the sawtooth signals with fixed frequency, and its maximal value/peak value equals the first reference voltage VRH42, and its minimum value/valley is zero.In preferred embodiment, switch 25 has bigger size, so ducting capacity is strong, the electric current that switch 25 conducting transient flows are crossed is many, thereby makes the speed of capacitor 13 discharges very fast.Therefore, being far smaller than the cycle of oscillator signal RTCT the discharge time of capacitor 13, thus can be left in the basket the discharge time of this capacitor 13, thus the frequency of avoiding oscillator signal RTCT changes with the variation of direct voltage source VIN.In actual applications, can disturb with the noise that reduces circuit with the first reference voltage VRH and the second reference voltage VRL by voltage buffer or go lotus root electric capacity to be connected to earth terminal.
As seen from the above description, the amplitude of the oscillator signal RTCT of high frequency oscillator 130 outputs is directly proportional with direct voltage source VIN, and when direct voltage source VIN changed, the amplitude of oscillator signal RTCT changed thereupon, and error signal CMP remains unchanged.Comparer 140 is realized the feedforward compensation to direct voltage source VIN according to the dutycycle that error signal CMP and oscillator signal RTCT regulate the PWM drive signal.
In converting system shown in Figure 1 100, for reaching the purpose of control CCFL brightness, utilize low-frequency pulse width modulated (LPWM) dim signal that the CCFL electric current is carried out switching control, CCFL brightness is proportional to the dutycycle of LPWM dim signal.The LPWM dim signal can be to produce behind the analog signal digital with user input.The frequency of LPWM dim signal is far smaller than the frequency of the PWM drive signal of comparer 140 output, and for example, the frequency range of PWM drive signal is 35kHz to 80kHz, and the frequency range of LPWM dim signal is 50 to 200Hz.The error signal CMP of LPWM dim signal departure amplifier 120 outputs.When the LPWM dim signal was in low level, the electric charge on an enable circuits (not shown) the absorption compensation capacitor 11 made error signal CMP be reduced to low level.At this moment, the PWM drive signal is that the minimum of oscillator signal RTCT and error signal CMP obtain after relatively.Therefore, when the LPWM dim signal was in low level, the PWM drive signal was a low level, and the CCFL electric current is zero substantially.When the LPWM dim signal was in high level, enable circuits was inoperative to compensation condenser 11, and 120 pairs of compensation condensers 11 of error amplifier charge to initial value again, and error signal CMP becomes high level, promptly represents the output when CCFL is in high-high brightness.Adopt the converter controller of feedforward compensation of the present invention, the value of error signal CMP remains unchanged.Therefore, under the control of LPWM dim signal, error signal CMP remains unchanged to the duration of charging TRISE (as shown in Figure 4) and TFALL discharge time (as shown in Figure 4) of compensation condenser 11, the influence that the brightness of CCFL is not changed by voltage source V IN can.
Shown in Figure 4 is the sequential chart of unlike signal waveform in the converter controller 110 of the present invention.Curve 41 expressions are to the oscillogram of the direct voltage source VIN variation of CCFL power supply.In one embodiment, direct voltage source VIN changes between 6 to 30V.Curve 42 is oscillograms of the first reference voltage VRH, and this first reference voltage VRH is directly proportional with direct voltage source VIN.In one embodiment, the ratio between the first reference voltage VRH and the direct voltage source VIN is 0.1, that is, when VIN equaled 6V, VRH equaled 0.6V; When VIN equaled 30V, VRH equaled 3V.Curve 43 is oscillograms of the oscillator signal RTCT of high frequency oscillator 130 outputs.The amplitude of this oscillator signal RTCT is directly proportional with direct voltage source VIN.Curve 44 is oscillograms of LPWM dim signal.Curve 45 is to be illustrated in the control of LPWM dim signal down, the oscillogram of the error signal CMP of error amplifier 120 outputs.When the LPWM dim signal was high level, error signal CMP was a high level; When the LPWM dim signal was low level, error signal CMP was a low level.Curve 46 is oscillograms of the PWM drive signal of comparer 140 outputs.When direct voltage source VIN increases, error signal CMP remains unchanged, the amplitude of oscillator signal RTCT increases thereupon and is directly proportional with direct voltage source VIN, therefore, the dutycycle of PWM drive signal reduces, be transferred to the voltage of CCFL with adjusting power-switching circuit 160, thereby control the variation of CCFL electric current.
Shown in Figure 5 be when direct voltage source VIN when first magnitude of voltage is changed to second magnitude of voltage, the sequential chart of unlike signal waveform.When curve 43A is illustrated in direct voltage source VIN and has first magnitude of voltage, the oscillogram of the oscillator signal RTCT of high frequency oscillator 130 outputs, its amplitude is directly proportional with first magnitude of voltage.Curve 43B is illustrated in direct voltage source VIN when first magnitude of voltage is reduced to second magnitude of voltage, the oscillogram of the oscillator signal RTCT of high frequency oscillator 130 outputs, and its amplitude is directly proportional with second magnitude of voltage.When curve 45 is illustrated in the LPWM dim signal and is in high level, the oscillogram of the error signal CMP of error amplifier 120 outputs.Curve 46A represents the oscillogram of the PWM drive signal that comparer 140 is exported behind the oscillator signal RTCT of comparison error signal CMP and curve 43A representative.Curve 46B represents the oscillogram of the PWM drive signal that comparer 140 is exported behind the oscillator signal RTCT of comparison error signal CMP and curve 43B representative.When oscillator signal RTCT had higher amplitudes shown in the curve 43A, the PWM drive signal had less dutycycle.When oscillator signal RTCT have shown in the curve 43B than short arc the time, the PWM drive signal has bigger dutycycle.This shows that the amplitude of oscillator signal RTCT is regulated the dutycycle of PWM drive signal, realize the feedforward compensation of direct voltage source VIN.
The present invention has the converter controller of feedforward compensation can realize transient compensation when mains voltage variations, keep the strict control to lamp current.Feedforward control can be regulated the dutycycle of PWM drive signal immediately when supply voltage changes, influence and the supply voltage that can avoid supply voltage to bring can have the scope of broad.Feedforward control has also been improved the input voltage regulation, and makes the correlativity that starts transient process and input voltage lower.During mains voltage variations, realize feedforward control by the amplitude that changes the sawtooth signal that internal oscillator produces, this is equivalent to the dutycycle that changes the PWM drive signal along with supply voltage, and error signal CMP is remained unchanged, do not need compensation condenser is discharged and recharged, controller is instantaneous to the response of mains voltage variations substantially.
At the embodiment of this narration is the some of them of many possible embodiment, these embodiment be illustrative and and nonrestrictive.Obviously, can also implement conspicuous for those skilled in the art other embodiment, not break away from as the defined the spirit and scope of the present invention of claim.
Claims (17)
1, a kind of converter controller that has feedforward compensation with the control load electric current, it is characterized in that: comprise the error amplifier that is connected in series, pulse signal producer and driver, be connected the power supply of powering load and the oscillator between the earth terminal, amplitude of oscillator output and the relevant oscillator signal of described power supply size, error amplifier receives the feedback signal of a reference signal and an expression load current and exports an error signal, described error signal is input to the first input end of pulse signal generator, the oscillator signal of described oscillator is input to second input end of pulse signal generator, pulse signal generator is exported a pulse signal to described driver according to described error signal and oscillator signal, the amplitude of described oscillator signal is controlled the dutycycle of described pulse signal, thereby realizes the feedforward compensation of described power supply.
2, the converter controller that has feedforward compensation with the control load electric current according to claim 1 is characterized in that: the amplitude of described oscillator signal is directly proportional with described power supply size.
3, the converter controller that has feedforward compensation with the control load electric current according to claim 1, it is characterized in that: described converter controller also comprises the time component that is connected between described power supply and the earth terminal.
4, the converter controller that has feedforward compensation with the control load electric current according to claim 3, it is characterized in that: described time component comprises resistor and the capacitor that is connected in series, and the contact between this resistor and the capacitor is connected to the output terminal of described oscillator.
5, the converter controller that has feedforward compensation with the control load electric current according to claim 1, it is characterized in that: described oscillator signal is the sawtooth wave with fixed frequency.
6, the converter controller that has feedforward compensation with the control load electric current according to claim 1 is characterized in that: described converter controller also comprises a compensation condenser between the output and ground that is connected described error amplifier.
7, the converter controller that has feedforward compensation with the control load electric current according to claim 1, it is characterized in that: described power supply is a direct voltage source.
8, a kind of converting system that has feedforward compensation with the control load electric current is characterized in that comprising:
Power-switching circuit, it connects the power supply of most described electric, and is the required signal of load with this power source conversion; With
Control the controller of described power-switching circuit, comprise the error amplifier that is connected in series, pulse signal producer and driver, be connected the oscillator between described power supply and the earth terminal, error amplifier receives the feedback signal of a reference signal and an expression load current, and according to this reference signal and error signal of feedback signal output, described error signal is input to the first input end of pulse signal generator, the oscillator signal of oscillator output is input to second input end of pulse signal generator, pulse signal generator is according to described error signal and pulse signal of oscillator signal output, described pulse signal is via the output of the described power-switching circuit of described driver control, the amplitude of described oscillator signal changes with described power supply size, thereby regulates the feedforward compensation of the dutycycle of described pulse signal with the realization power supply.
9, the converting system that has feedforward compensation with the control load electric current according to claim 8 is characterized in that: the amplitude of described oscillator signal is directly proportional with described power supply size.
10, the converting system that has feedforward compensation with the control load electric current according to claim 8, it is characterized in that: described controller comprises the time component that is connected between described power supply and the earth terminal.
11, the converting system that has feedforward compensation with the control load electric current according to claim 10, it is characterized in that: described time component comprises resistor and the capacitor that is connected in series, and the contact between this resistor and the capacitor is connected to the output terminal of described oscillator.
12, the converting system that has feedforward compensation with the control load electric current according to claim 8, it is characterized in that: described oscillator signal is the sawtooth wave with fixed frequency.
13, the converting system that has feedforward compensation with the control load electric current according to claim 8, it is characterized in that: described power supply is a direct voltage source.
14, the converting system that has feedforward compensation with the control load electric current according to claim 13, it is characterized in that: described power-switching circuit is converted to the required alternating voltage of described load based on described pulse signal with described direct voltage source.
15, the converting system that has feedforward compensation with the control load electric current according to claim 8 is characterized in that: described controller comprises a compensation condenser between the output and ground that is connected described error amplifier.
16, a kind of to realize the method for feedforward compensation to the power supply of lamp source power supply, it is characterized in that comprising:
Produce the oscillator signal that an amplitude and described power supply are in proportion;
Produce the feedback signal of an indication lamp source electric current;
Described feedback signal and a reference signal are relatively produced an error signal in the back; And
Produce the pulse signal of a dutycycle behind more described error signal and the described oscillator signal, to control the electric current in described lamp source with described oscillator signal amplitude variations.
17, according to claim 16 to realize the method for feedforward compensation to the power supply of lamp source power supply, it is characterized in that: produce the low-frequency pulse width modulated dim signal of a described error signal of control, to regulate the electric current in described lamp source.
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| CNB2005100880731A CN100410742C (en) | 2005-08-02 | 2005-08-02 | Converter controller having feedforward compensation, converting system and method for controlling same |
| HK07103832A HK1097051A1 (en) | 2005-08-02 | 2007-04-12 | Inverter controller with feed-forward compensationand its control method |
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| CNB2005100880731A CN100410742C (en) | 2005-08-02 | 2005-08-02 | Converter controller having feedforward compensation, converting system and method for controlling same |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102255506A (en) * | 2010-05-17 | 2011-11-23 | 昂宝电子（上海）有限公司 | High-accuracy oscillator system with feedforward compensation function and method thereof |
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| US8587962B2 (en) * | 2010-11-08 | 2013-11-19 | GM Global Technology Operations LLC | Compensation for electrical converter nonlinearities |
| US8860379B2 (en) | 2011-04-20 | 2014-10-14 | GM Global Technology Operations LLC | Discharging a DC bus capacitor of an electrical converter system |
| US8829858B2 (en) | 2011-05-31 | 2014-09-09 | GM Global Technology Operations LLC | Systems and methods for initializing a charging system |
| US8878495B2 (en) | 2011-08-31 | 2014-11-04 | GM Global Technology Operations LLC | Systems and methods for providing power to a load based upon a control strategy |
| US9770991B2 (en) | 2013-05-31 | 2017-09-26 | GM Global Technology Operations LLC | Systems and methods for initializing a charging system |
| TWI565209B (en) * | 2015-12-22 | 2017-01-01 | 國立臺灣師範大學 | Quasi universal feed forward dc to dc converter and method |
Family Cites Families (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5834906A (en) * | 1995-05-31 | 1998-11-10 | Philips Electronics North America Corporation | Instant start for an electronic ballast preconditioner having an active power factor controller |
| JPH09180889A (en) * | 1995-12-25 | 1997-07-11 | Murata Mfg Co Ltd | Cold cathode tube lighting device |
| KR100375513B1 (en) * | 2000-11-28 | 2003-03-10 | 삼성전기주식회사 | Inverter for back-light of LCD |
| CN1358057A (en) * | 2000-12-07 | 2002-07-10 | 国碁电子股份有限公司 | DC-AC converter |
| US6876157B2 (en) * | 2002-06-18 | 2005-04-05 | Microsemi Corporation | Lamp inverter with pre-regulator |
| JP4676685B2 (en) * | 2003-08-26 | 2011-04-27 | パナソニック電工株式会社 | Fluorescent lamp lighting device |
| CN2828860Y (en) * | 2005-08-02 | 2006-10-18 | 凹凸科技（中国）有限公司 | Switch controller with feedback compensation and conversion system |
-
2005
- 2005-08-02 CN CNB2005100880731A patent/CN100410742C/en not_active Expired - Fee Related
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2007
- 2007-04-12 HK HK07103832A patent/HK1097051A1/en not_active IP Right Cessation
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102255506A (en) * | 2010-05-17 | 2011-11-23 | 昂宝电子（上海）有限公司 | High-accuracy oscillator system with feedforward compensation function and method thereof |
| CN102255506B (en) * | 2010-05-17 | 2013-11-13 | 昂宝电子（上海）有限公司 | High-accuracy oscillator system with feedforward compensation function and method thereof |
| US9059688B2 (en) | 2010-05-17 | 2015-06-16 | On-Bright Electronics (Shanghai) Co., Ltd. | High-precision oscillator systems with feed forward compensation for CCFL driver systems and methods thereof |
Also Published As
| Publication number | Publication date |
|---|---|
| CN100410742C (en) | 2008-08-13 |
| HK1097051A1 (en) | 2007-06-15 |
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