CN1751444A - Techniques for correcting for phase and amplitude offsets in a MIMO radio device - Google Patents

Techniques for correcting for phase and amplitude offsets in a MIMO radio device Download PDF

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CN1751444A
CN1751444A CNA038214172A CN03821417A CN1751444A CN 1751444 A CN1751444 A CN 1751444A CN A038214172 A CNA038214172 A CN A038214172A CN 03821417 A CN03821417 A CN 03821417A CN 1751444 A CN1751444 A CN 1751444A
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antenna
relevant
amplitude
receiver
phase
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CN1751444B (en
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C·法得雅纳珊
G·L·苏格尔
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IPR Licensing Inc
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Cognio LLC
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/10—Monitoring; Testing of transmitters
    • H04B17/11—Monitoring; Testing of transmitters for calibration
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/0003—Software-defined radio [SDR] systems, i.e. systems wherein components typically implemented in hardware, e.g. filters or modulators/demodulators, are implented using software, e.g. by involving an AD or DA conversion stage such that at least part of the signal processing is performed in the digital domain
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/02—Transmitters
    • H04B1/04—Circuits
    • H04B1/0475—Circuits with means for limiting noise, interference or distortion
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/02—Transmitters
    • H04B1/04—Circuits
    • H04B1/0483—Transmitters with multiple parallel paths
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/20—Monitoring; Testing of receivers
    • H04B17/21—Monitoring; Testing of receivers for calibration; for correcting measurements
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems

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  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
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Abstract

Techniques to correct for phase and amplitude mismatches in a radio device in order to maintain channel symmetry when communicating with another device using MIMO radio communication techniques. Correction for the amplitude and phase mismatches among the plurality of transmitters and plurality of receivers of a device may be made at baseband using digital logic (such as in the modem) in the receiver path, the transmitter path or both paths of that device. In a device, amplitude and phase offsets are determined among the plurality of radio transmitter and radio receiver paths by measuring phase and amplitude responses when supplying a signal to a transmitter in a first antenna path of the device and coupling the radio signal from a first antenna to a second antenna path of that device where the signal is downconverted by a receiver associated with the second antenna path, and similarly coupling a signal from the second antenna path to the first antenna path. Measurements are obtained between the first antenna path and each of the other antenna paths when coupling a signal in both directions between them. Phase and amplitude offset correction values are computed from the phase and amplitude measurements during a self-calibration operation or mode of the device, and are used during a run-time operation or mode when processing the baseband transmit and/or receive signals to compensate for the phase and amplitude offsets among the plurality of transceiver paths of a device. Amplitude offset correction may not be necessary (or optional) for certain radio implementations or MIMO radio algorithms. The device may execute the self-calibration mode on device power-up, and then periodically thereafter. Self-calibration may also be performed at the factory on a device.

Description

The technology that phase place and amplitude offsets are proofreaied and correct in the MIMO radio device
Related application
The present invention advocates the priority of No. the 60/409th, 677, the provisional application case of the U.S. of filing an application on September 10th, 2002, and according to annex, it fully is shown among the application.
Technical field
The present invention is relevant to the technology that phase place and amplitude offsets are proofreaied and correct in wireless device, and described wireless device uses multi-input multi output (MIMO) radio communication.
Background technology
Multi-input multi output (MIMO) radio communication involves, and is side by side several by what communicate by letter in a plurality of antennas, launches a plurality of signals from one first device, and receives a plurality of signals from a plurality of antennas of one second device.Each device has a plurality of reflectors, the signal that will be launched in order to up-conversion (upconvert), and have a plurality of receivers, in order to down-conversion (downconvert) in the received signal of each a plurality of antennas.
In the art, the algorithm of many multi-input multi output (MIMO) signal processing is well known.There is some multi-input multi output (MIMO) wireless algorithm to be to use the information of relevant wireless channel between between two devices, in installing, maximizes the signal noise ratio SNR that receives at each.The wireless algorithm of these multi-input multi outputs (MIMO) relies on the channel symmetry that links between two devices.The example that relies on multi-input multi output (MIMO) wireless algorithm of channel symmetry discloses, for instance, generally be attributable to U.S. patent application case No. 10/174728, file an application on June 19th, 2002, submit case " using the method and system of the antenna diversity of total maximum wireless combination " (System and Method for Antenna Diversity Using Joint Maximal RadioCombining) by name to; U.S. patent application case the 10/174th, No. 689, file an application on June 19th, 2002, submit case " using the method and system of the antenna diversity of the total maximum wireless combination of equal homenergic " (System and Method for Antenna Diversity Using Equal Power JointMaximal Radio Combining) by name to; And U.S. patent application case the 10/064th, No. 482, file an application on July 18th, 2002, submit case " method and system that the total maximum wireless that uses time-domain signal to handle makes up " by name System and Method for Joint Maximal Radio CombiningUsing Time-Domain Signal Processing to).These algorithms increase the signal noise ratio SNR that receives widely, and by doing like this, and the scope that expansion instrument can be communicated by letter with other device.
When a device during in the path of the reflector that chains and receiver walking etc., will lose the symmetry of channel, thus, reduce the wireless algorithm performance of the multiple output of described heavy input (MIMO).Because the reflector in each antenna-path and imperfectization of analog circuit of receiver, cause between data converter and position between the antenna in each antenna-path of a device, mismatching of amplitude (obtaining) and phase response, may cause letter to lead response and become asymmetric.
In order utilize to rely on up hill and dale between between two devices, be to need a technology in order on the phase place of multi-input multi output (MIMO) wireless link of each device and amplitude offsets, to proofread and correct in the benefit of multi-input multi output (MIMO) wireless algorithm of the channel symmetry that chains.To have multi-input multi output (MIMO) wireless for chaining at it when a device for these technology, and another device is when having a signal antenna or suitching type multiaerial system, and same is of great use.
Summary of the invention
Simply, for when communicating by letter with another device that relies on channel symmetry multi-input multi output (MIMO) wireless communication technology, keep the symmetry of channel, and provide in order in a device, to go phase calibration and amplitude to mismatch the technology of (skew or imbalance that the face here of equally also can saying so is mentioned).In a plurality of reflectors that install and a plurality of recipient, go to proofread and correct mismatching of amplitude and phase place, can be used on the receiver path of described device, on the transmitter paths or two paths on Digital Logic (for example in a modulator-demodulator), and on base band, be done.In a device, the skew of amplitude and phase place, be by when providing a signal to establish device to of one first antenna-path that is arranged in described device, and one second thread path from the described wireless signal of one first antenna coupling to described device, described signal in described position by a receiver that links with described second antenna-path during by down-conversion (downconvert), measure the response of amplitude and phase place, and similarly when being coupled to described first antenna-path from described second antenna-path, measure the response of amplitude and phase place, and in a plurality of wireless launchers and recipient path, determined.When both direction all coupling one signal between the two the time, obtain the measured value between between other antenna-path of described first antenna-path and each.During described device one a self-correction running or a pattern, by the measured value that calculates amplitude and phase place, and obtain the corrected value of amplitude and phase deviation, and when handling baseband transmission and/or received signal when compensating amplitude between a plurality of transmitter paths of a device and phase deviation, in during a running one term of execution or the pattern, use the corrected value of described amplitude and phase deviation.For some wireless execution or multi-input multi output (MIMO) wireless algorithm, the correction of amplitude excursion may be unnecessary (or not necessarily).Described device may be carried out the self-correction pattern when the device electric power starting, periodically repeat after this.Self-correction also may be carried out on the station on the device.
When communicating by letter with second device that similarly is corrected as one first device of proofreading and correct as described herein, importing (DAC input) to the channel response between the numeral output (ADC output) of the described second device receiver path between the numeral in the described first device conveyer path, is to be symmetrical between the numeral in the described second device conveyer path to import (DAC input) to the channel response between the numeral output (ADC output) of the described first device receiver path.So, on the base band signal process level, be symmetrically between the channel response between two devices, this is satisfactorily for multi-input multi output (MIMO) the wireless algorithm that relies on channel symmetry.
These technology equally all are useful for single carrier modulation system and multicarrier modulation system, for example OFDM (OFDM, Orthogonal Frequency Division Multiplexing) system.
When simultaneously with reference to the series explanation with and during corresponding icon, it is more obvious that advantage of the present invention will become.
Description of drawings
Fig. 1 is the block diagram that two communicators use multi-input multi output (MIMO) wireless technology mutual communication each other.
Fig. 2 is the more detailed diagram of a device, and is shown in the source of phase deviation in a plurality of wireless transmitter and receivers.
Fig. 3 is the common block diagram that an operation technique removes to proofread and correct the communicator of shown phase deviation.
Fig. 4 is a use single carrier or an OFDM (OFDM, Orthogonal FrequencyDivision Multiplexing) block diagram of the device of all bandpass filters of system and parallelism matrix, in this device, the skew of phase place and amplitude is corrected.
Fig. 5 one uses the block diagram of device of the parallelism matrix of OFDM (OFDM, Orthogonal Frequency DivisionMultiplexing) system, and in this device, the skew of phase place and amplitude is corrected.
Fig. 6 is a block diagram, shows how skew being proofreaied and correct on the RX path in the device, transmission path or two paths.
Fig. 7 is a block diagram, shows how one low pass filter can be shared to simplify correction or to proofread and correct between emission and RX path.
Fig. 8 is a profile diagram, and demonstration ought be not be led because of in the average loss of deviation in link of amplitude and phase place as timing.
Embodiment
At first, the effect that amplitude and phase place mismatch will be described in NxM multi-input multi output (MIMO) channel with reference to figure 1.L 1With L 2Represent respectively from one first the device 100, that is to say, an access point (AP) to one second the device 200, that is to say, a base station (STA) with from a base station (STA) channel response matrix to an access point (AP).Multi-input multi output (MIMO) channel of one symmetry has L 1=L 2 TCharacteristic.
Device 100 has N antenna 110 (1) to 110 (N), has M antenna 210 (1) to 210 (M) and install 200.So device 100 has N transmission path and N RX path, has M transmission path and M RX path and install 200.With each in device transmission path in 100 relevant a digital analog converter (DAC) 115 (1) to 115 (N) arranged, it changes a digital baseband signal is an analog signal in order to by a corresponding emission in the antenna 110 (1) to 110 (N).With each in device RX path in 100 relevant an analog-digital converter (ADC) 130 (1) to 130 (N) arranged, analog signal that its conversion one receives is a digital baseband signal.Similarly, the device 200 in, have a DAC220 (1) to 220 (M) in each transmission path, and an ADC230 (1) to 230 (M) in each RX path.Moreover device 100 has a modulator-demodulator 140, has a modulator-demodulator 240 and install 200.Described modulator-demodulator 140 and 240 is processors, and (ASICs, application specific integrated circuits) can be fulfiled by the Digital Logic lock in integrated circuit.
For indoor Radio Communication System, for example, one IEEE 802.11x WLAN (WLAN), the a group network endpoint uses carrier wave induction multiple access (CSMA) to come swap data in identical carrier frequency therein, induction of signal between any two end points yes symmetry but only between their antenna array.For example, respond to difference to some extent responding on one first RX path of common and identical device 100 amplitude and the phase place between between antenna 110 (1) and ADC 130 (1) between amplitude between DAC 115 (1) and antenna 110 (1) and phase place on first device, 100 first transmission path.In addition, common and second install on 200 one first transmission path amplitude and the phase place between between DAC 220 (1) and antenna 210 (1) and respond to difference to some extent with the phase place induction on first device, 100 second transmission path between the amplitude between DAC 115 (2) and antenna 110 (2).In order to commend the wireless algorithm of MIMO that carries out luckily according to the symmetry of channel, described channel responds under base band, and the response that wherein offers MIMO radio algorithms calculating formula must be symmetrical.Therefore, the whole non-digital part of described channel (for example, be input to transmission path again to the ADC of receiver path output from DAC) amplitude and the effect of phase response must take in, and be also contained in the amplitude and the phase response of the emitter assemblies between each DAC and pairing antenna, and the amplitude and the phase response of the receiver assembly between an antenna and corresponding ADC.
Inharmonious along with amplitude and phase place, described channel response matrix, as what see in the logic by modulator-demodulator 140 and 240, revise as follows:
Install 100 auto levelizer 200:L 1=B 2HA 1
Install 200 auto levelizer 100:L 2=B 1H TA 2
A wherein 1, A 2For expression respectively by at device 100 and device 200 caused phase place of reflector and the unbalanced diagonal matrix of amplitude, and B 1, B 2Then expression is respectively by caused phase place of receiver and the unbalanced diagonal matrix of amplitude at device 100 and device 200, wherein:
A 1＝diag(α 11e jφ11，...，α 1Ne jθ1N)
A 2＝diag(α 21e jφ21，...，α 2Me jθ2M)
B 1＝diag(β 11e jφ11，...，β 1Ne jθ1N)
B 2＝diag(B 21e jφ21，...，β 2Me jθ2M)
The emission of each device and RX path the above phase place and amplitude effect with diagonal matrix A 1, A 2With B 1, B 2Respective value represent.Being exposed in the transmission weight that foregoing co-pending n rank of delivering the wireless algorithm of a kind of MIMO in the file iterate is expressed as follows:
W T，AP，n＝γ n(L2 *L1) nW T，AP，0
W T，STA，n＝ρ n?L 1 *(L2L1 *) nW * T，AP，0
Wherein, γ nWith ρ nFor modulation factor in order to described transmitting power is normalized into a unit.Described as can be seen weight iterates L respectively via a power from formula 2 *L 1With L 1 *L 2Main characteristic vector and restrain.
Please refer to shown in Figure 2, being described in more detail of its expression one device 100 (having N antenna) to be used for the source of interpretative phase effect.Have a plurality of wireless receivers in the way, each wireless receiver is relevant with in corresponding a plurality of antennas 100 (1) to 110 (N) one of them.Each wireless receiver comprises and described a plurality of antennas, a relevant reflector 120 (i) and the receiver 135 (i) of pairing one of them antenna from i=1 to N.The baseband signal that described wireless launcher 120 (i) conversion is provided by the DAC115 that is associated (i) is to a wireless frequency signal, so that the transmission of a corresponding antenna 110 (i) to be provided.The wireless frequency signal that described receiver 135 (i) conversion is detected via the antenna 110 (i) of a correspondence.It is wireless relevant with a MIMO to have a plurality of wireless transceivers.
The assembly that is contained in each reflector 120 (i) and the receiver 135 (i) may be according to the kind of employed wireless architecture, for example, and heterodyne system or direct change type, and difference to some extent.Fig. 2 only represents to can be used for the assembly on the direct converting structure for instance, but it must be appreciated, wherein the notion of described alignment technique can be able to be used for the wireless architecture of any kind.For example, Fig. 2 represents that each reflector 1205 (i) comprises conversion blender 150 (i), a power amplifier 165 (i) and other assembly miscellaneous.And each receiver for example in other assembly, then comprises a low assorted letter amplifier 167 (i) and a conversion blender 155 (i).A switch 137 (i) relevant with each antenna 110 (i) selects described reflector 120 (i) or receiver 135 (i) whether to be connected to described antenna.In described base band side, have on transmission path the low pass filter 125 (i) with the RF part of reflector 120 (i) between DAC 115 (i), and at the low pass filter 127 (i) between between described ADC 130 (i) and described receiver 135 (i) on the RX path.
As shown in Figure 2, a plurality of receivers and a plurality of reflector can be executed in a single semiconductor integrated circuit (IC).The one fully integrated wireless Application No. No.10/065 that ask, co-pending on October 11st, 2002 that has been exposed in of MIMO, in 388, the disclosure of this case is to classify the application's list of references as.Therefore, a MIMO is wireless may be made up of the single integrated circuit that a plurality of other wireless receivers or are carried out a plurality of receivers thereon.
The source φ of phase effect 1Tx, φ 1Rx, φ NTx, φ NRxPerhaps can be included in the blender 150 (i) in each path and the difference of the local oscillation phase place of 155 (i), and the delay difference of the microcommunity between other wireless module.Phase deviation may change because of processing procedure, voltage and temperature etc.Colony between wireless (RF) frequency component postpones difference τ RF Tx (1), τ RF Rx (1)To τ RF Tx (N), τ RF Rx (N)Can reach the order of magnitude of tens picoseconds (picoseconds), and cause frequency band to produce the phase deviation that quite slowly changes whole operation.For example, a 50ps colony postpones skew and causes one 92.7 degree phase deviations at 5.15GHZ, and causes one 96.3 degree phase deviations at 5.35GHZ.Therefore, a frequency of manipulable each frequency band of skew of these types is proofreaied and correct.In the heterodyne system wireless architecture, intermediate frequency (IF, intermediate frequency) assembly (for example, be not shown in IF filter, AGC amplifier on the figure) between colony's delay variance may postpone difference on skew big last 1 or 2 order of magnitude degree than RF colony, therefore the phase deviation that causes makes and produces difference on the frequency band more quickly.Therefore, may need to proofread and correct to each wireless channel that uses the IF component design.The delay variance τ of colony of (for example, the difference of low pass filter, the pipeline factor between ADCs and DACs) on base band component BBTx (1), τ BB Rx (1)To τ BB Tx (N), τ BB Rx (N), for IEEE 802.11x signal baseband, be about the order of magnitude of nanoseconds, therefore can cause huger phase change thereby interior generation of base band of a channel made a variation.
The method that can guarantee the optimum performance of the described wireless algorithm of symmetric MIMO according to channel is to proofread and correct each device to guarantee the symmetry at the channel of school disease.In some cases, this correction with phase place and amplitude is relevant, and in other cases, only relevant with phase deviation.For example, emulation from be exposed in foregoing designated reference document co-pending has proved that the MIMO radio algorithms of constant power is better than the MIMO radio algorithms of non-constant power, because the MIMO radio algorithms of described constant power can be exempted relatively large amplitude excursion.
In general, can be in the correction of the transmitter side of each device by carrying out a described correction matrix C=diag (c 1..., c N) transmission weight reach, wherein, c 1=γ 1Exp (j χ 1) ..., c N=γ NExp (j χ N), wherein, γ iBe correction of amplitude assembly χ iBe the phasing assembly.Described corrected signal response matrix becomes L 1=B 2HA 1C 1With L 2=B 1H TA 2C 2
One can guarantee that the symmetric necessary and sufficient condition of the channel on connecting is
B 1=A 1C 1And B 2=A 2C 2(1)
This situation can guarantee the channel of a symmetry, because
L 2 T＝(B 1H TA 2C 2) T＝B 2 THA 1 TC 1 T＝B 2HA 1C 1＝L1
Later see also Fig. 1, the method for condition (1) being write as an equivalence of the MIMO wireless channel that is used for one N * M symmetry is:
γ 11α 11/ β 11Exp[j (χ 11+ θ 11-φ 11)]=γ 12α 12/ β 12Exp[j (χ 12+ θ 12-φ 12)]=...=γ 1Nα 1N/ β 1NExp[j (χ 1N+ θ 1N-φ 1N)]; And
γ 21α 21/ β 21Exp[j (χ 21+ θ 21-φ 21)]=γ 22α 22/ β 22Exp[j (χ 22+ θ 22-φ 22)]=...=γ 2Mα 2M/ β 2MExp[j (χ 2M+ θ 2M-φ 2M)], wherein θ and φ distinguish the conveyer and the receiver phase response of indication device 100 and 200, and α and β then are the amplitude responses of the conveyer and the receiver of difference indication device 100 and 200.And the subscript i shown in Fig. 1, j difference indication device i (device 1 is represented device 100 or installed 2 and represent device 200), and j the antenna of device i (or corresponding antenna-path).
Another equivalent method of being write as condition (1) is:
For amplitude:
γ 11α 11/ β 11=γ 12α 12/ β 12=...=γ 1Nα 1N/ β 1NAnd
γ 21α 21/β 21＝γ 22α 22/β 22＝...＝γ 2Mα 2M/β 2M；
For phase place:
[χ 11+ θ 11-φ 11]=[χ 12+ θ 12-φ 12]=...=[χ 1N+ θ 1N-φ 1N]; And
[χ 21+θ 21-φ 21]＝[χ 22+θ 22-φ 22]＝...＝[χ 2M+θ 2M-φ 2M]
Linearity independently equation 2 (N-1) need specify the situation that is respectively applied for the 1st side and the 2nd side with 2 (M-1):
[χ 11+θ 11-φ 11]＝[χ 12+θ 12-φ 12]；γ 11α 11/β 11＝γ 12α 12/β 12
[χ 11+θ 11-φ 11]＝[χ 13+θ 13-φ 13]；γ 11α 11/β 11＝γ 13α 13/β 13
…
[χ 11+θ 11-φ 11]＝[χ 1N+θ 1N-φ 1N]；γ 11α 11/β 11＝γ 1Nα 1N/β 1N；
[χ 21+θ 21-φ 21]＝[χ 22+θ 22-φ 22]；γ 21α 21/β 21＝γ 22α 22/β 22
[χ 21+θ 21-φ 21]＝[χ 23+θ 23-φ 23]；γ 21α 21/β 21＝γ 23α 23/β 23
[χ 21+θ 21-φ 21]＝[χ 2M+θ 22M-φ 2M]；γ 21α 21/β 21＝γ 2Mα 2M/β 2M
Equation recited above for example, at the device of N side, can rewrite as follows at a device that is used to link:
[χ 1+θ 1-φ 1]＝[χ 2+θ 2-φ 2]；γ 1α 1/β 1＝γ 2α 2/β 2
[χ 1+θ 1-φ 1]＝[χ 3+θ 3-φ 3]；γ 1α 1/β 1＝γ 3α 3/β 3
…
[χ 1+θ 1-φ 1]＝[χ N+θ N-φ N]；γ 1α 1/β 1＝γ Nα N/β N (2a)
After some algebraic manipulations, equation (2a) can be rewritten as follows equivalently:
[χ 1+θ 1-φ 2]＝[χ 2+θ 2-φ 1]；γ 1α 1/β 2＝γ 2α 2/β 1
[χ 1+θ 1-φ 3]＝[χ 3+θ 3-φ 1]；γ 1α 1/β 2＝γ 3α 3/β 1
…
[χ 1+θ 1-φ N]＝[χ N+θ N-φ 1]；γ 1α 1/β 2＝γ Nα N/β 1 (2b)
At equation (2a) and (2b), it is to be used for representing not losing generality that first time shown target falls, and these two equations can be used for the wherein binding of a side.In order to ensure the symmetry of channel, equation (2a) or relation (2b) must maintain two devices in the binding equivalently.These two equations (2a) and relation (2b) are described below.A certain basic naming method is provided.At each antenna, the reflector that has a correspondence on a device is in order to transforming a signal of being launched by antenna, and the receiver of a correspondence in order to conversion by signal that antenna received.In addition, each antenna the emission with receive direction on all have a corresponding antenna-path.Can be relevant from the signal path of the output of the antenna that is input to its correspondence of reflector with the transmission path of this antenna.Same, also can be relevant from the signal path of the output that is input to pairing receiver of an antenna with a RX path of this antenna.Phase place and (selection) amplitude excursion corrected value are the signals (in the transmission path direction, RX path direction, or this both direction) that is applied to relevant with these a plurality of antennas every day of thread path.
A method describing this equation (2a) relation is in a device, (a) from one of a reflector input to its respective antenna output this amplitude and phase response and (b) input to the poor of this amplitude of this output of its corresponding receiver and phase response from this of this antenna, concerning all antennas (N is antenna assembly i=1 to N), all be identical (and fixing).A method describing this equation (2b) relation is in a device, from input to this amplitude and phase response about one of a reflector of an antenna (for example antenna 1) about the output of the receiver of another antenna (for example antenna i), be to be equal to (b) from this amplitude and the phase response of inputing to about the output of the receiver of antenna 1 about the reflector of antenna i, it is applicable to all antennas (a N-antenna assembly, i=2 to N).
The explanation of this equation (2b) is suggestion one loopback configuration, to be described in down, it is in order to obtain to need to calculate the measurement of this corrected value γ i and χ i, to proofread and correct a plurality of reflectors that install and this amplitude and the phase deviation between a plurality of receiver, use when this device emission and received signal, satisfy the condition of this equation (2b).What must reaffirm is that the corrected value that satisfies equation (2b) also will satisfy these efficacious prescriptions formulas (2a).
Fig. 3 shows the device 100 with MIMO wireless 160, and wherein corrected value (γ i and χ i) is calculated, to reach this equation (2a) or condition (2b).Modulator-demodulator 140 comprises a classification that produces the signal that is used for the classification process of measurement and calculates square 145, measures and calculate and store this corrected value to carry out.This modulator-demodulator 140 also has one and proofreaies and correct square 147, and it is used for this base band transmit or transmission weight with corrected value, or is used for this baseband receiving signals, or is used for this base band transmit and this baseband receiving signals, proofreaies and correct to reach an ideal network.There are many technology can produce this value parameter, and use these parameters, as described below.One controller processor 170, a microprocessor for example can produce a signal that is coupled to modulator-demodulator 140, with when the initial power-up of this device, initialization one self-hierarchical pattern, and/or after termly or off and on, to upgrade this value parameter.Each relies on the connected symmetrically device with another device, with self-classification in a similar manner.This corrected value also is called place value at this, and/or value parameter.
When variable gain amplifier was used in this receiver and/or this reflector, classification can be considered the phase change of setting about the using gain of these assemblies.One technology is that this phase place of decision receiver and emitter assemblies concerns gain setting, and store (for example in a table) in the no gain calibration value be modulated to this internal memory 165, or alternately, this modulation value of hard coded in this Digital Logic of this modulator-demodulator 140, as shown in Figure 3.The no gain modulation of these of these corrected values can once produce in factory, and then in an operation duration of runs of this device of this field or pattern, and this modulation is that the existing gain setting according to this device uses; Alternately, the no gain modulation of this corrected value can be calculated in this field in a self-hierarchical pattern or operation.No gain calibration value can reach or calculate in this factory in this field in a self-hierarchical pattern of a device.The no gain modulation of this corrected value can be used following technology about Fig. 4 and Fig. 5, and produces (in this factory or in this field) at each gain setting.
This classification logic is to be arranged in this modulator-demodulator 140, because this modulator-demodulator is typically to realize with a Digital Logic lock of handling the ASIC of this baseband signal.Will be understood that, use for some, or along with the progress of the microprocessor performance of Portable or Embedded Application, this classification logic can store or be encoded in the software of processor read-only memory medium and realize, and carries out (it also carries out this modulator-demodulator logic) via this processor 170.
After carrying out classification conversation,, be to use corrected value when handling base band transmit and/or baseband receiving signals when reaching equation (2a) or condition (2b).When one first device with these condition classifications communicates with second device with the conditions of similarity classification, channel response between this numeral output (ADC output) of this numeral input (DAC input) of this transmission path of this first device and this RX path of this second device is that this numeral that this numeral of being symmetrical in this transmission path of this second device is imported (DAC input) and this first this RX path of installing is exported the channel response between (ADC output).Therefore, these two be installed on this base band signal process layer between channel response be symmetrical, it is desirable for the wireless algorithm of MIMO that relies on the channel symmetry.
For relatively large group delay skew (being caused by baseband transmitter and/or receiver assembly usually), the phase place between transmission path mismatches in the base band that will transmit at this and changes, therefore the phase bit-by-bit that need change in frequency.As shown in Figure 5 and be described in down, for multicarrier modulation system, for example orthogonal frequency division multitask (OFDM) system, it can be via using at this reflector, this receiver, or the out of phase contraposition Matrix C (k) of each OFDM subcarrier is reached among both.Other method is shown in Fig. 4 and is described in down, its use (1) is at this reflector, receiver or the all-pass filter among both (for example sampler) again and again, reach the non-selection phase correcting value of (2) frequency (a single-frequency independence correction matrix) and compensate wideband phase deviation, with this group delay in each transferring and receiving apparatus path of contraposition.For example, this sampler can be a pig type (farrow) sampler program again.
See also Fig. 4, the relevant part that can carry out the n antenna assembly (for example device 100 of Fig. 3) of mimo wireless communication is shown among Fig. 4, and the correction of its amplitude and phase deviation is performed.The method of Fig. 4 is useful to single carrier or multicarrier modulation system.This modulator-demodulator 140 comprises this classification and calculates square 145 and this correction square 147.This correction square 147 comprises all-pass filter 180 (1) to 180 (N) and multiplexer 190 (1) to 190 (N).These multiplexers 190 (1) to 190 (N) are used this single (frequency-non-selects) correction matrix C=diag (c 1..., c N) corresponding assembly, wherein Ci is defined as γ iexp (j χ i), with compensation of phase skew and amplitude excursion.The assembly of phase correcting value γ i will be described in down in more detail.
The method of Fig. 4 is carried out this receiver this base band group delay contraposition partly of this modulator-demodulator.This method is a lock counting viewpoint, and (for example sampler) again and again must be used for most receiver modem structures because an all-pass filter, to reply as data time sequence, and be of value to single-carrier system, IEEE 802.11b for example, but also be applicable to multicarrier system, for example ofdm system.Below about the narration of Fig. 6, realize that the Digital Logic lock of this all-pass filter and multiplexer can be in this transmitter paths, in the receiver path, or in these both paths, with compensate for amplitude and phase deviation.
These multiplexers 190 (1) to 190 (N) can be with before last commentaries on classics and emission, and it is identical to the multiplexer of this base band transmit to use this transmission weight WT.In this example, this transmission weight W T(more than one) multiply by this correspondence assembly c of this diagonal matrix C i
Next carry out a program, with this value parameter of the N antenna assembly that produces a Fig. 4.This classification is calculated square 145 and is comprised this logic, carrying out this classification procedure, and produces this value parameter of these all-pass filters 180 (1) to 180 (N) and these multiplexers 190 (1) to 190 (N).
Step 1.One frequency synthesizer 195 is modulated to the known frequency channel in the interests radio band.This modulator-demodulator produces a base band continuous wave (CW) that is coupled to this dac115 (1) that is connected with antenna 110 (1) (antenna-path 1) and transfers e 2 π j φ kt, to launch via antenna 110 (1) to reflector 120 (1).And use a cable or to cross aerial binding, this transmitting RF output of antenna-path 1 is this RF input that is recycled to this antenna 110 (2) (antenna-path 2).One first phase difference between the signal of the output of the signal of the input of this DAC115 (1) in the antenna-path 1 and this ADC130 (2) in the antenna-path 2 is to measure on some frequencies (f for example k={ 3f s/ 8 ,-f s/ 8, f s/ 8,3f s/ 8} is characterized in that the fs=symbol rate).In general, measure in the frequency place execution of the frequency range of enough this baseband signals of leap.This first phase difference 12(k)=[θ 1(k)+φ 2(k)+and φ ant (1,2)], θ wherein 1(k) and φ 2(k) represent in frequency f respectively kThe place is via reflector 120 (1) phase-shifts with receiver 135 (2), and φ ant (1, the 2) phase-shifts that this is crossed in the air or cable is connected between representative antennas 110 (1) and antenna 110 (2) then.In addition, one first amplitude γ of the signal of the output of this ADC130 (2) 12(k) in each frequency f kThe place is measured.
Step 2.Use antenna-path 2 to be used as this reflector, and use antenna-path 1 to be used as this receiver and come repeating step 1, to measure one second phase difference ψ 21(k)=[θ 2(k)+φ 1(k)+φ ant (1,2)], and measure each frequency f kOne second amplitude γ of the signal of the output of this ADC130 (1) at place 21(k).
In above-mentioned steps 1 and step 2, before being received, will can not experience enough decay because be sent to the signal of another antenna-path from an antenna-path, so (low noise) amplifier in the RX path can cut out, or its gain setting can reduce (decline),, so this received signal also can be damaged blender and other assembly in this RX path.
Step 3.Postpone skew or antenna-path 1 is estimated with the following equation of use that mismatches of 2 of antenna-path with the frequency group group:
δ τ 2=-(1/2 π) * crossover frequency f kPoint { (f k, ψ 12(k)-ψ 21The slope of the best line (k)) }.
Step 4.The following equation of use that mismatches that wideband phase deviation or antenna-path 1 and an antenna-path are 2 is estimated:
δ θ 2=y-crossover frequency f kPoint { (f k, ψ 12(k)-ψ 21The intercept of the best line (k)) }.
Amplitude mismatches γ 2Be that estimation is from a crossover frequency f kFirst and second measure amplitude that is { (f k, γ 12(k)/γ 21One mean value of ratio (k)) }.
Step 5, step 1-4 repeats between antenna-path 1 to i, with from crossover frequency f K-Point { (f k, ψ 1i(k)-ψ I1(k)) calculate group delay skew δ τ } iWith wideband phase deviation δ θ i, and from { (f k, γ 1i(k)/γ I1(k)) calculate amplitude excursion γ } 1, i=3 wherein ..., N.δ τ 1..., δ τ N, δ θ 1..., δ θ N, and γ 1..., γ NBe to save as value parameter or proofread and correct numerical value, it is characterized in that, this group delay skew δ τ for this antenna-path that is connected in this first antenna 1=0, this wideband phase deviation δ θ 1=0, and this amplitude excursion γ 1=1.δ τ iThe unit be sampling with a suitable sampling rate.
In step 6, group delay in the band in the radio transceiver path (in-band group delay) mismatch is proofreaied and correct in can be during normal running, and this is by use the all-pass filter that is presented among Fig. 4 in the i of recipient path, i=1 wherein, ..., N, and create δ τ iThe group delay of sampling.δ τ wherein iThe＞0th, implying time delay, and δ τ iThe＜0th, implying in advance.Broadband phase deviation (may be selected to be amplitude excursion) in the radio transceiver path can be multiplied by cornerwise calculation Matrix C and is removed by launching weighting or base band transmit, wherein:
c 1＝1
c 2＝γ 2exp(jδθ 2)
c 3＝γ 3exp(jδθ 3)
…
c N＝γ Nexp(jδθ N)
Do not proofread and correct if do not carry out amplitude excursion, so to all i, its γ i=1
In step 7, if necessary, can in the multiple channel in the RF band, so that being responsible for, slow variation phase skew can not influence any result of numerical computations by the phase deviation of antenna and/or coupling cable by repeating step 1 to 6.And can store at the corrected value of each channel, or the set of the corrected value of independent channel can store with the correlated channels modulation set of independent channel separately to calibration parameter in each channel and also can store separately.
The program of Fig. 4 can be by using multiple carrier (boc) modulated signals to improve, and for example an ofdm signal replaces in frequency f kMultiple tone.Moreover the multiple carrier modulation scheme (scheme) that extends to that program as described above can broad sense as OFDM, wherein replaces by single carrier wave baseband signal in frequency f kThe phase difference measurement of being carried out, measurement are that a plurality of subcarrier k (subcarrier k that need not be all) at a multiple carrier wave baseband channel are performed, and efficient as previously described execution linear analysis (numerical computations of slope and y intercept).
Sum up and opinion is calculating deviant corresponding to antenna i=1 in the antenna-path of N, wherein Dui Ying broadband phase pushing figure δ θ iWith group delay value δ θ in the band of correspondence iBe from frequency f by single baseband signal broadband kSequence { the ψ that is derived 1i(k)-ψ I1(k) } estimate, wherein ψ 1i(k) be in frequency f kIn be associated with the reflector input of first antenna and be associated with phase difference (being also referred to as first phase difference) between the receiver output of antenna i, and ψ I1(k) be in frequency f kIn be associated with the reflector input of antenna i and be associated with phase difference (being also referred to as second phase difference) between the receiver output of first antenna, δ θ wherein 1=1=δ τ 1, and corresponding amplitude excursion γ iBe quantitatively to calculate from amplitude described above.
Use phase place (can select is amplitude) skew to be described the calibration figure calculating square that is associated with Fig. 4 by the front to be calculated, can handle (similarly being the action of multiplying each other) many base band transmit (or emission weighting) and/or many baseband receiving signals by corresponding corrected value at the correction square 147 of modulator-demodulator 140, so the phase amplitude that can proofread and correct between a plurality of reflectors and a plurality of recipient is poor, with convenient signal during by the emission of a plurality of reflectors and/or signal when receiving, be all to be identical (promptly all antenna-path are fixed) from the phase response of the output that is input to respective antenna of a reflector and (2) from the difference between the phase response of the output that is input to corresponding receiver of described antenna in a plurality of antennas each in (1) by a plurality of receivers.
Especially, when timing is carried out in (broadband) phase deviation, described modulator-demodulator 140 is handled many base band transmit and/or many baseband receiving signals by the broadband phase deviation corrected value of correspondence, is to equal to be associated with the broadband phase deviation that antenna-path calculated of i=1 to the antenna i of N so can reach the biased shift correction of a net phase.In the same manner, when timing is carried out in amplitude excursion, described modulator-demodulator 140 (using described correction square 147) is handled many base band transmit and/or many received signals by the amplitude correction values of correspondence, is to equal to be associated with the amplitude excursion that antenna-path calculated of i=1 to the antenna i of N so can reach a net amplitude offset correction.In addition, when timing is carried out in phase deviation in being with, described modulator-demodulator 140 is handled many base band transmit and/or many baseband receiving signals by the group delay phase deviation corrected value of correspondence, is to equal to be associated with group delay that antenna-path the calculated skew of antenna i=1 to N so can reach a clean group delay offset correction.
Fig. 5 is illustrated in the way that is applicable to as the multiple carrier modulation plan of OFDM.Described correction square 147 comprises many multipliers 197 (1) to 197 (N), adopts emission location or correction matrix C kIn each OFDM subcarrier k, go to remove phase place and optionally amplitude excursion.Described multiplier 197 (1) to 197 (N) can be to be applied in to utilize emission weighting W Ti(wherein i=1 is to N) is transmitted into the same multipliers of base band transmit.Launch positional matrix C and produce kTechnology as follows:
Step 1: frequency synthesizer 194 in interesting wireless frequency band to be modulated to known frequency channel.One baseband OFDM channel is that to use known BPSK modulation pattern by DAC 115 (1) in antenna-path 1 be not that cable links by aerial (over the air) exactly and launches with using, and making the RF of signal from the antenna 110 (1) of antenna-path 1 to antenna-path 2 import becomes ring.First phase difference is by the output of the ADC 130 (2) of the input of the DAC 115 (1) of antenna-path 1 in each OFDM subcarrier and antenna-path 2 and measure.The first phase difference ψ 12(k)=[θ 1(k)+φ 2(k)+φ Ant(1,2)], θ wherein 1(k) and φ 2(k) be the phase-shifts of receiving device of seizing that is illustrated respectively in k the OFDM subcarrier reflector by antenna-path 1 and antenna-path 2, and φ Ant(1,2) is illustrated between antenna 110 (1) and antenna 110 (2) both either directions by phase-shifts aerial or that cable links.In addition, in the output of ADC 130 (2), one first amplitude γ of signal 12(k) can measure.
Step 2: use antenna-path 2 as reflector with use antenna-path 1 as receiver and repeating step 1, in order to measure one second phase difference ψ 21(k)=[θ 2(k)+φ 1(k)+φ Ant(1,2)] and the second amplitude γ that measures the signal in the output of ADC 130 (2) 2(k).
Step 3: repeating step 1 and step 2 between antenna-path 1 and antenna-path i (i=3 is to N), in order to measure the first phase difference ψ 1i(k) and the second phase difference ψ I1(k) and the first and second amplitude γ I1(k) and γ 1i(k).
Step 4: cornerwise phase place location or correction matrix C (k) are calculated as follows:
c 1(k)＝1
c 2(k)＝γ 2(k)exp(j[ψ 12(k)-ψ 21(k)])＝γ 2(k)exp(j[θ 1(k)+φ 2(k)]-[θ 2(k)+φ 1(k)])
c 3(k)＝γ 3(k)exp(j[ψ 13(k)-ψ 31(k)])＝γ 3(k)exp(j[θ 1(k)+φ 3(k)]-[θ 3(k)+φ 1(k)])
…
Cc N(k)＝γ N(k)exp(j[ψ 1N(k)-ψ N1(k)])＝γ N(k)exp(j[θ 1(k)+φ N(k)]-[θ N(k)+φ 1(k)])
γ wherein 1(k) being that ratio from first and second amplitudes measured calculates, promptly is (γ 1i(k)/γ I1And γ (k)), 1=1.The numerical value of Matrix C (k) can be used as calibration parameter and stores, and selecting of Matrix C (k) is that all k are satisfied symmetric case (3).Phase deviation and optionally amplitude excursion can be by will be multiplied by cornerwise positional matrix C (k) at the data symbol of subcarrier k in each subcarrier in the radio transceiver path.Therefore, be not presented at especially among Fig. 5, multiplier 197 (i) comprises that the multiplier array carries out C in all subcarrier k i(k) multiplication.
Step 5: if needs are arranged, can in the multiple channel in the RF band, be responsible for phase deviation by repeating step 1 to 4, can not influence any result of numerical computations by the phase deviation of antenna and/or coupling cable to slow variation.
Sum up and opinion, to including numerical value C i(k) each subcarrier is to calculate diagonal excursion matrix, wherein c i(k)=γ i(k) exp (j[ψ 1i(k)-ψ I1(k)]), and i=2 is to N, and wherein N is antenna amount and ψ wherein 1i(k) be in subcarrier k, to be associated with the reflector input of first antenna and to be associated with phase difference (being also referred to as first phase difference) between the receiver output of antenna i, and ψ I1(k) be in subcarrier k, to be associated with the reflector input of antenna i and to be associated with phase difference (being also referred to as second phase difference) between the receiver output of first antenna, γ i(k)=(γ 1i(k)/γ I1And γ (k)), 1=1.When handling baseband signal, modulator-demodulator 140 comes each subcarrier k is handled many base band transmit and/or many baseband receiving signals by the phase deviation corrected value, is to equal a matrix diagonal angle [c so can reach the biased shift correction of a net phase 1(k), c 2(k) ..., c N(k), c wherein i(k)=γ i(k) exp (j[ψ 1i(k)-ψ I1(k)] ψ), and wherein 1i(k) be first phase difference and ψ I1(k) be second phase difference, and i=2 is to N, and c wherein 1(k)=1.
In some cases, for example under the situation of the following stated, the frequency that may not need to produce multicarrier system is selected or the subordinate correction matrix.A single frequency non-selective (frequency is independent) correction matrix has ability and proofreaies and correct the base band phase shift.For these cases, be need on each subcarrier k, not calculate a phase shift offset correction numerical value at each antenna-path, the single offset correction numerical value of each antenna-path be via calculate by with a plurality of subcarrier k connected a plurality of point { (subcarrier k, ψ 1i(k)-ψ I1The y-intercept of straight line (k)) }, wherein ψ 1i(k) be first measured on the subcarrier phase difference, ψ Ii(k) be second measured on the frequency subcarrier phase difference, and be to be 0 wherein with the phase deviation of the connected antenna-path of first antenna.Similarly, when calculating an amplitude excursion, be wirelessly to calculate a single amplitude excursion in average from striding across one between first and second amplitude of a plurality of subcarrier k for each antenna for amplitude excursion rather than at each antenna and at each subcarrier k.These phase differences are measured and need do not carried out at each subcarrier, but need certain quantity so that aforesaid linear analysis (y-intercept).This program then is very close with the described process of Fig. 4.
The advantage of the described collimation technique of the application is to be that it does not need extra equipment.It can be by the logic flush mounting is implemented so that make this device carry out self-calibrating.
On the other hand, if desired, the described technology of the application in the laboratory or when test, be can and the RF testing equipment use in the lump and measure phase place and amplitude excursion between the antenna loop return path, rather than use in the lump with the DSP logic.When use test equipment, reference signal (CW or OFDM) is to be introduced into wireless receiver; Described signal is to return so that the phase difference of use test device measuring RF in loop, base band place.
See also Fig. 6, offset correction numerical value is in transmission path, RX path or two paths that can be applicable to modulator-demodulator.For instance, as skew c 1To c NCan be when calculating with reference to figure 4 and Fig. 5 and aforementioned content, but correction is a mat multiplier 191 (i) and carrying out in receiver path, c wherein i' be c iInverse, and if correction of amplitude is not carried out, c then i' be c iConjugate number.In addition, correction be can transmission path and receiver path two on carry out the therefore accumulation in antenna-path or clean the correction is to equal the correspondence skew c that calculates at this antenna-path iSimilarly, emission all-pass filter 181 (i) (for example: sampler) again is to can be used to replace receive all-pass filter, wherein numerical value δ τ iBe to calculate by the content of reference earlier figures 4, and δ τ i' be δ τ iInverse (postpone to replace development, or development replace postpone).Alternatively, all-pass filter can be used for RX path and transmission path, and therefore accumulation in antenna-path or clean correction are that the corresponding group delay that equals to calculate at this antenna-path is offset δ τ iThe multiplier in reception of being drawn among Fig. 6 and the transmitting baseband path and the order of all-pass filter be not be defined but changeable.
In all sources that group delay in the MIMO transceiver mismatches, the group delay difference between base band component bothers most, because they can cause big with the phase difference of frequency-independent, its in the base band of signal to be transmitted for changeable.It is a kind of that to remove method that this class base band postpones to hold difference be to share identical low pass filter (LPF) between the reflector of each antenna-path and receiver.This will have remarkable other benefit that can save silicon area.
See also Fig. 2, be by reflector 1 to the group delay in the path of receiver i:
τ BBTX(1)+τ RFTX(1)+τ ANT(i)+τ RFRX(i)+τ BBRX(i)
And to the group delay in the path of reflector 1 be by receiver i:
τ BBTX(i)+τ RFTX(i)+τ ANT(i)+τ RFRX(1)+τ BBRx(1)
If same filter is all shared by emission and reception in each path, so τ BBTX(1)=τ BBRX(1), τ BBTX(i)=τ BBRX(i), and the difference between two paths be τ RFTX(1)+τ RFRX(i)-(τ RFTX(i)+τ RFRX(1), it only depends on the RF assembly.Because symmetrical situation only depends on the phase deviation between this phase path, aforesaid analysis meeting presents when using one to share LPF, and channel symmetry will be kept regardless of the group delay uncertainty of LPF.Fig. 7 has drawn a legend that filter is shared, and has wherein provided a transducer 128 (1) to 128 (N), and it is chosen at the output of the DAC in the transmission path or the output of the low-converter in RX path when inputing to the LPF of each wireless transceiver.
If these find that the expression wireless transceiver designs launching and receiving shared LPF in the operation, does not mismatch just do not need to compensate the base band group delay so.In this case, for an OFDM scheme, only need a frequency non-selective (frequency is independent) transmitter, phase operation matrix, and for an OFDM or a single carrier schemes, need not the computing of all-pass group delay.
Another discovery then is relevant with the delay contribution of ADC and DAC, and wherein, the pile line operation tachnical delay may cause the big group delay between emission and RX path.Because each emission-to receiving loop-return path always to deposit that group postpones be the summation of DAC and ADC group delay, the summation of these delays will be identical with the delay of all loop-return paths combination, so symmetric case will be ignored the difference between the group delay between these assemblies (most typical case is that all DACs of hypothesis have identical group delay with ADCs) and is maintained.
Carry out emulation with decision phase place and amplitude excursion (when timing not also) on the wireless operation method of a MIMO influence, wherein said operation method is to depend on channel symmetry.200 accidental channels between 2 antennas of four antennas of a device and another device have been used in described emulation.
Mismatch matrix A at random at each channel H generation 1, B 1, A 2, B 2And the loss of calculating the binding limit.It is to be applied to emission matrix A that amplitude and phase place mismatch 1With A 2In.Because for for the radio transmit-receive structure of kenel, probably not fixing, only have random phase to mismatch and be applied to receiving matrix B in the amplitude mistake in the receiver 1With B 2B 1, A 2It is that mat uses and has standard deviation and be σ that amplitude mismatches 20log (α) αThe normal distribution of dB and producing.Phase place mismatches θ, and φ is evenly distributed in-U θ/ 2 and U θBetween/2 rank.At σ αNumerical value be 1,2,3, one among the 6}dB and U θNumerical value is that { 10,20,45,90, its of 180} rank produces one and mismatch matrix group for the moment.For each random antenna is to have produced four of 20 tools altogether to mismatch matrix group at random.
Fig. 8 has presented the data block of the first-class power CBF operation method that uses between two devices, also presented in other object, constant power CBF is to be lower than non-constant power CBF significantly for the susceptibility of the imbalance of phase place and amplitude, and it is not necessary having presented the amplitude excursion correction in addition yet.
Summation and discussing, the present invention has proposed a kind of wireless device, it comprises a plurality of reflectors, a plurality of receiver and a processor, the pairing base band transmit in a plurality of base band transmit that described reflector has been a up-conversion in case via more pairing antennas in a plurality of antennas synchronized transmissions; Described a plurality of receiver is down-conversion detected wireless signal of more pairing antennas in a plurality of antennas, advances to produce the baseband receiving signals of a plurality of correspondences; Described processor is to handle described a plurality of base band transmit and/or a plurality of baseband receiving signals with the correction numerical value of correspondence, and wherein said correction numerical value is the difference of having proofreaied and correct the phase response between described a plurality of reflectors and described a plurality of recipient.
In addition, the application also provides a kind of method of calibrating wireless device, and described wireless device comprises the receiver of a plurality of antennas, a plurality of correspondences and the reflector of a plurality of correspondences; Described method comprises the step of the phase response of measuring described a plurality of reflectors and described a plurality of recipients, and calculates a plurality of in order to the step of correction at the correction numerical value of the difference of the phase response of described a plurality of reflectors and described a plurality of recipients.
In addition, the application has also proposed a kind of method of wireless communication of carrying out between first wireless device and second wireless device, and described first wireless device comprises the receiver of a plurality of antennas, a plurality of correspondences and the reflector of a plurality of correspondences; The step of described method on described first wireless device is to comprise with the correction numerical value of correspondence to handle armed a plurality of base band transmit and/or baseband receiving signals, and wherein said correction numerical value is the difference in order to the phase response of a plurality of reflectors of proofreading and correct described first wireless device and described a plurality of recipients.
Moreover, the application has provided a kind of method of measuring the characteristic of wireless device, described wireless device has the reflector of a plurality of antennas, a plurality of correspondences and the receiver of a plurality of correspondences, and wherein said method comprises and a signal is coupled to one first reflector so that the step of launching by first antenna of a correspondence and to come received signal with the connected receiver of one second antenna.
Aforementioned content only is to be used for being used as being the application's example but not being the enforcement of thinking to limit in any form the application.

Claims (70)

1. wireless device, described wireless device comprises:
A. many reflectors, described reflector carries out up-conversion with base band transmit corresponding in a plurality of base band transmit, in order to launch simultaneously via antenna corresponding in a plurality of antennas;
B. many receivers, described receiver carries out down-conversion with a plurality of wireless signals that antenna detected corresponding in a plurality of antennas, to produce corresponding a plurality of baseband receiving signals; And
C. a processor, described processor is and described a plurality of reflectors and the coupling of a plurality of receiver, wherein said processor is handled described a plurality of base band transmit and/or described a plurality of baseband receiving signals with the corrected value of correspondence, and described corrected value is to proofread and correct the difference in the phase response between described a plurality of reflectors and a plurality of receiver.
2. device according to claim 1, it is characterized in that, described processor is handled described a plurality of base band transmit and/or described a plurality of baseband receiving signals with the corrected value of correspondence, make that when transmitting by a plurality of reflectors and/or coming received signal phase response and (2) difference between the phase response of the output of the corresponding receiver of the described antenna of being input to of that antenna of being input to the output of reflector institute respective antenna in (1) from one of a reflector all are identical these a plurality of antennas respectively by a plurality of receivers.
3. device according to claim 1 is characterized in that, the difference in the described phase response of described processor measurement between described a plurality of reflectors and a plurality of receiver, and calculating is from the corrected value of the difference of described phase response.
4. device according to claim 3, it is characterized in that, described processor is handled described a plurality of base band transmit and/or described a plurality of baseband receiving signals with the corrected value of correspondence, and described corrected value is that skew is proofreaied and correct at the baseband phase between described a plurality of reflectors and described a plurality of receiver.
5. device according to claim 4, it is characterized in that, one first phase difference between one output of one input of the reflector that described processor measurement is relevant with one first antenna and the receiver of being correlated with an antenna i, and one second phase difference between an output of an input of the reflector that measurement is relevant with antenna i and the receiver relevant with described first antenna, i=2 is to N, and wherein N is the number of antenna.
6. device according to claim 5, it is characterized in that, when being applied in the input of the described first antenna associated transmitter and via one, a signal links or cable when connecting the reception that is coupled to the receiver relevant and importing with described antenna i by air, described processor is measured described first phase difference, and be applied in the input of the reflector relevant with described antenna i and link or cable is when connecting the input that is coupled to the described first antenna correlation receiver by air via one when a signal, described processor is measured described second phase difference.
7. device according to claim 6 is characterized in that, described processor produces signal and represents in frequency f as one kThe continuous wave digital signal of transferring, and wherein said processor is at a plurality of continuous wave frequency rate f of the bandwidth of passing a baseband signal kDescribed first phase difference of last measurement and described second phase difference.
8. device according to claim 7, it is characterized in that, described processor is measured first phase difference between the digital signal in digital signal in the input of a digital analog converter and the output at an analog-digital converter, described digital analog converter is the described Emitter-coupling relevant with described first antenna, and described analog-digital converter is the described receiver output coupling relevant with antenna i, and described processor is measured second phase difference between the digital signal in digital signal in the input of a digital analog converter and the output at an analog-digital converter, described digital analog converter is the described Emitter-coupling relevant with antenna i, and described analog-digital converter is the described receiver output coupling relevant with described first antenna.
9. device according to claim 7 is characterized in that, described processor is from meeting and described frequency f kRelevant point { (f k, ψ 1i(k)-ψ I1The y-intercept of straight line (k)) } is calculated the broadband phase deviation to the antenna-path of N corresponding to antenna i=1, wherein ψ 1i(k) be in frequency f kMeasured described first phase difference, ψ I1(k) then be in frequency f kMeasured described second phase difference, and the broadband phase deviation of wherein relevant with described first antenna described antenna-path is 0.
10. device according to claim 9, it is characterized in that, described processor is handled described a plurality of base band transmit and/or described a plurality of baseband receiving signals with the broadband phase deviation corrected value of correspondence, to reach a biased shift correction of net phase that equals the broadband phase deviation of described correspondence.
11. device according to claim 10, it is characterized in that, described processor is further handled described a plurality of base band transmit and/or described a plurality of baseband receiving signals with the amplitude excursion corrected value of correspondence, and the amplitude excursion corrected value of wherein said correspondence is the amplitude excursion of proofreading and correct between described a plurality of reflectors and described receiver.
12. device according to claim 11, it is characterized in that, when described continuous wave being called when the described reflector relevant with described first antenna imported, described processor is measured first amplitude at a signal of described receiver output place relevant with antenna i, and when with described continuous wave call in antenna i, i=2 is to N, and when relevant described reflector was imported, described processor was measured second amplitude of a signal of described receiver output place relevant with described first antenna.
13. device according to claim 12 is characterized in that, described processor from frequency f kBetween relevant described first amplitude and described second amplitude ratio on average calculate described respective antenna, i=1 is to N, a plurality of amplitude excursions of described antenna-path, and the amplitude excursion of wherein relevant with described first antenna described antenna-path is 1.
14. device according to claim 13, it is characterized in that, described processor is further handled described a plurality of base band transmit and/or described a plurality of baseband receiving signals with the amplitude correction values of correspondence, to reach a net amplitude offset correction that equals corresponding amplitude excursion.
15. device according to claim 3, it is characterized in that, when described a plurality of reflectors and described a plurality of receiver being modulated to a plurality of frequency letters arrive in the radio band operation each frequency letter then, described processor is measured the difference in phase response.
16. device according to claim 5, it is characterized in that, described processor is more handled a plurality of baseband receiving signals and described a plurality of base band transmit with the group delay corrected value of correspondence, and the group delay corrected value of described correspondence is used for proofreading and correct between described a plurality of reflectors and a plurality of receiver the group delay skew in a baseband signal bandwidth.
17. device according to claim 16 is characterized in that, described processor is in frequency f k, from a plurality of group delays skews of the described antenna-path of described first phase difference and the described second phase difference calculating respective antenna i=1 to N, and wherein relevant described antenna-path group delay with described first antenna to be offset be 0.
18. device according to claim 17 is characterized in that, described processor calculates described group delay skew and equals-(1/2 π) *With described a plurality of frequency f kCorrelative symbol chalaza { (f k, ψ 1i(k)-ψ I1(k)) line slope }, wherein ψ 1i(k) be in frequency f kMeasured described first phase difference, and ψ I1(k) be in frequency f kMeasured described second phase difference, i=2 to N.
19. device according to claim 18, it is characterized in that, described processor is handled described a plurality of base band transmit and a plurality of baseband receiving signals with corresponding group delay corrected value, advances a clean group delay offset correction that equals described corresponding group delay deviation to reach.
20. device according to claim 19 is characterized in that, described processor uses the all-pass filter processing and carries out described group delay corrected value.
21. device according to claim 4, it is characterized in that, use a multi-carrier modulation program and modulate described a plurality of base band transmit and described a plurality of baseband receiving signals, and wherein said processor calculates phase deviation at a plurality of subcarrier k relevant with described multi-carrier modulation program.
22. device according to claim 21, it is characterized in that, when the multicarrier baseband signal is used for the input of a described reflector relevant with described first antenna, and become when the reception of the described receiver relevant with antenna i is imported when linking by aerial binding or cable be coupled, described processor is measured one first phase difference at each subcarrier k, and be used for one during when multi-carrier signal to relevant with described antenna i described reflector input, and become when the reception of the described receiver relevant with first antenna is imported when linking by aerial binding or cable be coupled, measure one second phase difference at each subcarrier k, i=2 to N wherein, N is a number of antennas.
23. device according to claim 22 is characterized in that, described processor is handled described a plurality of base band transmit and described a plurality of baseband receiving signals with the phase deviation corrected value of each subcarrier k, reaches to equal a matrix diag[c 1(k), c 2(k) ..., c N(k)] the biased shift correction value of net phase, wherein c i(k)=exp (j[ψ 1i(k)-ψ I1(k)] ψ), and wherein 1i(k) be described first phase difference and ψ I1(k) be described second phase difference, i=2 to N and c 1(k)=1.
24. device according to claim 22, it is characterized in that, when the multicarrier baseband signal is used for one during to the input of the described reflector relevant with described first antenna, and become when the reception of the described receiver relevant with antenna i is imported when linking by aerial binding or cable be coupled, described processor is measured one first phase difference at a plurality of subcarrier k, and be used for one during when multi-carrier signal to the input of the described reflector relevant with described antenna i, and become when the reception of the described receiver relevant with first antenna is imported when linking by aerial binding or cable be coupled, measure one second phase difference, wherein i=2 to N at a plurality of subcarrier k.
25. device according to claim 24 is characterized in that, described processor is from meeting point { (fk, the ψ relevant with described a plurality of subcarrier k 1i(k)-ψ I1(k)) } the y intercept of line, the phase deviation of calculating respective antenna i=1 to N antenna-path, wherein ψ 1i(k) be at measured described first phase difference of subcarrier k, and ψ I1(k) be at measured described second phase difference of frequency subcarrier k, and wherein relevant with described first antenna described antenna-path phase deviation is 0.
26. device according to claim 25, it is characterized in that, described processor is handled described a plurality of base band transmit and a plurality of baseband receiving signals with the corresponding phase offset correction values, and then reaches the biased shift correction of a net phase and equal the skew of described corresponding phase.
27. device according to claim 26, it is characterized in that, described processor is more handled described a plurality of base band transmit and described a plurality of baseband receiving signals with corresponding amplitude excursion corrected value, and wherein said corresponding amplitude excursion corrected value is the amplitude excursion of proofreading and correct between described a plurality of reflectors and described a plurality of receiver.
28. device according to claim 26, it is characterized in that, when multi-carrier signal is used for the described input of the described reflector relevant with described first antenna, in the described receiver output relevant with described a plurality of subcarrier k antenna i, described processor is first amplitude of measuring a signal, and when described multi-carrier signal is used for relevant with antenna i described reflector input, in the described receiver output relevant with described a plurality of subcarrier k first antennas, described processor is second amplitude of measuring a signal, i=2 to N.
29. device according to claim 28, it is characterized in that, described processor is the amplitude excursion of the average computation of ratio between described first amplitude by described a plurality of subcarrier k and described second amplitude corresponding to antenna i=1 to N antenna-path, and it is characterized in that the described amplitude excursion of the antenna-path relevant with described first antenna is 1.
30. device according to claim 29, it is characterized in that, described processor is further handled described a plurality of base band transmit and described a plurality of baseband receiving signals with corresponding amplitude correction values, and then makes a net amplitude offset correction equal corresponding amplitude excursion.
31. device according to claim 23, it is characterized in that, described processor is more handled described a plurality of base band transmit and described a plurality of baseband receiving signals with corresponding amplitude excursion corrected value, and described corresponding amplitude excursion corrected value is proofreaied and correct the amplitude excursion between described a plurality of reflector and described a plurality of receiver.
32. device according to claim 31, it is characterized in that, when multi-carrier signal is used for the described input of the described reflector relevant with described first antenna, in the described receiver output relevant with described antenna i, described processor is first amplitude of measuring each subcarrier of signal k, and when described multi-carrier signal is used for relevant with antenna i described reflector input, in the described receiver output relevant with described first antenna, described processor is second amplitude of measuring each subcarrier of signal k, i=2 to N.
33. device according to claim 32, it is characterized in that, described processor is described first amplitude and the amplitude excursion of the calculation of the proportional meter between described second amplitude corresponding to each subcarrier k of antenna i=1 to N antenna-path of comfortable each frequency subcarrier k, and it is characterized in that the described amplitude excursion of each subcarrier of the antenna-path relevant with described first antenna is 1.
34. device according to claim 33, it is characterized in that described processor further handling described a plurality of base band transmit and described a plurality of baseband receiving signals, and then reach a net amplitude offset correction and equal corresponding amplitude excursion at the corresponding amplitude excursion corrected value of each subcarrier k.
35. device according to claim 1 is characterized in that, described processor comprises a baseband signal processor, and it carries out baseband modulation to produce the baseband modulation of described a plurality of base band transmit and described a plurality of baseband receiving signals.
36. device according to claim 35 is characterized in that, described baseband signal processor is to implement by the Digital Logic grid.
37. device according to claim 1 is characterized in that, implements described a plurality of reflectors and a plurality of receiver on single semiconductor integrated circuit.
38. device according to claim 1, it more comprises a low pass filter, and it is shared by the described reflector and the receiver that are connected to a corresponding antenna.
39. device according to claim 1, it is characterized in that in a self-calibrating (self-calibration) mode process, skew measured by described processor and calculated correction value is offset to proofread and correct, and in a duration of runs pattern, described processor is with described corrected value, and handles described a plurality of base band transmit and a plurality of baseband receiving signals.
40., it is characterized in that described processor is periodically carried out described self-calibrating pattern according to the described device of claim 39 when the device energising.
41. device according to claim 1 more comprises an internal memory, its store information is to modulate corrected value according to the gain setting of described a plurality of reflectors and the gain setting of described a plurality of receivers.
42. according to the described device of claim 41, it is characterized in that, skew in the described processor Measurement Phase response and the corrected value that calculates and gain and have nothing to do, and wherein said processor is the described corrected value that has nothing to do with gain of described gain setting modulation of the information described in the described internal memory that is stored in according to use.
43. one kind in order to calibrate the method for a wireless device, described wireless device comprises a plurality of antennas, corresponding a plurality of reflectors and corresponding a plurality of receiver, and described method comprises the following steps:
A. measure the phase response of described a plurality of reflector and described a plurality of receivers; And
B. calculate a plurality of corrected values to proofread and correct the difference in the described phase response of described a plurality of reflectors and described a plurality of receivers.
44. according to the described method of claim 43, it is characterized in that, described calculation procedure comprises calculates the corrected value that is used in the described a plurality of base band transmit of processing and/or described a plurality of baseband receiving signals, make that when transmitting by a plurality of reflectors and/or coming received signal the phase response and (2) that are input to the output of reflector institute respective antenna in (1) from one of a reflector all are identical from the difference between the phase response of the output of the corresponding receiver of the described antenna of being input to of that antenna at these a plurality of antennas respectively by a plurality of receivers.
45., it is characterized in that described calculation procedure comprises the broadband phase deviation of calculating between described a plurality of reflectors and described receiver according to the described method of claim 43.
46. according to the described method of claim 45, it is characterized in that, described measuring process comprises one first phase difference of one of input of measuring the reflector relevant with one first antenna and the receiver of being correlated with an antenna i between exporting, and an input of the measurement reflector relevant and one second phase difference between one output of relevant receiver with described first antenna with antenna i, i=2 is to N, and wherein N is the number of antenna.
47. according to the described method of claim 46, it is characterized in that, described measuring process comprises when a signal is applied in the input of the described first antenna associated transmitter and via one and linking or a cable is connected by air, and couple reception when input of the receiver relevant with antenna i, measure described first phase difference, and be applied in the input of the emission gas relevant with antenna i and link or cable is when connecting the reception input that is coupled to the described first antenna correlation receiver by air via one when a signal, measure described second phase difference.
48., it is characterized in that the step of described first phase difference of described measurement and described second phase difference can be at a plurality of frequency f that are applied to the bandwidth of passing a baseband signal according to the described method of claim 47 kOn continuous wave transfer and repeat.
49. according to the described method of claim 48, it is characterized in that, described measuring process comprises first phase difference of measurement between the digital signal in digital signal in the input of a digital analog converter and the output at an analog-digital converter, described digital analog converter is the described Emitter-coupling relevant with described first antenna, and described analog-digital converter is the described receiver output coupling relevant with antenna i, and measure second phase difference between the digital signal in digital signal in the input of a digital analog converter and the output at an analog-digital converter, described digital analog converter is the described Emitter-coupling relevant with antenna i, and described analog-digital converter is the described receiver output coupling relevant with described first antenna.
50., it is characterized in that described calculation procedure comprises from meeting and described frequency f according to the described method of claim 49 kRelevant point { (f k, ψ 1i(k)-ψ I1(k)) } straight y-intercept calculate the broadband phase deviation corrected value to the antenna-path of N, wherein ψ corresponding to antenna i=2 1i(k) be in frequency f kMeasured described first phase difference, ψ I1(k) then be in frequency f kMeasured described second phase difference, and the broadband phase deviation corrected value of wherein relevant with described first antenna described antenna-path is 0.
51., it is characterized in that described measuring process comprises the amplitude excursion of measurement between described a plurality of reflectors and described a plurality of receiver according to the described method of claim 48.
52. according to the described method of claim 51, it is characterized in that, described measuring process comprises when described continuous wave being called when the described reflector relevant with described first antenna imported, measurement is at first amplitude of a signal of described receiver output place relevant with antenna i, and when with described continuous wave call in antenna i, i=2 is to N, and when relevant described reflector was imported, described processor was measured second amplitude of a signal of described receiver output place relevant with described first antenna.
53. according to the described method of claim 52, it is characterized in that, described calculation procedure comprise from frequency f kRatio on average calculates corresponding to antenna between relevant described first amplitude and described second amplitude, i=1 is to N, the amplitude excursion corrected value of antenna-path, and the described amplitude excursion corrected value of wherein relevant with described first antenna described antenna-path is 1.
54. according to the described method of claim 43, it is characterized in that, described calculation procedure comprises, when described a plurality of reflectors and described a plurality of receiver being modulated to a plurality of frequency letters arrive in the radio band operation each frequency letter then, measure at described first phase difference and described second phase difference.
55., it is characterized in that described measuring process comprises the group delay difference of measurement between described a plurality of reflectors and described a plurality of receiver according to the described method of claim 48.
56. according to the described method of claim 52, it is characterized in that, described measuring process further comprises from described first phase difference and described second phase difference and calculates a plurality of group delay offset correction values corresponding to the antenna-path of antenna i=1 to N, and the group delay offset correction values of wherein relevant with described first antenna described antenna-path is 0.
57. according to the described device of claim 56, wherein from according with and described a plurality of frequency f kRelevant point { (f k, ψ 1i(k)-ψ I1The slope of a straight line (k)) }-(1/2 π) *Calculate a plurality of group delay offset correction values, wherein ψ corresponding to the described antenna-path of antenna i=2 to N 1i(k) be in frequency f kMeasured described first phase difference, and ψ I1(k) be in frequency f kMeasured described second phase difference.
58. according to the described method of claim 46, it is characterized in that described measuring process comprises, when the multicarrier baseband signal being used for the input of a described reflector relevant with described first antenna, and become when the reception of the described receiver relevant with antenna i is imported when linking by aerial binding or cable be coupled, measurement is at one first phase difference at the subcarrier k place relevant with a multicarrier baseband modulation program, and when multi-carrier signal being used for the input of a described reflector relevant with described antenna i, and become when the reception of the described receiver relevant with described first antenna is imported when linking by aerial binding or cable be coupled, measurement is at second phase difference of each subcarrier k.
59., it is characterized in that described calculation procedure comprises a diagonal correction matrix diag[c who calculates each subcarrier k according to the described method of claim 58 1(k), c 2(k) ..., c N(k)], it is characterized in that c i(k)=exp (j[ψ 1i(k)-ψ I1(k)]), i=2 to N, wherein N is a number of antennas, and ψ wherein 1i(k) be one first phase difference between an input of the output of the receiver i of subcarrier k place and one first reflector, and ψ I1(k) be one second phase difference between an input of output of one first receiver at subcarrier k place and reflector
60., it is characterized in that described calculation procedure comprises from according with the point { (f relevant with a plurality of subcarriers according to the described method of claim 58 k, ψ 1i(k)-ψ I1The y-intercept of straight line (k)) } is calculated the broadband phase deviation to the antenna-path of N corresponding to antenna i=2, wherein ψ 1i(k) be at measured described first phase difference of subcarrier, ψ I1(k) then be at measured described second phase difference of subcarrier, and the broadband phase deviation of the described antenna-path relevant with described first antenna is 0.
61. according to the described method of claim 58, it is characterized in that, described measuring process further comprises, when multi-carrier signal being used for the input of the described reflector relevant with described first antenna, measure one first amplitude on the subcarrier k of signal of described receiver output place relevant with antenna i, and when multi-carrier signal being used for the input of the described reflector relevant, measure one second amplitude on the subcarrier k of signal of described receiver output place relevant with described first antenna with antenna i.
62. according to the described method of claim 61, it is characterized in that, described calculation procedure comprises from described first amplitude of each subcarrier k and the proportional meter between described second amplitude calculates amplitude excursion corrected value corresponding to the antenna-path of antenna i=1 to N, and the described amplitude excursion corrected value of wherein relevant with described first antenna antenna-path is 1.
63. according to the described method of claim 61, it is characterized in that, described calculation procedure comprises average computation by ratio between described first amplitude of a plurality of subcarrier k and described second amplitude corresponding to the amplitude excursion corrected value of the antenna-path of antenna i=1 to N, and the described amplitude excursion of wherein relevant with described first antenna antenna-path is 1.
64. one kind is carried out method of wireless communication between a first wireless device and a second wireless device, described first wireless device comprises a plurality of antennas, corresponding a plurality of reflectors and corresponding a plurality of receiver, comprise a plurality of base band transmit and/or the baseband receiving signals that will be launched, the difference in a plurality of reflectors in the described first wireless device of described corrected value recoverable and the phase response of described a plurality of receivers at communication means described in the described first wireless device with corresponding corrected value processing.
65. according to the described method of claim 64, it is characterized in that, the treating step comprises the step of handling described a plurality of base band transmit and/or described a plurality of baseband receiving signals with the corrected value of correspondence, make that when transmitting by a plurality of reflectors and/or coming received signal the phase response and (2) that are input to the output of reflector institute respective antenna in (1) from one of a reflector all are identical from the difference between the phase response of the output of the corresponding receiver of the described antenna of being input to of that antenna at these a plurality of antennas respectively by a plurality of receivers.
66. according to the described method of claim 64, further be included in a plurality of base band transmit of being launched by the respective antenna in a plurality of antennas with the corrected value processing of correspondence in the described second wireless device, and/or handle the step of a plurality of baseband receiving signals of deriving, the difference in a plurality of reflectors of the described second wireless device of wherein said corrected value recoverable and the phase response of described a plurality of receivers by antenna received signal corresponding in a plurality of antennas.
67. according to the described method of claim 64, it further comprises the following steps:
A. measure the phase response of described a plurality of reflector and described a plurality of receivers; And
B. calculate described corrected value to proofread and correct the difference in the described phase response of described a plurality of reflectors and described a plurality of receivers.
68. one kind in order to measure the method for a wireless device characteristic, described wireless device comprises a plurality of antennas, corresponding a plurality of reflectors and corresponding a plurality of receiver, and described method comprises the following steps:
A. a signal is coupled to one first reflector, to launch by corresponding first antenna;
B. utilize the receiver relevant to receive described signal with one second antenna.
69., comprise that further measurement is in the step that is coupled as the phase difference between the signal that the signal that inputs to described first reflector and the described receiver relevant with described second antenna export according to the described method of claim 68.
70., it is characterized in that described receiving step further comprises, when receiving the signal of launching by described first antenna, reduces the step of an Amplifier Gain in the described receiver relevant with described second antenna according to the described method of claim 68.
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