CN1739274A - Receiving apparatus and method for digital multi-carrier transmission - Google Patents
Receiving apparatus and method for digital multi-carrier transmission Download PDFInfo
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- CN1739274A CN1739274A CN 200480002360 CN200480002360A CN1739274A CN 1739274 A CN1739274 A CN 1739274A CN 200480002360 CN200480002360 CN 200480002360 CN 200480002360 A CN200480002360 A CN 200480002360A CN 1739274 A CN1739274 A CN 1739274A
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Abstract
A receiving apparatus and method for performing carrier detection in a frequency domain for a digital wavelet multi-carrier transmission. A wavelet transform of received data is performed to output complex data and then the complex data is delayed for one sampling period. Subsequently, the delayed complex data and delayed complex data are divided. A number of the divided complex data present within each of plural quadrants on orthogonal coordinates is calculated and a maximum number of data present within one of the quadrants is selected and compared with a threshold in order to decide whether the received data is intended data.
Description
Technical field
The present invention relates to use the receiving equipment and the method (the following digital wavelet multi-carrier transmission method is called " DWMC transmission method ") of the multicarrier transmitting method that utilizes real coefficient wavelet filters group.
Background technology
This transmission method relates to digital modulation and the demodulation process of utilizing real coefficient wavelet filters group, and it is a kind of multi-carrier modulation method, wherein, synthesizes a plurality of digital modulation waves by real coefficient wavelet filters group, so that produce transmission signals.In the method, with the method for PAM (pulse amplitude modulation) as each carrier wave of modulation.
Below, with reference to Figure 23 to 26 data transmission method according to the DWMC transmission method is described.
As shown in figure 23, each subcarrier has an impulse response, transmits the impulse response of each subcarrier in a plurality of subcarriers according to overlapped relation.As shown in figure 24, constitute each transmitted symbol (symbol) by time waveform, and time waveform is the combination of the impulse response of a plurality of subcarriers.
The spectrogram of Figure 25 has illustrated an example that comes transmission frequency spectra according to the DWMC transmission method.According to the DWMC transmission method, a transmission frame (shown in Figure 26) constitutes to a hundreds of transmitted symbol by tens.This transmission frame comprises information data and lead data (preamble data), and lead data comprises the slope code element (ramp symbol) that has slope processing (ramp treatment).Handle on the slope can prevent the distortion in amplifier of information data and lead data.
In multi-carrier communication, often in same circuit, carry out carrier wave simultaneously and detect and symbol synchronization.Yet, in the DWMC transmission method that uses wavelet transform, may also set up the mode of carrying out carrier wave detection and symbol synchronization as yet.Therefore, the carrier wave detection in the improvement receiving system and/or the accuracy of symbol synchronization just may be problematic.It also may be problematic how preventing the decline of efficiency of transmission when in addition, carrying out carrier wave detection and/or symbol synchronization in receiving system.
Summary of the invention
The present invention has been proposed in view of the above-mentioned problems.The object of the present invention is to provide a kind of receiving equipment and method of reseptance, they can carry out carrier wave and detect and/or symbol synchronization in the frequency domain in the DWMC transmission method.
According to the present invention, this receiving equipment comprises: utilize wavelet transform data converting apparatus, delay element, be used to produce the right subcarrier of subcarrier to generator, be used to calculate subcarrier between the phase difference calculating device of phase difference, and identifying unit, be used for judging the data that receive according to the phase difference that calculates by the phase difference calculating device.
The invention provides a kind of receiving equipment and method, they can carry out carrier wave and detect in the frequency domain scope in the DWMC transmission method.
Description of drawings
Fig. 1 constitutes the ripple test section of a part of receiving system of the first embodiment of the present invention and the calcspar of carrier wave test section.
Fig. 2 is a curve chart, the figure shows the relation between subcarrier frequency and sine wave freuqency.
Fig. 3 is illustrated under the situation of (communication) signal that does not have expection the diagrammatic sketch of the distribution of the signal that receives on Cartesian coordinate.
Fig. 4 is illustrated under the situation of (communication) signal that has expection the diagrammatic sketch of the distribution of the signal that receives on Cartesian coordinate.
Fig. 5 is the calcspar of the phase difference distribution calculator in according to a second embodiment of the present invention the receiving system.
Fig. 6 is the diagrammatic sketch that expression is put into the distribution of the composite signal in the phase difference distribution calculator.
Fig. 7 shows the situation according to Fig. 6, is put into to have Π/distribution of composite signal in the phase difference distribution calculator of 4 phase shifts.
Fig. 8 is the calcspar of the configuration of the phase difference distribution calculator in the receiving system of a third embodiment in accordance with the invention.
Fig. 9 shows the symbol distribution of the in-phase signal of being judged by identifying unit.
Figure 10 shows the symbol distribution of the orthogonal signalling of being judged by identifying unit.
Figure 11 is the calcspar of ripple test section, carrier detector and Symbol Synchronization Circuit that constitutes the receiving equipment part of fourth embodiment of the invention.
Figure 12 is the calcspar of ripple test section, carrier detector and Symbol Synchronization Circuit that constitutes the receiving equipment part of fifth embodiment of the invention.
Figure 13 is the carrier detector and the calcspar that has the ripple test section of wavelet transform device that constitutes the receiving equipment part of sixth embodiment of the invention.
Figure 14 shows the calcspar of the prototype filter with heterogeneous configuration among Figure 13.
Figure 15 is the calcspar according to the receiving equipment of seventh embodiment of the invention.
Figure 16 is the calcspar of ripple test section, carrier wave test section and symbol synchronisation circuit of a part that constitutes the receiving system of eighth embodiment of the invention.
Figure 17 is a schematic diagram, and this illustrates an example of signal amplitude spectrum in power line communication.
Figure 18 is a schematic diagram, and this illustrates an example of the signal amplitude spectrum that is received by receiving equipment.
Figure 19 is the calcspar of ripple test section, selector, carrier detector and symbol synchronisation circuit of a part that constitutes the receiving system of ninth embodiment of the invention.
Figure 20 is the schematic diagram of expression transmission frame.
Figure 21 is the calcspar according to the receiving equipment of the use fast fourier conversion of ninth embodiment of the invention.
Figure 22 constitutes the ripple test section of a receiving equipment part of tenth embodiment of the invention and the calcspar of carrier detector.
Figure 23 is an oscillogram, the figure shows an example of wavelet waveform.
Figure 24 is an oscillogram, the figure shows the example according to a waveform of DWMC transmission method transmission.
Figure 25 is a spectrogram, the figure shows the example according to a frequency spectrum of DWMC transmission method transmission.
Figure 26 is a schematic frame figure, the figure shows the example of structure according to a frame of DWMC transmission method transmission.
Figure 27 shows the ripple test section with two sub-wave converters.
Embodiment
Below, describe the embodiment of recommendation of the present invention in detail with reference to accompanying drawing 1 to 27.
(first embodiment)
In Fig. 1, receiving equipment 1000 comprises carrier detector 15 and ripple test section 17.
Ripple test section 17 comprises: wavelet transform device 1, complex data generator 3 and parallel/serial (to call P/S in the following text) transducer 5.(at this, M is a positive integer) that wavelet transform device 1 is made up of orthogonal M real wavelet filters.Wavelet transform device 1 receives data, and the data that receive are carried out wavelet transform, exports M subcarrier (being 0 to M-1 among Fig. 1) then.Complex data generator 3 produces complex data according to the same phase constituent (I channel) of composite information and the orthogonal component (Q channel) of composite information, wherein, the I channel is (2n-1) the individual subcarrier from wavelet transform device 1, the Q channel is a 2n subcarrier from wavelet transform device 1, wherein, (1≤n≤M/2-1).Complex data is represented some compound subcarriers respectively.In addition, complex data generator 3 outputs to complex data in the P/S transducer 5.P/S transducer 5 will be converted to the serial complex data from the parallel complex data that complex data generator 3 receives.
The operation of the receiving equipment 1000 with such configuration is described now with reference to Fig. 2 and 3.Suppose that the data that send from receiving equipment 1000 outsides are known and equal " 1 ".In addition, in the present embodiment, suppose and to be input to by the composite wave that sine wave produces in the receiving equipment that wherein, this sine wave has the frequency shown in the heavy line among Fig. 2 (f1, f2 and f3), and its phase place is respectively Φ 1, Φ 2 and Φ 3.At this moment, in the scope of Π, each sine wave is all at one arbitrarily among the phase place " Φ n " (n=1,2 or 3) at-Π.
At first, in ripple test section 17, carry out wavelet transform with the data that 1 pair of wavelet transform device receives.Then, M subcarrier of wavelet transform device 1 output (being numbered 0 to M-1 of subcarrier).Then, except subcarrier # 0 and subcarrier # (M-1), all subcarriers are input in the complex data generator 3.At this moment, from (2n-1) of wavelet transform device 1 individual and 2n subcarrier (1≤n≤M/2-1) is respectively cos that Fig. 2 medium frequency is the sine wave of fn (Φ n) and sin (Φ n).Complex data generator 3 produces compound number of sub certificate, and these data comprise real part branch that is made of cos (Φ n) and the dummy data part that is made of sin (Φ n), and this compound number of sub certificate is outputed in the P/S transducer 5.Then, P/S transducer 5 receives from the subcarrier # 0 of wavelet transform device 1 and subcarrier # (M-1) and from the compound number of sub certificate of complex data generator 3 with parallel mode.Then, P/S transducer 5 is converted to serial data from the top of Fig. 1 with parallel data.Then, P/S transducer 5 from the ripple test section 17 output these serial complex datas.
As mentioned above, ripple test section 17 is converted to the serial complex data by wavelet transform device 1, complex data generator 3 and P/S transducer 5 with the data that receive, and then, ripple test section 17 outputs to the serial complex data in the carrier detector 15.
Then, will be input to from the serial complex data of ripple test section 17 in the delay element 7 and complex divider 9 in the carrier detector 15.Delay element 7 makes the serial complex data postpone a sampling period, and the complex data that will postpone outputs in the complex divider 9.Complex divider 9 receives the serial complex data and postpones complex data.Then, complex divider 9 is divided by serial complex data and the complex data that postponed, and the complex data that output was divided by in the phase difference distribution calculator 11.The complex data of being divided by in the present embodiment, has been represented the phase difference between compound subcarrier continuously.Phase difference distribution calculator 11 calculates phase difference and the complex data that each was divided by is formulated in four quadrants of Cartesian coordinate, and calculates the quantity of the data in each quadrant on the Cartesian coordinate.Fig. 3 shows under the situation of (communication) signal that does not have expection, the distribution of the signal that receives on the Cartesian coordinate.。Fig. 4 shows under the situation of (communication) signal that has expection, the distribution of the signal that receives on the Cartesian coordinate.If have additive white Gaussian noise (below be called AWGN), so, in the data that receive by receiving equipment 1000, do not exist under the data conditions of expection, just have only background noise.As a result, as shown in Figure 3, the phase difference between subcarrier then is distributed on the Cartesian coordinate disorderly.In contrast, exist under the data conditions of expection in the data that received by receiving equipment 1000, the phase difference between subcarrier then is distributed in the specific zone, for example, as shown in Figure 4, be distributed in (it is under low noise situation for a dragon) in the quadrant on the Cartesian coordinate.Subsequently, phase difference distribution calculator 11 is just selected the maximum number of data in one of four quadrants, and the maximum number of these data is outputed in the identifying unit 13.Maximum number that identifying unit 13 relatively receives from phase difference distribution calculator 11 and the threshold value that is retained in the identifying unit.If this maximum number is greater than threshold value, identifying unit 13 comprises the data of expection with regard to the data of determining to receive.On the contrary, if this maximum number less than threshold value, identifying unit 13 just determines that the data that receive do not comprise the data of expection.The result that identifying unit 13 will be judged exports to the controller (not shown) of receiving equipment 1000.Controller sends to modulator and/or demodulator (the two is all not shown) according to the result who judges with the data that receive.
Above-mentioned configuration makes may obtain composite information (complex data) by more a spot of calculating.In addition, may carry out carrier wave and detect in frequency domain, this carrier wave detection utilizes the phase difference of intercarrier to distribute and determines whether to exist the data of expection.
Although used (M/2-1) individual complex data generator 3 in the present embodiment, but, use single complex data generator, and, also can serial data (2n-1) is individual and 2n be input in the complex data generator 3 by the output from wavelet transform device 1 being walked abreast/serial conversion and timing control.In addition, carrier detector in the present embodiment also can be used to have the multi-carrier receiver apparatus of the fast fourier conversion that can handle complex data.
Although present embodiment has only been used a sub-wave converter 1, what go out as shown is such, and also available a plurality of wavelet transform devices are carried out present embodiment.As shown in figure 27, ripple test section 17 has two sub-wave converter 1-1 and 1-2.Wavelet transform device 1-1 and 1-2 have the configuration identical with the wavelet transform device 1 described in first embodiment.Wavelet transform device 1-1 and 1-2 receive data and export M subcarrier (0 among Figure 27 is to M-1) respectively.Complex data generator 3 receives subcarrier from wavelet transform device 1-1 and 12, and produces complex data.M complex data generator receives M subcarrier from wavelet transform device 1-1 and 1-2.Along with detecting and/or the number of the serial complex data of the population parameter of symbol synchronization doubles as carrier wave in this configuration, above-mentioned configuration makes and may improve that carrier wave detects and/or the accuracy of symbol synchronization.
(second embodiment)
Except phase difference distribution calculator and, the receiving equipment of present embodiment has the configuration identical with the receiving equipment of first embodiment.Therefore, will describe phase difference distribution calculator in the present embodiment in detail.
As shown in Figure 5, phase difference distribution calculator 39 (coming it is illustrated as the phase difference distribution calculator 11 among Fig. 1) comprises phase shifter 31, sign determination unit 33, counter 35 and maximum value detector 37.
The operation of the phase difference distribution calculator 39 with such configuration is described with reference to Fig. 6 and 7 below.Supposing to be known and to have identical information from the receiving equipment 1000 outside data that send, for example, all is " 1 ".Fig. 6 shows the distribution that is put into the complex data in the phase difference distribution calculator.Fig. 7 also shows the distribution that is put into the complex data in the phase difference distribution calculator, still, compares with the situation among Fig. 6, and Π/4 phase shifts are arranged.
In Fig. 9 and embodiment shown in Figure 10, three complex datas that phase difference distribution calculator 53 receives from complex divider 9.Sign determination unit 330 directly receives each complex data from complex divider 9.
Three complex datas that sign determination unit 330 receives from complex divider 9, and the symbol of " A " and " B " of judgement complex data (A+Bi).If A and B are positive, sign determination unit 330 just judges that the complex data point is in first quartile and to counter 350 output symbol data.If A be bear and B is positive, sign determination unit 330 just judges that complex data is o'clock in second quadrant and to counter 351 output symbol data.If A and B bear, sign determination unit 330 just judges that the complex data point is in third quadrant and to counter 352 output symbol data.If A is positive and B bears, sign determination unit 330 just judges that complex data is o'clock in four-quadrant and to counter 353 output symbol data.Counter 350 to 353 calculates each number of the symbol data that is sent by sign determination unit 330.In other words, counter 350 to 353 calculates the number of the complex data point in each quadrant and the result is outputed in the maximum value detector 37.In the embodiment shown in fig. 6, a complex data point is arranged in first quartile, two complex data points are arranged in four-quadrant, therefore, sign determination unit 330 is to counter symbol data of 350 outputs and to two symbol datas of counter 353 outputs.Then, counter 350 to 353 calculates each number of the symbol data that is sent by sign determination unit 330, and respectively to maximum value detector 37 dateouts " 1 ", " 0 ", " 0 " and " 2 ".
Then, maximum value detector 37 detects the maximum number from the number of each complex data point that is sent by counter 350 to 357, and to identifying unit 13 these maximums of output.
Like this, under near the situation the complex data point concentrates on I axle and/or Q axle, phase difference distribution calculator 39 just can detect maximum exactly.In addition, as shown in Figure 5, though corresponding to each sign determination unit 33 4 counters 35 are arranged,, it also is possible using the configuration of 3 counters 35 corresponding to each sign determination unit 33.
Concentrate under the situation in the particular quadrant (communication) signal of the feasible possibility of above-mentioned configuration detection of desired in complex data.
(the 3rd embodiment)
Except that phase difference distribution calculator and, receiving equipment of the present invention also has the configuration identical with the receiving equipment of first embodiment.Therefore, will describe phase difference distribution calculator in the present embodiment in detail.
In Fig. 8, phase difference distribution calculator 53 comprises sign determination unit 51, counter 36 and maximum value detector 37.In this embodiment, in phase difference distribution calculator 53, two sign determination unit 510 and 511, four counters 360 to 363 and maximum value detector 37 are arranged respectively.The in-phase signal that sign determination unit 510 receives in the complex data, the orthogonal signalling that sign determination unit 511 receives in the complex data.Each counter of counter 360 to 363 all calculates from the number of each symbol data of sign determination unit 510 and 511 outputs.Maximum value detector 37 compares the output of each counter in the counter 360,361,362 and 363, and detects the maximum in these outputs.
The operation of the phase difference distribution calculator 53 with such configuration is described now with reference to Fig. 8,9 and 10.Supposing to be known and to have identical information from the data that the outside of receiving equipment 1000 sends, for example, all is " 1 ".Fig. 9 shows the symbol distribution (in this embodiment, positive side has 3 data) of the in-phase signal of being determined by identifying unit.Figure 10 shows the symbol distribution (in this embodiment, minus side has two data, and positive side has data) of the orthogonal signalling of being determined by identifying unit.In Fig. 9 and embodiment shown in Figure 10, phase difference distribution calculator 53 receives three complex datas from complex divider 9.Each complex data all comprises in-phase data and orthogonal data.In-phase data is input in the sign determination unit 510, and orthogonal data is input in the sign determination unit 511.Each symbol (plus or minus) that sign determination unit 510 is determined in the in-phase data.Sign determination unit 510 is positive and negative respectively to counter 360 or counter 361 output symbol data according to symbol.Sign determination unit 511 is positive and negative respectively to counter 362 or counter 363 output symbol data according to symbol also.Each counter in the counter 360 to 363 is the quantity of compute sign data all, and each incremental data is outputed in the maximum value detector 37.Then, maximum value detector 37 receives this incremental data among each of counter 360 to 363, relatively more all incremental datas, and the maximum of amount detection data outputs to this maximum in the identifying unit 13 then.
When the distribution of complex data concentrates on when striding I or Q axle, above-mentioned configuration makes may detect maximum exactly.Therefore, can determine the existence of (communication) data of in receiving equipment, expecting with comparalive ease.In addition, in the present embodiment, being arranged in zone on the complex plane, that be used to detect complex data quantity is this regional twice of second embodiment.In addition, though corresponding to a sign determination unit two counters are arranged,, only also can carry out the present invention with a counter corresponding to a sign determination unit.Therefore, this configuration allows to simplify the structure of phase difference distribution calculator.
(the 4th embodiment)
In Figure 11, receiving equipment 1000 comprises ripple test section 17, symbol synchronisation circuit 77 and carrier detector 81.The ripple test section of present embodiment has the configuration identical with the ripple test section of first embodiment.In addition, except that phase difference distribution calculator 79, the ripple test section 17 of present embodiment has the configuration identical with the ripple test section of first embodiment with carrier detector 81.Therefore, with the ripple test section 17 and the carrier detector 81 that no longer describe in detail in the present embodiment.
In carrier detector 81, the phase difference distribution calculator 11,39 that illustrates respectively in embodiment 1 to 3 and any configuration of 53 can both be as among the phase difference distribution calculators 79.
The operation of the receiving equipment 1000 with such configuration is described now with reference to Figure 11.Supposing to be known and to have identical information from the data that the outside of receiving equipment 1000 sends, for example, all is " 1 ".
The operation of ripple test section 17 and carrier detector 81 is identical with the operation that illustrates in first embodiment.The serial complex data that symbol synchronisation circuit 77 receives by 17 outputs of ripple test section.At this moment, if code element in timing accurately synchronously, so, equate from the value of whole outputs of ripple test section 17.If code element is asynchronous in timing accurately, just export some values, this value has reflected that it depends on the number of degrees " τ " and the frequency " fc " of phase shift by the phase place rotation of " 2nfc. τ " representative.
Then, 9 pairs of adjacent subcarriers of delay element 7 and complex divider carry out the complex division computing, to calculate the phase difference on complex coordinates.Since adjacent subcarrier between frequency interval " fi " equate that all therefore, all phase differences (complex value) have identical value " 2nfc. τ " (in fact, under the influence of transmission path, their value and " 2nfc. τ " depart to some extent).With the phase difference between the complex adder 71 accumulative total subcarriers, so that obtain the mean value (θ m) of phase difference, simultaneous phase-shifting calculator 73 obtains simultaneous phase-shifting " τ " according to frequency interval " fi " and average subcarrier phase poor (θ m).This result is offered time synchronisation estimation circuit 75, so that provide the time synchronisation feedback to ripple test section 17.
Above-mentioned configuration makes may simplify the circuit of carrier detector 81 and the structure of symbol synchronisation circuit 77, and shortens the transitional period that detects symbol synchronization from carrier wave.For example, carrying out with wavelet under the situation of DWMC communication, the time between carrier wave detection and the symbol synchronization can shortened the time that is equivalent to three Baud Lengths with four Baud Lengths.
In addition, carrier detector 81 in the present embodiment and symbol synchronisation circuit 77 can be used together with multicarrier receiver, and wherein, this multicarrier receiver uses the fast Fourier transform that can handle complex data.
(the 5th embodiment)
In Figure 12, receiving system 1000 comprises ripple test section 17, symbol synchronisation circuit 97 and carrier detector 99.The ripple test section of present embodiment has the configuration identical with the ripple test section of first embodiment.In addition, except that index buffer 91 and selector 93 and, the carrier detector 99 of present embodiment has the configuration identical with the carrier detector of the 3rd embodiment.In addition, except that selector 95 and, the symbol synchronisation circuit 97 of present embodiment has the configuration identical with the symbol synchronisation circuit of the 4th embodiment.Therefore, in the present embodiment in detail, the configuration identical with these embodiment will be described no longer.
Carrier detector 99 comprises delay element 7, complex divider 9, sign determination unit 51, counter 36, index buffer 91, maximum value detector 37, identifying unit 13 and selector 93.。
In this embodiment, four index buffers 910 to 913 are arranged.Index buffer 910 to 913 is stored each index number " n " (1≤n≤(M/2-1), subcarrier number change to M-1 from 0) of the complex data of being divided by that calculated by each counter in the counter 360 to 363 respectively.The index that selector 93 is selected in four counters 360 to 363 with peaked counter.
Symbol synchronisation circuit 97 comprises delay element 7, complex divider 9, selector 95, complex adder 71, be shifted calculator 73 and time synchronisation estimation circuit 75 synchronously.As shown in figure 12, in this embodiment, by carrier detector 99 and symbol synchronisation circuit 97 shared delay element 7 and complex dividers 9.The corresponding data of index that 95 selections of selector and carrier detector 99 are selected.
The operation of the receiving equipment 1000 with such configuration is described now with reference to Figure 12.Supposing to be known and to have identical information from the receiving equipment 1000 outside data that send, for example, all is " 1 ".
The operation of ripple test section 17 is with identical in the operation described in first embodiment.In addition, the operation of symbol synchronisation circuit 97 and carrier detector 99 is with identical in the operation described in third and fourth embodiment.In third and fourth embodiment, sign determination unit 33 or 51 are to counter 35 and 36 output symbol data.In the carrier detector 99 of present embodiment, will send to counter 36 and index buffer 91 by 51 symbol datas of exporting from the sign determination unit.Therefore, each index buffer in index buffer 910 to 913 is all stored the index number of the complex data of being divided by that is calculated by counter 360 to 363 respectively.Then, selector 93 is selected an index buffer from index buffer 910 to 913, and it is corresponding to have peaked that counter in this index buffer and four counters 360 to 363.At this moment, the information that will have a peaked counter is fed to selector 93 from maximum value detector 37.Then, selector 93 outputs to the index data of selected index buffer in the selector 95 in the symbol synchronisation circuit 97.In symbol synchronisation circuit 97, selector 95 is according to the index data from selector 93, from by the complex data of selecting expection all complex datas of being divided by of complex divider 9 output, and this selector 95 outputs to the complex data of this expection in the complex adder.
In addition, carrier detector 99 comprises the phase difference distribution calculator based on the 3rd embodiment, but it also can be used in configuration described in second embodiment as the phase difference calculator that distributes.
Compare the feasible accuracy that may improve the time synchronisation of estimation symbol synchronisation circuit 97 of above-mentioned configuration with the 4th embodiment.Such improvement is possible, this is may use the complex data (phase difference between the compound subcarrier) of being divided by to suppose time synchronisation because this configuration makes, wherein, this complex data of being divided by is present in the specific region that the phase difference on the complex coordinate system distribute to concentrate.
In addition, carrier detector in the present embodiment 93 and symbol synchronisation circuit 97 can be used with the multi-carrier receiver apparatus that uses the fast Fourier transform that can handle complex data.
(the 6th embodiment)
Figure 13 is the calcspar of receiving equipment according to a sixth embodiment of the invention.The ripple test section of present embodiment has the configuration identical with the ripple test section of Figure 11 and 12.In this embodiment, will describe the configuration of wavelet transform device 1 in detail.In addition, a carrier detector 307 with configuration different with the above embodiments 1 to 5 also to be described.
In Figure 13, receiving equipment 1000 comprises wavelet transform device 1, ripple test section 17 and carrier detector 307.Wavelet transform device 1 comprises the cosine transform device (type 4) 117 (below be called DCT117) of delay element 111, downsampled device (down samplers) 113, prototype filter 115 and fast discrete.M-1 delay element 111 is with the sampling period of data delay that receives.Downsampled device reduces M doubly with the sampling rate of the data that receive.
Carrier detector 307 comprises delay element 301, multiplier 303 and moving average circuit 305.Delay element 301 is the code element phase of data delay that receives, and exports this delayed data.Multiplier 303 multiplies each other data and the delayed data that receives, and the data of output multiplication.Moving average circuit 305 obtains moving average so that data and the delayed data that receives associated.When the result of moving average indicated peak value to detect, moving average circuit 305 was to DCT117 output peak detection signal.
Describe the configuration of prototype filter 115 below in detail with reference to Figure 14.Prototype filter 115 can be the filter that heterogeneous configuration is arranged and have the real coefficient that is used to receive downsampled data.Prototype filter 115 comprises adder 131, two input (two-input) adder 133 and delay elements 135.The filter factor of adder 131 storage prototype filters 115.Delay element 135 made by sampling period of data delay of two input summer outputs.
The operation that has the receiving equipment 1000 of such configuration below with reference to Figure 13 and 14 explanation.Supposing to be known and to have identical information from the receiving equipment 1000 outside data that send, for example, all is " 1 ".
To be input to by the data that carrier detector 307 receives in delay element 301 and the multiplier 303.Delay element 301 with code element phase of the data delay that receives to produce delayed data, again this delayed data is input in the multiplier 303.Multiplier 303 receives from the data of outside with from the delayed data of delay element 301.Adder 303 multiply by the data that receive mutually with delayed data and produces the data that multiply each other, and the data that this multiplied each other are outputed in the moving average circuit 305.Carrier detector 307 is detected carrier in this way.Moving average circuit 305 receives the data that multiplied each other, and the data that receive by utilization and the time-based correlation between the delayed data obtain moving average.
Except DCT117 and, all elements shown in Figure 13 are all stably worked.When carrier detector 307 carried out the carrier wave detection, DCT117 brought into operation.
In carrier detector, when using the time-based correlation of data, above-mentioned configuration makes may shorten the transitional period that detects demodulation from carrier wave.(for example, when DWMC communication is carried out in the wavelet transition that has four Baud Lengths in utilization, just can detect the time period that the time period shortening of handling the Data Receiving processing is equivalent to three code elements from carrier wave.) in addition,, therefore, can improve the power consumption of receiving equipment 1000 owing to DCT117 in the data carrier of carrier detector 307 detection of desired just brings into operation.
(the 7th embodiment)
In Figure 15, receiving equipment 1000 comprises: automatic gain control circuit 151 (below be referred to as AGC151), A/D converter 153 (below be referred to as A/D converter 153), 155, symbol synchronisation circuit 157 and level identifying unit 159.Carrier detector described in embodiment 1 to 6 and any configuration of symbol synchronisation circuit can be used separately as carrier detector 155 and symbol synchronisation circuit 157.Level identifying unit 159 compares the gain level and the threshold value that is stored in the identifying unit 159 from the data of AGC151.If gain level is lower than threshold value, level identifying unit 159 is just to carrier detector 155 and symbol synchronisation circuit 157 outputs " connection (on) " information.If gain level is not less than threshold value, level identifying unit 159 is just to carrier detector 155 and symbol synchronisation circuit 157 outputs " shutoff (off) " information.
The operation of the receiving equipment 1000 with such configuration is described with reference to Figure 15 below.
If there are not the data of expection in the data that receive, just the gain of AGC151 is set to maximum gain.If in the data that receive, there are the data of expection, the gain of AGC151 just is set according to the level of the data that receive.If there are the data of expection, just the gain of AGC151 is set to less than maximum.
The gain level of level identifying unit 159 compare thresholds and AGC151.If gain level is higher than threshold value, the level identifying unit is just to carrier detector 155 output " shutoff " information, and symbol synchronisation circuit 157 is not worked.If gain level is lower than threshold value, level identifying unit 159 is just to carrier detector 155 and symbol synchronisation circuit 157 output " connection " information.
To carrier detector 155 and symbol synchronisation circuit 157 input " connection " information the time, carrier detector 155 and symbol synchronisation circuit 157 just come into operation, with detected carrier respectively and make symbol synchronization.To carrier detector 155 and symbol synchronisation circuit 157 input " shutoff " information the time, the running that carrier detector 155 and symbol synchronisation circuit 157 just stop to carry out detected carrier respectively and make symbol synchronization.
Because when only in the data that receive, having anticipatory data, promptly when being input to " connection " information carrier detector 155 and the symbol synchronisation circuit 157 from level identifying unit 159, carrier detector 155 and symbol synchronisation circuit 157 just operate, therefore, above-mentioned configuration makes the power consumption that may improve receiving equipment 1000.
In addition, although level identifying unit 159 in the present embodiment is to carrier detector 155 and symbol synchronisation circuit 157 output " connection " and " shutoff " information, but, use level identifying unit 159 as follows: if gain level is higher than threshold value, the level identifying unit is not just exported the operation signal that allows carrier detector 155 and symbol synchronisation circuit 157 operate yet.If gain level is lower than threshold value, level identifying unit 159 is with regard to the output function signal.When operation signal was input in carrier detector 155 and the symbol synchronisation circuit 157, carrier detector 155 and symbol synchronisation circuit 159 just began operation, with detected carrier respectively and make symbol synchronization.
(the 8th embodiment)
In Figure 16, receiving equipment 1000 comprises ripple test section 17, carrier detector 801 and symbol synchronisation circuit 77.Ripple test section 17 has the configuration identical with the receiving equipment of the 4th embodiment with symbol synchronisation circuit 77.Therefore, will only describe carrier detector 801 in detail below.
The operation of the receiving equipment 1000 with such configuration is described referring now to Figure 16 and 17.Usually, if the lead-out wire (plug outlet) that branch line and/or plug arranged in the power line does not link to each other with any other equipment, because not matching of impedance impedance and reflection will occur in power line.Therefore, in power line communication (below be referred to as PLC), under the common outofkilter of transmission line.
If data at first have a waveform as shown in figure 17, receiving equipment 1000 just receives the waveform data that has as shown in figure 18.According to data the threshold value that carrier wave detects is set with amplitude spectrum as shown in figure 17.Specifically, the quantity of the phase difference that will find among the subcarrier that is used to communicate by letter is decided to be sum, and threshold value is set to 70% (being defined as " A ") of sum.Under the situation about flattening at waveform top as shown in figure 18, can not carry out carrier wave according to threshold value and detect, even the CNR (ratio of noise power and carrier power) of that a part of amplitude spectrum that does not flatten at the top also is like this in being under the good state.
Therefore, in order to address this problem, used carrier detector 801 in the present embodiment.The phase difference that carrier detector 801 calculates between each adjacent subcarrier, and calculate the quantity (complex data) that its value is lower than the phase difference of certain threshold level.At this, this quantity is defined as " B ".
In this embodiment, state utilization " A " and " B " according to transmission line is provided with threshold value.For example, in the 3rd embodiment, threshold value is set to (A-0.5*B) * and o.7 (is called " formula 1 ").Because this threshold value is to be provided with according to the state of transmission line, therefore can improve the accuracy that carrier wave detects.
If come detected carrier with above-mentioned method in carrier detector 801, carrier detector 801 sends detection information to symbol synchronisation circuit 77.Symbol synchronisation circuit 77 is carried out symbol synchronization according to detecting information operating, and produces synchronizing information.This synchronizing information is fed to ripple test section 17.
In addition, in this embodiment, although be used as an example of calculated threshold with the method for the 3rd embodiment,, in other embodiments or change at state under the situation of " A " and " B ", also can come calculated threshold by enough method for distinguishing according to each transmission line.This configuration makes and may improve the accuracy that the carrier wave under other nearly all situation detects.In addition, this configuration also can be used for using other communication means of cable, for example, and in telephone wire or the coaxial wire that is pre-existing in.Under the situation of using this configuration, in these communication meanss, almost can reach identical effect.
(the 9th embodiment)
In Figure 19, receiving equipment 1000 comprises ripple test section 17, selector 500, carrier detector 801 and symbol synchronisation circuit 77.Ripple test section 17 has the configuration identical with the receiving equipment of the 8th embodiment with symbol synchronisation circuit 77.Therefore, will describe whole operations of selector 500 and present embodiment in detail at this.
As mentioned above, if the lead-out wire that branch line and/or plug arranged in the power line does not link to each other with any other equipment, because impedance does not match, in power line impedance and reflection will appear.Therefore, the transmission line in PLC is usually all under the outofkilter.
Particularly, can become a problem among the PLC, and cause the defective mode of transmission line from the interference of other system that is pre-existing in of like radio amateur's radio wave and shortwave broadcasting and so on.Complex data is used among carrier detector 801 shown in the 4th embodiment and the symbol synchronisation circuit 77.By using complex data, if having from the interference and the interference level of another system higherly in PLC, the result of calculation in carrier detector 801 and symbol synchronisation circuit 77 just has big error margin.This big error margin may produce harmful effect to PLC.In order to reduce this big error margin, receiving equipment 1000 in the present embodiment comprises selector 500.Selector 500 by the subcarrier removing average level with complex data big-difference arranged very much from by the data of selecting expection the complex data of ripple test section 17 outputs.Having very with the average level of complex data, the subcarrier of big-difference more may be the disturbing wave with high level.The average level of deriving complex data is so that average to the level of all subcarriers.In the present embodiment, if with the difference of average level greater than 12db, just in selector 500, remove this subcarrier.Subcarrier is not sent among carrier detector 801 and the symbol synchronisation circuit 77.The feasible accuracy that may improve carrier detector 801 and symbol synchronisation circuit 77 of this configuration.
In addition, can be according to certain situation, for example, the accuracy of the situation of transmission line or carrier detector 801 and symbol synchronisation circuit 77 changes the threshold value (12db) of 12db.
In addition, (in frame) carries out above-mentioned operation in the data block of exchanges data if be wherein to carry out, and selector 500 just can detect the narrow band interference that whether has the high 12db of its level ratio average level.Yet, be difficult to detect whether have a narrow band interference that has with the average level same level.Exist the narrow band interference that has with the average level same level to cause harmful effect to PLC.In order to reduce this harmful effect, be preferably in the non-data block (between frame, or in the space between frame) operate.As shown in figure 20, each frame among frame " A ", " B " and " C " all comprises leading part and data division.Between adjacent frame, the space is arranged, to prevent the overlapping of consecutive frame.When detected carrier, can recall and detect this space.The feasible accuracy in detection that may improve ever-present narrow band interference of this configuration.As a result, when using the complex data of exporting by the ripple test section to carry out the carrier wave detection and making symbol synchronization, can improve the disposal ability of receiving equipment 1000.
In addition, this configuration also can be used for using other communication means of cable, for example, and in telephone wire or the coaxial line that is pre-existing in.When using this configuration, these communication meanss almost can reach identical effect.
In addition, cannot think, carrier detector in the present embodiment is limited in the multi-carrier receiver apparatus that is used in the compound wavelet transform of use, but can use with the multi-carrier receiver apparatus that uses the fast Fourier transform (hereinafter referred to as FFT) that can handle complex data.Will describe the receiving equipment that has FFT in detail below.
In Figure 21, receiving equipment 1000 comprises ripple test section 17, ripple test section 600, selector 500, carrier detector 801 and symbol synchronisation circuit 77.Ripple test section 17, selector 500, carrier detector 801 and symbol synchronisation circuit 77 have the configuration identical with above-mentioned receiving equipment.With regard to leading part, the operation of the operation of receiving equipment 1000 and above-mentioned receiving equipment is approaching.Therefore, will describe ripple test section 600 in detail in the present embodiment.Ripple test section 600 is used FFT rather than is used the wavelet transform device of output complex data to detect ripple.
Transmitting apparatus (not shown among Figure 21) produces lead data with reverse wavelet transform device.Lead data is the relevant ripple that comprises a plurality of sine waves.Therefore, use the ripple test section 600 of FFT just can detect narrow band interference.Similarly, narrow band interference also can be detected in ripple test section 17.
Describe the operation of receiving equipment below in detail with such configuration with reference to Figure 21.
If the detection of narrow band interference greater than four times of a Baud Length, under four times the situation of wavelet filter length greater than Baud Length, in the space between frame, just can be carried out more accurately in the space between the frame.Yet, if this space less than four times of Baud Length because the detection of narrow band interference is to comprise under the situation of a part of frame to carry out in filtering, therefore, in receiving equipment 1000, the accuracy that narrow band interference detects can descend.
Yet if use the ripple test section 600 of adopting FFT, because filter length and the Baud Length in FFT are much at one, therefore, this space at least need be greater than a Baud Length.Correspondingly, when detecting narrow band interference in the space between frame, in the DWMC transmission method of filter length greater than Baud Length, the space of use FFT just can be less than the space of using wavelet.The feasible data transmission efficiency that may improve receiving equipment of this configuration.
In addition, this configuration can use wherein filter length greater than some systems of Baud Length, for example, and the OFDM of OFDM/OQAM or filtering.
And then, can in ripple test section 17, use the FFT processing of fast discrete cosine transform device (type 4) 117 (especially for).Therefore, all comprise under the situation of public FFT the just feasible circuit structure that may simplify receiving equipment shown in Figure 21 of this configuration in ripple test section 17 and ripple test section 600.
(the tenth embodiment)
In Figure 22, ripple test section 17 with 600 and carrier detector 801 all have the configuration identical with the receiving equipment of the 9th embodiment.
Describe the operation of the receiving equipment of present embodiment below in detail with reference to Figure 22.In Figure 19, the subcarrier that adopts FFT is detected in ripple test section 600.The structure of frame is identical with structure shown in Figure 20.
Carry out in the ripple test section 17 of using common wavelet transform device under the situation of carrier wave detection, use by carrying out carrier wave and detect with the wavelet transform data of corresponding waveform use of the time of filter length.In the case, the wavelet transform data from the output of ripple test section comprise the wavelet transform ramp data that is used to carry out the slope processing.Usually, in receiving equipment, use the AGC of ramp data to handle (especially, step-type gain controlling).Therefore, because the wavelet transform ramp data is contained among the wavelet transform data, the accuracy that carrier wave detects can descend.In order to prevent the degeneration of wavelet transform data, the length of lead data needs sufficiently long.Yet in the case, the availability of frequency can descend to some extent.
In the present embodiment, carrier wave detects the Fourier transform data of having used by ripple test section 600 outputs of adopting FFT.Detect by the ripple that uses the FFT mode, make and to carry out Fourier transform to each code element.The AGC operation that the head of frame carries out become stable after, can carry out carrier wave and detect.
Correspondingly, because the Fourier transform data of 600 outputs comprise the data that Nonlinear Processing is crossed hardly from the ripple test section, therefore, can improve the accuracy that carrier wave detects by using the Fourier transform data of exporting from the ripple test section 600 of adopting FFT.
In addition, this configuration can use wherein filter length greater than the system of Baud Length, for example, and the OFDM of OFDM/OQAM or filtering.
And then, FFT can be used in the ripple test section 17 processing of discrete fast cosine transform device (type 4) 117 (especially for).Therefore, if ripple test section 17 and ripple test section 600 all comprise public FFT, the just feasible circuit structure that may simplify receiving equipment shown in Figure 22 of this configuration.
In addition, although the ripple test section 17 in first to the tenth embodiment comprises a sub-wave converter,, ripple test section 17 also can comprise two or more wavelet transform devices.
And then, though described in first to the tenth embodiment, be real wavelet filters,, also can use other filter and the system of filter length greater than Baud Length, for example, adopt the OFDM of OFDM/OQAM or filtering to replace real wavelet filters.
In addition, if necessary, also the various configurations among first to the tenth embodiment can be made up mutually.
Utilizability on the industry
The receiving equipment of describing in first to the tenth embodiment can be by carrying out less calculating again Logarithmic data. In addition, the receiving equipment described in first to the tenth embodiment can use intercarrier Phase difference distributes and carry out carrier detect in frequency domain. And connecing described in first to the tenth embodiment Receiving unit is so that may simplify the circuit structure of receiving equipment. In addition, institute in first to the tenth embodiment The receiving equipment of describing is so that may reduce the impact of arrowband disturbing wave.
Claims (25)
1. receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The complex data output device is used to carry out the wavelet transform that receives data and export complex data;
Delay element is used for complex data is postponed the complex data of a sampling period and output delay;
Complex divider is used for the complex data of complex data and delay is divided by, and exports the complex data of being divided by, and wherein, the complex data of being divided by is represented the phase difference between the compound subcarrier;
Phase difference distribution calculator is used for calculating the quantity that is present in the complex data of being divided by of each quadrant on the orthogonal coordinates, and selects maximum number from the number that calculates;
Identifying unit is used for by relatively this maximum number and number of threshold values judge whether the data that receive are anticipatory datas.
2. according to the receiving equipment of claim 1, wherein, described complex data output device comprises:
The wavelet transform device, it comprises M orthogonal real coefficient wavelet filters (M is a positive integer), is used to carry out the wavelet transform of the data that receive;
The complex data generator, it will be by being defined as the same phase component of composite information from (2n-1) individual output of described wavelet transform device, and will be from 2n output of described wavelet transform device (1≤n≤(M/2-1), and subcarrier being numbered from 0 to M-1) the quadrature component that is defined as composite information produces complex data, and the parallel complex data of output; And
Parallel-to-serial transducer is used for the parallel complex data of described complex data generator output is converted to the serial complex data, and output serial complex data.
3. according to the receiving equipment of claim 1, wherein, described phase difference distribution calculator comprises:
Phase shifter is used for phase shifts П/4 of the complex data of will be divided by;
The sign determination unit is used to judge the symbol of the complex data of being divided by;
A plurality of counters are used to calculate the number of complex data point among each quadrant that is distributed to a plurality of quadrants, that be divided by, and the number that calculates of output;
The maximum number detector is used for detecting the maximum number by the number that calculates of described a plurality of counter outputs.
4. according to the receiving equipment of claim 1, wherein, described phase difference distribution calculator comprises:
The sign determination unit is used to judge the same phase component of the complex data of being divided by and the symbol of the quadrature component of the complex data of being divided by;
A plurality of counters are used to calculate from the number of each of the symbol of described sign determination unit output, and the number that calculates of output;
The maximum number detector is used for detecting the maximum number by the number that calculates of described a plurality of counter outputs.
5. receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The complex data output device is used to carry out the wavelet transform of the data that receive, and exports complex data;
Delay element is used for complex data is postponed a sampling period, and the complex data of output delay;
Complex divider is used for the complex data of complex data and delay is divided by, and exports the complex data of being divided by, and wherein, the complex data of being divided by is represented the phase difference between the compound subcarrier;
Phase difference distribution calculator is used for calculating the number that is present in the complex data of being divided by of each quadrant on the orthogonal coordinates, and selects maximum number from the number that calculates;
Identifying unit is used for by relatively maximum number and number of threshold values judge whether the data that receive are anticipatory datas;
Complex adder, the complex data that is used for being divided by is obtained cumulative data mutually, and obtains mean value by cumulative data;
The simultaneous phase-shifting calculator is used to utilize mean value to calculate the simultaneous phase-shifting value;
The time synchronisation estimation circuit is used for estimating possible time synchronisation by the simultaneous phase-shifting value, and this time synchronisation is fed back to described complex data output device.
6. according to the receiving equipment of claim 5, wherein, described complex data output device comprises:
The wavelet transform device, it comprises M orthogonal real coefficient wavelet filters (M is a positive integer), is used to carry out the wavelet transform of the data that receive;
The complex data generator, it will be by being defined as the same phase component of composite information from (2n-1) individual output (n is a positive integer) of described wavelet transform device, and the quadrature component that will be defined as composite information from 2n the output (1≤n≤(M/2-1) and from 0 to M-1 subcarrier is numbered) of described wavelet transform device produces complex data, and the parallel complex data of output;
Parallel-to-serial transducer is used for the parallel complex data by described complex data generator output is converted to the serial complex data, and output serial complex data.
7. receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The wavelet transform device, it comprises M orthogonal real coefficient wavelet filters (M is a positive integer), is used to carry out the wavelet transform that receives data;
The complex data generator, it will be by being defined as the same phase component of composite information from (2n-1) individual output (n is a positive integer) of described wavelet transform device, and will be from 2n output of described wavelet transform device (1≤n≤(M/2-1), and subcarrier being numbered from 0 to M-1) the quadrature component that is defined as composite information produces complex data, and the parallel complex data of output;
Parallel-to-serial transducer is used for the parallel complex data by described complex data generator output is converted to the serial complex data, and output serial complex data;
Delay element is used for the serial complex data by parallel-to-serial transducer output is postponed a sampling period, and the complex data of output delay;
Complex divider is used for the complex data of complex data and delay is divided by, and exports the complex data of being divided by, and wherein, the complex data of being divided by is represented the phase difference between the compound subcarrier;
The sign determination unit is used to carry out the judgement to the symbol of the quadrature component of the same phase component of the complex data of being divided by and the complex data of being divided by;
A plurality of counters are used to calculate the number from each symbol of described sign determination unit output;
A plurality of index buffers are used for storing n the index (1≤n≤(M/2-1), subcarrier number change to M-1 from 0) of the complex data of being divided by accordingly with each symbol of exporting from described sign determination unit;
The maximum number detector is used for detecting maximum number from the number of described a plurality of counter outputs;
Selector is used for selecting to index accordingly with detected maximum number;
Identifying unit is used for by relatively maximum number and number of threshold values judge whether the data that receive are anticipatory datas;
Selector is used to the corresponding a part of complex data of being divided by of index of selecting and choosing;
Complex adder, the complex data of being divided by that is used for being selected by described selector is obtained cumulative data mutually, and obtains mean value from cumulative data;
The simultaneous phase-shifting calculator is used to utilize this mean value to calculate the simultaneous phase-shifting value;
The time synchronisation estimation circuit is used for estimating possible time synchronisation according to the simultaneous phase-shifting value, and this time synchronisation is fed back to described complex data output device.
8. receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The wavelet transform device is used to carry out the wavelet transform of the data that receive;
Carrier detector is used to detect the carrier wave from the data that receive;
Wherein, described wavelet transform device comprises:
The delay element of M-1 primary sample (one sample) (M is the positive integer greater than 2), the data that are used for receiving sequentially postpone a sampling period;
M downsampled device is used for the data of downsampled data that receive and sequential delays;
Prototype filter with heterogeneous configuration and real coefficient is used to receive downsampled data;
M point quick Fourier converter carries out fast Fourier transform in order to the data to the filtering of exporting from described prototype filter;
Wherein, described carrier detector comprises:
The delay element of one code element is so that with the code element phase of data delay that receives;
Multiplier is used for data that will receive and the data that postponed a code element and multiplies each other;
The moving average circuit of one code element, it is by making the data that receive relevant with delayed data, with the data that receive addition and obtain moving average.
9. receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
Automatic gain control circuit is used for controlling automatically the gain of the data that receive;
The level identifying unit is used for carrying out electrical level judging by the gain level and the threshold level that compare the data that received by described automatic gain control circuit;
Analog/digital converter is used for the analogue data from described automatic gain control circuit output is converted to numerical data;
Carrier detector is used for judging according to the level of being judged by described level identifying unit whether the numerical data that receives from described analog/digital converter is the data of expection;
Symbol synchronisation circuit is used to make the data sync that receives from described carrier detector output.
10. receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The ripple test section is used for the data that receive are carried out wavelet transform;
Carrier detecting circuit, it utilizes from the data of described ripple test section output and the threshold value that can change with the situation of transmission line comes detected carrier;
Symbol synchronisation circuit, it utilizes from the data of described carrier detecting circuit output estimates time synchronisation.
11. a receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The ripple test section is used for the data that receive are carried out wavelet transform;
Selector is used for selecting subcarrier according to the signal level of the data of exporting from described ripple test section;
Carrier detecting circuit, it utilizes the subcarrier of being selected by described selector to carry out carrier wave and detects;
Symbol synchronisation circuit, it utilizes the subcarrier of being selected by described selector to estimate time synchronisation.
12. a receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The ripple test section is used for the data that receive are carried out wavelet transform;
Selector is used for selecting subcarrier according to the signal level in the space between the consecutive frame of the data of exporting from described ripple test section;
Carrier detecting circuit, it utilizes the subcarrier of being selected by described selector to carry out carrier wave and detects;
Symbol synchronisation circuit, it utilizes the subcarrier of being selected by described selector to estimate time synchronisation.
13. a receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The first ripple test section is used for the data that receive are carried out wavelet transform;
The second ripple test section is used for the data that receive are carried out Fourier transform;
Selector is used for selecting subcarrier according to the signal level in the space between the consecutive frame of the data of exporting from the described second ripple test section;
Carrier detecting circuit, it utilizes the subcarrier of being selected by described selector to carry out carrier wave and detects;
Symbol synchronisation circuit, it utilizes the subcarrier of being selected by described selector to estimate time synchronisation.
14. a receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The first ripple test section is used for the data that receive are carried out wavelet transform;
The second ripple test section is used for the data that receive are carried out Fourier transform;
Selector is used for selecting subcarrier according to the signal level in the space between the consecutive frame of the data of exporting from the described second ripple test section;
Carrier detecting circuit, it utilizes the subcarrier of being selected by described selector to carry out carrier wave and detects;
Symbol synchronisation circuit, it utilizes by the data of described first ripple test section output estimates time synchronisation.
15. according to the receiving equipment of claim 13, wherein, the shared public fast Fourier transformer in described first ripple test section and the described second ripple test section.
16. a receiving equipment, it uses the digital multi-carrier transmission method, and this equipment comprises:
Data converting apparatus, it utilizes wavelet transform with the data conversion that the receives data for conversion;
Delay element is used for producing delayed data by the data that delayed transformation is crossed;
Subcarrier is to generation device, and it is right to be used for producing subcarrier by the data of conversion and delayed data;
The phase difference calculating device, be used to calculate subcarrier between phase difference;
Identifying unit is used for judging the data that receive according to the phase difference that is calculated by described phase difference calculating device.
17. according to the receiving equipment of claim 14, wherein, the shared public fast Fourier transformer in described first ripple test section and the described second ripple test section.
18. a receiving equipment, it adopts the digital multi-carrier transmission method that utilizes real coefficient wavelet filters group, and this equipment comprises:
The complex data output device is used to carry out the wavelet transform of the data that receive, and exports complex data;
Deferred mount is used for complex data is postponed a sampling period, and output delay complex data;
The division arithmetic device is used for complex data and the complex data that postponed are divided by, and the output complex data of being divided by, and wherein, the complex data of being divided by is illustrated in the phase difference between the compound subcarrier;
Calculation element is used for calculating the number of the complex data of being divided by of each quadrant of a plurality of quadrants on orthogonal coordinates, and selects maximum number from the number that calculates;
Decision maker is used for by relatively maximum number and number of threshold values judge whether the data that receive are anticipatory datas.
19. according to the receiving equipment of claim 18, wherein, described complex data output device comprises:
Orthogonal M real coefficient wavelet filters (M is a positive integer) is used to carry out the wavelet transform of the data that receive;
The complex data generator, it will be by being defined as the same phase component of composite information from (2n-1) individual output (n is a positive integer) of described wavelet filters, and will be from 2n output of described wavelet filters (1≤n≤(M/2-1), and subcarrier being numbered from 0 to M-1) the quadrature component that is defined as composite information produces complex data, and the parallel complex data of output;
Conversion equipment is used for the parallel complex data by described complex data generator output is converted to the serial complex data, and exports this serial complex data.
20. according to the receiving equipment of claim 18, wherein, described calculation element comprises:
Phase shifting equipment is used for phase shifts П/4 of the complex data of will be divided by;
Decision maker is used to carry out the judgement to the symbol of the complex data of being divided by;
Counting device is used for calculating the number of the complex data point that was divided by of each quadrant that is distributed to a plurality of quadrants, and exports the number that calculates;
Checkout gear is used for detecting the maximum number by the number that calculates of described a plurality of counting device outputs.
21. according to the receiving equipment of claim 18, wherein, described calculation element comprises:
Decision maker is used to carry out the judgement to the symbol of the quadrature component of the symbol of the same phase component of the complex data of being divided by and the complex data of being divided by;
Counting device is used for being counted by each of the symbol of described decision maker output, and the number that calculates of output;
Checkout gear is used for detecting the maximum number by the number that calculates of described counting device output.
22. a method of utilizing real coefficient wavelet filters group to receive data from the digital multi-carrier transmission, this method comprises:
The data that receive are carried out wavelet conversion and output complex data;
With complex data postpone a sampling period and output delay complex data;
Complex data and the complex data that postponed are divided by, and the output complex data of being divided by, wherein, the complex data of being divided by is represented the phase difference between the compound subcarrier;
Calculating is present in the number of the complex data of being divided by in each quadrants of a plurality of quadrants on the orthogonal coordinates, and the maximum number in the number of selecting to calculate; And
By relatively this maximum number and number of threshold values judge whether the data that receive are anticipatory datas.
23., wherein, the data that receive carried out wavelet transform and export complex data comprise according to the method for claim 22:
Use orthogonal M real coefficient wavelet filters (M is a positive integer) to come the data that receive are carried out wavelet transform;
By being defined as the same phase component of composite information from (2n-1) individual output (n is a positive integer) of described wavelet filters, and will be from 2n output of this wavelet filters (1≤n≤(M/2-1), and subcarrier being numbered from 0 to M-1) the quadrature component that is defined as composite information produces complex data, and the parallel complex data of output;
To be converted to the serial complex data by the parallel complex data of described complex data generator output, and export this serial complex data.
24. according to the method for claim 22, wherein, described calculating comprises:
The phase shifts П of the complex data that will be divided by/4;
Execution is to the judgement of the symbol of the complex data of being divided by;
Calculating is distributed to the number of the complex data point that was divided by in each quadrants of a plurality of quadrants, and the number that calculates of output;
Maximum number in the number that calculates that detection is exported in described counting.
25. according to the method for claim 22, wherein, described calculating comprises:
Execution is to the two the judgement of symbol of the quadrature component of the same phase component of the complex data of being divided by and the complex data of being divided by;
Each of the symbol of output in described execution is judged is counted, and the number that calculates of output;
Maximum number in the number that calculates that detection is exported in described counting.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP041118/2003 | 2003-02-19 | ||
| JP2003041118 | 2003-02-19 | ||
| JP345408/2003 | 2003-10-03 |
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| Publication Number | Publication Date |
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| CN1739274A true CN1739274A (en) | 2006-02-22 |
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Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 200480002360 Pending CN1739274A (en) | 2003-02-19 | 2004-02-18 | Receiving apparatus and method for digital multi-carrier transmission |
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Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102113282A (en) * | 2008-07-31 | 2011-06-29 | 松下电器产业株式会社 | OFDM existence detection method, communication apparatus, integrated circuit, and circuit module |
| CN102668428A (en) * | 2009-11-13 | 2012-09-12 | 索尼公司 | Communication apparatus, communication method, computer program and communication system |
| CN107659334A (en) * | 2011-12-05 | 2018-02-02 | 巴特勒能源同盟有限公司 | The method and apparatus for using multicarrier spectrum-spread signal wave filter group |
| US10581481B1 (en) | 2018-09-18 | 2020-03-03 | Battelle Energy Alliance, Llc | Communication device, spread-spectrum receiver, and related method using normalized matched filter for improving signal-to-noise ratio in harsh environments |
-
2004
- 2004-02-18 CN CN 200480002360 patent/CN1739274A/en active Pending
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102113282A (en) * | 2008-07-31 | 2011-06-29 | 松下电器产业株式会社 | OFDM existence detection method, communication apparatus, integrated circuit, and circuit module |
| CN102113282B (en) * | 2008-07-31 | 2013-10-09 | 松下电器产业株式会社 | OFDM existence detection method, communication apparatus, integrated circuit, and circuit module |
| CN102668428A (en) * | 2009-11-13 | 2012-09-12 | 索尼公司 | Communication apparatus, communication method, computer program and communication system |
| CN102668428B (en) * | 2009-11-13 | 2015-03-18 | 索尼公司 | Communication apparatus, communication method and communication system |
| US9001757B2 (en) | 2009-11-13 | 2015-04-07 | Sony Corporation | Communication apparatus, communication method, computer program and communication system |
| CN107659334A (en) * | 2011-12-05 | 2018-02-02 | 巴特勒能源同盟有限公司 | The method and apparatus for using multicarrier spectrum-spread signal wave filter group |
| US10581481B1 (en) | 2018-09-18 | 2020-03-03 | Battelle Energy Alliance, Llc | Communication device, spread-spectrum receiver, and related method using normalized matched filter for improving signal-to-noise ratio in harsh environments |
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