CN1555608A

CN1555608A - Mode controller for signal acquisition and tracking in very wideband communication systems

Info

Publication number: CN1555608A
Application number: CNA028176669A
Authority: CN
Inventors: 蒂莫西・R・米勒; 蒂莫西·R·米勒; ・P・林齐; 杰勒德·P·林齐; ・M・约瑟夫; 迪派克·M·约瑟夫
Original assignee: Freescale Semiconductor Inc
Current assignee: NXP USA Inc
Priority date: 2001-08-10
Filing date: 2002-08-09
Publication date: 2004-12-15
Anticipated expiration: 2022-08-09
Also published as: CN1311645C; KR100910071B1; CA2456915A1; EP1415406A1; JP2005518111A; KR20040047789A; WO2003015302A1

Abstract

A system and method of controlling an operating mode in a UWB receiver is provided. In one variation, the system and method determines the mode of operation by reading a set number of signal samples, estimating mode parameters, calculating a mode probability, and switching between tracking and acquisition states in a finite state machine according to the value of the mode probability. An exemplary version of the mode controller includes a signal-to-noise ratio calculator, a signal and noise power estimator, and an AGC initialization circuit.

Description

Be used for the mode controller that ultra-broadband communication system signal obtains and follows the tracks of

Relevant patent documentation

Present patent application is the U.S. Patent application of submitting on October 10th, 2,000 09/685,197, " be used for the mode controller that ultra-broadband communication system signal obtains and follows the tracks of " and U.S. Patent application 09/209,460, the part continuity of " ultra-broadband spread spectrum communication system ".Present patent application requires the U.S. Provisional Patent Application 60/311,114 of submission on August 10 calendar year 2001, the priority of " being used for the mode controller that ultra-broadband communication system signal obtains and follows the tracks of ".Here intactly with reference to having quoted the content of all these patent applications.

Technical field

The present invention relates to use the radio communication receiver of ultra-broadband (UWB) signal transmission technology, system and method.More specifically, the present invention relates to a kind of system and method, it is configured to control in receiver to keep quality of service when the UWB signal is imported in UWB signal and tracking into when obtaining.

Background technology

In wireless communication system, transmitter obtains data, it is modulated, and resulting waveform is sent to amplifier and antenna, and antenna becomes electromagnetic radiation with waveform from electrical signal conversion.This electromagnetic radiation is by airborne spread, and the antenna that is connected to receiver converts electric current to.These electric currents (or voltage) then amplified before being sent to the transducer that converts the electrical signal to numeral sample and handle, and extraction source information from signal subsequently.

In order to keep specific quality of service on receiver, " locking is " to input signal for receiver.So receiver monitors the signal quality of input signal, and use equipment determines when receiver should be in and do not have the signal of the enough signals of the quality of reception to obtain operator scheme, or the signal trace operator scheme of the enough signal of the quality of reception.In " digital communication ", the 8th chapter, B.Sklar, Prentice Hall can find the synchronous more detailed description of relevant receiver in 1988, here with reference to the whole contents of having quoted the document.

Some wireless device is incorporated into mode controller in the receiver.Mode controller monitors whether reception input signal and definite signal to noise ratio (snr) are enough to keep acceptable quality of service.If it is not enough that mode controller is determined SNR, receiver is forced to break away from tracing mode and enters obtaining mode.

Some wireless device uses RSSI (receiver S meter) deterministic model controller should be in what pattern, promptly follows the tracks of or obtaining mode.RSSI measures input signal intensity merely.Yet the problem of this quasi-controller is when noise power significantly improves, and signal strength signal intensity still shows and can accept, and in fact signal quality is to contain noise and unacceptable.

Other wireless device uses two RSSI, a measured signal power, and another measures noise power.In frequency spectrum, measure noise power in the unappropriated substantially band exterior domain of any signal.Suppose that noise is identical in being with exterior domain and being with inner region, this measures the accurate noise power that indicates the band inner region substantially.Yet this hypothesis may be incorrect.Suppose the estimated signals that vacant zone may comprise can influence the supposition noise power.In addition, out-of-band noise power may be different from in-band noise power.These wireless devices are measured according to inband signaling and out-of-band noise is measured estimation SNR.Relevant noise changes very little basis hypothesis and allows this technology is applied to narrowband systems in less relatively frequency range.The out-of-band noise of UWB system is then nonsensical.Therefore expectation obtains the more real estimation of SNR.

The inventor recognizes, in order to obtain the true indication of wireless performance, should measuring-signal and noise power, and two kinds of measurements should carry out in band, especially for the UWB system.The true indication of wireless performance allow mode controller wireless device obtain and tracking mode between accurately switch, obtain thereby prevent to miss, and falseness is obtained, wherein miss to obtain system throughput is had adverse influence, because should can attempt picked up signal by spended time when can accept bit error rate (BER) (BER) and receive data at it, and falseness is obtained and is caused receiver deal with data and unacceptable BER.

This mistake to obtaining mode can occur in input signal is easy to occur the system of the burst error for example or the intermittently loss of signal changes.The bursty nature of input signal is especially true for the UWB channel.In these burst communication channels, receiver can force break away from tracking mode continually because of short interruptions, thus received signal no longer.Wireless device is attempted regaining signal so that obtain acceptable SNR, although it is shorter relatively to receive break period.This frequent reception when wireless device is attempted obtaining again interrupts that effective throughput of system is had adverse influence.

Determine effectively in the mode of the degeneration minimum of quality of service (for example, the accepted BER under certain throughput) when receiver should and obtain that to switch between the state be a challenge in tracking mode.

Summary of the invention

Shown in the title of this part, only provide the concise and to the point description of relevant selected feature of the present invention now.Relevant more complete explanation of the present invention should be as the criterion with all files.

An object of the present invention is to provide a kind of UWB receiver that comprises the synchronous mode controller, the synchronous mode controller estimate to import into the UWB signal with respect to the signal power of background noise determining SNR, and determine according to SNR whether receiver should be in and obtain or tracing mode.

Another object of the present invention provides a kind of UWB receiver that comprises mode controller, and mode controller uses processor efficient calculation SNR, obtains or tracing mode to determine whether receiver should be in.

Another feature of the present invention is to overcome the above-mentioned of general communication system and method and other deficiency.

Realize these and other objects by the wireless receiver that is configured to receive the UWB transmission.Though disclosed herein is some embodiment, yet an embodiment can comprise the snr computation device, whether and another embodiment can comprise signal and noise power estimator, be used to detect receiver and lock onto and import the UWB signal into, and whether receiver should be in and obtain or tracing mode.

Some purpose in these purposes also can reach by a kind of mode controller, and described mode controller is identified for obtaining or following the tracks of the desired operation mode of importing data-signal into.Mode controller comprises: data dependence clearing cell (data dependence removal element), be used for receiving and import data-signal into, and output is independent of and imports the data that comprise in the data-signal, the data-independent signals that the intensity of data-signal is imported in indication into into; Signal path comprises being used for the operating data irrelevant signal to determine the first processor of first M signal; With the first nonlinear function unit, be used for first M signal is carried out nonlinear function to determine signal parameter; The noise associated pathway, it comprises and is used for the data irrelevant signal is carried out nonlinear function to determine the second nonlinear function unit of second M signal; Second processor is used to operate second M signal to determine the noise relevant parameter; With the 3rd processor, be used for processing signals parameter and noise relevant parameter and import the pattern Control Parameter of the relative signal intensity of data-signal into to determine indication.

Mode controller can also comprise first subsampler between the first processor and the first nonlinear function unit, is used for first rate first M signal being sampled, and exports first M signal of sampling to the first nonlinear function unit.Mode controller also can comprise second subsampler between second processor and comparator, is used for second speed signal parameter being sampled, and exports the signal parameter of sampling to comparator.

Mode controller can also comprise input scaler (scaler), is used for before data dependence clearing cell input input signal itself and first proportionality coefficient being multiplied each other.First proportionality coefficient can be a coefficient 2.First proportionality coefficient also can be programmable.

Mode controller can also comprise the signal path scaler, is used for before comparator input signal parameter itself and second proportionality coefficient being multiplied each other.Second proportionality coefficient can be a coefficient 2.Second proportionality coefficient also can be programmable.

Mode controller can also comprise noise associated pathway scaler, is used for before comparator input noise coherent signal itself and the 3rd proportionality coefficient being multiplied each other.The 3rd proportionality coefficient can be a coefficient 2.The 3rd proportionality coefficient also can be programmable.

First processor can be first filter.First filter can be a finite impulse response filter, moving average filter, and infinite impulse response filter leaks integration filter or any other expectation filter.Similarly, second processor can be second filter.Second filter can be a finite impulse response filter, moving average filter, and infinite impulse response filter leaks integration filter or any other expectation filter.

Especially, in one embodiment, first processor is an infinite impulse response filter, and second processor is to leak integration filter.In this case, infinite impulse response filter can be configured to approach the coherent signal of expectation.In another embodiment, first processor is first moving average filter, and second processor is second moving average filter.

The data dependence clearing cell can be to export the absolute value of input signal with the absolute value element as data-independent signals.

The first nonlinear function unit be output first M signal square with first squarer as signal parameter.Similarly, the second nonlinear function unit can be the dateout irrelevant signal square with second squarer as second M signal.

Some purpose in these purposes also can reach by a kind of mode controller, and described mode controller is identified for obtaining or following the tracks of the desired operation mode of importing data-signal into.Mode controller comprises: absolute value element is used to receive the absolute value that imports data-signal into and determine to import into data-signal; Signal path comprises that the absolute value that is used for data-signal carries out filtering to determine first filter of first M signal; With first squarer, be used for first M signal is carried out square to determine the noise relevant parameter; The noise associated pathway comprises being used for the absolute value that imports data-signal into is carried out square second squarer with definite second M signal; With second filter, be used for second M signal is carried out filtering to determine signal parameter; And comparator, be used for comparison signal parameter and noise relevant parameter and import the pattern Control Parameter of the relative signal intensity of data-signal into to determine indication.

Mode controller can also comprise first subsampler between first filter and first squarer, is used for first rate first M signal being sampled, and exports first M signal of sampling to first squarer.Mode controller also can comprise second subsampler between second filter and comparator, is used for second speed signal parameter being sampled, and exports the signal parameter of sampling to comparator.

Mode controller can also comprise the input scaler, is used for before absolute value element input input signal itself and first proportionality coefficient being multiplied each other.First proportionality coefficient can be a coefficient 2.First proportionality coefficient can be programmable.

Mode controller can also comprise the signal path scaler, is used for before comparator input signal parameter itself and second proportionality coefficient being multiplied each other.Second proportionality coefficient can be a coefficient 2.Second proportionality coefficient can be programmable.

Mode controller can also comprise noise associated pathway scaler, is used for before comparator input noise coherent signal itself and the 3rd proportionality coefficient being multiplied each other.The 3rd proportionality coefficient can be a coefficient 2.The 3rd proportionality coefficient can be programmable.

First filter can be a finite impulse response filter, moving average filter, and infinite impulse response filter leaks integration filter or any other expectation filter.Similarly, second filter can be a finite impulse response filter, moving average filter, and infinite impulse response filter leaks integration filter or any other expectation filter.

Some purpose in these purposes also can reach by a kind of mode controller in the ultra-broadband receiver, and described mode controller is identified for obtaining or following the tracks of the desired operation mode of ultra-broadband receiver.Mode controller comprises: the signal path that is used to determine import into the signal parameter of data-signal; Be used to determine to import into the path based on the parameter of noise of data-signal based on noise; Be used for processing signals parameter and noise relevant parameter processor with the deterministic model Control Parameter; And controller, be used between obtaining mode and tracing mode, switching according to the pattern Control Parameter.

Signal parameter can be the estimation of signal strength signal intensity, and is the estimation of signal plus noise intensity (signal plus noise strength) based on the parameter of noise.Processor can be a comparator.

Mode controller can also comprise the signal path scaler, is used for signal parameter is calibrated to produce the rate-aided signal parameter.Processor then can receive rate-aided signal parameter rather than signal parameter.

Mode controller can also comprise the noise path scaler, is used for calibrating based on the parameter of noise to produce the parameter based on noise of calibration.Processor then can receive the parameter based on noise of calibration, rather than based on the parameter of noise.

Signal path can comprise the filter of heel squarer.Noise path can comprise the squarer of heel filter.

Mode controller can also comprise absolute value block, is used to determine to import into the absolute value of data-signal, and to signal path with the absolute value of data-signal is provided based on the path of noise.

Description of drawings

Can easily understand the present invention and many attendant advantages thereof more all sidedly, because with reference to understanding the present invention and described advantage better, wherein below in conjunction with the detailed description that accompanying drawing carried out:

Fig. 1 is based on the module map of ultra-broadband (UWB) transceiver of the preferred embodiment of the present invention;

Fig. 2 be among Fig. 1 based on the receiver of the transceiver of the preferred embodiment of the present invention, and the module map of controlled in wireless and interface section;

Fig. 3 is based on the module map of obtaining the path of the receiver of the preferred embodiment of the present invention among Fig. 2;

Fig. 4 is based on the module map of the track path of the receiver of the preferred embodiment of the present invention among Fig. 2;

The module map of Fig. 5 has illustrated among Fig. 2 obtaining and track path based on the receiver of the preferred embodiment of the present invention;

Fig. 6 is based on the module map of obtaining controller of the receiver of the preferred embodiment of the present invention among Fig. 5;

Fig. 7 A is based on the module map of the leakage integration filter of the preferred embodiment of the present invention;

Fig. 7 B is based on the module map of the moving average filter of the preferred embodiment of the present invention;

Fig. 7 C is based on the module map of the bipolar infinite impulse response filter of the preferred embodiment of the present invention;

Fig. 7 D is based on the module map of the finite impulse response filter of the preferred embodiment of the present invention;

Fig. 8 is the more detailed module map of the UWB transceiver of Fig. 1;

Fig. 9 is based on the sequential chart of the two-phase simple venation swash of wave of the preferred embodiment of the present invention;

The sequential chart of Figure 10 A shows solid size sheet simulation code word according to a preferred embodiment of the invention;

The sequential chart of Figure 10 B shows 5 chips simulation code word according to a preferred embodiment of the invention;

The sequential chart of Figure 11 shows 2 chip digital word according to a preferred embodiment of the invention;

The sequential chart of Figure 12 A shows the local signal that produces in input signal and the UWB transceiver;

The sequential chart of Figure 12 B shows the correlated results that the input signal of Figure 12 A and the local signal that produces are compared;

The sequential chart of the error channel of Figure 13, when input signal and the local signal phase that produces near the time, described error channel indication input signal and the local phase difference between signals that produces;

Figure 14 A shows the work of tracing mode at the correlation curve of Figure 12 B to the sequential chart of 14C;

The sequential chart of Figure 15 shows the input signal and the coherent signal of the practical operation that is used for the preferred embodiment of the present invention;

Figure 16 is based on the state diagram of the mode controller of the preferred embodiment of the present invention;

Figure 17 is based on the state diagram of the mode controller of the optional preferred embodiment of the present invention;

Figure 18 is the module map of the specific embodiment that obtains controller or lock detector of Fig. 6;

Figure 19 shows the step that state machine is carried out of obtaining of Figure 16 and 17 according to the embodiment that obtains controller of Figure 18;

The chart of Figure 20 is according to the behavior of probability curve that controller or lock detector show each numerical value of K of obtaining of Figure 18;

Figure 21 is at (B=16) and (K=50) show the performance curve that obtains controller or lock detector of Figure 18;

Figure 22 shows the optional embodiment that obtains controller 545 or lock detector 550 of mode controller among Fig. 5;

Figure 23 shows another optional embodiment that obtains controller or lock detector of the present invention, and wherein whether the AGC initialization is used to the deterministic model controller and should be in and obtains or tracing mode;

Figure 24 illustrates the processor system based on the preferred embodiment of the present invention.

Embodiment

With reference now to accompanying drawing, more detailed the preferred embodiments of the present invention is described.In institute's drawings attached, represent identical or corresponding part with similar Reference numeral.

Transceiver design

Fig. 1 is based on the module map of ultra-broadband (UWB) transceiver of the preferred embodiment of the present invention.As shown in Figure 1, transceiver comprises 3 critical pieces, and promptly receiver 1, wireless controller and interface 3, and transmitter 5.Receiver 1 comprises reception antenna 10, front end 15, UWB waveform correlator 20 and reception timing generator 25.Transmitter comprises transmitting antenna 40, UWB waveform generator 45, encoder 50 and transmission timing generator 55.

Though single wireless controller and interface 3 are used for receiver 1 and transmitter 5 among the figure, yet optional embodiment can comprise each discrete wireless controller and the interface 3 that is used for receiver 1 and transmitter 5.In addition, the separate antenna that switches between transmitter and receiver can be used to replace discrete reception and transmitting antenna 10 and 40.Receive and send

timing generator

25 and 55 and also can be merged into single timing generator, perhaps can remain discrete unit.

Preferably based on the unit of processor, it, is perhaps realized by one or more programmable processor for example by one or more application-specific integrated circuit (ASIC) (ASIC) by firmware hardwired logic for wireless controller and interface 3.In operation, wireless controller and interface 3 or serve as medium access control (MAC) controller, perhaps serve as the UWB radio communication function of realizing by receiver 1 and transmitter 5, and the MAC interface between the application of use UWB communication channel and remote equipment swap data.

When the positive received signal of transceiver, the UWB electromagnetic waveforms that reception antenna 10 will import into converts the signal of telecommunication (or optical signalling) to, and provides this signal of telecommunication to wireless front end 15.According to the type of waveform, wireless front end 15 is handled the signals of telecommunication, makes the spectrum component of the level of signal and signal be suitable for the processing in the UWB waveform correlator 20.This processing can comprise frequency spectrum shaping, for example matched filtering, and the part matched filtering is simply roll-offed or the like.

After front-end processing, UWB waveform correlator 20 then makes the different candidate signals that produce according to the clock signal from timing generator 25 relevant with input signal, whether synchronous to determine receiver 1 with input signal, and if synchronously, the data that comprise in the input signal of determining to receive.

Timing generator 25 is worked under the control of wireless controller and interface 3, with the clock signal clk that uses in the relevant treatment that is provided at 20 execution of UWB waveform correlator _RThis clock signal clk _RHas a phase place, the input signal that this phase place preferably relatively receives on the reception antenna 10 and changing.The UWB waveform correlator is used clock signal clk _RIn the part coupling of this locality generation, and has clock signal clk with input signal _RThe coherent signal of phase place.During phase alignment, UWB waveform correlator 20 provides high s/n ratio (SNR) data to carry out subsequent treatment to wireless controller and interface 3 each other for coherent signal (the local signal that produces) that produces when this locality and input signal.

Conceptive, UWB waveform correlator 20 can be considered to have the correlation window that comprises local signal.When the phase place of the relative input signal of phase place of clock signal changed, correlation window was moved.Then correlation window is compared with the instantaneous sampling of input signal, up to obtaining acceptable correlated results at two signals, it shows realizes obtaining locking.

In some cases, the output of UWB waveform correlator 20 is data itself.In other cases, UWB waveform correlator 20 provides intermediate correlation result simply, and wherein wireless controller and interface 3 use the intermediate correlation result specified data, and when synchronous with input signal definite receiver 1 is.

UWB waveform correlator 20 is worked under two operator schemes, i.e. signal trace pattern (" tracing mode ") and signal obtaining mode (" obtaining mode ").When occurring synchronously not or lost synchronously, and receiver 1 just attempting to realize this when synchronous, uses obtaining mode.When having occurred synchronously and needs when keeping synchronous, use tracing mode.

During obtaining mode, wireless controller and interface 3 provide control signal to obtain synchronously to receiver 1.Correlation window in this control signal indication receiver 1 slip UWB waveform correlator 20 is with the phase place of trial and coupling input signal, and locking is obtained in realization.Especially, by regulating,, realize this purpose up to the correlated results that obtains expectation from the phase place and the frequency of the clock of timing generator 25 outputs.

In case obtain synchronously, receiver enters tracing mode.During tracing mode, transceiver is operated to keep and to improve synchronously.Especially, wireless controller and interface 3 is analyzed correlated results from UWB waveform correlator 20 to determine the correlation window in the UWB waveform correlator 20, and promptly whether the phase place from the local signal of timing generator needs to regulate.

In addition, during tracing mode, receiver 1 provides data to the input port (" receiving the data input ") of wireless controller and interface 3, and wireless controller and interface 3 then provide this data by output port (" receiving data output ") to external procedure.External procedure can be to utilize the data that receive by receiver 1, maybe will send in the several processes that the data of remote receiver carry out any one by transmitter 5.

When transceiver just sent signal, wireless controller and interface 3 were gone up from external source reception sources data at input port (" sending the data input ").Wireless controller and interface 3 then provide data by output port (" sending data output ") to the encoder 50 of transmitter 5.Wireless controller and interface 3 also are provided for discerning the control signal of the signaling sequence of UWB pulse to transmitter 5.As mentioned above, in certain embodiments of the present invention, the function of receiver 1 and transmitter 5 can be used common resource, for example common timing generator and/or community antenna.

Encoder 50 receives subscriber-coded information and data from wireless controller and interface 3, and preprocessed data is imported with the timing that UWB waveform generator 45 is provided with coding.UWB waveform generator 45 then produces the UWB pulse according to waveform and/or time encoding, so that transmit data to remote location.Encoder 50 is according to carrying out this function from the timing signal that sends timing generator 55 receptions.

Encoder 50 produces control signals, and this control signal is that the modulation of generation needs is necessary.For example, encoder 50 can obtain serial bit stream and utilize forward error correction (FEC) algorithm (for example Reed-Solomon code, Gray code, Hamming code, convolution code or the like) that it is encoded.Encoder 50 also can interweave to prevent burst error to data.Encoder 50 also can provide the albefaction function to prevent the long string of " 1 " or " 0 ".Encoder 50 also can provide the spread spectrum function specific to the user, for example produces the predetermined length chip code that the group as an expression bit (for example noninverting bit of the anti-phase bit of " 1 " bit and " 0 " bit or the like) sends.Encoder 50 can be divided into subclass with serial bit stream, so that each wavelet or each chip code send a plurality of bits, and produce a plurality of control signals so as any combination that influences aforesaid modulation scheme (for example at Lathi, " Modern Digital and AnalogCommunications Systems ", Holt, Rinehart and Winston describe in 1998, here with reference to quoting its whole contents).

Wireless controller can provide relevant with interface 3 and go up certain sign that receives the data source of data from it, for example user ID or the like at input port (" sending the data input ").In one embodiment of the invention, this user ID can be inserted in the transfer sequence, seems the group head of information block.In other embodiments of the invention, user ID itself can be used to data are encoded, and makes the receiver that receives transmission need suppose or have the priori about user ID, so that understand data.For example, ID can be used to provide different range signals (for example having amplitude " f ") to the fast modulation control signal, with as the mode that applies coding to signal.

Output from encoder 50 is provided for UWB waveform generator 45, and UWB waveform generator 45 then produces the impulse waveform that has according to the burst length according to the command signal of its reception, and it can be in the different schemes of any amount one.The output of UWB generator 45 then is provided to transmitting antenna 40, and transmitting antenna 40 then sends the UWB energy to receiver.

In a UWB modulation scheme, can use the relative spacing of transmission pulse (for example PPM warbles or the like) that data are encoded.In other UWB modulation scheme, can be as mentioned above the shape (shape) of (and/or describing among the Lathi) use pulse data are encoded.Should be noted that the present invention can modulate the modulation scheme of the shape of (for example pulse position modulation is warbled or the like) and other operating impulse the assembly time.

Above ability has many advantages, for example sends a more than data bit from transmitter 5 each symbol, or the like.Yet one more importantly character be to use this technology to realize the spread spectrum multi-user system, this system needs a plurality of spreading codes (for example each spreading code all has spike auto-correlation function, and has ebb crosscorrelation function jointly, or the like).

In addition, regularly, phase place, the spreading code function that is combined as of frequency and amplitude modulation(PAM) has increased the extra degree of freedom, thereby allows to optimize more crosscorrelation and autocorrelation performance.Owing to improved auto-correlation and crosscorrelation characteristic, system of the present invention has improved ability, thereby allows many transceiver units in approaching position work, but is not subjected to the influence of interference each other.

Fig. 2 be among Fig. 1 based on the receiver of the transceiver of the preferred embodiment of the present invention, and the module map of controlled in wireless and interface section.As shown in Figure 2, UWB waveform correlator 20 also comprises pulse forming network (PFN) and timer 2 05, data correlator 210, and error channel correlators 215.Wireless controller and interface 3 comprise first and second A/

D converters

220 and 225, and digitial controller 230.The operation of receiver 1 and wireless controller and interface 3 can be described below.

According to the clock signal that receives from timing generator 25, PFN and timer 2 05 produce a series of earth pulses, for example rectangular pulse or wavelet (that is, the local signal that produces), and it is provided for data correlator 210 and error channel correlators 215.PFN and timer 2 05 also provide control signal to data and

error channel correlators

210 and 215, and provide the clock order to first and second A/D converters 220 and 225.The operation of control signal control data and

error channel correlators

210 and 215, and clock signal indicates the corresponding output of first and second A/D converters 220 and the 225 pairs of data and

error channel correlators

210 and 215 to sample.

First and second A/

D converters

220 and 225 receive simulation output from data and

error channel correlators

210 and 215 respectively, and convert thereof into digital signal, and digital signal then is provided for digitial controller 230.Digitial controller 230 then determines whether to receive the enough signals of quality (be used to obtain or inhibit signal locking), and the execution pattern control operation should be in tracing mode or obtaining mode so that selective reception device 1 is current.In addition, if receiver 1 is in tracing mode, digitial controller 230 also provides information to improve semaphore lock to receiving timing generator 25.

Fig. 3 is based on the module map of the data path in the receiver of the preferred embodiment of the present invention.As shown in Figure 3, front end 15 comprises amplifier 305; Data correlator 210 comprises data mixing device 310 and data integrate device 315; And timing generator 25 comprises local oscillator (" LO ") 320 and phase controller 325.

Amplifier 305 amplified it before sending input signal to data correlator 210.In optional embodiment, front end can be modified to as required carries out the least possible operation.For example, also can carry out filtering and as required such as the Signal Regulation of automatic gain control (AGC).

Data mixing device 310 receives the input signal that amplifies from front end 15, receives the local signal that produces from PFN and timer 2 05, and mixes two signals to produce signal (on-time signal) on time.Signal then is provided for data integrate device 315 on time, and data integrate device 315 is carrying out integration to signal on time on the time period between the reset command that receives from PFN and timer 2 05.The integration that produces to digitial controller 230 dateout integrators 315 by first A/D converter is signal on time, and digitial controller 230 determines whether occur successfully obtaining at obtaining mode, perhaps whether keep data interlock in tracing mode.

Optional embodiment can use a plurality of blenders of being separated by one or more other processing unit (such as amplifier, filter or the like).First blender is reduced to the IF signal with input signal, and second blender is reduced to base band with signal.

Fig. 4 is based on the module map of the error channel path in the receiver of the preferred embodiment of the present invention.As shown in Figure 4, front end 15 comprises amplifier 305; Error channel correlators 215 comprises the first error channel mixer, 405, the second error channel mixer 410, error channel adder 415 and error channel integrator 420; And timing generator 25 comprises local oscillator 320 and phase controller 325.

The first error channel mixer 405 receives the input signal that amplifies from front end 15, receives first duplicate of the local signal that produces from PFN and timer 2 05, and mixes two signals.The second error channel mixer 410 receives the input signal that amplifies from front end 15, from second duplicate of PFN and the local signal that produces of timer 2 05 reception, and with two signal multiplications.

First and second duplicates that offer the signal that this locality of the first and second

error channel mixer

405 and 410 produces preferably postpone the amount of setting each other, make the error channel mixer 405 of winning investigate the signal of this locality generation, and the second error channel mixer 410 is investigated the signal of this locality generation with second phase place with first phase place.This permissible error channel correlators 215 is investigated correlation values according to two of local signal different phase places.According to this relatively, digitial controller 230 can be determined necessity of local signal phase place is regulated.

As mentioned above, optional embodiment can use a plurality of blenders of being separated by one or more other processing unit (such as amplifier, filter or the like).First blender is reduced to the IF signal with input signal, and second blender is reduced to base band with signal.

When realizing, postpone a required amount by the input signal that will offer the first and second

error channel mixer

405 and 410, perhaps the phase place of first and second duplicates by will offering the signal that the first and second error channel mixer 405 and this locality of 410 produce be positioned to central phase place at a distance of identical amount, can on function, realize the phase delay of input signal.

Local oscillator 320 produces initial clock signal.This signal preferably and input signal have same frequency, although needn't be like this.According to initial clock signal with from the phase control signal of wireless controller and interface 3 (being specially digitial controller 230), phase controller 325 produces the signal that this locality with particular phases produces.When processing signals, can be according to regulating this phase place from the instruction of digitial controller 230.

In an optimum embodiment of the present invention, the spreading rate of input signal, the whole nominals of spreading rate (nominally) of initial clock signal and the local signal that produces have the frequency of 1.3GHz, and offer data integrate device 315, the reset command of the error integrator 420 and second A/D converter 225, and the clock signal that offers first A/D converter 220 has the frequency of 100MHz.Yet in optional embodiment, these frequencies can change.

The module map of Fig. 5 shows based on the data of the receiver 1 of the preferred embodiment of the present invention and error channel path.As shown in Figure 5, digitial controller 230 comprises numeric data code processor 520, error channel code processor 530 and mode controller 540.Mode controller 540 also comprises and obtains controller 545, lock detector 550 and error channel controller 555.In addition, postpone 505,510 and 515 by the first, the second and the 3rd respectively from the phase place of the local signal of PFN and timer 2 05 output and be delayed value 2 τ, 0 τ and 1 τ.

The function that numeric data code processor 520 and error channel code processor 530 are carried out is similar at digital field device 210 associated with the data and error channel correlators 215.The signal that mixes input signal and local generation just as data correlator 210 is such with the correlated results that obtains simulation field, and numeric data code processor 520 is carried out similar function in digital field.Numeric data code processor 520 receives simply and imports digital signal and the local digital signal that produces into, and carries out correlated results.Error channel processor 530 makes digital error signal relevant with digital word to produce the final error value.

Though numeric data code processor 520 can have identical code word size with error channel code processor 530, yet needn't be like this.For example, it is 4 code word that numeric data code processor 520 can use length, is 1 code word and error channel code processor 530 can use length.

(for example can omit these

digital code processors

520 and 530 in case of necessity, if code word size is configured to equal 1, then can error of omission channel code processor 530), but it exists the signal that allows to receive to have higher reliability, because it allows the digital correlation of adding.The realization of these unit is similar to the operation of carrying out in the correlator 20, except the mode with Digital Logic realizes.

According to the result from data and error

channel code processor

520 and 530, mode controller 540 determines which pattern receiver 1 is in, and provides correction signal to improve obtaining or following the tracks of of receiver 1.When receiver 1 is in obtaining mode, obtains controller 545 and determined whether suitably picked up signal.If it changes over tracing mode with receiver; If not, it waits for that next group data-signal obtains definite to carry out another time.

When receiver 1 was in tracing mode, lock detector 550 determined whether signal should remain on tracing mode.If it waits for that next group data-signal is definite to carry out another time semaphore lock; If not, it changes into obtaining mode with receiver.In addition, when being in tracing mode, error channel controller 555 provides corrected value to follow the tracks of to improve.

The the first, the second and the 3rd postpones 505,510 and 515 postpones local signals, makes data mixing device 310, the first error channel mixer 405 and the different slightly local signal of the second error channel mixer, 410 equal receiving phases.This allows data correlator 210 to receive the signal that its phase places enough produce near this locality of the phase place of input signal, and permissible error channel correlators 215 receives two local signals that produce, and its phase place that has is the amount of setting that is positioned at before and after the signal that this locality that data correlator 210 uses produces.

In the embodiment show in figure 5, the phase place of the signal that this locality that PFN and timer 2 05 produce produces preferably postpones 505,510 and 515 by the first, the second and the 3rd respectively and is delayed 2 τ, 0 τ and 1 τ (wherein τ sets retardation).Yet in optional embodiment, can change these retardations and position.In addition, delay can be provided for input signal rather than the local signal that produces.

Fig. 6 is based on the module map of obtaining controller or lock detector of the preferred embodiment of the present invention.As shown in Figure 6, obtain controller 545 or lock detector 550 and comprise the first calibration blender 605, absolute value block 610, the first squarers 615, noise path filter 620, noise path subsampler 223, the second calibration blender 625, signal path filter 630, signal path subsampler 223, second squarer, 635, the three calibration blender 640 and comparators 645.

In whole specification, use term " noise path " sometimes.This term is meant the noise associated pathway that comprises noise component(s).It does not also mean that the path only transmits noise.Yet for simply, it is known as noise path sometimes.In this manual, term " noise path " and " noise associated pathway " can be exchanged use.

In this embodiment, the first, the second and the 3rd calibration blender 605,625 and 640 is distinguished proportionally COEFFICIENT K ₁, K ₂And K ₃To obtain the amplitude calibration of the signal that controller 545 handles on each aspect.Under the simplest situation, these proportionality coefficients can be jointly or are equaled 1 separately, can omit relevant calibration blender fully in this case.These proportionality coefficients K ₁, K ₂And K ₃Can be constant in whole operation, maybe can be programmable.

By having the second and the 3rd

discrete calibration blender

625 and 640, system can allow second blender to carry out mark (fractional) calibration.So, even the second and the 3rd proportionality coefficient K ₂And K ₃Be constrained to integer, also can be at the 3rd proportionality coefficient K ₃It is standardized.This means that signal path can have proportionality coefficient 1, and noise path has K ₂/ K ₃Effective proportionality coefficient.

Though proportionality coefficient can be got any number in some preferred embodiment, yet in other embodiments, some proportionality coefficient can be configured to coefficient 2.This allows to use shift register to realize the relevant calibration blender, thus simplified design and realization.

During handling, 610 pairs of signals that receive from the first calibration blender 605 of absolute value block are carried out absolute value function, so that all negative value that will receive convert its corresponding positive to.This absolute value signal then is provided for noise path (first squarer 615, the noise path filter 620 and the second calibration blender 625) and signal path (signal path filter 630, the second squarers 635 and the 3rd calibration blender 640).

Noise path is at first carried out square absolute value signal on first squarer 615, then transmits quadrature signal by noise path filter 620, and calibrates 625 pairs of filtering signals of blender with second as required and calibrate.This result with the signal path combination has produced the parameter based on noise, and it is the estimation to the noise intensity of input signal.

Noise path can comprise noise path subsampler 623, the periodicity speed of noise path subsampler 623 changing is for example whenever the 4th output, whenever the 15th output, whenever the 228th output or the like, periodically the output of noise path filter 620 is sampled.If yet sampling rate is set at 1 equably, promptly each result is sampled, can omit noise path subsampler 223 fully.

Signal path at first carries out filtering to absolute value signal on signal path filter 630, then carry out square with 635 pairs of filtering signals of second squarer, and calibrate 640 pairs of quadrature signal of blender with the 3rd as required and calibrate.This has produced a kind of signal parameter, and this signal parameter is the estimation to the signal strength signal intensity of input signal.

The signal path signal can comprise signal path subsampler 633, the periodicity speed of signal path subsampler 623 changing is for example whenever the 4th output, whenever the 15th output, whenever the 228th output or the like, periodically the output of signal path filter 630 is sampled.If yet sampling rate is set at 1 equably, promptly each result is sampled, can omit noise path subsampler 223 fully.In addition, the sampling rate of signal path subsampler 633 needn't be identical with the sampling rate of noise path subsampler 223.

Comparator 645 is then according to parameter and the signal parameter of some threshold condition comparison based on noise, to have determined whether suitably picked up signal.Determine according to this threshold value, comparator 645 output mode Control Parameter, whether this pattern Control Parameter indication receiver 1 should be in and obtain or tracing mode.Preferably, if output signal is higher than threshold value, then receiver 1 should be in tracing mode, and if output signal is lower than threshold value, then receiver 1 should switch to obtaining mode.

Though show comparator 645 in this embodiment, yet optional embodiment can use more complicated processor to come the processing signals parameter and based on the parameter of noise, to produce the pattern Control Parameter.For example, sort processor can be carried out the nonlinear mathematics function to signal parameter with based on the parameter of noise, and uses the Control Parameter of deterministic model as a result of this mathematical function.

Preferably select noise may estimate with the optimum that relevant noise and signal strength signal intensity are provided with 630 with signal path filter 620.In the preferred embodiment that obtains controller 545, leak integration filter and be used as noise path filter 620, and bipolar infinite impulse response filter is used as signal path filter 630.In the preferred embodiment of lock detector 550, moving average filter is used as noise path filter 620 and signal path filter 630.Yet also can use various other filters.

Fig. 7 A is based on the module map of the leakage integration filter of the preferred embodiment of the present invention.Shown in Fig. 7 A, leaky integrating device comprises first blender 705, and adder 710 postpones 715 and second blender 720.

In operation, leak integration filter and on first blender 705, receive input signal, wherein it is calibrated with the first proportionality coefficient G.The input signal of calibration then is sent to adder 710, wherein the feedback signal addition that itself and second blender 720 are provided.The output of adder 710 is as the filtering result, and also is provided for and postpones 715.The output of delay 715 then is provided for second blender 720, wherein according to the second proportionality coefficient H it is calibrated.So leak integration filter according to following equation work.

y _n＝Gx _n+Hy _n-1 (1)

X wherein _nBe the current numerical value of input signal, y _nBe filtering result's current numerical value, y _N-1Be filtering result's last numerical value, and G and H are respectively first and second proportionality coefficients.

The first and second proportionality coefficient G and H be preferably all less than 1, so that provide stability for filter.In an optimum embodiment, following equation is set up:

G＝α (2)

H＝(1-α) (3)

Wherein α is the real number less than 1.Yet can use the optional numerical value of the first and second proportionality coefficient G and H.

Fig. 7 B is based on the module map of the moving average filter of the preferred embodiment of the present invention.Shown in Fig. 7 B, moving average filter comprises first to the 3rd and postpones 725,730 and 735, adder 740 and calibration blender 745.

In operation, the embodiment of the moving average filter of Fig. 7 B postpones to receive input signal on 725 first, and the propagation delay signal postpones 730 and 735 by the second and the 3rd.Input signal and first to the 3rd postpones 725,730,735 first to the 3rd inhibit signals of exporting respectively and is provided for adder 740 as input.These 4 numerical value are added together on adder 740, and passing ratio coefficient D calibration in calibration blender 745.Proportionality coefficient equals 1/4 in this embodiment.So shown in equation (3), moving average filter is to the current numerical value of input signal, and the result of preceding 3 numerical value of input signal averages.

y_{n} = \frac{x_{n} + x_{n - 1} + x_{n - 2} + x_{n - 3}}{4} - - - (4)

Y wherein _nBe current filtering result, x _nBe the current numerical value of input signal, x _N-1, x _N-2And x _N-3Be preceding 3 numerical value of input signal.

In this embodiment, 4 numerical value of input signal are averaged to obtain the filtering result.In optional embodiment, can increase or reduce this quantity as required.And, though proportionality coefficient D equals 1/4 in this embodiment, yet can easily it be changed over any desired numerical value, comprise 1.If (D=1), then can omit calibration blender 745.

Fig. 7 C is based on the module map of the bipolar infinite impulse response filter of the preferred embodiment of the present invention.Shown in Fig. 7 C, infinite impulse response filter comprises first and

second adders

750 and 755, the first and second and postpones 760 and 765 and first and

second blenders

770 and 775.

In operation, infinite impulse response filter receives current input signal x on first adder 750 _n, wherein it is obtained current output signal y mutually with correction coefficient C _nThen postpone 760 and 765 delay output signals, to obtain the first and second delay output signal y respectively by first and second _N-1And y _N-2In the first and

second calibration blenders

770 and 775, pass through the first and second proportionality coefficient β respectively ₁And β ₂These numerical value are calibrated.The output that then deducts the second calibration blender 775 in second accumulator 755 from the output of the first calibration blender 770 is to produce correction coefficient C, and then correction coefficient C is fed to first adder 750.According to the first and second delay output signal y _N-1And y _N-2, and the first and second proportionality coefficient β ₁And β ₂Numerical value, this corrected value C can be plus or minus.So infinite impulse response filter is according to following equation work.

y _n＝x _n+(β ₁y _n-1-β ₂y _n-2) (5)

X wherein _nBe the current numerical value of input signal, y _nBe filtering result's current numerical value, y _N-1And y _N-2Be that filtering result's first and second postpones numerical value, and β ₁And β ₂Be respectively first and second proportionality coefficients.

It preferably from the output of the first calibration blender 770, deducts the output of the second calibration blender 775, although can be opposite in optional embodiment.Similarly, can provide additional delay and rate-aided signal with calculation correction coefficient C.

Fig. 7 D is based on the module map of finite impulse response (FIR) (FIR) filter of the preferred embodiment of the present invention.Shown in Fig. 7 D, moving average filter comprises first to the 3rd and postpones 772,774 and 776, first to fourth calibration blenders 778,780,782 and 784, adder 786 and the 5th calibration blender 788.

In operation, the embodiment of the FIR filter of Fig. 7 D postpones to receive input signal on 722 first, and the propagation delay signal postpones 774 and 776 by the second and the 3rd.First to the 3rd inhibit signals of input signal and from first to the 3rd delay 772,774,776 outputs are respectively offered first to fourth calibration blender 778,780,782 and 784 respectively as input.

First to fourth calibration blender 778,780,782 and 784 is respectively by first to fourth proportionality coefficient α ₁, α ₂, α ₃And α ₄Its respective input signals is calibrated.First to fourth output signal of calibrating blender 778,780,782 and 784 then is provided for adder 786, and adder 786 is added together with them.Then in the 5th calibration blender 788 by the 5th proportionality coefficient E to calibrating with number.

In this embodiment, preferably select first to the 5th proportionality coefficient α ₁, α ₂, α ₃, α ₄Respond to mate preferred input filter with E.Equation (6) shows y when the 5th proportionality coefficient E that uses 1/4 _nThe output equation:

y_{n} = \frac{α_{1} x_{n} + α_{2} x_{n - 1} + α_{3} x_{n - 2} + α_{4} x_{n - 3}}{4} - - - (6)

In this embodiment, to 4 numerical value calibration of input signal with obtained the filtering result mutually.In optional embodiment, can increase or reduce this quantity as required.And proportionality coefficient E can be an any desired numerical value, comprises 1.If (E=1), then can omit the 5th calibration blender 788.

Fig. 8 is the more detailed module map of the UWB transceiver of Fig. 1.As shown in Figure 8, the UWB transceiver comprises antenna 800, transmitter/receiver (T/R) switch 805, front end 15, dispenser 810, a plurality of correlators 20 ₁-20 _N, wireless controller and interface 3, encoder 50, waveform generator 45, one groups of filters 815, amplifier 820 and timing generator module 825.Timing generator module 825 comprises output timing generator 825 ₀And a plurality of incoming timing generator 825 ₁-825 _NThis embodiment allows, and a plurality of " rake refers to (fingers) " (also being known as " arm (arms) ") handle input signal simultaneously, thereby improve the speed and the efficient of obtaining and following the tracks of.

Whether sending or receiving according to transceiver, T/R switch 805 is connected to amplifier 820 or front end 15 with antenna 800.In optional embodiment, can omit T/R switch 805 by variety of way, comprise and use discrete transmission and reception antenna.

When by antenna 800 received energies, received energy is coupled to T/R switch 805, and T/R switch 805 sends energy to wireless front end 15 as input signal.Provide input signal to dispenser 810 before, wireless front end 15 carries out filtering, the amplitude of extracting noise and regulating input signal.

Dispenser 810 is divided into N duplicate of input signal with input signal, and to different correlator 20 ₁-20 _NN input signal is provided.Correlator 20 ₁-20 _NIn each corresponding incoming timing generator 825 from timing generator module 825 shown in Figure 8 ₁-825 _NThe receive clock input signal.In these correlators each is corresponding to the difference " rake refers to " of transceiver.

As shown in Figure 8, the incoming timing generator 825 ₁-825 _NReceiving phase and frequency adjustment signal, but fast modulation signal or other control signal also can be received.Wireless controller and interface 3 also can provide control signal (for example phase place, frequency and fast modulation signal or the like) to carry out time synchronized and modulation control to timing generator module 825.The fast modulation control signal can be used to realize for example chirp waveforms, PPM waveform (for example quick time scaling PPM waveform) or the like.

Though not shown, wireless controller and interface 3 are also to for example encoder 50, waveform generator 45, bank of filters 815, amplifier 820, T/R switch 805, front end 15, correlator 20 ₁-20 _N(corresponding to UWB waveform correlator 20 of Fig. 1) or the like provides control signal, so as control example such as amplifier gain, signal waveform, filter passband and mark function (notch functions), optional mediation detection processing, the user code separated, spreading code, overlay code (cover codes) or the like.

During signal obtained, wireless controller and interface 3 were regulated incoming timing generator 825 ₁Phase place input, to attempt making correlator 20 ₁The timing of the signal that identification produces on the receiver, and its timing with arriving signal mated.When received signal and the local signal that produces when the time is consistent each other, wireless controller and interface 3 detect high signal intensity or high SNR, and begin tracking, make that receiver and received signal are synchronous.

In case synchronously, receiver can be operated in tracing mode, wherein by continuous phase adjusted series adjusted incoming timing generator 825 ₁, to offset incoming timing generator 825 ₁Any timing difference with input signal.Yet a feature of the present invention is that by detecting phase-adjusted average on the known time section, wireless controller and interface 3 are regulated incoming timing generator 825 ₁Frequency, make that phase-adjusted average is zero.

Frequency is adjusted in this case, because can find at incoming timing generator 825 according to phase-adjusted pattern ₁And there is frequency shift (FS) between the clock of received signal.Can be at incoming timing generator 825 ₂-825 _NLast execution similar operations makes receiver each " rake refer to " can recover to be delayed different values, for example the signal of the delay that causes of multipath (being the scattering along different paths that local reflected by objects causes).

One of the transceiver of Fig. 8 is characterised in that, it comprises a plurality of tracking correlators 20 ₁-20 _NBy a plurality of correlators are provided, can obtain some advantages.The first, can realize synchronously (that is, by operating parallel associated arm group) more apace to find the strong SNR point in different code-discs (code-wheel) segmentation.The second, during receiving operator scheme, a plurality of arms can be resolved and the different multi-path components that lock onto signal.By relevant addition, the UWB communication system is used and is strengthened received signal from the energy of different multi-path signal components, thereby improves signal to noise ratio.The 3rd, by a plurality of tracking correlator arms are provided, also can use the signal of an arm continuous sweep channel with the signal that obtains being better than just receiving on other arm.

In one embodiment of the invention, if, and when scan arm found that its SNR is higher than the multipath item of another arm that is used to demodulating data, the role of operating rocker was (promptly, arm with higher SNR is used to demodulating data, begins to search and have the arm that hangs down SNR).In this way, the channel conditions of communication system dynamically adapting change.

Wireless controller and interface 3 are never with correlator 20 ₁-20 _NReception information and data are decoded.Wireless controller and interface 3 also provide control signal with control front end 15, for example gain, and filter is selected, and filter is adjusted or the like, and regulates synchronously and follow the tracks of operation by timing generator module 825.

In addition, wireless controller and interface 3 serve as communication link feature of the present invention and use the wireless UWB communication link to carry out interface between other higher layer applications of other function.Some function in these functions comprises for example carries out the scope seek operations, radio telephone, and file-sharing, the PDA(Personal Digital Assistant) function embeds controlled function, and operation or the like is found in the position.

In the transmitter part of the transceiver shown in Fig. 8, output timing generator 825 ₀Also receive phase place, frequency and/or the fast modulation conditioning signal of the UWB waveform that is used to encode from wireless controller and interface 3.Data and user code (passing through control signal) are provided for encoder 50, and wherein under the situation of the embodiment of modulation service time of the present invention, encoder 50 is to output timing generator 825 ₀Transmit command signal (for example Δ t) so that the time that sends pulse according to this to be provided.In this way, can encode the data to the transmission waveform.

When according to the shape of the different pulses of data and/or code modulated, encoder 50 produces command signals with as the difform mode of selecting to be used for producing at waveform generator 45 specific waveforms.For example, data can be combined into a plurality of data bits of every channel symbol.Waveform generator 45 is then at timing generator 825 ₀The special time of indication produces the waveform that requires.By T/R switch 805, before sending by antenna 800, the output of waveform generator is then filtered in bank of filters 815, and amplifies in amplifier 820.

In another embodiment of the present invention, transmitted power is enough low, makes to need not T/R switch 805, and transmitter and receiver just can alternately be closed simply, and another is in running order.And in certain embodiments of the present invention, bank of filters 815 and amplifier 820 all do not need, because the power level and the frequency spectrum that can directly obtain expecting from waveform generator 45.In addition, according to realization of the present invention, bank of filters 815 and amplifier 820 can be contained in the waveform generator 45.

One of disclosed UWB communication system is characterised in that, for example by using high spreading rate, can make the transmission waveform have subcontinuous power circuit, and wherein each wavelet in the waveform almost leans against location privately.This structure allows system to work under ebb voltage, yet produces enough average transmitting power so that effectively work.As a result, the cmos switch of sub-micron (sub-micron) physical dimension for example is operated in 1 volt of cmos switch under the voltage and can be used to direct driven antenna 800, and making does not need amplifier 820.In this way, all wireless device can be integrated on the independent monolithic integrated circuit.

Under some condition of work, system can work under the situation that does not have bank of filters 815.If yet system to work together with for example another wireless system, bank of filters 815 can be used to provide mark function to limit the interference of other wireless system.In this way, system can work with other wireless system simultaneously, thereby the advantage better than conventional equipment is provided, and wherein conventional equipment uses the avalanche-type equipment that is directly connected to antenna, makes it be difficult to comprise therein filter.

Transceiver signal

The operation of the preferred embodiment of above-mentioned transceiver is described referring now to Fig. 9-14.In this embodiment, transceiver uses the two-phase simple venation to bring transmission information.The sequential chart of Fig. 9-11 shows the various arrangements that send signal; The sequential chart of Figure 12 A-14C shows the operation of error channel; And the sequential chart of Figure 15 shows the input signal and the coherent signal of the practical operation that is used for the preferred embodiment of the present invention.

The two-phase pulse

Fig. 9 is based on the sequential chart of the two-phase simple venation swash of wave of the preferred embodiment of the present invention.As shown in Figure 9, each two-phase pulse 900 is to have the posivtive spike of formation located adjacent one another and the signal of negative peak.The polarity of pulse can be inverted as required, and this polarity difference is used to transmission information.

According to a preferred embodiment of the invention, use the data-signal of pulse to send first degree information bit by the simulation chip.Each simulation chip has the setting simulation chip period T of indication chip duration _AcAnd simulate chip frequency F accordingly _Ac(or simulation spreading rate), and comprise the bit of expression information or the independent pulse of partial bit.

Unfortunately, owing to the character of pulse, be very difficult to accurately measure the width of pulse.Yet, be easy to measure the peak-peak pulse width T of pulse relatively _pTherefore, in fact, be necessary to be provided with simulation chip period T _AcPeak-peak pulse width T with pulse _pBetween relation, make the peak-peak pulse width T _pBe configured to be lower than simulation chip period T _Ac, that is:

T _p＜T _ac (7)

In a preferred embodiment, T _pApproximately be T _AcNumerical value 1/9.

Simulation chip period T _AcBe measured as the corresponding peak-to-peak time on the contiguous pulse 900.Can select to simulate the actual beginning and the end point of chip as required, suppose that they are not overlapping with the time interval of pulse 900.Fig. 9 shows an embodiment, wherein simulates chip and is defined by having the dead band part that approximately equates in pulse 900 front and back.Yet in optional embodiment, can change the beginning of simulation chip and the position of end point.In a preferred embodiment, peak-peak pulse width T _pBe about 80ps, and simulation chip period T _AcBe about 770ps.

The simulation code word

Each simulation chip is ranked into the simulation code word together, so that press the specific data rate transmissioning data, wherein each simulation code word is corresponding to the bit or the partial bit of the information that will transmit.The simulation code word has the simulation code word period T of instruction simulation code word duration _Aw, with relevant simulation code word frequency F _AwThis can be corresponding to data rate, although needn't be like this.Figure 10 A and 10B show two examples of simulation code word.

The sequential chart of Figure 10 A shows solid size sheet simulation code word according to a preferred embodiment of the invention.This simple case has the simulation code word that comprises independent simulation chip.In this case, simulation code word period T _AwWith simulation chip period T _AcIdentical (that is, sending simulation chip and simulation code word) according to same frequency.Shown in Figure 10 A, a specific orientation of simulation chip is corresponding to simulation " 1 ", and another orientation of simulation chip is corresponding to simulation " 0 ".This can be opposite in optional embodiment.

The sequential chart of Figure 10 B shows 5 chips simulation code word according to a preferred embodiment of the invention.This embodiment has the simulation code word that comprises 5 simulation chips.In this case, the simulation code word cycle is 5 times (that is, sending the simulation code word according to 1/5 of simulation chip frequency) of simulation chip period.

In other words:

T _aw＝n*T _ac (8)

For n chip simulation code word.So, simulation chip period T _AcSimulate the period T of the simulation number of chips n decision simulation code word of code word with each _Aw

Shown in Figure 10 B, the specific orientation of 5 simulation chips is corresponding to simulation " 1 ", and the contrary orientation that should be orientated is corresponding to simulation " 0 ".The specific selection of chip orientation and arrangement is not crucial in the simulation code word, but can change as required.Importantly simulation " 1 " and simulation " 0 " code word are inverted each other.

A preferred embodiment comprises 13 simulations of each simulation code word chip, and the simulation chip frequency (770ps simulates chip period) of 1.3GHz is set.This causes the simulation code word frequency of 100MHz (10ns simulates the code word cycle), and it is corresponding to the analogue data transfer rate of per second 100 megabit information.

Can change the peak-peak pulse width T as required _p, simulation chip period T _Ac, simulation chip frequency F _Ac, the simulation number of chips n of each simulation code word, simulation code word period T _AwWith simulation code word frequency F _AwVarious parameters like this are to realize the expected performance characteristics of transceiver.For example, Figure 10 A has identical simulation code word period T with the disclosed embodiment of 10B _Aw, no matter simulating number of chips n why not together has.Use in the independent pulse of the embodiment that this means at Figure 10 A and specify simulation code word period T _AwTransmitted power, but in the embodiment of Figure 10 B the expansion on 5 pulses.Optional embodiment obviously can change these parameters as required.

Digital word

The simulation code word can be merged into digital word, and digital word is transmitted the signal data that transceiver sends or receives.In this case, the simulation code word is used as digital chip to produce digital word.So each digital chip has and equals to simulate the code word period T _AwDigital chip period T _DcAnd equal to simulate code word frequency F _AwDigital chip frequency F _DwIn other words:

T _dc＝T _aw (9)

F _dc＝F _aw (10)

By the demand of balanced transmission speed and reliability, determine to be used to form the quantity m of the digital chip of digital word (promptly simulating code word).In its simplest form, digital word can comprise independent digital chip (m=1), so can send according to simulation code word frequency.Along with the raising of the size of digital word, transmission reliability and average transmitting power improve in specified scope, but actual data transfer speed reduces.Figure 11 shows the example of digital word.

The sequential chart of Figure 11 shows 2 chip digital word according to a preferred embodiment of the invention.This embodiment has the digital word that comprises two simulation chips (m=2).In this case, digital word period T _DwBe double (promptly the sending digital word) of digital chip period according to half of the frequency of digital chip.In other words:

T _dw＝m*T _dc (11)

As shown in figure 11, a particular arrangement of two digital code sheets is corresponding to numeral " 1 ", and being inverted corresponding to digital " 0 " of this orientation.Yet the specific selection of digital chip and arrangement are not crucial in the digital word, but can change as required.Though when using opposite arrangement, certain advantage is being arranged aspect the decoding, yet this is dispensable.For example, numeral " 1 " can be made of simulation " 11 ", and numeral " 0 " can be made of simulation " 01 ".

In addition, along with the digital number of chips of each digital word is brought up to above 1, each digital word can surpass binary by the information encoded bit.Be different from simply " 0 " or " 1 " is encoded, binary code word can be to " 0 ", and " 1 ", " 2 " or " 3 ", perhaps any other coding level that digital number of chips allowed of each digital word is encoded.(note: for the simulation code word also is like this.)

Using an advantage of digital word except the simulation code word is the size that can easily change digital word during operation.The simulation number of chips of each simulation code word is fixed in design usually, and the digital number of chips of each digital word can change during operation as required.For example can carry out this operation to change the expectation reliability of transmission.So transceiver can be worked under the maximum data transfer rate that equals analogue transmission speed, perhaps can under the transmission rate that reduces, work, but have bigger reliability.

A preferred embodiment will be simulated code word frequency F _AcBe set to 100MHz (10ns simulation code word period T _Aw), it is corresponding to the analogue data transfer rate of per second 100 megabit information.If the size m of digital word is configured to 1, then with digital word frequency F corresponding to the 100MHz of the numerical data transfer rate of per second 100 megabits _DwSend digital word.If the size m of digital word is configured to 2, then send digital word F with digital word frequency corresponding to the 50MHz (half of simulation code word frequency) of the numerical data transfer rate of per second 50 megabits _DwAlong with the raising of digital word size, digital word frequency and numerical data transfer rate can corresponding reductions.Finally, such size that changes digital word that can be as shown in the figure is up to the expectation balance that obtains data rate and reliability.

The most important thing is, can change this digital word length at different transmission.If interference level is lower and in advance in respect of less mistake, then can select less digital word length m so that the data transfer rate maximum.If yet in advance in respect of a large amount of interference, can select higher digital word length m, the result data transfer rate reduces.

Signal obtains and follows the tracks of

Obtain and follow the tracks of operation referring now to Figure 12 A to 14 description.The sequential chart of Figure 12 A and 12B shows the correlated results of two signals according to the phase difference between the two-phase single pulse signal that imports two-phase single pulse signal and local generation into.Especially, the sequential chart of Figure 12 A shows the local signal that produces in input signal and the UWB transceiver; And the sequential chart of Figure 12 B shows the correlated results that the input signal of Figure 12 A and the local signal that produces are compared.

Shown in Figure 12 A, comprise the input signal 1200 that imports pulse 1202,1204 and 1206 into and be known as T according to certain _AcThe fixed clock of (promptly simulating chip period) arrives at interval.Then to be similar to the mode of importing pulse into, still according to unknown phase skew Φ with respect to input signal _oConstitute the signal 1210 of this locality generation that comprises this earth pulse 1212,1214 and 1216.Then these 2 signals are compared to obtain correlated results, the degree of closeness of the phase place of two signals of described correlated results indication.

In the disclosed preferred embodiment of Fig. 1-8, input signal 1200 arrives antenna 10, and passes front end 15 and obtain correlator 210 with arrival.PFN and timer 2 05, constitute the local signal 1210 that produces according to the signal that receives from timing generator 25.Then, input signal 1200 and the local signal 1210 that produces multiply each other in data mixing device 310 (obtaining blender), and integration is to obtain correlated results in data integrate device 315 (obtaining integrator), and described correlated results is used to obtaining mode.Input signal 1200 and the local signal 1210 that produces in the first and second error channel mixer 405 and 410 (tracking blender) according to multiplying each other two time of delays, and the result is used to obtain error channel (or error signal), wherein when input signal and and phase place near the time, the error channel can be used to determine input signal and the local phase difference between signals Φ that produces _oDuring tracing mode, use this error channel.

Figure 12 B shows input signal and obtains simple version integrator 315 output, produce the correlated results 1220 of pulse as this locality of the function of time (or phase place, if the scanning phase place).This transmission as a result arrives digitial controller 230 by first A/D converter 220, and digitial controller 230 uses this result to determine the degree of correlation.

When the phase alignment of input signal 1200 and the local signal 1210 that produces is good, in obtaining correlator 210, there is maximal correlation.At first, do not know two signals whether (synchronously) aligned with each other.So what this earth pulse 1212,1214,1216 that produces in PFN and the timer 2 05 can be positioned in the input signal 1200 shown in Figure 12 A imports pulse 1202,1204 into, between 1206.

Under the out-of-alignment situation of this phase place, the magnitude of output of obtaining correlator 210 is less, this means that signal has less correlated results.Relevant maximum in order to make, the phase place of the phase controller 325 of change PFN and timer 2 05 back under the control of digitial controller 230 is up to obtaining local signal that produces 1210 and input signal 1200 homophases in the correlator 210.

If the signal to noise ratio (snr) from the output of obtaining correlator 210 does not surpass assign thresholds T _R, then digitial controller 230 sends signal to regulate the phase place of the local signal 1210 that produces to phase controller 325.Similarly, this earth pulse 1212,1214,1216 slip phase places are being obtained in the correlator 210 up to them and to be aimed at (synchronously) with importing pulse train into, and therefore realize maximal correlation.

Figure 12 B shows in obtaining correlator 210 input signal and produces the correlated results 1220 of pulse with this locality as the function of time (or phase place, if the scanning phase place).In fact, the magnitude of the output of correlator 210 is input signal and the local phase difference between signals Φ that produces _oFunction.

SNR threshold value T is set _R, to be used for discerning the specific part with expectation degree of correlation of correlation function.At the appointed time (or phase place) goes up and checks correlated results 1220, up to the relevant exemplary SNR threshold value T that surpasses _RPart be found.Be correlated with above exemplary SNR threshold value T _RThe phase place place, can think that receiver and input signal are synchronous.

Clear for what illustrate, supposition inbound data stream 1200 comprises all same orientation of pulse in Figure 12 B.Yet the bi-phase modulated data can not influence this discussion.And Figure 12 B only shows the coherent signal that does not have additive noise.

As put shown in 1222, when the phase alignment of signal is good, relevant maximum.In addition, 1222 surpass magnitude threshold value T together with relevant adjacent part _RCan change threshold value T as required _RTo realize the degree of correlation of expectation.In fact, when the higher or lower degree of correlation of needs, can revise threshold value T during operation _R

The simplified timing diagram of Figure 13 shows the amplitude of error signal, and it is input signal and the local phase difference between signals Φ that produces _oFunction.As shown in figure 13, error channel 1300 is such signals, and it has wherein input signal and the local very different flat site F of signal phase that produces, wherein input signal and local two the approaching slightly curve regions C of signal phase that produce ₁And C ₂And wherein input signal and the local very approaching approximately linear area L of signal phase that produces.

In the disclosed embodiment of Fig. 1 to 5, the error channel is corresponding to the output of following the tracks of correlator 215.Follow the tracks of correlator and on a phase place, mix input signal and the local signal that produces, this phase place have institute's phase place that obtains amount of setting before with the phase place that the obtains amount of setting afterwards.

If error channel 1300 is in range of linearity L, its magnitude and input signal and the local phase difference between signals that produces are proportional.In case it leaves range of linearity L, error channel 1300 becomes the bad estimation of phase difference.

As shown in figure 13, if the amplitude of the calculating difference between early stage tracking signal and the later stage tracking signal is zero, then input signal is zero with the local phase difference between signals that produces, and does not need to carry out correction (the some P on the error channel ₁).If the amplitude of the calculating difference between early stage tracking signal and the later stage tracking signal is positive A ₊, then the phase place of the local signal that produces and the phase place of input signal depart from a value Φ at assigned direction ₊(the some P on the error channel ₃).If the amplitude of the calculating difference between early stage tracking signal and the later stage tracking signal is negative value A _-, then the phase place of the local signal that produces and the phase place of input signal in the opposite direction depart from a value Φ _-(the some P on the error channel ₂).

The definite shape of error curve, and how to determine that phase difference then can depend on the realization of following the tracks of correlator 215.

Figure 14 A shows the work of tracing mode at the correlation curve of Figure 12 B to the sequential chart of 14C.Shown in Figure 12 B, when the SNR of coherent signal (being amplitude in this case) surpasses threshold value T _RThe time, obtain input signal.Ideally, when the amplitude of coherent signal is maximum this situation can appear.Yet more likely coherent signal is positioned at above threshold value T _RPoint on, rather than maximum.In addition, though picked up signal on desired phase at first, however certain may take place and slides in phase place during operation, certain position that causes acquisition point to slide into being different from maximum point on the correlation curve.

Therefore, in case obtain input signal, receiver 1 just leaves obtaining mode to enter tracing mode.In tracing mode, follow the tracks of correlator 215 and determine whether the phase place of the local signal that produces is correct, too high or too low, and specify relevant indication of how to proofread and correct.

Figure 14 A illustrates 3 possible conditions that are used to obtain phase place to 14C.In Figure 14 A, obtain phase place Φ _A1Be positioned at ideal point; In Figure 14 B, obtain phase place Φ _A2After ideal point; And in Figure 14 C, obtain phase place Φ _A3Before ideal point.In each case, we investigate phase place departed from the point of the amount of setting τ and phase place departs from same magnitude τ after obtaining phase place point before obtaining phase place.How the polarity indication of the slope of the line of drawing between these 2 points should change is obtained phase place, and which kind of degree ground change the indication of the value of slope should obtain phase place.

Figure 14 A shows such situation, wherein first obtains phase place and is selected as Φ _A1, cause first to follow the tracks of phase place Φ _T1Obtain phase place Φ first _A1Previous value τ, and second follow the tracks of phase place Φ _T2Obtain phase place Φ first _A1Value τ afterwards.First obtains phase place Φ _A1Corresponding to the first acquisition point A on the correlation curve ₁And the first and second tracking phase place Φ _T1And Φ _T2Correspond respectively to the first and second trace point T on the correlation curve ₁And T ₂

In Figure 14 A, first acquisition point is on the maximum point of correlation curve, so first to obtain phase place be quite correct.As a result, the first and second trace point T ₁And T ₂On correlation curve, has identical value.Therefore, the first and second trace point T ₁And T ₂Between the line drawn have zero slope, this indication does not need to change first and obtains phase place Φ _A1

Figure 14 B shows such situation, wherein second obtains phase place and is selected as Φ _A2, cause the 3rd to follow the tracks of phase place Φ _T3Obtain phase place Φ second _A2Previous value τ, and the 4th follow the tracks of phase place Φ _T4Obtain phase place Φ second _A2Value τ afterwards.Second obtains phase place Φ _A2Corresponding to the second acquisition point A on the correlation curve ₂And the third and fourth tracking phase place Φ _T3And Φ _T4Correspond respectively to the third and fourth trace point T on the correlation curve ₃And T ₄

In Figure 14 B, second obtains phase place Φ _A2Be higher than the value that it should have, this means the second acquisition point A ₂Value be lower than maximum point on the correlation curve.In addition, the 3rd trace point T ₃Value be higher than the 4th trace point T ₄Therefore, the third and fourth trace point T ₃And T ₄Between the line drawn have negative slope, this indication should reduce second and obtain phase place Φ _A2In addition, obtain phase place Φ when second _A2When further slipping away ideal point, the third and fourth trace point T ₃And T ₄Between the slope of line can reduce, phase place Φ is obtained in this indication second _A2Must be reduced bigger value.

Figure 14 C shows such situation, wherein the 3rd obtains phase place and is selected as Φ _A3, cause the 5th to follow the tracks of phase place Φ _T5Obtain phase place Φ the 3rd _A3Previous value τ, and the 6th follow the tracks of phase place Φ _T6Obtain phase place Φ the 3rd _A3Value τ afterwards.The 3rd obtains phase place Φ _A3Corresponding to the 3rd acquisition point A on the correlation curve ₃And the 5th and the 6th tracking phase place Φ _T5And Φ _T6Correspond respectively to the 5th on correlation curve and the 6th trace point T ₅And T ₆

In Figure 14 C, the 3rd obtains phase place Φ _A3Be lower than the value that it should have, this means the 3rd acquisition point A ₃Value be lower than maximum point on the correlation curve.In addition, the 5th trace point T ₅Value be lower than the 6th trace point T ₆Therefore, the 5th and the 6th trace point T ₅And T ₆Between the line drawn have positive slope, this indication should improve the 3rd and obtain phase place Φ _A3In addition, obtain phase place Φ when the 3rd _A3When further slipping away ideal point, the 5th and the 6th trace point T ₅And T ₆Between the slope of line can increase, this indicates the 3rd to obtain phase place Φ _A3Must be enhanced bigger value.

So, have that to obtain the indication meeting of slope of the circuit between two trace points of phase place both sides about appointment very useful.The error channel that is in range of linearity L among Figure 13 a kind of estimation that comes to this.As long as input signal and the local phase difference between signals Φ that produces _oEnough little, make the error channel be in range of linearity L, the error channel signal just can be used to calculate the slope of two lines between the trace point, and this slope can be used to indicate the phase place that should how to change the local signal that produces.

By obtaining 3 phase retardations (each value τ of all on phase place, being separated by) of the local signal that produces, can carry out this analysis.First signal (postponing value 0 τ) is used as early stage tracking signal; Secondary signal (postponing value 1 τ) is used as and obtains signal; And the 3rd signal (postponing value 2 τ) is used as the later stage tracking signal.Postpone 505,510 and 515 by having first to the 3rd, in the embodiment of Fig. 1-5, reach this purpose.Yet in optional embodiment, delay can be provided for input signal, and can transmit the local signal that produces without changing ground.

As shown in Figure 5, early stage tracking signal is provided for first and follows the tracks of blender 405, and the later stage tracking signal is provided for second and follows the tracks of blender 410, and wherein the two all receives the duplicate of input signal.The result of these 2 married operations is sent to and follows the tracks of adder 415 to obtain difference.In the preferred embodiment of Figure 4 and 5, from the result of the first tracking blender 405, deduct the result of the second tracking blender 410.This point is just in order to carry out graphic extension shown in the figure.Can easily carry out opposite operation, wherein from the result of the second tracking blender 410, deduct the result of the first tracking blender 405.In this case, unique difference is from the polarity of the signal of following the tracks of adder 415 outputs opposite.

Figure 13 shows from following the tracks of the error tracking results of integrator 420 outputs, and it is the function of input signal and the local phase difference between signals that produces.This transmission is as a result passed through second A/D converter 230 to arrive digitial controller 230, digitial controller 230 uses these results to determine actually to obtain phase place and the desirable degree of closeness of obtaining phase place, and should how to change and actually obtain phase place so that its more approaching ideal is obtained phase place.

Transceiver operations

The sequential chart of Figure 15 shows the input signal and the coherent signal of the practical operation that is used for the preferred embodiment of the present invention shown in Fig. 1-7.

Signal properties

For being used for the transceiver of Fig. 1 to 7, the sequence of the most handy shape modulation wavelet produces the UWB signal, wherein also can modulation shape modulate the time of occurrence of wavelet.For analog-modulated, use at least one in the analog signal modulation shape Control Parameter.More generally, wavelet has M kind possibility shape.Digital information is encoded into uses one of M wavelet shape and time of occurrence or its to make up transmission information.

In the above-described embodiments, each wavelet uses two shapes of for example two-phase to transmit a bit.In other embodiments of the invention, each wavelet can be configured to transmit q bit, wherein M 〉=2 ^qFor example, 4 shapes can be configured to transmit 2 bits, for example by quadrature phase or 4 grades of amplitude modulation(PAM)s.In another embodiment of the present invention, each wavelet is " chip " in the code sequence, and wherein sequence transmits one or more bit as a group.The chip level of code can be a M unit, wherein may select the shape from M at each chip.

At chip or wavelet level, embodiments of the invention produce the UWB waveform.By various technology modulating uwb waveforms, described technology is including but not limited to (i) bi-phase modulated signal (+1 ,-1), (ii) multistage biphase signaling (+1 ,-1, + a1 ,-a1 ,+a2 ,-a2..., + aN ,-aN), (iii) quadrature phase signal (+1 ,-1, + j ,-j), (iv) multi-phase signals (1 ,-1, exp (+j π/N), exp (j π/N), exp (+j π 2/N), exp (j π 2/N), ..., exp (+j π (N-1)/N), exp (j π (N-1)/N)), (v) multistage multi-phase signals (a _iExp (j2 π β/N) | a _i∈ 1, and a1, a2..., aK}, β ∈ 0,1..., N-1}), (vi) frequency modulation(FM) pulse, (vii) pulse position modulation (PPM) signal (may send identical shaped pulse), (the viii) modulation waveform g of M unit with different candidate's time slot _Bi(t), B wherein _i∈ 1 ..., the M} and (ix) combination in any of above waveform, for example the leggy channel symbol that sends according to the signaling schemes of warbling.Yet various equivalent modifications is appreciated that, the present invention is applicable to that the modification of above modulation scheme and other modulation scheme are (for example at Lathi, " Modem Digital and Analog Communications Systems ", Holt, Rinehart and Winston, describe in 1998, here with reference to the full content of quoting the document).

Some example waveform and correlation properties equation are described now.For example, the time modulation product can be defined as follows.Make t _iIt is the time interval between (i-1) individual pulse and i the pulse.Therefore, the total time to i pulse is

Ti = Σ_{j = 0}^{i} t_{j} .

Can be at data, part spreading code or user code, or its certain make up code signal T _iFor example, signal T _iCan be equally spaced, or part spreading code, wherein T _iCorresponding to warbling, i.e. T _iThe zero crossing of sequence, and for the predetermined set of a and k,

T_{i} = \sqrt{\frac{i - a}{k}} .

Here, also can from finite aggregate, select a and k according to user code or coded data.

Can use the modulation of M unit to describe embodiments of the invention.Following equation 11 can be used to represent the sequence of exemplary transmission or received pulse, and wherein each pulse is the UWB wavelet g of shape modulation _Bi(t-T _i).

x (t) = Σ_{i = 0}^{\infty} g_{B_{i}} (t - T_{i}) - - - (12)

In the equation in front, i pulse in the UWB pulse train that subscript i represents to send or receive.Wavelet function g has M possibility shape, so B _iExpression from data to the sequence in one mapping in the M unit modulation shape of i pulse.Wavelet generator hardware (for example the UWB waveform generator 45) has some control lines (for example from wireless controller and interface 3), and it controls wavelet shape.Therefore, B _iCan be considered in the look-up table M combined indexes, this M combination results M expected wavelet shape at control signal.Encoder 21 data splittings stream and sign indicating number are to produce M unit state.In waveform correlator 5 and wireless controller and interface 9, carry out demodulation to revert to initial data stream.Time location and wavelet shape are combined into pulse train, with transmission information, realize user code or the like.

In above-mentioned situation, signal comprises from i=0 to infinitely-great wavelet.Along with increasing progressively of i, produce wavelet.Following equation 13 can be used to represent general wavelet impulse function, can change its shape one by one pulsedly with transmission information or realization user code or the like.

g_{B_{i}} (t) = Re (B_{i, 1}) \cdot f_{B_{i, 2}, B_{i, 3}, . . .} (t) + Im (B_{i, 1}) \cdot h_{B_{i, 2}, B_{i, 3}, . . .} (t) - - - (13)

In above-mentioned equation, function f definition basic wavelet shape, and function h is the Hilbert conversion of function f.B parameter _{I, 1}Be value and the plural number of phase place, the i.e. B that allows to regulate each wavelet pulse _{I, 1}=a _i∠ θ _i, wherein from the finite aggregate of amplitude, select a _i, and from the finite aggregate of phase place, select θ _iParameter { B _{I, 2}, B _{I, 3}... } and the general parameter group of expression control wavelet shape.

Example waveform sequence x (t) can be based on a series of wavelet pulse shape f, and this series wavelet pulse shape is the derivative as the Gaussian waveform of following equation 14 definition.

f_{B_{i}} (t) = Ψ (B_{i, 2}, B_{i, 3}) (\frac{d^{B_{i, 3}}}{{dt}^{B_{i, 3}}} e^{- {[B_{i, 2} t]}^{2}}) - - - (14)

In above-mentioned equation, function ψ () is with f _Bi(t) peak absolute value is normalized into 1.B parameter _{I, 2}Control impuls time delay and centre frequency.B parameter _{I, 3}Be derivative quantity (number ofderivatives), and control bandwidth and centre frequency.

Another example waveform sequence x (t) can be based on a series of wavelet pulse shape f, and this series wavelet pulse shape is the Gauss's weighting SIN function as 15 definition of following equation.

f_{B_{i, 2}, B_{i, 3}, B_{i, 4}} = f_{ω_{i}, k_{i}, b_{i}} (t) = e^{- {[b_{i} t]}^{2}} \sin (ω_{i} t + k_{i} t^{2}) - - - (15)

In above-mentioned equation, b _iThe control impuls time delay, ω _iControl centre's frequency, and k _iThe control chirp rate.Except that Gauss, be equally applicable to other exemplary weighting function of the present invention and comprise for example rectangle, Hanning, Hamming, Blackman-Harris, Nutall, Taylor, Kaiser, Chebychev or the like.

Another example waveform sequence x (t) can be based on a series of wavelet pulse shape f, and this series wavelet pulse shape is the contrary exponential weighting SIN function as 16 definition of following equation.

g_{B_{i}} (t) = (\frac{1}{e^{\frac{- (t - {t 1}_{i})}{. 3 * {tr}_{i}}} + 1} - \frac{1}{e^{\frac{- (t - t 2_{i})}{. 3 * {tf}_{i}}} + 1}) \cdot \sin (θ_{i} + ω_{i} t + k_{i} t^{2}) - - - (16)

{ B wherein _{I, 2}, B _{I, 3}, B _{I, 4}, B _{I, 5}, B _{I, 6}, B _{I, 7}, B _{I, 8}}={ t1 _i, t2 _i, tr _i, tf _i, θ _i, ω _i, k _i}

In above-mentioned equation,, open speed by tr control by the t1 control forward position opening time.Along the shut-in time, control shutdown rate by t2 control back by tf.Suppose and warble in the beginning of t=0 place, and T _DBe impulse time delay, then by θ control start-phase, by ω control initial frequency, by k control chirp rate, and by ω+kT _DThe control stop frequency.The exemplary allocations of communication resources of parameter values is ω=1, tr=tf=0.25, t1=tr/0.51, and t2=T _D-tr/9.

The invention is characterized in that the M unit parameter set of selecting to be used to control wavelet shape closes to form UWB signal, wherein the centre frequency f of the power spectrum of g (t) _cSatisfy 2f with bandwidth B _c＞B＞0.25f _cShould be noted that conventional equation is defined as sine and cosine term with homophase and orthogonal signalling (for example being commonly referred to as I and Q).Yet an important discovery is that this conventional definition is inadequate for the UWB signal.The present invention recognizes, uses this conventional definition can cause DC offset problem and abominable performance.

In addition, this insufficiency along with bandwidth away from .25f _cAnd trend 2f _cAnd run down.Exemplary wavelet is (or at for example U.S. Patent application 09/209 of common pending trial, the wavelet of describing in 460, here with reference to having quoted the content of this patent application) determinant attribute be, select each parameter, make f and h in the equation 12 all not have the DC component, and f and h show the relative bandwidth of the required broad of UWB system.

Similarly, as B＞.25f _cThe result, should be noted that the time delay of the matched filter output of UWB signal has only a spot of cycle usually, even have only the single cycle.

Define compression (the being coherent matched filter) pulse duration of UWB wavelet referring now to Figure 15.In Figure 15, the time domain version of wavelet is represented g (t), and G (ω) expression fourier transform (FT) version.Therefore, matched filtering is expressed as G* (ω), and promptly complex conjugate makes matched filter be output as P (ω)=G (ω) G* (ω).By P (ω) being carried out contrary fourier transform (IFT) to obtain p (t), promptly the output of matched filter in the time domain is observed in compression or matched filtering pulse.Pass through T _CThe width of definition compression pulse p (t), T _CThe envelope E (t) that is compression pulse goes up than the time between the point of low 6 dB of its peak value, as shown in figure 16.Can determine envelope waveform E (t) by following equation 17.

E (t) = \sqrt{{(p (t))}^{2} + {(p^{H} (t))}^{2}} - - - (17)

P wherein ^H(t) be the Hilbert conversion of p (t).

Therefore, above parametrization waveform is the example of UWB wavelet function, wherein can control described UWB wavelet function, has big parameter information at interval with transmission, and described information is used to form has good auto-correlation and cross correlation function.For digital modulation, from based on each parameter of selecting the predetermined tabulation of the encoder that receives the numerical data that to transmit in the parameter.For analog-modulated, dynamically change at least one parameter according to certain function (for example in proportion) of the analog signal that will transmit.

Obtain and follow the tracks of

As mentioned above, in operation, receiver operation is in obtaining or tracing mode.When receiver locked onto input signal, receiver was in tracing mode; Significantly degenerate or also do not have when locked when signal integrity, receiver enters obtaining mode to obtain or to regain signal.

In obtaining mode, import the UWB signal into by antenna 10 receptions.PFN and timer 2 05 produce its order corresponding to the pulse train that offers the sign indicating number that sends signal in this locality.This pulse train then mixes with input signal in obtaining blender 310.Obtain the output that 315 pairs of integrators obtain blender 310 and carry out integration, and the output correlation values, relevant between the pulse train that UWB signal and PFN and timer 2 05 produce imported in this correlation values indication into.When two input signal phase alignment was good, the output of obtaining integrator 315 had maximal correlation numerical value.

At first, do not know whether two signals are aligned with each other.The local stream of pulses that produces in PFN and the timer 2 05 may with input signal homophase not, i.e. the pulse of local stream of pulses appears between the pulse of input signal.In this case, can be less from the correlation values of obtaining integrator 315 outputs.Sufficiently high relevant for obtaining between these 2 signals, phase controller 325 changes the phase place of clock in PFN and the timer 2 05, is obtaining in the blender 310 up to the stream of pulses that produces and is enough closely mating on phase place with input signal.

By using from the threshold value T of the relevant SNR that obtains integrator 315 outputs _RCome this is controlled.If be lower than preset threshold from the relevant SNE that obtains integrator 315 outputs, then digitial controller 230 sends signal to regulate the phase place of the local stream of pulses that produces to phase controller 325.For this reason, the phase place of re-adjustments local oscillator 320 to be being offset the phase place of local stream of pulses, up to itself and the enough homophases of input signal.So local stream of pulses its homophase that slides up to obtaining in the blender 310 and the input signal time alignment, thereby obtains maximal correlation SNR.Determine to occur the point of maximal correlation SNR by in the various acquisition routines any one.

When using term " maximal correlation SNR ", its expression is higher than setting threshold T _RRelevant SNR, rather than absolute maximal correlation numerical value.According to the rank that threshold value is set, the number of the position of " maximal correlation SNR " can change.

When observing relevant SNR with enough quality, promptly observe absolute relevant SNR or with absolute relevant peaks in the time can accepting the point of distance, digitial controller 230 switches so that receiver 1 works in tracing mode.Here, be necessary the pattern of sample of signal point in the output of output by monitoring first A/D converter 220 or numeric data code processor 520, come the signal to noise ratio (snr) of continuous monitoring input signal, keep to accept service quality determining whether, for example have the data rate that to accept bit error rate (BER) (BER).

In a preferred embodiment, first A/D converter 220 is configured to have and equals to simulate code word frequency F _AwSampling rate, thereby the sampling rate of each simulation code word sample is provided.According to the realization of first A/D converter 220, all these samples have the data bit width of 3 to 8 bits.Therefore, import bit into and be have A or-sample point of the noiseless numerical value of A, wherein A is a signal amplitude.Amplitude A is represented input signal " 1 ", and amplitude-A represents input signal " 0 " (by " 1 " expression).Yet because the noise in the input signal, bit mode in fact amplitude A and-change around the A.

Because different coding or signal inversion, the explanation of input signal can change.For example, in optional embodiment, amplitude A can easily be represented input signal " 0 ", and amplitude-A can represent input signal " 1 ".

Signal power can be expressed as bit mode absolute value average square, this corresponding to the compression of UWB signal after amplitude.Come designated noise power by the variance around this average.In order to determine whether suitably to follow the tracks of, be necessary to measure SNR to determine that signal has enough SNR.

In a preferred embodiment of the invention, input signal is a biphase signaling, and promptly it communicates by anti-phase and noninverting channel symbol.(A/ σ) specifies BER ideally by function Q, and wherein A is a signal amplitude, and σ is a noise standard deviation.As an example, if tolerable BER is 10 ^-2(make 100 import into allow 1 mistake in the bit), then system can remain on tracing mode, imports 1 error of bit into as long as be lower than per 100.

For bi-phase modulated, BER is relevant with SNR.Recognize this point, the inventor has realized estimation SNR, makes it possible to determine for certain preferred operation mode, the mechanism and the process of promptly obtaining or following the tracks of.System hereto, it is x that order receives sample _i=b _iA+ σ n _i, b wherein _iBe bit value, b _i{ 1,1}, A are signal amplitudes to ε, n _iBe the white Gauss noise of zero-mean, unit variance, σ is the standard deviation of noise component(s).If A/ σ is greater than 2.3, then | x _i| statistical property and A+ σ n _iStatistical property approximate identical.Therefore, absolute value rationally approach into

|x _i|≈A+σn _i (18)

When A/ σ enough big, promptly greater than about 2.3 o'clock.

Mode controller of the present invention has been realized finite state machine.Figure 16 is based on the state diagram of the mode controller of the preferred embodiment of the present invention.Mode controller comprises initial state 1600, obtains state 1601 and tracking mode 1602.

In obtaining state 1601, obtain controller 545 and during obtaining operator scheme, obtain input signal.In tracking mode 1602, during tracking modes of operation, error channel controller 555 is followed the tracks of input signal, the SNR of lock detector 550 supervisory signals.By determining when that mode controller should switch between state, and what pattern receiver should be in, the numerical value drive pattern controller of variables L.So L is the pattern Control Parameter.

In operation, mode controller is from initial condition 1600.Obtain then picked up signal in state 1601 of controller 545, and repeat to determine the numerical value of L.

In this preferred embodiment, threshold value is obtained in required setting if SNR is higher than picked up signal, and L is configured to equal 1, and if SNR be lower than and obtain threshold value, L is configured to equal-1.So if L=-1, mode controller 540 remains on state 1601, and if L=1 then switches to tracking mode 1602.This process constantly repeats during operation, switches to tracking mode 1602 (promptly up to L=1) up to mode controller 540.

In case mode controller 540 switches to tracking mode 1602, error channel controller 555 is tracking signal then.Here lock detector 550 repeats to determine the numerical value of L once more.

In this preferred embodiment, if SNR is higher than and keep follows the tracks of required setting and follow the tracks of threshold value, L is configured to equal 1, and if SNR is lower than the tracking threshold value, L is configured to equal-1.So if L=1, mode controller 540 remains on state 1602, and if L=-1 then switches the state of obtaining 1601 of getting back to.Constantly repeat this process during operation.

In other embodiments, mode controller 540 also can comprise a plurality of tracking modes, as shown in figure 17.Figure 17 is based on the state diagram of the mode controller of the optional preferred embodiment of the present invention.In the embodiment of Figure 17, mode controller 540 comprises initial state 1700, obtains state 1701 an and N tracking mode, and is illustrated to 1708 as state 1702.In this case, N is the integer greater than 1.

Be similar to the mode controller 540 of Figure 16, the mode controller 540 of Figure 17 is then obtaining state 1701 picked up signal from initial condition 1700.Obtain with reference to obtaining to carry out as described in the state 1601 as the front.

After obtaining, mode controller 540 is come the 1st tracking mode 1702, wherein calculates L.In the embodiment of Figure 16, if SNR is higher than and keep follows the tracks of required setting and follow the tracks of threshold value, L is configured to equal 1, and if SNR is lower than the tracking threshold value, L is configured to equal-1.

If L=1, mode controller 540 remain on the 1st tracking mode 1702; If L=-1, mode controller 540 switch to the 2nd tracking mode 1704.Then determine the numerical value of L once more.If mode controller 540 calculates L=-1 continuously, mode controller 540 switches to N tracking mode 1708 by the 3rd tracking mode 1706 always.The 1st tracking mode 1702 can be considered to initial tracking mode, and the 2nd to N tracking mode 1704 to 1708 can be considered to intermediateness.When being in these intermediatenesses, receiver still is in tracing mode.

If yet at N tracking mode 1708L=-1, mode controller 540 is jumped out N tracking mode 1708 and is turned back to the state of obtaining 1701.Here, mode controller 540 indication receivers regain signal.After obtaining, mode controller 540 turns back to the 1st tracking mode 1702 with control, and repeats this process.

When mediating tracking mode 1704 to 1708, the numerical value of L=1 causes switching to tracking mode (i-1) from tracking mode i.So mode controller can recover to come out from the bad brief period of signal integrity.

The function of middle tracking mode 1704 to 1708 is to prevent to skip to immediately when receiver receives burst noise the state that obtains again.Mode controller 540 is configured to improve the steepness of wireless performance curve, and guarantees not occur unexpected signal non-locking.So it needs the long time to become non-locking, and curve becomes precipitous.These intermediatenesses allow receivers to bear intermittently faults and need not to enter the state of obtaining.The increase of intermediateness number or minimizing can be regulated the time quantum required to the tracing process release.

This function is particularly useful when having burst error.These burst errors cause the faults of short time to increase.If yet signal be easy to unlock, these intermittent bursts mistakes can cause signal to enter the frequent state that obtains again, thereby reduce system throughput.Can in the programmable processor of for example ASIC, realize Figure 16 and 17 required mode controllers 540.

Tracking mode in the middle of the preferred embodiment of the mode controller state machine that Figure 17 describes can comprise 3.According to the time quantum that recovers the bad cycle from signal integrity to come out to be allowed, optional embodiment can select more or less intermediateness.

Mode controller-first preferred embodiment

The embodiment of Fig. 6 shows such situation, and wherein mode controller 540 is determined according to the estimation of signal and noise power whether receiver 1 should be in and obtained or tracing mode.This is determined from calculating two parameter: signal strength signal intensity s ₁Estimation and noise plus signal intensity n ₁Estimation.Figure 18 is the module map of the specific embodiment that obtains controller 545 or lock detector 550 of Fig. 6.In this embodiment, the first and the 3rd proportionality coefficient K ₁And K ₂Be configured to 1, and the second proportionality coefficient K ₃Be configured to K.Because (K ₁=K ₃=1), the first and the

3rd calibration blender

615 and 640 has been omitted.The operation of obtaining controller 545 or lock detector 550 is described below.

Equation 19 shows s ₁Calculating, sample x wherein adds up on one group of B bit of input signal _i, and then ask square.Similarly, equation 20 shows n ₁Calculating, x wherein adds up on one group of B bit of input signal _iSquare.

s_{1} = {(Σ_{i = 1}^{B} | x_{i} |)}^{2} - - - (19)

n_{1} = Σ_{i = 1}^{B} x_{i}^{2} - - - (20)

Locking parameter L determines whether signal satisfies the SNR requirement.It is 1 probability that the locking constant K influences L, i.e. the signal threshold value that must satisfy.So, for acceptable SNR, s ₁Should compare n ₁Exceed a coefficient that equals to lock constant K.Similarly, this process compares s in equation 21 ₁And n ₁If signal power is sufficiently more than noise power, then L=1 represents to have enough SNR.On the contrary, enough big if signal power is compared with noise power, then L=-1 represents the SNR deficiency.

L＝sign(s ₁-Kn ₁) (21)

Here, s ₁And n ₁It is stochastic variable.Equation 22-24 shows s ₁, n ₁And s ₁-Kn ₁Expectation numerical value, equation 18 wherein | x _i| in substitution equation 19 and 20, and obtain estimating numerical value.

E (s_{1}) = E [{Σ_{i = 1}^{B} (A + k_{i} σ)}^{2}]

= E [B^{2} A^{2} + σ^{2} Σ_{i - 1}^{B} k_{i}_{2} + 2 BAσ Σ_{i = 1}^{B} k_{i}]

= B^{2} A^{2} + B σ^{2} - - - (22)

Wherein ki is zero-mean and unit variance, E[(∑ k _i) ²]=B and E[∑ k _i]=0.

E (n_{1}) = E [Σ_{i = 1}^{B} {(A + k_{i} σ)}^{2}]

= E [{BA}^{2} + σ^{2} Σ_{i - 1}^{B} k_{i}_{2} + 2 Aσ Σ_{i = 1}^{B} k_{i}]

= {BA}^{2} + {Bσ}^{2} - - - (23)

Similarly, k _iItem is by abbreviation.So,

E(s ₁-Kn ₁)＝B ²A ²+Bσ ²-KBA ²-KBσ ²

＝BA ²(B-K)-Bσ ²(K-1) (24)

For guaranteeing at most of the time L=1 E (s ₁-Kn ₁)＞0.Ground of equal value,

\frac{A^{2}}{σ^{2}} > \frac{K - 1}{B - K} - - - (25)

Because BER is the function of SNR, mode controller is regulated so as to entering the BER threshold value of the state of obtaining by the numerical value of K and B in the change equation 25.This mathematical analysis provides power for pattern control procedure and mechanism, and is low-cost because its allows, the realization of high reliability.

Shown in the embodiment that describes in the equation 19 to 25, noise and

signal path filter

620 and 630 are the moving average filters that carry out sub sampling with coefficient B.Yet in optional embodiment, also can use different filters.In this case, equation 19 to 25 can be changed to adapt to the behavior of selected filter.In addition, if the first and the 3rd proportionality coefficient K ₁And K ₂Be configured to equal to be different from 1 numerical value, then will be added in the equation that needs corresponding to the new constant of these numerical value.

As shown in figure 18, in operation, import into and sampled data stream x _iPass absolute value block 610, and determine to import into the absolute value of sampled data stream | x _i|.Then in parallel computation, use the absolute value of calibration input signal | x _i| determine the relevant n of estimation of noise ₁Estimate s with signal ₁

By in first squarer 615, asking the absolute value of calibration input signal | x _i| square and then in noise path filter 620 to square carrying out filtering, determine the relevant n of estimation of noise ₁Then noise is correlated with and estimates n in the second calibration blender, 625 passing ratio COEFFICIENT K ₁Calibrate, and the relevant estimation of calibration noise Kn ₁Be provided for comparator 645.The numerical value of K is preferably in and is configured at first corresponding to expectation BER.

By in signal path filter 630 at the absolute value of setting on the sample of quantity the calibration input signal | x _i| carry out filtering, and then in second squarer 635, ask filtering signal square, determine that signal estimates s ₁Signal is estimated s ₁Then be provided for comparator 645.Alternatively, also can before offering comparator 645, estimate to calibrate to signal.

At comparator 645 places, comparison signal is estimated s ₁With the relevant estimation of calibration noise Kn ₁To determine the probability of blocked input signal.This relatively produces locking parameter L.L is imported into mode controller state machine 1805.As described in reference Figure 16 and 17, according to this signal, mode controller state machine 1805 or remain on current state perhaps switches to different conditions.

The numerical value of comparator 645 output L, this numerical value determines whether signal has and will obtain the enough quality that obtain under the state, and perhaps whether signal has can keep enough quality of locking under tracking mode.Therefore need in equation 24, reduced value directly not calculate, because 24 numerical value that are used to set K of equation.Of equal valuely, can set the numerical value of K according to analog result empirically.This normally is used to noise and

signal path filter

620 and 630 o'clock employed technology at more complicated filter.

Figure 19 shows the performed step of mode controller state machine 1805 of Figure 18 according to the embodiment of the mode controller 540 of Fig. 6, wherein no matter is that to be in the state of obtaining 1601,1701 still be tracking

mode

1602,1702,1704,1706,1708 (shown in Figure 16 and 17).

Regardless of initial state, mode controller state machine 1805 is all carried out following steps.At step S1902, gather one group of bit B in the input signal.Use B sample of this group,

current state

1601,1602,1701,1702,1704,1706 or 1708 calculate one group of intermediate parameters S1904.According to these intermediate parameters, calculate output parameter at step S1906, and provide this output parameter with as exporting at step S1908.

Intermediate parameters is signal parameter and noise relevant parameter preferably.They can be the s of first preferred embodiment description of front reference pattern controller ₁And n ₁The second and the 3rd preferred embodiment as following reference pattern controller is also described in conjunction with Figure 22, and they also can be l and g, or l ₁And g ₁Can constantly monitor these parameters, or can sample according to setting cycle.

Be preferably in " in the band " and calculate intermediate parameters.In other words, in identical bandwidth, calculate them.

In a preferred embodiment, output parameter is the pattern Control Parameter that is known as locking parameter L, and its value is 1 or-1.Whether locking parameter L pointing-type controller state machine 1805 should switch to new state, and what state is new state can be.

As Figure 16 and 17 and related description shown in, locking parameter L indicates B sample of this group whether to have the high SNR that enough switches to new state.In the embodiment of Figure 16 and 17, sufficiently high SNR can cause having the L of numerical value 1, and this numerical value can cause mode controller state machine 1805 to move to tracking mode, or switches to lower tracking mode.Similarly, enough low SNR can cause having the L of numerical value-1, and this numerical value can cause mode controller state machine 1805 to move to higher tracking mode, or switches to the state of obtaining.

When being in different conditions, the operation meeting of mode controller state machine 1805 is different slightly.Especially, when being in when obtaining state, compare when being in tracking mode, can slightly differently carry out the step S1906 that calculates output parameter.

In the embodiment that does not use the sub sampling moving average filter, can constantly monitor intermediate parameters, promptly signal parameter and noise relevant parameter are to detect the appearance of effective keyed end.In certain embodiments, noise and

signal path filter

620 and 630 can be finite impulse response (FIR) (FIR) or infinite impulse response (IIR) filter.

The example of this embodiment uses the form that has Fig. 7 C and describe, the IIR traffic filter 620 that is designed to have the impulse response of closely mating with the autocorrelation pulse shape of Figure 12 B.So, in the signal estimation path of Figure 18, use and approach matched filter.

Also can use equivalence, this scheme is used FIR filter or the iir filter with different structure.The example of the filter that uses in the noise associated pathway of Figure 18 is the moving average filter of the leakage integration filter shown in Fig. 7 A or Fig. 7 B.Also can use the FIR and the iir filter of other form.

The chart of Figure 20 is according to the behavior of probability curve that controller or lock detector show each numerical value of K of obtaining of Figure 18, and wherein the sub sampling moving average filter is used to noise and signal path filter 620 and 630.In this embodiment, the selected numerical value of B is 16, and carries out sub sampling with 16 pairs of filters of coefficient.According to these curves as can be known, bigger K value is driven into-1 of lower BER place with L.As mentioned above, the BER in this exemplary embodiment is configured to 10 ^-2This means and allow per 100 to import into 1 mistake is arranged in the bit.If BER arrives or greater than 10 ^-2, then on average, mode controller drives receiver and obtains new signal.Because obtain is being " costliness " aspect the loss system throughput, therefore selects to obtain constant K _A, make 10 ^-2The probability of the L=1 of BER place is higher.For currently preferred embodiment, (K=50).

The performance curve of the mode controller state machine 1805 of tracking mode in the middle of Figure 21 shows and has 3 among Figure 18.(referring to Figure 17.) lockout controller uses (B=16) and (K=50).By calculating the par that after being introduced into tracking mode, enters the required bit of the state of obtaining, produce this curve.According to this curve as can be known, 10 ^-2The BER place, system can unlock in 1,000 ten thousand bits.This curve significantly improves, and makes 10 ^-3The BER place, system keeps locking in the extremely long time.

Mode controller-second preferred embodiment

Figure 22 shows the optional embodiment that obtains controller 545 or lock detector 550 of mode controller among Fig. 5.As shown in figure 22, obtain controller 545 or lock detector 550 comprises absolute value block 2205, first filter 2210, first subsampler, 2213, the first calibration blenders, 2215, the first squarers 2220, second squarer 2230, second filter, 2235, the second subsampler, 2238, the second calibration blender 2240 and comparators 2245.

The processes that take place in the

tracking mode

1602,1702 based on the tracking mode machine of the lock detector 550 of Figure 22 are described in Figure 16 and 17 by example.In this embodiment, calculate SNR by calculating two parameter l and g.Equation 26 has illustrated the expectation numerical value that how to calculate l, supposes that wherein first filter 2310 is moving average filters.Equation 26 has illustrated the expectation numerical value that how to calculate g, supposes that wherein second filter 2335 is moving average filters.

l = \frac{1}{B} Σ_{i = 1}^{B} | x_{i} |

E (l) = E [\frac{1}{B} Σ_{i = 1}^{B} | x_{i} |]

= E [A + \frac{1}{B} σ Σ_{i = 1}^{B} k_{i}] = A - - - (26)

g = \frac{1}{B} Σ_{i = 1}^{B} {| x_{i} |}^{2}

E (g) = E [\frac{1}{B} Σ_{i = 1}^{B} {| x_{i} |}^{2}]

= E [A^{2} + \frac{1}{B} 2 Aσ Σ_{i = 1}^{B} k_{i} + \frac{1}{B} σ^{2} Σ_{i = 1}^{B} k_{i}^{2}] = A^{2} + σ^{2} - - - (27)

l ²Power estimator signal.G-l ²Estimating noise power.So according to definition, equation 28 shows the direct estimation of SNR.

\frac{l^{2}}{g - l^{2}} \approx \frac{A^{2}}{A^{2} + σ^{2} - A^{2}} = \frac{A^{2}}{σ^{2}} - - - (28)

Because BER is the function of SNR, as mentioned above, can determine and monitor SNR corresponding to expectation BER.When SNR is brought down below target level T _hThe time, mode controller can detect unlocked state by locking parameter L.Similarly, the present invention compares SNR and target level in equation 29.

As shown in figure 22, import bit stream x in absolute value block 2205 receptions _i, wherein absolute value block 2205 is calculated and is imported bit stream x into _iAbsolute value.This absolute value is then filtered in first filter, and multiply by definite l mutually with proportionality coefficient 1/B in the first calibration blender 2215.Then this numerical value of l is carried out square to determine numerical value l2.By asking x at second squarer 2230 _iSquare, and in second filter 2235, determine numerical value g to square carrying out filtering.This output is multiplied each other with 1/B in the second calibration blender 2240.Comparator 2245 then compares l and g to determine locking parameter L.Locking parameter L is provided for controller, and wherein mode controller uses locking parameter L to determine that receiver should be in tracing mode or obtaining mode.As shown in figure 17, tracking mode can comprise a plurality of sub-states, makes that state controller also can be with receiver between the sub-state of a plurality of tracking, and follows the tracks of and obtain between the state and move.

Can between first filter 2210 and the first calibration blender 2215, provide first subsampler 2213.First subsampler 2213 is periodically sampled to the output of first filter 2210, and wherein periodically speed can change, for example whenever the 4th output, whenever the 15th output, whenever the 228th output or the like.If yet sampling rate is set at 1 equably, promptly each result is sampled, can omit first subsampler 2213 fully.Similarly, can between second filter 2235 and the second calibration blender 2240, provide second subsampler 2238.As mentioned above,, promptly each result is sampled, then can omit second subsampler 2238 fully if its sampling rate is set at 1 equably.First and second subsampler 2213 needn't be identical with 2238 sub sampling time.

Shown in the embodiment that equation 26 to 29 is described, first and second filtering 2210 and 2235 are adders.Yet in optional embodiment, also can use different filters.In this case, equation 26 to 29 can be changed to adapt to the behavior of selected filter.

Mode controller-Di three preferred embodiments

Figure 23 shows another optional embodiment that obtains controller 545 or lock detector 550 of the present invention, wherein the deterministic model controller whether should be in obtain or tracing mode before use the AGC initialization.During the AGC initialization, estimating noise standard deviation v.

When coming initialization AGC by the measurement noise variance, quantization level might be directly changed into BER.For example, if noise variance is configured to certain any number by AGC control, then the amplitude of the input signal of A/D converter output means and the proportional SNR of this amplitude.The proportionality constant depends on the level that noise variance is set.This numerical value is directly changed into BER.So, before obtaining, noise variance being set at signal, quantization level is directly changed into BER.

By using the noise standard deviation v of this estimation, mode controller 540 can monitor simply from the input signal x of first A/

D converter

220 or 520 outputs of numeric data code processor _iTo determine suitable pattern.

The noise standard deviation of estimating calibrated and with input signal x _iThrough filtering (may also pass through sub sampling) absolute value compare.Such L that calculates shown in equation 30:

L＝sign(q-K ₅v)， (30)

Wherein q is filtering (may also the pass through sub sampling) absolute value that imports bit stream into, K ₅Be proportionality coefficient, and v is the noise standard deviation of estimating.

As shown in figure 23, obtain controller 545 or lock detector 550 comprises absolute value block 2305, filter 2310, subsampler 2315, calibration blender 2220 and comparator 2225.

On absolute value block 2305, receive and import bit stream x into _i, wherein absolute value block 2305 is calculated and is imported bit stream x into _iAbsolute value.Then in filter 2310, this absolute value is carried out filtering to determine the numerical value of q.The numerical value of the noise standard deviation v that on calibration blender 2320, receive to estimate, and with proportionality coefficient K ₅Multiply each other.

Comparator 2245 then compares q and K ₅V is to determine locking parameter L.Locking parameter L is provided for controller, and wherein mode controller uses locking parameter L to determine that receiver should be in tracing mode or acquisition model.As shown in figure 17, tracking mode can comprise a plurality of sub-states, makes that state controller also can be with receiver between the sub-state of a plurality of tracking, and follows the tracks of and obtain between the state and move.

Can between filter 2310 and comparator 2325, provide subsampler 2315.Subsampler 2215 is periodically sampled to the output of filter 2310, and wherein periodically speed can change, for example whenever the 4th output, whenever the 15th output, whenever the 228th output or the like.If yet sampling rate is set at 1 equably, promptly each result is sampled, can omit subsampler 2215 fully.

If initial Noise Variance Estimation v is underestimated, then SNR looks and can be better than its actual value.On the other hand, if initial Noise Variance Estimation v is over-evaluated, then SNR looks and can be inferior to its actual value.But owing to can periodically update Noise Variance Estimation v by the distribution that monitors absolute value data when being in tracing mode, Noise Variance Estimation v finally can converge to reasonable numerical value.

Though show 3 different embodiment at mode controller, yet they should be considered to exemplary and limited.Other embodiment can be arranged.In addition, can make up as required various embodiment and with obtain and tracking and matching, to satisfy the requirement obtain and follow the tracks of.

In bigger system, use transceiver

Can be used to carry out wireless communication functions referring to figs. 1 through the 8 UWB transceivers of describing, so that carry out interface with different application as the part of stack-protocol architecture.In this structure, very alike with wired I/O port, the UWB transceiver is carried out as the signal at the communication service of using and is produced, transmission and receiving function, and described application sends data and receives data from transceiver to transceiver.In addition, the UWB transceiver can be used in various device any one radio communication function is provided, described equipment can comprise by the interconnection to miscellaneous equipment of cable technology or wireless technology.So the UWB transceiver of Fig. 1 can be used as the part of the Local Area Network that is connected and fixed structure, or connect for example part of the wireless personal domain network of mobile device (WPAN).

In any this realization, the technical staff in microprocessor system field obviously can realize all or a part of the present invention easily in the microprocessor system of the conventional general purpose microprocessor that uses instruction according to the present invention to programme.The technical staff of software field understands that obviously ordinary procedure person can easily prepare appropriate software according to instruction of the present invention.

Figure 24 illustrates the processor system 2400 based on the preferred embodiment of the present invention.In this embodiment, processor system 2400 comprises processor unit 2401, display 2415, one or more input equipment 2417, cursor control 2419, printer 2421, network link 2423, communication network 2425, master computer 2427, Internet protocol (IP) network 2429 and mobile device 2431.Processor unit 2401 comprises bus 2403, processor 2405, main storage 2407, read-only memory (ROM) 2409, memory device 2411 and communication interface 2413.Optional embodiment can omit various unit.

Bus 2403 is transmission information in entire process device unit.It is data/address bus or be used to other communication agency of the information that transmits preferably.

Processor 2405 is connected and process information with bus 2403.

Main storage 2407 can be random access storage device (RAM) or other dynamic memory (for example dynamic ram (DRAM), static RAM (SRAM) (SRAM), synchronous dram (SDRAM), fast erasable RAM).It preferably is connected to bus 2403 with stored information and the instruction that will be carried out by processor 2405.In addition, main storage 2407 also can be used to the term of execution storage temporary variable or other average information of the instruction carried out at processor 2405.

ROM 2409 can be simple read-only memory, also can be another kind of static memory devices (for example programming ROM (PROM) can be wiped PROM (EPROM) and electric erasable PROM (EEPROM)).It is connected to the instruction of bus 2403 and storage static information and processor 2405.

Memory device 2411 can be a disk, and CD or any other are suitable for storing the equipment of data.It is provided and is connected to bus 2403, and stored information and instruction.

Processor unit 2401 also can comprise special purpose logic devices (for example application-specific integrated circuit (ASIC) (ASIC)) or configurable logic device (for example simple programmable logical device (SPLD), CPLD (CPLD) or Reprogrammable field programmable gate array (FPGA)).Other removable media device (CD for example, tape and removable magneto optical disk medium) or fixedly the high-density medium driver can be added on the processor unit 2401 that uses suitable device bus (for example small computer system interface (SCSI) bus strengthens integrated device electronic technology (IDE) bus or super direct memory visit (DMA) bus).Processor unit 2401 can also comprise optical-disc reader, and CD reads-writing unit, or the CD planter, and wherein each can be connected to identical device bus or another device bus.

Processor system 2401 can be connected to display 2415 by bus 2403.Display unit can be a cathode ray tube (CRT), and LCD (LCD) or any other are suitable for the equipment to the system user display message.Display 2415 can be controlled by display or graphics card.

Processor system 2401 preferably is connected to comprise and is used for to the input equipment 2417 of processor 2405 transmission information and command selection and one or more equipment of cursor control 2419.One or more input equipment can comprise keyboard, keypad or be used for the miscellaneous equipment of transmission information and command selection.Cursor control 2419 can be mouse, trace ball, and cursor direction key or be used for to processor 2405 direction of transfer information and command selection, and be used to control any suitable equipment that moves of cursor on display 2415.

In addition, printer 2421 can provide the printing tabulation of processor system 2401 storages and/or the data structure that produces or any other data.

One or more sequence of one or more instruction that comprises in the memory that answer processor 2405 is carried out such as main storage 2407, processor unit 2401 is carried out some or all treatment steps of the present invention.Can this instruction be read the main storage 2407 from another computer-readable medium of for example memory device 2411.One or more processor in the multiprocessing structure also can be used to carry out the command sequence that comprises in the main storage 2407.In optional embodiment, can use hard-wired circuit to replace software instruction or combination with it.So embodiments of the invention are not limited to any particular combinations of hardware circuit and software.

As mentioned above, processor unit 2401 comprises instruction according to the present invention programmes, and is used to comprise data structure described herein, form, at least one computer-readable medium or the memory of record or other data.By being stored in any one computer-readable medium or its combination, the present invention comprises the software that is used for control system 2401, is used for driving arrangement to realize software of the present invention and to be used for permission system 2401 and the mutual software of human user.This software can be including but not limited to device driver, operating system, developing instrument and application software.This computer-readable medium also comprises computer program of the present invention, is used to carry out realize that all or part of being finished when of the present invention (is distributed if handle) handles.

Computer code devices of the present invention can be any explanation or executable code mechanism, including but not limited to script, and interpretable programs, dynamic link library, Java or other OO class and complete executable program.In addition, the various piece of processing of the present invention can be distributed, to obtain good performance, reliability and/or cost.

Term used herein " computer-readable medium " is meant that participation provides instruction so that any medium of carrying out to processor 2405.Computer-readable medium can adopt many forms, including but not limited to non-volatile media, easily loses medium and transmission medium.Non-volatile media comprises for example CD, disk, and magneto optical disk, and for example memory device 2411.Easily lose medium and comprise dynamic memory, for example main storage 2407.Transmission medium comprises coaxial cable, and copper cash and optical fiber include the lead that comprises bus 2403.Transmission medium also can have sound wave or light wave, for example the ripple that produces during radio wave and infrared data communication.

The common form of computer-readable medium comprises for example hard disk, floppy disk, tape, magneto optical disk, PROM (EPROM, EEPROM, fast erasable EPROM), DRAM, SRAM, SDRAM or any other magnetizing mediums, CD (for example CD-ROM), or any other optical medium, punch card, paper tape, or other has the physical medium of sectional hole patterns, carrier wave, carrierfree transmission, or any other medium that can be read by system.

Various forms of computer-readable mediums can be used for providing one or more sequence of one or more instruction so that carry out to processor 2405.For example, can on the disk of remote computer, carry instruction at first.Use modulator-demodulator, remote computer can be used to realize all or part instruction of the present invention to the long-range loading of dynamic memory by telephone wire, and sends instruction.The modulator-demodulator of system 2401 this locality can receive data by telephone wire, and uses infrared transmitter that data transaction is become infrared signal.The Infrared Detectors that is connected to bus 2403 can receive the data that infrared signal is transmitted, and data are sent on the bus 2403.Bus 2403 is to main storage 2407 Data transmission, and processor 2405 takes out data and execution command from main storage 2407.Alternatively, before or after being carried out by processor 2405, the instruction that main storage 2407 receives can memory device 2411 on.

Communication interface 2413 provides the two-way UWB data communication that is connected to network link 2423, and network link 2423 is connected to communication network 2425.Communication network 2425 can be a Local Area Network, PAN (Personal Area Network) (PAN) or the like.For example, communication interface 2413 can be a network interface unit, and communication network can be the packet switching PAN that supports UWB.Again for example, communication interface 2413 can be the addressable Asymmetrical Digital Subscriber Line of UWB (ADSL) card, and integrated services digital network (ISDN) card or modulator-demodulator are to provide the data communication connection at the communication line of respective type.

Communication interface 2413 also can be included as network link 2423 provides the two-way wireless communication that is different from the UWB connection to connect, or the hardware of hardwired connection.So communication interface 2413 can be introduced the UWB transceiver of Fig. 1 or Fig. 8, with the part of the general-purpose interface that is connected with non-UWB radio communication as the hardwired that comprises at network link 2423.

Network link 2423 is provided to the data communication of other data equipment usually by one or more network.For example, network link 2423 can provide by LAN and arrive master computer 2427, or arrives the connection of the data equipment of service provider's operation, and wherein the service provider provides data communication services by IP network 2429.In addition, network link 2423 can be by communication network 2425 to mobile device 2431, personal digital assistant (PDA) for example, and laptop computer or cell phone provide connection.

Communication network 2425 and IP network 2429 best persons use electric, and electromagnetic or optical signal transmits digital data stream.By the signal of each network transmission and the signal that transmits on network link 2423 by communication interface 2413, transmit numerical datas at system 2401 is the exemplary form of the carrier wave of transmission information.Processor unit 2401 can pass through communication network 2425, and network link 2423 and communication interface 2413 send notice and receive the data that comprise program code.

Obviously, can carry out many modifications and change to the present invention according to above-mentioned guidance.Thereby should be appreciated that within the scope of the appended claims and can realize the present invention by the mode that is different from the mode of clearly describing the front.

Claims

1. a mode controller is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, comprising:

The data dependence clearing cell is used for receiving and imports data-signal into, and output is independent of and imports the data that comprise in the data-signal, the data-independent signals that the intensity of data-signal is imported in indication into into;

Signal path comprises

Be used for the operating data irrelevant signal to determine the first processor of first M signal; With

The first nonlinear function unit is used for first M signal is carried out nonlinear function to determine signal parameter;

The noise associated pathway comprises

The second nonlinear function unit is used for the data irrelevant signal is carried out nonlinear function to determine second M signal;

Second processor is used to operate second M signal to determine the noise relevant parameter; With

The 3rd processor is used for processing signals parameter and noise relevant parameter and imports the pattern Control Parameter of the relative signal intensity of data-signal into to determine indication.

2. mode controller as claimed in claim 1, be used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprise first subsampler between the first processor and the first nonlinear function unit, be used for first M signal of sampling first M signal and sampling to the output of the first nonlinear function unit with first rate.

3. mode controller as claimed in claim 1, be used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprise second subsampler between second processor and comparator, be used for the second speed sampled signal parameter and to the signal parameter of comparator output sampling.

4. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprises the input scaler, is used for before data dependence clearing cell input input signal itself and first proportionality coefficient being multiplied each other.

5. mode controller as claimed in claim 4 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, and wherein first proportionality coefficient is a coefficient 2.

6. mode controller as claimed in claim 4 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, and wherein first proportionality coefficient is programmable.

7. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprises the signal path scaler, is used for before comparator input signal parameter itself and second proportionality coefficient being multiplied each other.

8. mode controller as claimed in claim 7 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, and wherein second proportionality coefficient is a coefficient 2.

9. mode controller as claimed in claim 7 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, and wherein second proportionality coefficient is programmable.

10. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprises noise associated pathway scaler, is used for before comparator input noise coherent signal itself and the 3rd proportionality coefficient being multiplied each other.

11. mode controller as claimed in claim 10 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein the 3rd proportionality coefficient is a coefficient 2.

12. mode controller as claimed in claim 10 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein the 3rd proportionality coefficient is programmable.

13. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first processor is first filter.

14. mode controller as claimed in claim 13 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is a finite impulse response filter.

15. mode controller as claimed in claim 14 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is a moving average filter.

16. mode controller as claimed in claim 13 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is an infinite impulse response filter.

17. mode controller as claimed in claim 16 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is to leak integration filter.

18. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second processor is second filter.

19. mode controller as claimed in claim 18 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second filter is a finite impulse response filter.

20. mode controller as claimed in claim 19 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second filter is a moving average filter.

21. mode controller as claimed in claim 18 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second filter is an infinite impulse response filter.

22. mode controller as claimed in claim 21 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second filter is to leak integration filter.

23. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein the data dependence clearing cell is to export the absolute value of input signal with the absolute value element as data-independent signals.

24. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein the first nonlinear function unit be output first M signal square with first squarer as signal parameter.

25. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein the second nonlinear function unit be the dateout irrelevant signal square with second squarer as second M signal.

26. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first processor is an infinite impulse response filter, and second processor is to leak integration filter.

27. mode controller as claimed in claim 26 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein infinite impulse response filter is configured to approach the coherent signal of expectation.

28. mode controller as claimed in claim 1 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first processor is first moving average filter, and second processor is second moving average filter.

29. a mode controller is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, comprising:

Absolute value element is used to receive the absolute value that imports data-signal into and determine to import into data-signal;

Signal path comprises

Be used for the absolute value of data-signal is carried out filtering to determine first filter of first M signal; With

First squarer is used for first M signal is carried out square to determine the noise relevant parameter;

The noise associated pathway comprises

Be used for the absolute value that imports data-signal into is carried out square second squarer with definite second M signal; With

Second filter is used for second M signal is carried out filtering to determine signal parameter; With

Comparator is used for comparison signal parameter and noise relevant parameter and imports the pattern Control Parameter of the relative signal intensity of data-signal into to determine indication.

30. mode controller as claimed in claim 29, be used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprise first subsampler between first filter and first squarer, be used for first M signal being sampled, and export first M signal of sampling to first squarer with first rate.

31. mode controller as claimed in claim 29, be used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprise second subsampler between second filter and comparator, be used for signal parameter being sampled, and export the signal parameter of sampling to comparator with second speed.

32. mode controller as claimed in claim 29 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprises the input scaler, is used for before absolute value element input input signal itself and first proportionality coefficient being multiplied each other.

33. mode controller as claimed in claim 32 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first proportionality coefficient is a coefficient 2.

34. mode controller as claimed in claim 32 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first proportionality coefficient is programmable.

35. mode controller as claimed in claim 29 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprises the signal path scaler, is used for before comparator input signal parameter itself and second proportionality coefficient being multiplied each other.

36. mode controller as claimed in claim 35 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second proportionality coefficient is a coefficient 2.

37. mode controller as claimed in claim 35 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second proportionality coefficient is programmable.

38. mode controller as claimed in claim 29, be used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, also comprise noise associated pathway scaler, be used for before comparator input noise coherent signal, itself and the 3rd proportionality coefficient being multiplied each other.

39. mode controller as claimed in claim 38 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein the 3rd proportionality coefficient is a coefficient 2.

40. mode controller as claimed in claim 38 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein the 3rd proportionality coefficient is programmable.

41. mode controller as claimed in claim 29 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is a finite impulse response filter.

42. mode controller as claimed in claim 41 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is a moving average filter.

43. mode controller as claimed in claim 29 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is an infinite impulse response filter.

44. mode controller as claimed in claim 43 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is to leak integration filter.

45. mode controller as claimed in claim 29 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second filter is a finite impulse response filter.

46. mode controller as claimed in claim 45 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second filter is a moving average filter.

47. mode controller as claimed in claim 29 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second filter is an infinite impulse response filter.

48. mode controller as claimed in claim 47 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein second filter is to leak integration filter.

49. mode controller as claimed in claim 29 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is an infinite impulse response filter, and second filter is to leak integration filter.

50. mode controller as claimed in claim 49 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein infinite impulse response filter is configured to approach the coherent signal of expectation.

51. mode controller as claimed in claim 29 is used to determine to obtain or follow the tracks of the desired operation mode of importing data-signal into, wherein first filter is first moving average filter, and second filter is second moving average filter.

52. a mode controller is used for determining that the ultra-broadband receiver obtains or follow the tracks of the desired operation mode of importing data-signal into, comprising:

Signal path is used to determine to import into the signal parameter of data-signal;

Based on the path of noise, be used to determine to import into the parameter based on noise of data-signal;

Processor is used for processing signals parameter and noise relevant parameter with the deterministic model Control Parameter; With

Controller is used for switching between obtaining mode and tracing mode according to the pattern Control Parameter.

53. mode controller as claimed in claim 52, be used for determining that the ultra-broadband receiver obtains or follow the tracks of the desired operation mode of importing data-signal into, wherein signal parameter is the estimation of signal strength signal intensity, and is the estimation of signal plus noise intensity based on the parameter of noise.

54. mode controller as claimed in claim 52 is used for determining that the ultra-broadband receiver obtains or follow the tracks of the desired operation mode of importing data-signal into, wherein processor is a comparator.

55. mode controller as claimed in claim 52, be used for determining that the ultra-broadband receiver obtains or follow the tracks of the desired operation mode of importing data-signal into, also comprise the signal path scaler, be used for signal parameter is calibrated to produce the rate-aided signal parameter, wherein processor receives rate-aided signal parameter rather than signal parameter.

56. mode controller as claimed in claim 52, be used for determining that the ultra-broadband receiver obtains or follow the tracks of the desired operation mode of importing data-signal into, also comprise the noise path scaler, be used for calibrating based on the parameter of noise to produce the parameter based on noise of calibration, wherein processor receive calibration based on the parameter of noise rather than based on the parameter of noise.

57. mode controller as claimed in claim 52 is used for determining that the ultra-broadband receiver obtains or follow the tracks of the desired operation mode of importing data-signal into, wherein signal path comprises filter.

58. mode controller as claimed in claim 52 is used for determining that the ultra-broadband receiver obtains or follow the tracks of the desired operation mode of importing data-signal into, wherein noise path comprises filter.

59. mode controller as claimed in claim 52, be used for determining that the ultra-broadband receiver obtains or follow the tracks of the desired operation mode of importing data-signal into, also comprise absolute value block, be used to determine to import into the absolute value of data-signal, and to signal path with the absolute value of data-signal is provided based on the path of noise.