CN1434566A - Preparing device and method for imput and set of predistortion comparative signal in amplifier - Google Patents
Preparing device and method for imput and set of predistortion comparative signal in amplifier Download PDFInfo
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Abstract
The present invention relates to preparing device and method for imput and set of predistortion comparative signal in amplifier. The invention relates to a method of preparing signals (X and Y) to be compared to establish predistortion at the input of an amplifier (12), the signals comprising a signal (X) before amplification and a signal (Y) after amplification by said amplifier. Preparation includes time aligning (22) the signal before amplification (X) with the signal after amplification (Y) before using them to establish said predistortion. The invention preferably operates in two stages, namely a stage of coarse time alignment, in which the signal before amplification (X) is subjected to a time delay comprising an integer number of first time units, and a stage of fine time alignment, in which a delay or advance value of a fraction of the first time unit is determined.
Description
Technical field
The present invention relates to the signal processing field, especially proofread and correct the field of the distortion of amplifying the link generation.Link output signal and the feature of importing initialize signal are promptly relatively amplified in described correction, so that determine the distortion of generation.So just can calculate contrary predistortion response, it is added on the input signal,, therefore, can improve the linearity and the electrical efficiency of amplifying link to eliminate described distorted signals.
Background technology
Starting point of the present invention is, amplifies the delay that link produces---this time-delay makes signal and its accurately can't compare (as ignore and amplify the intrinsic distortion of link) between the response, and when causing calculating predistortion, error that occurs can not be ignored and principle restriction.
The error problem that time delay when present pre-distortion technology also can't solve this owing to comparison between the signal produces.
Because signal more generally adopts digital technology, so, must will amplify the analog signal digital of link output at least.This output signal that is digitized at given time t0 promptly is that wherein, Γ is for amplifying the time-delay of link generation to the response (described signal response is because amplifier, more or less distortion to some extent) at amplification link upstream, t0-Γ signal constantly.
Must note in addition, this time-delay is unfixing, its can change with factors such as aging, the temperature of amplifying link, amplifying signal, power and institute's service bands, like this, if only the constant time lag of the comparison signal (reference signal) that amplifies the link upstream side is proofreaied and correct, the effect of this correction is also bad.
Fig. 1 there is shown its each critical piece for the employed a kind of traditional amplification link sketch that predistortion is carried out gamma correction that passes through of electromagnetic wave transmitter.Assembly 2 has a digital pre-distortion unit 4, and its first input 4a receives and treats amplifier digital signal X from one of digital modulation source 6.Pre-distortion unit 4 adds a predistortion on described digital signal X, make it to become a pre-distorted signals X ', and this pre-distorted signals is provided to output 4b.Then, described signal X ' process digital-analog convertor (CNA) 8 converts analog form to, this analog signal is sent to frequency multiplication conversion stage (TX-IF and TX-RF) 10 with emission by described transducer output, the power amplifier 12 that described converter stage starting links to each other with the transmitting antenna (not shown).
The output signal Y of power amplifier 12 sentences and compares through the second input 4c that a negative feedback (loop 14) is sent to digital pre-distortion unit 4.For this reason, there is a RF (radio frequency) end 16 in the loop, the output signal of its input received power amplifier 12, make it be converted to frequency and reduce conversion stage (RX-IF and RX-RF) the 18 receivable forms of utilizing, (even frequency is also inequality in the middle of it) antithesis of the function of described converter stage 18 and converter stage 10.The output signal of converter stage 18 is through analogue-to-digital converters (CAN) 20 digitlizations, and digitized signal Y is transferred to the second input 4c place of pre-distortion unit again.
Transducer CNA 8 and CAN 20 are by importing the signal M é ch at EM place by the time interval at each clock.Signal M é ch has determined the periodicity of signal X to each instantaneous digital value conversion of transducer CNA, and each instantaneous analogue value Digital Cycle, i.e. sample rate of the signal of power amplifier 12 outputs place detection.In an embodiment, signal psi é ch offers two transducer CNA 8 and CAN 20 simultaneously by the phase-locked loop of being supplied with by reference clock φ r é f 21 (being abbreviated as PLL hereinafter, promptly English " phase locked loop " acronym).
Can find out that the signal X and the Y of pre-distortion unit comparison Variable delay may take place, described time-delay may be greater than the cycle of clock φ é ch, and its exact value does not correspond to the integral multiple of described clock cycle.
In present technology, do not do any processing, just directly the Base Band output signal Y of transducer CAN 20 and signal X are compared.
Phasing and sampling time calibration have been carried out between the signal to transducer CNA 8 emissions and transducer CAN 20 receptions, amplify the propagation time of link itself in addition---the described propagation time is not allowed to ignore, and changing, especially because analog filter is arranged, thereby intrinsic calibration (l ' é talonnage intriseque) function is restricted.If time-delay that can control figure formula signal level, if during analog signal level, problem can more bother.
The defective of this time calibration is unfavorable for realizing good predistortion performance with should cost for the modern radio transmission station that is utilized such as third generation cellular system especially.They are encoded a kind of what is called " code division multiple access " (AMRC, english abbreviation are CDMA) type as the electromagnetic wave interface.Consider cost and volume, transceiver base station (english abbreviation is BTS, i.e. " basetransceiver station ") only can use a unique radio transmitting power amplifier 12 to send one or more carrier waves for all users' signal.Therefore, send a speech and promptly comprise whole transmission link in the base station, the numerical portion of existing information of described link and signal processing has again particularly including the pure simulation part of power amplifier; The radio part also includes the described last chain link that sends link.
Adopt some arithmetic technology, though can proofread and correct the predistortion error that causes by described time-delay, can essential heavy computing equipment.Especially, these technology also just are based upon on approximation and the extrapolated value basis, and accuracy is restricted.
Using a kind of optimized new pre-distortion technology is wave chopping technology, can obtain efficiency power amplifier and reach 15% to 17%.
With respect to traditional amplifying technique (English is called " feedforward " (feedforward)), this is a a progressive step, and efficient is about 8% in the described conventional art.In addition, also can reduce cost, and, be substituted in the complex technology that is adopted in high-power simulation and the radio frequency level by digital processing.
But, will be in the face of the power amplifier and the transistor of number of different types and the calibration that minimizes even avoid former factory, pre-distortion system is necessary can be with dynamical fashion, nonlinear change on variation, the especially frequency band of monitoring and correcting power amplifier transfer function, carrier number, temperature, aging, storage effect
Fast, the most the most frequently used method that takes effect all is based on map table, described map table can be determined the anti-non-linear of power amplifier, so that it is applied on the modulation signal, thereby can shield the frequency spectrum on the adjacent channel simultaneously at the required source signal of power amplifier output place initialization the biglyyest.
But no matter their variation how, the algorithm of implementing predistortion table is based on can better duplicating the bandwidth that transmits and the receiver of high linearity.Implement predistortion based on the comparison, that is: the correlation between input signal and the output signal.Emission band and treat linearisation frequency band big more (be at least instant transmission frequency band three to five times), linear gain is directly related more with accuracy of this comparison.These methods all are based upon on classical LMS algorithm (English is " least meansquares ", the i.e. lowest mean square) basis, and its major part relatively is not subjected to the integration of signal to be compared and the influence of gain.But greatest problem still is the time accuracy of delaying between the comparison signal.In fact, the time-delay of the broadband of this problem and " feedforward " formula amplifier is proofreaied and correct similar, and only, predistortion is in a digital environment now.In the case, owing to treat that linearizing frequency band belongs to the broadband, problem thereby complicated more.In fact, if in the frequency band of 60 megahertzes, hope improves linear about 25 decibels of three or four carrier type amplifier UMTS, and then the time-delay that exists between the emission of signal and the measurement sample necessarily can not surpass 10 psecs.Because still there is bigger variation in the timer phase drift, also change in transmission and the reception link component, so this accuracy can not obtain because default correction of producer.
The problem that solves promptly is the method that finds, and can follow the tracks of and the Measuring Time calibration with dynamical fashion, and---preferably low-cost digital technology---proofreaies and correct to use easy device.
Prior art has adopted a kind of high efficiency reflector, and is equipped with an amplitude limiter and a digital pre-distortion unit.Foremost predistortion digital technology is based upon on the servo basis of time, i.e. high linear, broadband (broadband) receiver.Be that they have used intermediate frequency double sampling (error of can avoid gaining supporting (d ' appairage de gain), integration and continuous component), to improve the LMS algorithm that upgrades predistortion table best.
Can affirm that can not be interfered because gain, signal level or integration (in complex plane) between two signals to be compared possibility is inharmonious time calibration.Want the gain inequality between picked up signal X and the Y (as Fig. 1), the method for proposition would not directly be subjected to its influence.Integral error also in like manner.
The LMS algorithm can consider measuring-signal and transmit between phase place rotation and gain inequality.It can influence all plural coefficients in the predistortion table by a constant complex values.This constant value, especially gain component can be detected and eliminate, because usually, during minimum emissive power, gain calibration must be single (first numeric factors in the predistortion table).
Some modification around these methods maybe can improve performance, maybe can simplify enforcement, wherein:
---the so-called LMS technology of simplifying, the complex multiplication that can simplify some sampling rate coefficient is that symbol multiplies each other, and can not reduce convergence rate or linearisation accuracy, and
---two-dimentional predistortion, can solve the broadband problem, for example, the non-linearization that the sample power that has amplified with the instantaneous frequency or the front of signal changes (short term thermal memory effect).
In any case the skew of the lasting component that algorithm must be eliminated need is very sensitive.If what use in the receiver is Base Band CAN transducer, this task can be easy to realize by a simple narrow-band filter.
Prior art does not also solve accurate calibration problem between input signal and the measured signal, and like this, correction just only is confined in ρ 1/2 sample, and, reduce the error of measured signal difference, have only by the CAN technology to obtain fast as far as possible sampling rate, just can make the delay time error minimum.At present, to the frequency modulation of 80MSPS (heterogeneous serial-to-parallel-serial memory) and 15 megahertzes, corresponding linearisation gain-limitation is between 12 to 15 decibels.
If existing a kind of suitable metric system is measured time-delay, can consider another kind of known method:, make it according to adjusting from the signal of measuring receiver with ground able to programme mode source of delay signal.Like this, can use a programmable filter, its gain curve is smooth, delays time to be the sample mark in the required frequency band.Prices are rather stiff for multiplier used in this method, because need sampling rhythm (for example, at the filter of Farrow structural formula described in the patent document WO99/57806).
Summary of the invention
Based on these problems, the objective of the invention is to propose a kind of technology time calibration of the signal from a common signal source, described technology can and improve digital predistortion performance with the dynamical fashion correction, to improve the electrical efficiency of radio performance and radio amplifier in application.
Solution of the present invention is promptly reliable, and implementation cost is low again simultaneously.
Say exactly, according to first purpose, the present invention proposes a signal set-up procedure, more described signal to be setting up the predistortion of amplifier input, described signal comprise one amplify front signal and amplify by described amplifier after a signal,
It is characterized in that described preparation comprises the time calibration of amplifying between preceding and the amplified signal, utilizes them to establish described predistortion again.
Advantageously, described set-up procedure comprises:
---very first time coarse adjustment process, around here, will amplify front signal and postpone a time-delay, promptly the integral multiple of first chronomere is determined described delay value, time delayed signal before described delay produces and amplifies, this signal and amplified signal all have the Best Times calibration, and
---second time accurate adjustment process, around here, determine time lag or the value that shifts to an earlier date, it is a very first time unit fraction value, be applied to amplify it in signal that extracts the back, can obtain with amplify before the calibration of the same Best Times of time delayed signal, described time-delay or in advance value be applied in the amplified signal.
Carry out time ratio signal like this and can be used to set up described predistortion.
In very first time calibration phase, amplifying forward and backward signal can be digital form.
By the reference point between time delayed signal and the amplified signal before the paraphase amplifier amplification, can determine to have the preceding inhibit signal of amplification of Best Times calibration, and/or very first time unit fraction, the described preceding time delayed signal of amplification with Best Times calibration promptly is the signal that point of maximum correlation can be provided.
Therefore, when analyzing reference point, optional pick and place big before several different delayed time forms of time delayed signal, parallel arranged is carried out described analysis, this of time delayed signal is several before amplifying picks out time delayed signal before the amplification with Best Times calibration multi-form.
When analyzing reference point, can be at least one the signal complex representation in the coherent signal, for example, and the complex representation that inhibit signal is formed with real part and imaginary part before the described amplification, amplified signal is represented with real part.
In an embodiment, before the first coarse adjustment stage, amplified signal is digitized as first sampling frequency that harmonic relationships is arranged in the frequency with the amplification front signal.
According at least three reference points---the highest correlation in the corresponding reference point of first reference point, second and third reference point is respectively in the first reference point both sides, can determine to have a correlation curve of time delayed signal before the amplification of Best Times calibration, second time calibration, phase alignment are in the stage, and the sampling time of signal is so relatively:
---if the associated level of second reference point is lower than the associated level that third phase closes point, with respect to time delayed signal before amplifying, and the sampling time of delay amplifier amplified signal, and
---if the associated level of second reference point is higher than the associated level that third phase closes point, with respect to time delayed signal before amplifying, shifts to an earlier date the sampling time of amplifier amplified signal,
Otherwise or,
So that between second and third reference point to about equally an associated level convergence.
Determine correlation, the signal and the symbol of amplified signal on the other hand late time the before the one side that only needs to consider amplifier is amplified, described correlation is based upon on the calculating basis of the symbol unanimity between these two kinds of signals.
Best, to a phase control sample frequency, second stage promptly is the amplified signal digitlization, changes described sampling phase selectively, the time calibration of time delayed signal and described amplified signal before the amplifier that has a Best Times calibration with increase amplifies.
The described first phase control signal sample frequency can be created in first phase place closed loop output place, makes its variation by the reference frequency that changes described ring with pulse mode.
Advantageously, by one second phase place closed loop, can produce the reference frequency of first closed loop, variable frequency divider branches away frequency from its output frequency after, can be by changing quantity, the reference frequency of the first phase place closed loop is changed, with the described bit comparison mutually of time delayed signal and amplified signal before the amplification that obtains to have the Best Times calibration.
Can flow to the latter again amplifying front signal after the digital-to-analog conversion, conversion is carried out according to the sampled signal that produces in second phase place closed loop output place.
According to second aspect, the present invention relates to a signal preparation device, described signal needs the pre-distortion device through being placed in the amplifier input to handle, the signal after signal comprises an amplification front signal and passes through described amplifier amplification.
It is characterized in that it is included in the time calibration device that amplifies between preceding and the amplified signal.
The present invention can be applicable to described device (second aspect) fully in (first aspect) aspect the selectivity described in the signal set-up procedure.
According to the third aspect, the present invention relates to one and amplify link, described amplification link comprises at least one amplifier and pre-distortion device, described device is installed in the amplifier input, with the forward and backward signal of comparison amplifier distortion, it is characterized in that it comprises according to foregoing second aspect provides the time calibrating installation of input signal to make comparisons.
Amplify the linear power amplifier that link also can be applicable to a wide band radio-frequency reflector,---described bandwidth for example is the frequency band of frequency between 10 to 100 megahertzes, as 60 megahertzes, can launch multi-carrier signal, for example, so-called " code division multiple access " (AMRC) emission of type coding in the mobile phone.
Description of drawings
Hereinafter with reference to the accompanying drawings, describe several preferred forms of the present invention in detail with non-limited way, to be illustrated more clearly in advantage of the present invention and to understand the present invention.
In the accompanying drawing:
---Fig. 1 of having described is the block schematic that a power amplification transmits link, the figure shows a gamma correction that carries out according to the digital pre-distortion unit of known technology;
---Fig. 2 is the block schematic that is similar to the transmission link of Fig. 1, but it includes the time calibration device that amplification link according to the present invention amplifies forward and backward signal in addition;
---Fig. 3 is the block schematic of time calibration device shown in Fig. 2 and the amplifier chain circuit unit controlled thereof;
---Fig. 4 a, 4b and 4c show the correlative relationship that amplifies between anterior signal of link and the amplified signal, with can be to carrying out fine tuning time calibration.
Embodiment
Fig. 2 shows according to an a kind of embodiment with amplification link of predistortion function of the present invention.In described figure, still adopt identical numbering with the same parts of Fig. 1, and explanation no longer in detail, to save length.
In described embodiment, the derived digital signal 6 that amplifies link 100 produces a composite signal, and described signal is made up of some codings and frequency, as meets 3GTP UMTS standard.At this moment, carrier wave is overlapping orthogonal code, and they send information to user separately.In modern technologies, a cell site or determines that antenna field certainly preferably corresponding to unique complete transmission link 100, promptly amplifies link.This means that promptly same amplification link not only can be used for all users' a same carrier wave, also can be used for some carrier waves in public wireless power station.This scheme existing problems, one of reason is: the signal of each carrier wave is not in constant envelope.In fact, since the multi-user overlaps, then the instantaneous power time of signal changes meeting very greatly, and these are different with traditional constant envelope phase modulation or frequency modulation, always the latter's average, instantaneous power equate.Like this, need the size of regulation power amplifier 12, make it even before gamma correction, just have one can utilize linearity, but such extras, consumption additional energy just need acquired.When handling the multiple tracks carrier wave simultaneously, described phenomenon is particularly outstanding, because will make like this by the signal that produces near all carrier waves of its peak value simultaneously and arrive the top as far as possible.
The digital signal X in source 6 exports with pre-distorted signals X ' form through digital pre-distortion unit 4 again.Described signal X ' is sent to a numeral--the input of analog converter 8 (or have two, this depend on Base Band or with digital intermediate frequency).Signal X ' is an analog form in transducer output place, again in intermediate frequency and radio-frequency stage (TX-IF and TX-RF) 10 places conversion once or the several times frequency, is transported to the input of power amplifier 12 at last again, and it can start the transmission antenna.
The dynamic control of predistortion begins from power amplifier output output signal, by negative feedback 14, transmits along a measure link.Described measure link comprises an analog directional coupler 16, and described coupler extracts a part from the output signal of amplifier, and it can implement directional protection, avoiding the interference of the same frequency band signal that antenna trapping arrives, and guarantees impedance matching.Described coupler 16 startings one converter stage 18, it is corresponding to the receiver (XR-IF and XR-RF) that can implement the frequency translation opposite with the converter stage 10 of power amplifier upstream.Frequency variation signal is by analogue-to-digital converters (CAN) 20 digitlizations, and digitlization preferably is transformed to intermediate frequency by so-called double sampling technology.Therefore, transducer CAN has dual-use function: on the one hand, by double sampling, it can extract the signal response (nyquist first district) that is positioned at low-frequency band, and this is just meeting frequency change; On the other hand, it can transmit the digital signal response of low-frequency band.
According to the present invention, after unit 22 processing time calibration, be transferred to the second input 4c place of digital pre-distortion unit 4 again from CAN 20 output signal Y.Time calibration, unit 22 function was: erasure signal Y is with respect to error time calibration (at input 22a place) from the signal X in source 6, like this, correspondingly, for example just can monitor the variation and the drift in the propagation time of the link that causes by variations in temperature, aging, service condition etc.In the case, dynamically monitor time and phase deviation between signal X and the Y, can adopt digital form the sample between them is proofreaied and correct again, thereby can in digital pre-distortion unit 4, under optimum condition, be compared.
Time calibration, unit 22 operation was divided into following two stages:
---the coarse adjustment stage very first time, around here, to amplify front signal (X) and postpone a time-delay, it is the integral multiple of first chronomere, and definite described delay value, time delayed signal (XR) before described delay produces and amplifies, digitized signal (Y) all has the Best Times calibration after extract also for this signal and amplification, and
---the accurate adjustment stage second time,, relatively have the preceding time delayed signal (XR) of amplification and the described signal (Y) after amplifier amplifies of Best Times calibration around here,
The signal of the meticulous comparison of process like this is used for setting up predistortion.
In the phase I, signal X has produced some kinds of signal responses behind the time calibration unit, and they all are the time delayed signal form XR with different delayed time.Each is spaced apart a very first time unit between the time-delay continuously, and obviously, described very first time unit equals the sampling period of signal X ' at the CNA8 place.Each signal response can compare with the time calibration of signal Y.Thereby time calibration, the delay which the most approaching amplification link 12 of time-delay takes place among these time delayed signals responses XR can be determined in unit 22.Described phase place produces first time correlation approximation that accuracy equals 0.5 times of the ρ of very first time unit.So, and the relatively input (the 3rd input 4d) that the described signal response XR of amplified signal (Y) with Best Times calibration can be transferred to digital pre-distortion unit 4 is located.Just in time opposite with traditional schematic diagram of Fig. 1, digital pre-distortion unit 4 no longer the first defeated 4a place, from the signal X in source 6 basis as a comparison, and it is basic as a comparison to import the signal XR at 4c place to the described the 3rd.But can find out that the described first input 4a always is used to provide signal from source 6 so that predistortion to be provided.
In second stage, need the sample time of fine adjustment signal Y, it is adjusted according to response XR with Best Times calibration.For this reason, time calibration, unit 22 acted on the phase place of periodic sampling signal Ivar at the sampling timer input EI place of transducer CAN 20, described phase place thereby answer variable.
The phase variable of sampled signal Ivar makes that described sampled signal is different from the sampled signal of transducer CNA 8, and the latter's frequency and phase place are invariable, need remain with the servo-actuated of ideal long-term frequency between two signals simultaneously.Therefore, need to be equipped with two timing circuit PLL, promptly 24 and 26, they provide sampled signal to CAN 20 and CNA 8 respectively.
In the present embodiment, change the phase place of the sampled signal Ivar of transducer CAN 20, can obtain by the reference signal Ivar.r é f that changes its PLL 24.Described PLL 24, because its filtering ring, its effect is equivalent to an integrator, like this, has caused the phase delay of signal Ivar around the frequency pulse of the interior nominal value N of frequency divider.Described variable reference signal Ivar.r é f results from output place of frequency divider N/N+1/N-128, can change the scale division value N of the described frequency divider of frequency, can be from unit 22 output 22c starting program time calibration, because the average permanent attitude value of setting up always is N.
The timing signal of frequency divider 28 inputs has constituted reference signal Ivar.r é f source, promptly is the sampled signal I é ch by the CNA 8 of PLL 26 generations.Therefore, can draw: reference frequency Ivar.r é f=frequency I é ch/N.
So, the reference clock phase place Ivar-r é f of PLL 24 by changing transducer CAN, can postpone the phase place of the signal Ivar of described transducer CAN 20 with being directly proportional, so just can realize fine tuning, and guarantee the phase place locking between the clock of two transducers 8,20.
The sampling frequency at transducer CAN 20 places generally is about 100 megahertzes, even bigger.This just must have the sampling clock of good light spectral purity, and described clock obtains from the PLL with a reference clock, and described reference clock provides time reference, and can guarantee filtering and spectral purity.
Therefore, preferably the signal that the frequency divider by the output starting of the PLL 26 of transducer CNA 18 is sent is as the benchmark of the PLL 24 of transducer CAN 20, accuracy is just very big like this, because in described time accurate adjustment, the input of one high frequency can obtain bigger accuracy and speed concerning the command N-1 or N+1 of frequency divider 28.
Make in this benchmark control, less relatively at interval, a quick clock that can use PLL 26 to provide.The absolute precision of adjusting is still in digital environment.But phase place is that Be Controlled constantly, because PLL 24 has a filtering ring.Therefore, the absolute quantized interval in PLL 24 adjustment can not cause restriction.Because promptly in instantaneous correction, in other words, promptly in the variable-frequency pulse that will inject, this pulse is relevant with frequency divider stage in unique restriction that the maximum N+1 of frequency divider causes.Frequency divider N is big more, at interval can be more little, and the filtration that PLL bears is more little, but on the contrary, convergence time but can be longer.When ring lock closes, there is one to trade off between convergence time and the residual noise.
Notice that for reducing cost and implementing simple reason, the signal Y of CAN and output place of measurement receiver can do double sampling with respect to the signal X of signal source.Concerning described signal X and predistortion principle antithesis, adopted with respect to the transmission band of signal to be sent one surpass sampling, with the high order harmonic component of control opposite phase.This promptly refers to a wide passband, and sampling frequency for example is higher than the factor of passband 5 to be sent or 7.But embodiments of the invention also can reduce the sampling rate of signal Y, thereby and reduce the cost of transducer CAN 20 and the computational costs in the time calibration unit 22.In general, importantly to the moment of Y sampling and the accuracy of amplitude.Usually, more little to the sampling frequency of Y, determine that the predistortion required time is of a specified duration more, because the convergence rate of predistortion table is relevant with an informational capacity that uses and extract on the signal Y.
The functional part that can implement described two stage time calibration of unit is detail as per Fig. 3,4.
Equally as shown in Figure 3, time calibration, unit 22 input 22b received the digital signal X of the signal source 6 on the Variable delay device 30, and it is with the spacing form of the integral multiple of sampling, and described time-delay mechanism 30 for example is the variable shift register of a quantity.Therefore, spacing is corresponding to foregoing first timer.Therefore, the time delay of signal X should equal to produce the maximum delay that takes place on the amplification of signal Y and the measure link at least.Time-delay mechanism 30 is sent to each first input 32a place of three correlator 32-1,32-2 and 32-3 to three signal response XR respectively, and they each have a different delayed time, for example they are transferred on defeated output of each side of shift register.Offer two sampling periods between the continuous time-delay of correlator interval greater than transducer CAN 20 for the mean value of fine tuning mode signal Ivar.
Therefore, three correlators move with parallel way, determine constantly to provide three reference points one.If make them by the serial-parallel mode operation---promptly repeat three reference points and produce operation, obtain three new delay values, therefore promptly obtain the multiple of three reference points, can obtain more reference points.Certainly, used correlator number is not limit.
The reference point quantity of Jian Liing can be different between the first coarse adjustment stage and the second fine tuning stage like this.
The output signal Y of CAN 20 is transported to each second input 32b (with numeral 32 expressions) of three correlators concurrently.
Therefore, each correlator is set up relevant between signal Y and the inhibit signal XR that specific time-delay is arranged, and like this, three displacement hypothesis continuously (or more) of coarse adjustment phase place can be worked the while concurrently.
Can find out that two signals are Y and X herein, cross-correlation mould or power, be the delay function between these two signals, it gives to detect each time to proofread and correct provides a signal similar tolerance (metrique).Embodiment is such as described in sampling mode, if correlation is a N specimen length, then reference point P (k) (as Fig. 4) is the time-delay sample sum of products of signal X and Y, promptly P (k)=X (0) * Y (k)+X (1) * Y (k+1)+... + X (n) * Y (k+n).
If X and Y are complex signal, reference point P then is the complex function of time-delay k between signal X and the Y; Its modular representation the related power of signal X and Y, phase place is represented the average phase rotation of signal X and Y.
Especially, the real part of signal Y or imaginary part represent and can compare by the correlation and the plural number of the different delayed time X that transmits, and like this, relevant peak is in the correlator window (have three or five points at least, each interval one sampling period) just.
In this process, can in correlator, extract reference point.In Fig. 4, these reference point quantity are five, for example, they are select from 6 reference points of the serial-parallel extraction in service of shown in Figure 3 three correlator 32-1,32-2 and 32-3, and each all can respectively produce two reference points for two delay values described reference point.
The mould of more selected reference point square, just can realize that signal is relatively.
Earlier time delayed signal response XR before the amplification of sample with maximum correlation enters second stage again, and this process acts on the analog to digital compounded link, with the phase place of correction samples clock Ivar, realize the simulation interpolation, but cost may be expensive.
In particular, available Fractional-N frequency device 28 able to programme, differentiator/integrator effect of described frequency divider control PLL is to adjust it with servo mode.The servo feasible interpolation that acts on the clock delay is not open loop.
Confirm that the correlation curve on wide horizontal plane is one bell, there is a syntactics in the inside.The width of clock and gradient thereof depend on the quantification (only is-symbol or mantissa in addition) of X and Y simultaneously, and modulation type, number of carriers and signal frequency range.Fig. 4 a, 4b and 4c have described described phenomenon, wherein:
---Fig. 4 a shows a correlation curve Cret., is used for when the sample time of signal Y is too early, and it understands inhibit signal Ivar,
---Fig. 4 c shows a correlation curve Cav., is used for passing when late when the signal sampling time, and it can shift to an earlier date signal psi var,
---Fig. 4 b shows a correlation curve Ceor., when being used for that signal carried out time calibration, promptly implements accurate adjustment.
These curves result from homogeneity cross-correlation point P*conjP, and described point is the power function of displacement k, with the phase place irrelevant to rotation.
Because correlation curve in true both sides, summit, steep relatively and dull, thereby can contrast symbol according to correlation, for example, poor at the immediate correlation (being respectively a P-1 and P+1 point) of the some P0 and arranged on left and right sides that does not rise to the peak fully determined the phase place of signal Ivar and the change direction of frequency.In this expression, some P0 is corresponding to the best correlation that obtains in the very first time coarse adjustment process, and some P-1 and P+1 are corresponding to the best correlation except that a P0.Therefore, only need utilize the information that symbol reflected of the difference between the maximum left and right sides, just can make corrective system ground towards good direction convergence, by increasing/reduce reference signal frequency Ivar r é f, also being the continuous spacing of phase place of the sampling clock of counter N-1/N/N+1 and 24 couples of transducer CAN 20 of PLL, realize described convergence.
For example, shown in Fig. 4 a, be peak P0 right side reference point P+1, rather than its left side reference point P-1, more near the summit of curve C ret, i.e. (P-1)-(P+1)＜0, this represents the related symbol that what is called " is born ".
On the contrary, shown in Fig. 4 c, peak P0 right side reference point P+1, reference point P-1 compares with its left side, and is farther from the summit of curve C av., i.e. (P-1)-(P+1)＞0, this has represented the related symbol of a what is called " just ".
Certainly, " just ", " bearing " related symbol must be as determining with reference to point left side reference point (P-1) by choosing at random as related entities.
The symbol of Chan Shenging can regularly be detected by master controller 28 like this, and described controller has been determined counter scale value N, N+1, N-1, and it is worked like this:
---when detected symbol was " bearing ", increase value N to reduce the frequency of signal Ivar, promptly postponed its phase place,
---when detected symbol is " just ", reduce to be worth N,, promptly shift to an earlier date its phase place to increase the frequency of signal Ivar.
This control is repeating with the loop form, all value N adjusted at every turn, and up to the condition time calibration of picked up signal XR and Y, i.e. (P-1)=(P+1) (as Fig. 4 b).For avoiding occurring vibration or drift phenomenon in the control loop, can determine a permissible range of absolute time calibration, in view of the above, when error is lower than a fixed threshold, controller 38 stops adjusted value N, so just can open servomechanism installation, to obtain positive-effect, improve the spectrum of CAN clock, loop 24 is interference-free.Otherwise, to have only when signal Y can measure with respect to the time-delay of signal XR (value of (P-1)-(P+1) is meaningful), just can restart time calibration.
As reaching N-2 and N+2, value N can change one or several unit at every turn according to convergence rate and required accuracy.
Known, especially be difficult to timing when predistortion, promptly saturated and when intermodulating when amplifier, signal XR and Y so correlation weaken, and correlation curve is more flat, more be subject to interference, and the control loop of value N can be restrained.
A kind of simplification is but quite effectively used and is, calculates three place's correlations on N or N-1 sample horizontal plane, so just can systematically calibrate described associated window according to the counting of frequency divider N/N-1/N+ 1.
The fine tuning loop is a time closed-loop type.It can monitor+time-delay in/-0.5 sample window (even almost reach+/-1 sample, concerning great changes, this has just been avoided carrying out coarse adjustment by main delayer 30).Simultaneously, the correlation maximum guaranteeing when main calibration phase 1 is essential, restrains and resets among selected three reference points.
The plural number of two comparison signal XR and Y-plural correlation can be broken away from fixed gain and phase difference between two signals, especially when comparing related power.
But, only can consider real number representation with a signal Y, to simplify correlator 32, method is: two factors are kept to one, to reduce the detector sensitivity of orientation, like this, even signal XR still be a plural number, the result also can occur and blur and disperse danger.
Therefore, can directly compare the correlation of transducer CAN 20 output signals, will it not convert complex signal again to, adopt unique CAN real number signal, to the natural double sampling of intermediate frequency, more favourable.
This simplification to correlator 32 can increase the tens of approximately millisecond of convergence time, even hundreds of millisecond, but but original coarse adjustment time before the compatible system starting time still, and general because thermal change and the aging slow variation that causes.
In case of necessity, can continue component to the output signal Y of CAN 20 and eliminate handle (device of representing as dotted line 34).
Therefore, the signal Y after unit 22 processing time calibration can carry out time calibration together again with signal XR.Signal Y after this is calibrated is transferred to the relatively input 4c place of digital pre-distortion unit 4 (as Fig. 2) again, and signal XR is transferred to the 3rd input 4d of described pre-distortion unit.
In a possibility modification of present embodiment, can only consider the arithmetic sign of signal XR and Y, to simplify correlator and standardization correlation.For this reason, can one first and second symbol detector 40 and 42 (detector 40 and 42 is to select piece installing, dots) be installed at first, second input 32a of correlator 32 and each upstream of 32b.According to this modification, only need the homogeneity value between signal XR and the Y, i.e. symbol detector 40 and 42 symbols that need to extract signal.Advantageously, described operation has adopted conventional digital to represent, only needs to calculate " complement of two's two's complement " (" compl é ment à 2 "), promptly only considers the seniority top digit of conventional letter.If a complex signal, described operation can independently be implemented on component I and the Q, promptly represent described signal, corresponding foursquare each summit of described four numerical value with four probable values: 1+j, 1-j ,-1+j ,-1-j.
Certainly, also can consider any middle solution, in view of the above, the value of available cylindricality or circular expression signal XR and Y.
Can find out that the complexity that the complexity of correlator reaches signal XR, the Y that dynamically can monitor symbol detector 40 and 42 downstreams reaches dynamically.
Although embodiments of the present invention can cooperate multiple known pre-distortion technology to implement, but especially advantageously can be fit to the broadband reception device in these technology, as the LMS algorithm, utilize this algorithm, renewable and study predistortion table, specific practice is: by relatively each emission and actual time of received signal, and the actual time (or if the harmonic wave rhythm of CAN turn signal stream X then receives sample for each) that respectively transmits and receives sampling.
By the present invention, both can be parallel and implement predistortion enduringly simultaneously, recoverable learning table again, these parameters are cooperated mutually in positive mode.The robustness of the technology of the present invention can guarantee the carrying out of time calibration, when start-up system, or when losing the storage of all predistortions---this may cause power amplifier 12 near saturation condition.Therefore, need a detection signal,---no matter its power---work because present technique is according to normal amplifying signal.Like this, just with tradition proofread and correct different, in traditional correction method, regularly stop signal emission of cell site, injecting a detection signal of determining, with as the reference signal of calibrating.So can turn round lastingly in the cell site.
In fact,, only utilized the characteristic of correlation and certain symmetry of correlation by the method that correlation is carried out time calibration and study, signal whatsoever, comprise certainly the effective signal radiated of cell site all provable they.
Note that time calibration and study can influence each other, and are positive, " correction " is many more, and by very weak residual noise table, predistortion table just can be got over rapid convergence on appropriate value; Correspondingly, predistortion is accurate more, and the peak of correlation curve C (as Fig. 4 a-c) is just steep more, and noise is low more, and the symbol accuracy is subjected to the The noise of intermodulating of amplifier remnants more little.
The invention describes the plurality of advantages of a kind of embodiment of the amplifier that has a self-adapted pre-distortion function, as:
---existing clock PLL 26 both can be used for the reflector of transducer CNA 8, can be used as the receiver of transducer CAN 20 again, and at this moment, it is as the reference frequency source of the PLL 24 of transducer CAN;
---only adopt existing transmission and receive digital data, need not detection signal, can guarantee complete, lasting correction.
---with digital form integrated nearly all optional feature, (english abbreviation is FPGA to this field programmable gate array that user is used, i.e. " field programmable gatearray ") or application-specific integrated circuit (ASIC) (english abbreviation is ASIC, i.e. " application specificintegrated circuit ") very favourable, only several thousand strobe pulses just can be implemented function time calibration approximately;
---PLL and counter also can be integrated;
---be applicable to any degenerative self adapting digital predistortion of time that has;
---the accuracy of time calibration can be provided, and (during multicarrier) in case of necessity utilizes a sensitiveer correlation contrast device, can increase described accuracy;
---compatible correlation reduction procedure: the symbol of the multiplier of any bit table is relevant.
Attention: be correlated with as if a correlation symbolization, i.e. the signal XR﹠amp that represents by the real part and the imaginary part of symbol; Y, correlation then only is the counting that the distance provided/contrary counting group by symbol.Related power only is counting square sum.
Therefore, advantage of the present invention is that correlation equals the symbol concordance rate between signal XR and the Y, and is not subjected to the influence of dependent phase, especially each signal power.On the one hand, the control that this has greatly made things convenient for the control loop gain on the other hand, makes the correlation curve steeper, more is not subjected to distortion effect (in other words, if power amplifier 12 is in saturation condition, also can or can not change the symbol and the zero passage moment thereof of Y hardly);
---because the average speed of control loop assembly, thereby can refine the loop parameter standard, and be applied in digital signal processor or the microcontroller with form of software;
---because the robustness of correlator and be used for controlling PLL 24 employed metric systems (details see before literary composition), can be at the predistortion prestart, convergence time calibration.
---because the original correction that has sampling time-delay integral multiple to constitute, even do not know the time-delay of whole transmission and reception, or time-delay has many variations of one-period, also can avoid reinstating the time calibration that any former factory is provided with;
---can keep effective time calibration (by using the correlation contrast of normalization), even when the transmitting power cycle is extremely weak (details see above);
---by a too flat correlation curve, can detect all convergence problems, so just can obtain DPD table protective device, with at the useless even dangerous operation of off resonance error update.
The present invention especially can be applicable to all single carrier waves or multicarrier standard such as 3G/CDMA.In principle, it is applied in the linear amplifier of fixed radio cell site of wireless and even wide-band modulation such as CDMA or OFDM.In described application, therefore advantageously, it has also utilized feature single or CDMA multiple carrier signal broadband and pseudo noise.
Can find out, the present invention its material and function implement and at practical application on, have other multiple modification, but all do not exceed claim scope of the present invention.
This specification is described according to the cell site's amplification link that has adopted pre-distortion technology.Also can be applicable to the time calibration of the present invention's proposition need carry out in all technical fields of time calibration but obviously, to a plurality of signals.
Claims (29)
1, be used to set up the set-up procedure of the comparison signal (being respectively X and Y) of an amplifier (12) input predistortion, signal comprises that one amplifies front signal (X) and the signal (Y) after described amplifier amplifies,
It is characterized in that described preparation comprises the time calibration (22) of amplifying between preceding and the amplified signal (being respectively X and Y), utilizes them to determine described predistortion again.
2, set-up procedure according to claim 1 is characterized in that:
---in the coarse adjustment stage very first time, around here, will amplify front signal (X) postponement one and be the time-delay of first chronomere's integral multiple, and definite described delay value, time delayed signal (XR) before described time-delay produces and amplifies, this signal and amplified signal (Y) all have the Best Times calibration, and
---the accurate adjustment stage second time, around here, determine time lag or the value that shifts to an earlier date, it is the fractional value of very first time unit, be applied to amplify it in the signal (Y) that extracts the back, can obtain and amplify the calibration of the same Best Times of preceding time delayed signal (XR), described hysteresis or in advance value be applied in the amplified signal
(Y XR) can be used to set up described predistortion to carry out time ratio signal like this.
3, process according to claim 2 is characterized in that, in very first time calibration phase, before the described amplification and the signal (being respectively X and Y) after amplifying can be digital.
4, according to claim 2 or 3 described processes, it is characterized in that, by analyzing the reference point (P) between preceding time delayed signal (XR) of (32) amplifier amplification and the amplified signal (Y), determine to have the preceding inhibit signal (XR) of amplification of Best Times calibration, and/or described very first time unit fraction, the described preceding time delayed signal of amplification with Best Times calibration is the signal that point of maximum correlation can be provided.
5, process according to claim 4, it is characterized in that, when carrying out described reference point (P) analysis, can choose several different delayed time forms of the preceding time delayed signal (XR) of amplification of parallel arranged and carry out described analysis (32-1,32-2,32-3), this of time delayed signal is several before amplify picks out time delayed signal (XR) before the amplification with Best Times calibration multi-form.
6, according to claim 4 or 5 described processes, it is characterized in that, carry out described reference point (P) when analyzing with coherent signal (XR, Y) at least one complex representation.
7, according to one of them described process of claim 4 to 6, it is characterized in that, when carrying out described reference point (P) analysis, can adopt complex representation, for example, the complex representation that inhibit signal (XR) is formed with real part and imaginary part before the described amplification, amplified signal (Y) is only used real number representation.
8, according to one of them described process of claim 2 to 7, it is characterized in that, before the first coarse adjustment stage, amplified signal (Y) digitlization (20) for and the frequency of amplifying front signal (X) first sampling frequency (Mvar) of harmonic relationships is arranged.
9, according to one of them described process of claim 4 to 8, it is characterized in that, according at least three reference points (P-1), P (0), (P+1), wherein, the highest correlation in the corresponding reference point of first reference point (P0) (P), second and third reference point (P-1) and (P+1) respectively in the first reference point both sides, can determine a correlation curve (C) of time delayed signal (XR) before the described amplification with Best Times calibration, its feature also is, at second time, phasing in the stage, signal (XR, sampling time Y) are so relatively:
If---the associated level of second reference point (P-1) be lower than the associated level that third phase closes point (P+1) (as Fig. 4 a), with respect to time delayed signal (XR) before amplifying, the sampling time of delay amplifier amplified signal (Y), and
---if the associated level of second reference point (P-1) is higher than the associated level (as Fig. 4 c) that third phase closes point (P+1), with respect to time delayed signal (XR) before amplifying, shifts to an earlier date the sample time of amplifier amplified signal (Y),
Otherwise or,
So that second reference point (P-1) and third phase close between point (P+1) reference point to about equally an associated level convergence (as Fig. 4 b).
10, according to one of them described process of claim 4 to 9, it is characterized in that, determine correlation, the signal (XR) and the symbol (40 of amplified signal (Y) on the other hand late time the before the one side that only needs to consider amplifier is amplified, 42), described correlation is based upon this two signal, and (XR, Y) symbol between is consistent calculates on the basis.
11, according to one of them described process of claim 2 to 10, it is characterized in that, the sample frequency (Ivar) of amplified signal (Y) digitlization to a phase control, second stage promptly is, change described sampling phase selectively, have the preceding time delayed signal (XR) of amplifier amplification of Best Times calibration and the time calibration of described amplified signal (Y) with increase.
12, process according to claim 11 is characterized in that, the described first phase control sample frequency (Ivar) can be created in first phase-locked loop output (24) and locate, and the reference frequency (φ var.r é f) by change described ring with pulse mode makes its variation.
13, process according to claim 12, it is characterized in that, by one second phase-locked loop (26), can produce the reference frequency (φ var.r é f) of first phase-locked loop (24), after variable frequency divider (N) divides (28) to come out from its output frequency (I é ch) frequency, can be by changing number (N), the described reference frequency (Ivar.r é f) of first phase-locked loop (24) is changed, with the described phase place of time delayed signal (XR) and amplified signal (Y) before the amplification that relatively has the Best Times calibration.
14, process according to claim 13, it is characterized in that, can be transported to the input of described transducer again amplifying front signal (X) after digital-to-analog conversion (8), described conversion is a rhythm with a sampled signal (Ivar) that produces in described second phase-locked loop (26) output place.
15, signal (being respectively X and Y) preparation device, described signal need the pre-distortion device through being placed in amplifier (12) input to handle, the signal (Y) after signal comprises an amplification front signal (X) and passes through described amplifier amplification,
It is characterized in that being included in the time calibration device (22) that amplifies between preceding and the amplified signal (being respectively X and Y).
16, device according to claim 15 is characterized in that, it comprises:
---very first time rack and rinion adjustment (30,32,38), they can be the time-delay of first chronomere's integral multiple amplifying front signal (X) postponement one, and can determine described delay value, time delayed signal (XR) before described delay produces and amplifies, this signal and amplified signal (Y) all have the Best Times calibration, and
---the second time adjuster, they can be defined as the time lag of very first time unit fraction value or the value that shifts to an earlier date, and it is applied to amplify in back sampled signal (Y), can obtain the Best Times calibration the same with amplifying preceding time delayed signal (XR), can described time-delay or in advance value be applied in the amplified signal
Carry out time ratio signal like this and be transferred to described pre-distortion unit again.
17, device according to claim 16, it is characterized in that, described first device and/or second device include reference point (P) analytical equipment (32), the reference point (P) before but its paraphase amplifier amplifies between time delayed signal (XR) and the amplified signal (Y), with inhibit signal (XR) before the amplification of determining to have the Best Times calibration, time delayed signal is the signal that point of maximum correlation can be provided before the described amplification with Best Times calibration.
18, device according to claim 17 is characterized in that, it comprises reference point (P) analytical equipment, to the analysis of reference point be based upon a coherent signal (XR, Y) at least one with on basis of complex representation.
19, device according to claim 18, it is characterized in that described reference point (P) analytical equipment is based upon on the basis of complex representation, promptly, the complex representation that inhibit signal (XR) is formed with real part and imaginary part before the described amplification, amplified signal (Y) is only used real number representation.
20, according to one of them described device of claim 16 to 19, it is characterized in that, it comprises device (20), can the amplified signal of very first time calibrating installation upstream (Y) digitlization to and the frequency of amplifying front signal (X) first sampling frequency (Mvar) of harmonic relationships is arranged.
21, according to one of them described device of claim 17 to 20, it is characterized in that, it comprises definition device, described definition device can be according at least three reference points (P-1), P (0), (P+1) determine a described correlation curve (C) with preceding time delayed signal (XR) of amplification of Best Times calibration, wherein, the highest correlation in the corresponding reference point of first reference point (P0) (P), second, three reference points (P-1) and (P+1) respectively in the first reference point both sides, its feature also is, in second time, phasing is in the stage, described secondary signal (XR, Y) the sampling time comparison means comprises:
If---the associated level of second reference point (P-1) be lower than the associated level that third phase closes point (P+1) (as Fig. 4 a), with respect to time delayed signal (XR) before amplifying, but the device in the sample time of delay amplifier amplified signal (Y), and
---if the associated level of second reference point (P-1) is higher than the associated level (as Fig. 4 c) that third phase closes point (P+1), with respect to time delayed signal (XR) before amplifying, and the device that can shift to an earlier date the sample time of amplifier amplified signal (Y),
Otherwise or,
So that second reference point (P-1) and third phase close between point (P+1) reference point to about equally an associated level convergence (as Fig. 4 b).
22, according to one of them described device of claim 17 to 21, it is characterized in that, it also comprises symbol detection apparatus (40,42), time delayed signal (XR) reached the symbol (40,42) of amplified signal (Y) on the other hand before but the one side of described checkout gear detecting amplifier was amplified, to determine an only correlation relevant with symbol, described correlation is based upon this two signal, and (XR, Y) symbol between is consistent calculates on the basis.
23, according to one of them described device of claim 16 to 22, it is characterized in that, it comprises that device is used for described amplified signal (Y) digitlization to a phase control sample frequency (Ivar), described second time calibration device includes changeable device, can change described sampling phase selectively, have the time calibration of time delayed signal (XR) and the described amplified signal of amplifier (Y) before the amplification of Best Times calibration with improvement.
24, device according to claim 23 is characterized in that, it comprises one first phase-locked loop (24), and described ring can produce the described first phase control sample frequency (Ivar), and changeable device changes the reference frequency (Ivar.r é f) of described ring.
25, device according to claim 24, it is characterized in that, it also includes one second phase-locked loop (26), described ring can produce the reference frequency (Ivar.r é f) of first phase-locked loop (24) by the variable frequency divider (28) of a variable division number (N), the changeable device of the reference frequency of described first phase-locked loop (24) (Ivar.r é f) can be realized the described comparison to the described phase place of time delayed signal (XR) and amplified signal (Y) before the amplification with Best Times calibration by changing number (N).
26, device according to claim 25, it is characterized in that, it also comprises digital-analog convertor (8), described transducer can carry out the conversion of digital-to-analog formula amplifying front signal (X), and conversion is a rhythm with a sampled signal (I é ch) that produces in described second phase-locked loop (26) output place.
27, a kind of amplification link, described amplification link comprises at least one amplifier (12) and pre-distortion device (4), described device is installed in the amplifier input, to compare the forward and backward signal of distortion, it is characterized in that, it comprises a time calibrating installation, according to aforesaid right require 15 to 26 one of them to the input described signal of transmission (XR and Y) to make comparisons.
28, amplification link according to claim 27 is characterized in that, it is applied in the linear power amplifier of a wideband electromagnetic wave launcher.
29, amplification link according to claim 28 is characterized in that, it is between 10 to 100 megahertzes that the broadband is based upon frequency, as 60 megahertzes, its feature is that also it is used for launching multi-carrier signal, for example, emission (AMRC) the type coding of what is called " code division multiple access " that is used for mobile phone.
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| FR0200696A FR2835120B1 (en) | 2002-01-21 | 2002-01-21 | METHOD AND DEVICE FOR PREPARING SIGNALS TO BE COMPARED TO ESTABLISH PRE-DISTORTION ON THE INPUT OF AN AMPLIFIER |
| FR0200696 | 2002-01-21 |
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| EP (1) | EP1331729A1 (en) |
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Cited By (4)
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| CN100364250C (en) * | 2004-09-23 | 2008-01-23 | 华为技术有限公司 | Delay compensation method used in mobile communication and its system |
| CN101459636B (en) * | 2007-12-12 | 2012-04-18 | 中兴通讯股份有限公司 | Adaptive pre-distortion method |
| CN105721386A (en) * | 2014-12-18 | 2016-06-29 | 英特尔Ip公司 | Method and device of calibrating rf path delay and iq phase imbalance for polar transmitter |
| CN107241067A (en) * | 2017-06-08 | 2017-10-10 | 上海先积集成电路有限公司 | A kind of digital self calibration copped wave precision amplifier and implementation method |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7486722B2 (en) | 2001-04-18 | 2009-02-03 | Bae Systems Information And Electronic Systems Integration Inc. | Bandwidth efficient cable network modem |
| DE60126995T2 (en) * | 2001-06-25 | 2007-11-08 | Nokia Corp. | DATA TRANSMISSION METHOD AND ARRANGEMENT |
| FR2846813B1 (en) * | 2002-11-05 | 2005-01-28 | Eads Defence & Security Ntwk | METHOD AND DEVICE FOR LEARNING A DEVICE FOR LINEARIZATION OF AN RF AMPLIFIER, AND MOBILE TERMINAL INCORPORATING SUCH A DEVICE |
| FR2846812B1 (en) * | 2002-11-05 | 2005-01-28 | Eads Defence & Security Ntwk | IMPROVING THE METHODS AND DEVICES FOR LEARNING A DEVICE FOR LINEARIZING AN RF AMPLIFIER |
| JP4311034B2 (en) * | 2003-02-14 | 2009-08-12 | 沖電気工業株式会社 | Band restoration device and telephone |
| US7627055B2 (en) * | 2003-02-27 | 2009-12-01 | Nokia Corporation | Error adjustment in direct conversion architectures |
| CN1784837B (en) * | 2003-05-09 | 2011-01-26 | Nxp股份有限公司 | Method and arrangement for setting the transmission power of a mobile communication device |
| US7054391B2 (en) * | 2003-05-30 | 2006-05-30 | Efficient Channel Coding, Inc. | Receiver based saturation estimator |
| US7129778B2 (en) * | 2003-07-23 | 2006-10-31 | Northrop Grumman Corporation | Digital cross cancellation system |
| JP4641715B2 (en) * | 2003-11-14 | 2011-03-02 | 富士通株式会社 | Distortion compensation apparatus and radio base station |
| DE60325789D1 (en) * | 2003-11-26 | 2009-02-26 | Ericsson Telefon Ab L M | CIRCUIT AND METHOD FOR PRE-AVERAGE CONTROL, AND A CIRCUIT UNIT COMPRISING A PRESET-CURRENT CONTROL CIRCUIT |
| EP1548930A1 (en) * | 2003-12-23 | 2005-06-29 | Alcatel | Electronic circuit and method for predistorting a signal to be amplified |
| JP4323968B2 (en) * | 2004-01-14 | 2009-09-02 | 株式会社日立コミュニケーションテクノロジー | Timing adjustment method for wireless communication device |
| US20050163249A1 (en) * | 2004-01-27 | 2005-07-28 | Crestcom, Inc. | Predistortion circuit and method for compensating linear distortion in a digital RF communications transmitter |
| US20050163208A1 (en) * | 2004-01-27 | 2005-07-28 | Crestcom, Inc. | Equalized signal path with predictive subtraction signal and method therefor |
| US7430248B2 (en) * | 2004-01-27 | 2008-09-30 | Crestcom, Inc. | Predistortion circuit and method for compensating nonlinear distortion in a digital RF communications transmitter |
| US7342976B2 (en) * | 2004-01-27 | 2008-03-11 | Crestcom, Inc. | Predistortion circuit and method for compensating A/D and other distortion in a digital RF communications transmitter |
| US7469491B2 (en) * | 2004-01-27 | 2008-12-30 | Crestcom, Inc. | Transmitter predistortion circuit and method therefor |
| US20050163205A1 (en) * | 2004-01-27 | 2005-07-28 | Crestcom, Inc. | Equalized signal path with predictive subtraction signal and method therefor |
| US7099399B2 (en) * | 2004-01-27 | 2006-08-29 | Crestcom, Inc. | Distortion-managed digital RF communications transmitter and method therefor |
| US7305041B2 (en) * | 2004-02-20 | 2007-12-04 | Kiomars Anvari | Peak suppression of multi-carrier signal with different modulation |
| CA2560281A1 (en) * | 2004-03-25 | 2005-10-13 | Optichron, Inc. | Model based distortion reduction for power amplifiers |
| US20050242876A1 (en) * | 2004-04-28 | 2005-11-03 | Obernosterer Frank G E | Parameter estimation method and apparatus |
| DE602004029941D1 (en) * | 2004-05-19 | 2010-12-16 | Ericsson Telefon Ab L M | ADAPTIVE FORECASTING METHOD AND ARRANGEMENT |
| US7239671B2 (en) * | 2004-07-09 | 2007-07-03 | Powerwave Technologies, Inc. | System and method for digital timing error correction in a communications system utilizing adaptive predistortion |
| US20060039498A1 (en) * | 2004-08-19 | 2006-02-23 | De Figueiredo Rui J P | Pre-distorter for orthogonal frequency division multiplexing systems and method of operating the same |
| KR100605109B1 (en) * | 2005-01-18 | 2006-07-28 | 삼성전자주식회사 | Method and Apparatus for Improving SNR with Oversampling in an OFDM Systems |
| JP4664364B2 (en) * | 2005-07-29 | 2011-04-06 | 富士通株式会社 | Delay adjustment device |
| US20070082617A1 (en) * | 2005-10-11 | 2007-04-12 | Crestcom, Inc. | Transceiver with isolation-filter compensation and method therefor |
| KR100666179B1 (en) | 2005-11-18 | 2007-01-09 | 삼성전자주식회사 | Output driver and output driving method for preemphasis in output data with timing |
| US7542519B2 (en) * | 2005-12-29 | 2009-06-02 | Crestcom, Inc. | Radio frequency transmitter and method therefor |
| US7856105B2 (en) * | 2006-03-09 | 2010-12-21 | Andrew Llc | Apparatus and method for processing of amplifier linearization signals |
| US7653362B2 (en) * | 2006-03-16 | 2010-01-26 | Pine Valley Investments, Inc. | Method and apparatus for on-chip measurement of power amplifier AM/AM and AM/PM non-linearity |
| US7724840B2 (en) * | 2006-12-19 | 2010-05-25 | Crestcom, Inc. | RF transmitter with predistortion and method therefor |
| US20080285640A1 (en) * | 2007-05-15 | 2008-11-20 | Crestcom, Inc. | RF Transmitter With Nonlinear Predistortion and Method Therefor |
| US7778345B2 (en) * | 2007-11-07 | 2010-08-17 | Texas Instruments Incorporated | Distortion compensation in a communication system |
| JP5381202B2 (en) * | 2009-03-18 | 2014-01-08 | 富士通株式会社 | Time-division bidirectional transmission wireless device |
| JP5459158B2 (en) * | 2010-09-21 | 2014-04-02 | 富士通株式会社 | Transmitting apparatus and distortion compensation method |
| ES2614902T3 (en) * | 2011-03-21 | 2017-06-02 | Koninklijke Philips N.V. | Calculation of power loss in inductive power transmission |
| US8792583B2 (en) * | 2011-05-12 | 2014-07-29 | Andrew Llc | Linearization in the presence of phase variations |
| US8908797B2 (en) * | 2012-03-07 | 2014-12-09 | Samsung Electronics Co., Ltd. | Apparatus and method for time alignment of an envelope tracking power amplifier |
| EP3745664A1 (en) | 2012-07-23 | 2020-12-02 | Dali Systems Co. Ltd | Method and system for aligning signals widely spaced in frequency for wideband digital predistortion in wireless communication systems |
| US20140029683A1 (en) | 2012-07-26 | 2014-01-30 | Telefonaktiebolaget L M Ericsson (Publ) | Multi-Band Observation Receiver |
| US9014299B2 (en) * | 2012-12-07 | 2015-04-21 | Maxim Integrated Products, Inc. | Digital pre-distortion system for radio frequency transmitters with reduced sampling rate in observation loop |
| US9680423B2 (en) * | 2013-03-13 | 2017-06-13 | Analog Devices Global | Under-sampling digital pre-distortion architecture |
| US9608676B2 (en) * | 2013-07-12 | 2017-03-28 | Analog Devices Global | Digital pre-distortion systems in transmitters |
| US9054652B2 (en) | 2013-10-02 | 2015-06-09 | Nokia Solutions And Networks Oy | Using fractional delay computations to improve intermodulation performance |
| TWI533646B (en) * | 2014-06-10 | 2016-05-11 | 晨星半導體股份有限公司 | Signal processing system and signal processing method cooperating with variable gain amplifier |
| CN105227507B (en) * | 2014-06-13 | 2019-08-02 | 中兴通讯股份有限公司 | Nonlinear systematic distortion correction device and method |
| EP3195010A4 (en) | 2014-08-15 | 2018-04-11 | Aeye, Inc. | Methods and systems for ladar transmission |
| US10056863B2 (en) | 2015-01-05 | 2018-08-21 | Telefonaktiebolaget Lm Ericsson (Publ) | Technique for determining a time alignment error |
| US9362942B1 (en) * | 2015-01-12 | 2016-06-07 | Maxim Integrated Products, Inc. | System characteristic identification systems and methods |
| US10146739B2 (en) * | 2015-02-27 | 2018-12-04 | Alcatel Lucent | Vector signal alignment for digital vector processing using vector transforms |
| US10181825B2 (en) * | 2015-10-27 | 2019-01-15 | King Fahd University Of Petroleum And Minerals | Method and system for power amplifier characterization and digital predistortion |
| US10641872B2 (en) * | 2016-02-18 | 2020-05-05 | Aeye, Inc. | Ladar receiver with advanced optics |
| US10042159B2 (en) | 2016-02-18 | 2018-08-07 | Aeye, Inc. | Ladar transmitter with optical field splitter/inverter |
| US20170242104A1 (en) | 2016-02-18 | 2017-08-24 | Aeye, Inc. | Ladar Transmitter with Induced Phase Drift for Improved Gaze on Scan Area Portions |
| US9832007B2 (en) | 2016-04-14 | 2017-11-28 | Ibiquity Digital Corporation | Time-alignment measurement for hybrid HD radio™ technology |
| US10666416B2 (en) | 2016-04-14 | 2020-05-26 | Ibiquity Digital Corporation | Time-alignment measurement for hybrid HD radio technology |
| AU2018220938B2 (en) | 2017-02-17 | 2022-03-17 | Aeye, Inc. | Method and system for ladar pulse deconfliction |
| CN111344647B (en) | 2017-09-15 | 2024-08-02 | 艾耶股份有限公司 | Intelligent laser radar system with low-delay motion planning update |
| GB2569121A (en) * | 2017-12-05 | 2019-06-12 | Nokia Technologies Oy | Method, apparatus and arrangement for linearizing of a transmitter array |
| FR3076135B1 (en) * | 2017-12-21 | 2019-12-27 | Thales | LOW COMPLEXITY TIME SYNCRONIZATION IN A DIGITAL PREDISTORSION CALCULATION LOOP |
| US11009597B2 (en) * | 2018-12-17 | 2021-05-18 | Xilinx, Inc. | Phase noise compensation in digital beamforming radar systems |
| US11271601B1 (en) | 2020-10-19 | 2022-03-08 | Honeywell International Inc. | Pre-distortion pattern recognition |
| US11675059B2 (en) | 2021-03-26 | 2023-06-13 | Aeye, Inc. | Hyper temporal lidar with elevation-prioritized shot scheduling |
| US11630188B1 (en) | 2021-03-26 | 2023-04-18 | Aeye, Inc. | Hyper temporal lidar with dynamic laser control using safety models |
| US11480680B2 (en) | 2021-03-26 | 2022-10-25 | Aeye, Inc. | Hyper temporal lidar with multi-processor return detection |
| US11822016B2 (en) | 2021-03-26 | 2023-11-21 | Aeye, Inc. | Hyper temporal lidar using multiple matched filters to orient a lidar system to a frame of reference |
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| US11635495B1 (en) | 2021-03-26 | 2023-04-25 | Aeye, Inc. | Hyper temporal lidar with controllable tilt amplitude for a variable amplitude scan mirror |
| US20230091821A1 (en) * | 2021-09-22 | 2023-03-23 | Kymeta Corporation | Carrier predistortion to improve signal quality of links on flat panel antennas |
| US11695424B2 (en) | 2021-11-23 | 2023-07-04 | International Business Machines Corporation | Distortion reduction circuit |
| US12099006B1 (en) * | 2022-08-24 | 2024-09-24 | United States Of America As Represented By The Administrator Of Nasa | Wideband subharmonic mixer |
Family Cites Families (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5049832A (en) * | 1990-04-20 | 1991-09-17 | Simon Fraser University | Amplifier linearization by adaptive predistortion |
| FR2746563B1 (en) * | 1996-03-22 | 1998-06-05 | Matra Communication | METHOD FOR CORRECTING NON-LINEARITIES OF AN AMPLIFIER, AND RADIO TRANSMITTER IMPLEMENTING SUCH A METHOD |
| FI105506B (en) * | 1998-04-30 | 2000-08-31 | Nokia Networks Oy | Linearization procedure for amplifiers and amplifier arrangements |
| US6359508B1 (en) * | 2000-08-17 | 2002-03-19 | Spectrian Corporation | Distortion detection apparatus for controlling predistortion, carrier cancellation and feed-forward cancellation in linear RF power amplifiers |
| US6566966B1 (en) * | 2000-09-18 | 2003-05-20 | Texas Instruments Incorporated | Fast lock/self-tuning VCO based PLL |
-
2002
- 2002-01-21 FR FR0200696A patent/FR2835120B1/en not_active Expired - Fee Related
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2003
- 2003-01-16 US US10/345,222 patent/US6774834B2/en not_active Expired - Fee Related
- 2003-01-17 EP EP03290120A patent/EP1331729A1/en not_active Withdrawn
- 2003-01-20 JP JP2003011160A patent/JP2003243940A/en active Pending
- 2003-01-21 CN CNB031027881A patent/CN100349376C/en not_active Expired - Fee Related
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN100364250C (en) * | 2004-09-23 | 2008-01-23 | 华为技术有限公司 | Delay compensation method used in mobile communication and its system |
| CN101459636B (en) * | 2007-12-12 | 2012-04-18 | 中兴通讯股份有限公司 | Adaptive pre-distortion method |
| CN105721386A (en) * | 2014-12-18 | 2016-06-29 | 英特尔Ip公司 | Method and device of calibrating rf path delay and iq phase imbalance for polar transmitter |
| CN105721386B (en) * | 2014-12-18 | 2019-07-23 | 英特尔Ip公司 | The method and apparatus for calibrating polar transmitter RF path delay and IQ unbalance in phase |
| CN107241067A (en) * | 2017-06-08 | 2017-10-10 | 上海先积集成电路有限公司 | A kind of digital self calibration copped wave precision amplifier and implementation method |
Also Published As
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| US6774834B2 (en) | 2004-08-10 |
| CN100349376C (en) | 2007-11-14 |
| FR2835120B1 (en) | 2006-10-20 |
| JP2003243940A (en) | 2003-08-29 |
| EP1331729A1 (en) | 2003-07-30 |
| FR2835120A1 (en) | 2003-07-25 |
| US20030156658A1 (en) | 2003-08-21 |
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