CN1381942A - Supply transformer containing circuit for controlling synchronous rectifier - Google Patents
Supply transformer containing circuit for controlling synchronous rectifier Download PDFInfo
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Abstract
A power converter device using synchronous rectifiers and method for controlling operation thereof are provided. A first synchronous rectifier is coupled to the secondary transformer winding to pass a voltage induced at the secondary winding in response to an input voltage supplied to the primary transformer winding during an on-state of a main power switch. A first drive circuit is coupled to the gate terminal of the first synchronous rectifier to selectively activate and deactivate the first rectifier in correspondence with the respective on and off states of the main power switch based on a gate voltage supplied by the first drive circuit, with at least one circuit parameter being selected in the first drive circuit for maintaining the gate voltage within a predefined range regardless of variation in the level of the input voltage.
Description
The application requires the priority based on the 60/267th, No. 836 U.S. Patent application of submission on February 9 calendar year 2001.
Technical field
The control and the operation of relate generally to supply convertor equipment of the present invention more particularly, the present invention relates to be used to improve the circuit of the runnability of the synchronous rectifier of use in the DC/DC supply convertor equipment.
Background technology
DC/DC supply convertor equipment is widely used in the extensive application, for example telecommunications and working application.The dc/dc converter is that a kind of original dc (direct current) voltage input that is used for having certain variable range usually is converted to the dc voltage output of satisfying one group of standard.Along with the fast development of telecommunication apparatus technology, the requirement of dc/dc power density of transform and conversion efficiency is being improved constantly.
Fig. 1 illustrates the schematic diagram of basic self-device synchronous rectification device in the typical forward converter circuit layout.As everyone knows, under certain conditions, transformer secondary output winding voltage level may be too high or too low and can not correctly drives synchronous rectifier, SR1 and SR2.For example, because generally the excursion of input voltage (Vin) is big, so the dividing potential drop excursion of synchronous rectifier is also big.The undesirable fluctuation that is used to drive the voltage level of synchronous rectifier can cause producing harmful power loss and make and is difficult to realize optimal design in synchronous rectifier.In addition, because undesirable instantaneous " conducting " situation can appear in switching time delay and other circuit parasitic phenomenon, this instantaneous " conducting " situation can occur in synchronous rectifier SR1 and SR2 simultaneously.This might cause producing the quite high spike that electric current " passes (shooting-through) " at least one synchronous rectifier.Obviously, this situation can influence the life-span of efficient, reliability and/or influenced synchronous rectifier and associated components.Everybody also knows, can utilize independent winding to replace the main power source winding of supply convertor to drive two synchronous rectifier SR1 and SR2.Yet, in this configuration, feasible rectifier SR1 of conducting synchronously of interdependence and SR2 that the charging process of two synchronous rectifiers and discharge process are intrinsic, thus " passing " situation may appear.
Therefore, preferably provide the performance that can improve each self-device synchronous rectification device (SR) in the dc/dc supply convertor, use with low cost, thus favourable reduction power loss and improve the technology and the Circuits System of supply convertor overall efficiency.Technology or the Circuits System that can avoid or solve any " passing " situation in the synchronous rectifier preferably can also be provided.
Summary of the invention
Usually, by a kind of supply convertor is provided according to an aspect of the present invention, the present invention can realize above-mentioned requirements, described supply convertor comprises that described transformer has respective primary Transformer Winding and secondary transformer winding by transformer mutually magnetically coupled primary part and sub section.In the typical forward converter, the primary part of supply convertor comprises main power switch and the clamp switch that links to each other with the primary transformers winding respectively, main power switch and clamp switch are configured to usually to move under the conducting of complementation and cutoff switch state, between them, have some and postpone to avoid occurring the situation of passing and to make the leakage-source voltage of switch discharge into certain degree before it in conducting.
The sub section of supply convertor comprises first synchronous rectifier, first synchronous rectifier links to each other with the secondary transformer winding, during main power switch is in conducting state, the voltage of responding at secondary winding in response to the input voltage that is provided to the primary transformers winding.In an exemplary embodiments, for example, if during clamp switch is in conducting state, use a secondary winding, then also second synchronous rectifier is connected to the secondary transformer winding with when the secondary winding of heart tap in use at the voltage of secondary winding induction, perhaps provide path by output inductor for freewheel current.First drive circuit links to each other with the gate terminal of first synchronous rectifier, by in described first drive circuit, selecting a circuit parameter at least, grid voltage is remained in the preset range, and it is irrelevant with the level fluctuation of input voltage, the feasible grid voltage of supplying with according to described first drive circuit, consistent with the conducting and the cut-off state of main power switch, optionally start or close first rectifier.Usually, the electric capacity of the capacitor in the drive circuit is the preferred parameter of not regulating grid voltage with losing.In addition, also utilize the capacitor in the drive circuit that the interior voltage fluctuation of gate drive voltage and power transformer is directly proportional, can reduce the sensitivity that grid voltage changes input voltage like this, because the excursion of the voltage fluctuation in the power transformer is less than input voltage.If use second synchronous rectifier, then the gate terminal of second drive circuit with second synchronous rectifier linked to each other, by selecting a circuit parameter at described second drive circuit at least, grid voltage is remained in the preset range, and it is irrelevant with the level fluctuation of input voltage, make the grid voltage of supplying with according to described second drive circuit, consistent with the conducting and the cut-off state of clamp switch, optionally start or close second rectifier.The current path of each gate driver circuit of synchronous rectifier separated make to have remarkable flexibility to optimize its switch control separately regularly.
According to another aspect of the present invention, provide a kind of or,,, be used for the circuit of leading cutoff synchronization rectifier perhaps with respect to conducting they the two perhaps with respect to the conducting clamp switch with respect to the conducting main power switch.This circuit is configured to avoid occurring its possibility by instantaneous high current level, perhaps under " passing " situation, reduces its amplitude.
Description of drawings
By the present invention is described in detail below with reference to accompanying drawing, it is more obvious that feature of the present invention and advantage will become.Among the figure:
Fig. 1 shows the schematic diagram of a basic self-device synchronous rectification device in the known forward converter circuit layout;
Fig. 2 shows the insensitive drive voltage level of variation that is used to utilize to the input voltage level of supply convertor and controllably drives schematic diagram synchronous rectifier, that can realize the supply convertor of each side of the present invention;
Fig. 3 shows the schematic diagram of the first canonical transformation example that comprises discharge resistor, supply convertor embodiment shown in Figure 2;
Fig. 4 shows and comprises and be used to guarantee the schematic diagram of synchronous rectifier in the second canonical transformation example of the discharge switch of its each cut-off state remain off state, supply convertor embodiment shown in Figure 2;
Thereby Fig. 5 shows and realizes the schematic diagram of others of the present invention with respect to the supply convertor of one of the leading cutoff synchronization rectifier of the dynamic realization of the mains switch in the turn-on power converter (SR2);
Fig. 6 shows the typical circuit figure with respect to the leading cutoff synchronization rectifier of the mains switch of turn-on power converter SR2;
Fig. 7 illustrates some typical waveform curve charts of supply convertor embodiment shown in Figure 4;
Fig. 8 illustrates some typical waveform curve charts of supply convertor embodiment shown in Figure 6.
Embodiment
Fig. 2 shows the schematic diagram of the supply convertor 10 of realizing each side of the present invention.Supply convertor 10 comprises by having the transformer 14 of primary transformers winding 12 and secondary transformer winding 16, mutually magnetically coupled primary part 20 and sub section 30.The primary part of supply convertor comprises main power switch (the first switch Q1) and the clamp switch (second switch Q2) that links to each other with the primary transformers winding respectively, and main power switch and clamp switch are configured to usually to move under the conducting of complementation and cutoff switch state.That is to say that in the ideal case, when turn-on power switch Q1, clamp switch Q2 ends, on the contrary, when by mains switch Q1, clamp switch Q2 conducting.In fact, those skilled in the art of the present technique understand, have switching time delay between each switch periods usually, therefore can avoid two switches to occur conducting state simultaneously.Therefore, utilize suitable time delay, then before its conducting, the drain electrode end and the voltage between the source terminal of each switch can discharge into certain degree.
In the embodiment shown in Figure 2, when the first switch Q1 conducting, input voltage (Vin) is applied to the elementary winding 12 of transformer 14, then, secondary winding 16 electromagnetic coupled of input voltage and transformer 14.In an exemplary embodiments, the first switch Q1 comprises main power switch, for example: n channel mosfet (mos field effect transistor) switch.Yet, obviously, the principle of the invention is not limited to switch mosfet, because according to application requirements, can also use the power transistor switch of other type, for example: BJT (bipolar junction transistor), SIT (static induction transistor), IGBT (insulated gate bipolar transistor) etc.
As shown in Figure 2, first drive circuit 40 links to each other with the gate terminal of the first synchronous rectifier SR1, with the grid voltage of supplying with according to first drive circuit, consistent with conducting and the cut-off state of main power switch Q1, at least utilize that first drive circuit 40 is selected, make grid voltage remain on a circuit parameter in the preset range, optionally start or close first rectifier, and change irrelevant with the level of input voltage.
In an exemplary embodiments, first drive circuit 40 comprises the first driving winding Wd1 with the transformer electromagnetic coupled, and further comprises the first capacitor C1 that links to each other with the gate terminal of first synchronous rectifier.The grid 18 that can cause positive voltage being applied to the first synchronous rectifier SR1 by first voltage that drives winding (Wd1) generation by the first capacitor C1.Can see that the voltage magnitude of grid 18 is mainly determined by the ratio of effective grid capacitance of the electric capacity of voltage fluctuation on the winding Wd1 and capacitor C1 and synchronous rectifier SR1.In most of the cases, this scope range of the fluctuation of voltage is less than the fluctuation range of input voltage.In real world devices, when leakage-source voltage improved because of the phenomenon of so-called " Miller effect ", effective grid capacitance of MOSFET equipment can improve usually.This phenomenon can cause gate drive voltage not quite responsive with respect to the variation of incoming line, and improves property.Therefore, according to an aspect of the present invention, if at least correctly select a circuit parameter, for example: first drives the number of turn of winding Wd1, the perhaps capacitance of capacitor C1, perhaps they the two, then in the whole excursion of input voltage, the grid voltage of synchronous rectifier SR1 can remain in the correct scope.Those skilled in the art of the present technique understand that in actual implementation procedure, the capacitance of regulating capacitor is than the easier realization of the number of turn of regulating winding and more effective.Yet obviously, the present invention can imagine any one or two circuit parameters all can be used to realize correct grid voltage according to the requirement of given application.
As shown in Figure 2, driving winding Wd2 by second links to each other with the gate terminal of the second synchronous rectifier SR2 with second drive circuit 50 that the second capacitor C2 constitutes, with the grid voltage of supplying with according to second drive circuit, consistent with conducting and the cut-off state of clamp switch Q2, at least utilize select at second drive circuit 50, make grid voltage remain on a circuit parameter in the preset range, optionally start or close second rectifier, and change irrelevant with the level of input voltage.For example, in case the first switch Q1 conducting, second drives winding (Wd2) at first by the grid capacitance of the second synchronous rectifier SR2, by diode D2 the second capacitor C2 is charged then.When its grid voltage drops to when being lower than its threshold level, synchronous rectifier SR2 ends.When the first switch Q1 by and during the second switch conducting, the polarity of voltage on the primary winding 14 is opposite, the polarity of voltage on the secondary winding is also like this.In this case, the voltage that drives on the winding Wd2 will be applied to positive voltage the grid of synchronous rectifier SR2 with this synchronous rectifier of conducting by capacitor C2.In addition, correctly select the number of turn of the second driving winding Wd2 and/or the capacitance of capacitor C2 can guarantee in whole input voltage range, synchronous rectifier SR2 to be had correct drive voltage level.
In case second switch Q2 conducting, with the same manner of stage synchronous rectifier SR2 realization formerly, the voltage that drives on the winding Wd1 discharges the grid of synchronous rectifier SR1.That is to say, in case the first switch Q1 conducting, according to another aspect of the present invention following detailed description, utilize the first driving winding Wd1 and the second driving winding Wd2 to come that synchronous rectifier SR1 is separated the drive current path with SR2 and can advantageously finely tune the driving timing of synchronous rectifier SR1 and SR2 respectively, thereby further improve the efficient of converter.
For during " ending " state separately, guarantee the actual remain off of grid voltage of synchronous rectifier SR1 and SR2, as shown in Figure 3, can be optionally a pair of discharge resistor R1 and R2 be connected to each grid of synchronous rectifier SR1 and SR2.Those skilled in the art of the present technique understand that resistor can be released in the electric charge that accumulates on the grid separately of synchronous rectifier SR1 and SR2 to R1 and R2, otherwise these charges accumulated people starts to " conducting " state with any one synchronous rectifier with leading to errors.
According to another aspect of the present invention, as shown in Figure 4, can be optionally the first discharge switch Qd1 and the second discharge switch Qd2 be connected to the grid of synchronous rectifier SR1 and SR2.Those skilled in the art of the present technique understand, when these two rectifiers were set to " ending " state, operated discharge switch Qd1 and Qd2 can provide discharge path for synchronous rectifier SR1 and SR2.For example, when the voltage that driving winding Wd1 provides by capacitor C1 is high level, then the gate terminal of discharge switch Qd2 is charged to high level, and this discharge switch is set to " conducting " state, provides discharge path by discharge switch Qd2 for the gate terminal of synchronous rectifier SR2 then.Equally, deliver to the gate terminal of discharge switch Qd1 by capacitor C2 when driving positive voltage that winding Wd1 will be higher than the threshold voltage of the grid of discharge switch Qd1, and this discharge switch can also advantageously provide discharge path for the gate terminal of synchronous rectifier SR1 by discharge switch Qd1 when being set to " conducting " state.In an exemplary embodiments, suppose that discharge switch Qd1 and Qd2 comprise switch mosfet, then with in Fig. 2 and the diode D2 and the integrated embedding of D1 discharge switch Qd1 and Qd2 as shown in Figure 4 shown in Figure 3.As mentioned above, can also optionally add according to the discharge resistor R1 of Fig. 3 explanation and R2 with electric charge that accumulate, that can start to " conducting " state mistakenly on the grid separately of guaranteeing to be released in better synchronous rectifier SR1 and SR2.
Those skilled in the art of the present technique understand, in above-mentioned each circuit, damped resistor can be connected with capacitor C1 and C2 respectively to reduce current changing rate (di/dt) to (not shown),, thereby provide desirable damping drive circuit with the reduction electromagnetic interference (EMI).
In some designs, the leakage inductance of transformer 14 is less, and as mentioned above, behind the turn-on power switch Q1, foregoing circuit can bear of short duration but undesirable " passing " cycle.Specifically, when mains switch Q1 conducting, suppose roughly moment conducting, then the voltage on the primary winding 14 is input voltage, and this input voltage is connected to secondary power winding 16 and drives winding Wd1 and Wd2.Because in the attainable implementation procedure of physical method, because there are some non-zero impedance in the path, so the voltage on the grid voltage of synchronous rectifier SR2 and the capacitor C2 needs finite time to discharge and charges, if secondary winding voltage is for just, and instantaneous " conducting " state that still keeps of synchronous rectifier SR2 then can have cycle blink.As mentioned above, this situation is exactly " passing " situation, and therefore, the electric current by the synchronous rectifier SR2 and the first switch Q1 raises rapidly, and SR2 ends up to synchronous rectifier.Those skilled in the art of the present technique understand, can utilize the amount of resistance in " passing " situation duration, input voltage amplitude and the path to determine the current spike amplitude.
In order to eliminate or " to pass " situation, in an exemplary embodiments, be preferably in before the conducting synchronous rectifier SR1 cutoff synchronization rectifier SR2 in a moment from reducing this in fact.Embodiment shown in Figure 5 provides a kind of effectively circuit 100 of clamp forward converter cloth intra-office of typical case of supposing, circuit 100 is with respect to the dynamic leading cutoff synchronization rectifier SR2 of turn-on power switch Q1.Note that for fear of loaded down with trivial details dependent part element shown in not shown driving winding Wd1 and Wd2 and the above-mentioned accompanying drawing in Fig. 5.Yet obviously, driving winding Wd1 and Wd2 and associated components is the part of circuit shown in Figure 5.As shown in Figure 5, can will be connected to synchronous rectifier such as the drive circuit 90 that constitutes by the 3rd driving winding Wd3 and the 3rd capacitor C3.In an exemplary embodiments, when needing, can also drive winding Wd3 with the 3rd and be stacked on driving winding Wd1 upward to reduce the number of turn of winding Wd3.Can also other leading switching circuit (not shown) identical with circuit 100 be set in fact for synchronous rectifier SR1.
In a word, in active-clamp forward converter, before conducting main switch Q1, by clamp switch Q2.According to an aspect of the present invention, the present inventor recognizes that these characteristics can be advantageously used in respect to conducting main power switch Q1 with innovating, and synchronous rectifier SR2 is realized ending in advance of requirement.For example, when switch Q2 by the time, the voltage on the primary winding 14 will change along with the transformer magnetizing current to leakage-source capacitor discharge of switch Q1.During this period, become 0 across the voltage on the elementary winding of transformer T1 from negative value.Utilize the positive voltage on above-mentioned positive dv/dt rate of change (even the absolute value of discharge voltage is still for negative) and the capacitor C3, suppose this capacitor is pre-charged to suitable level, then positive voltage can be connected to the grid of discharge switch Qd2, thereby make the grid discharge of synchronous rectifier SR2.This action meeting cutoff synchronization rectifier SR2, and need not to wait for that switch Q1 is switched on.As mentioned above, in an exemplary embodiments, synchronous rectifier SR1 can not respond above-mentioned action, and can not be when cutoff synchronization rectifier SR2, conducting synchronous rectifier SR1, therefore can so just can avoid or eliminate the situation of passing between SR2 and conducting SR1, providing effective controlled time delay.
Fig. 6 shows the detailed circuit implementation procedure according to the exemplary embodiments of the circuit 100 of Fig. 5 explanation.Setting comprises the discharge switch Qd3 separately of gate terminal, source terminal and drain electrode end separately, and when needing, drive circuit 90 links to each other with transformer positive voltage is applied to the source terminal of discharge switch Qd3.When the needs positive pulse was come conducting discharge switch Qd2, capacitor C3 provided positive voltage to the drain electrode of discharge switch Qd3.The gate terminal of discharge switch Qd3 links to each other with second drive circuit of node N1 and detects the change in voltage that produces with (for example) by clamp switch the time.Further the gate terminal of discharge switch Qd3 is setovered, therefore, the gate voltage level that the change in voltage that causes when clamp switch produces can start to switch Qd3 corresponding conducting state, this positive voltage is delivered to the grid of the second discharge switch Qd2, and be provided to the path of the second synchronous rectifier SR2 grid by second discharge switch, so just can guarantee before the conducting first synchronous rectifier SR1, to end this second synchronous rectifier, and can avoid passing through thus the possibility of the high level of electric current in the appearance of following moment of " passing " situation.
In exemplary embodiments shown in Figure 6, the bias voltage that the Vsec representative applies by resistor R 20.As mentioned above, discharge switch Qd3 can provide following function: at first, according to the voltage on the switch Qd3 grid, discharge switch Qd3 controls the voltage that is applied to the second discharge switch Qd2 grid.In addition, after the grid to discharge switch Qd2 applies positive voltage, of short duration by discharge switch Qd3.In an exemplary embodiments, the method for ending the 3rd discharge switch Qd3 reduces the voltage of (as shown in Figure 4) by node N1 exactly.That is to say that by resistor R 10, the voltage that the line of node N1 can provide driving winding Wd2 is applied to circuit 100.Capacitor C4 provides the ability of the ON time of regulating the 3rd discharge switch Qd3.In case the 3rd discharge switch Qd3 ends, then the grid of the second discharge switch Qd2 is by resistor R 30 discharge, and before next switch events occurring the grid voltage of the second discharge switch Qd2 is set to the gate threshold that is lower than the second discharge switch Qd2.
Fig. 7 shows some typical waveform curve charts of supply convertor shown in Figure 4.Vg_Q1 and Vg_Q2 represent typical gating signal that mains switch Q1 and clamp switch Q2 are applied respectively.V_x represents the voltage of the convergence point between winding Wd1 and capacitor C1; V_y represents the voltage of the convergence point between winding Wd2 and capacitor C2.All voltages are benchmark with the source terminal of synchronous rectifier SR1 and SR2 all.
As mentioned above, utilize the product of ratio of the electric capacity of the electric capacity of the voltage fluctuation of respective drive winding (Wd1 and Wd2) and C1/C8_SR1 and C2/C8_SR2, come to determine respectively each gate voltage level Vg_SR1 and Vg_SR2 of synchronous rectifier SR1 and SR2.For example, if the fluctuation of the positive voltage on the Wd1 is 10v, and C1=Cg_SR1, then the amplitude of Vg_SR1 is 5V.Voltage fluctuation is the turn ratio that the amplitude of Vds_Q1 multiply by transformer.
As mentioned above, if when conducting SR1, or after conducting SR1, actual cutoff synchronization rectifier SR2, then because the cut-off speed of other appurtenances in physical equipment and the circuit is limited, so before complete cutoff synchronization rectifier SR2, have of short duration " passing " cycle, this can cause the transformer secondary output short circuit, thereby produces high current spike.In some cases, even this situation of passing can reduce supply convertor performance, break down and damage some parts.
Fig. 8 shows the wavy curve figure of supply convertor embodiment shown in Figure 6.V_z represents the voltage of the convergence point between winding Wd3 and capacitor C3.If first voltage amplitude that drives on the winding Wd1 is enough high, then do not need the 3rd to drive winding Wd3.If like this, then capacitor C3 can be connected to first and drive winding Wd1.Vg_Qd3 and Vg_Qd2 represent gating signal that discharge switch Qd3 and Qd2 are applied respectively.As shown in Figure 8, the graphical representation of gating signal Vg_SR2, can before actuating switch Q1, end this rectifier in advance, so just can make this technology advantageously be applied to the flyback converter that only constitutes in a controlled manner by a secondary synchronization rectifier, and the possibility that can avoid like this may occurring with other method, cause high current level in " passing " situation.
Those skilled in the art of the present technique understand that the principle of above-mentioned discussion can also be applied to other converter topology equally, for example: flyback converter, half bridge converter and full-bridge converter.Although can adopt centre tap secondary winding and a large amount of synchronous rectifiers in than complex topology at these, but the requirement of the synchronous rectifier of these cloth intra-offices roughly with the typical forward converter topology in the synchronous rectifier that adopts require identically, can also advantageously improve their performance in this technology that provides and circuit.
Although show and illustrated the preferred embodiments of the present invention at this,, obvious these embodiment that provide are only as an example.Those skilled in the art of the present technique can carry out various conversion, change and replacement to it within the scope of the present invention.Therefore, have only the described essential scope of claims that the present invention is had limited significance.
Claims (10)
1. a supply convertor comprises that described transformer has corresponding primary transformers winding and secondary transformer winding by transformer mutually magnetically coupled primary part and sub section, and this supply convertor comprises:
At least one first synchronous rectifier, link to each other with the secondary transformer winding, during being in conducting state, according to the input voltage that the primary transformers winding is applied, by voltage in described secondary winding induction at the main power switch that links to each other with the primary transformers winding; And
First drive circuit, link to each other with the gate terminal of first synchronous rectifier, by in described first drive circuit, selecting a circuit parameter at least, grid voltage is remained in the preset range, and it is irrelevant with the level fluctuation of input voltage, make the grid voltage of supplying with according to described first drive circuit, consistent with the conducting and the cut-off state of main power switch, optionally start or close first rectifier.
2. supply convertor according to claim 1, this supply convertor further comprises: second synchronous rectifier, second synchronous rectifier links to each other with the secondary transformer winding, during being in conducting state, by voltage in described secondary winding induction in the clamp switch that links to each other with the primary transformers winding; And
Second drive circuit, link to each other with the gate terminal of second synchronous rectifier, by in described second drive circuit, selecting a circuit parameter at least, grid voltage is remained in the preset range, and it is irrelevant with the level fluctuation of input voltage, make the grid voltage of supplying with according to described second drive circuit, consistent with the conducting and the cut-off state of clamp switch, optionally start or close second rectifier.
3. supply convertor according to claim 1 and 2, wherein said each drive circuit comprises the driving winding with the transformer electromagnetic coupled, and further comprises the capacitor that links to each other with the gate terminal of corresponding synchronous rectifier.
4. supply convertor according to claim 1 and 2, this supply convertor further comprise the continuous discharge resistor that is used for the grid of each synchronous rectifier is provided the correspondence of discharge path.
5. supply convertor according to claim 2, this supply convertor further comprises: first discharge switch, the gate terminal of first discharge switch links to each other with second drive circuit, with during being in the operational mode of cut-off state corresponding to first synchronous rectifier, by described first discharge switch, dynamically be provided to the discharge path of the grid of first synchronous rectifier, thereby guarantee described first synchronous rectifier remain off under its cut-off state; And second discharge switch, the gate terminal of second discharge switch links to each other with first drive circuit, with during being in the operational mode of cut-off state corresponding to second synchronous rectifier, by described second discharge switch, dynamically be provided to the discharge path of the grid of second synchronous rectifier, thereby guarantee described second synchronous rectifier remain off under its cut-off state.
6. supply convertor according to claim 2, this supply convertor further comprises and being used for respect to the conducting main power switch, end second synchronous rectifier in advance, and avoid under " passing " situation, occurring the circuit of the possibility of high current level by its moment.
7. supply convertor according to claim 6, the circuit that wherein is used for ending in advance second synchronous rectifier comprises: transistor has gate terminal, source terminal and drain electrode end; And drive circuit, with the transformer electromagnetic coupled during being in conducting state at main power switch positive voltage is applied to the source terminal of transistor switch, the change in voltage that the gate terminal of transistor switch links to each other with second drive circuit and produces by clamp switch the time to detect, further the gate terminal of bias transistor switch so that clamp switch by the time the gate voltage level that produces of change in voltage transistor switch is started to conducting state, thereby this positive voltage is applied to the grid of second discharge switch, and by described second discharge switch, be provided to the discharge path of the second synchronous rectifier grid, therefore, can guarantee before the conducting main power switch, to end this second synchronous rectifier, and avoid under " passing " situation, occurring the possibility of high current level by its moment.
8. method that is used to control supply convertor, this supply convertor comprises that described transformer comprises primary transformers winding and secondary transformer winding by transformer mutually magnetically coupled primary part and sub section, the method comprising the steps of:
Be connected to the secondary transformer winding to major general's first synchronous rectifier, during being in conducting state, according to the input voltage that is applied to the primary transformers winding, by voltage in described secondary winding induction at main power switch; And
First drive circuit is connected to the gate terminal of first synchronous rectifier, consistent with the grid voltage that applies according to described first drive circuit with the conducting and the cut-off state of main power switch, optionally start or close first rectifier; And
Described first drive circuit selects a circuit parameter to be used to make grid voltage to remain in the preset range at least, and irrelevant with the variation of input voltage level.
9. method according to claim 8, this method further comprises:
Second synchronous rectifier is connected to the secondary transformer winding, during being in conducting state, by voltage in described secondary winding induction in the clamp switch that links to each other with the primary transformers winding; And
Second drive circuit is connected to the gate terminal of second synchronous rectifier, consistent with the grid voltage that applies according to described second drive circuit with the conducting and the cut-off state of clamp switch, optionally start or close second rectifier; And
Described second drive circuit selects a circuit parameter to be used to make grid voltage to remain in the preset range at least, and irrelevant with the variation of input voltage level.
10. method according to claim 9, this method further comprises, under operational mode corresponding to the cut-off state of first synchronous rectifier, be provided to the discharge path of the grid of first synchronous rectifier, thereby guarantee described first synchronous rectifier remain off when it is in cut-off state; And under operational mode, be provided to the discharge path of the grid of second synchronous rectifier, thereby guarantee described second synchronous rectifier remain off when it is in cut-off state corresponding to the cut-off state of second synchronous rectifier.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US26783601P | 2001-02-09 | 2001-02-09 | |
| US60/267,836 | 2001-02-09 | ||
| US10/062,639 | 2002-02-01 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1381942A true CN1381942A (en) | 2002-11-27 |
| CN1295853C CN1295853C (en) | 2007-01-17 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 02104726 Expired - Lifetime CN1295853C (en) | 2001-02-09 | 2002-02-09 | Supply transformer containing circuit for controlling synchronous rectifier |
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Cited By (14)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN100369370C (en) * | 2003-07-28 | 2008-02-13 | 艾斯泰克国际公司 | Circuit and method for controlling a synchronous rectifier in a power converter |
| CN100388609C (en) * | 2003-10-24 | 2008-05-14 | 中兴通讯股份有限公司 | Driving device of synchronous rectifier transistor |
| CN100479317C (en) * | 2003-12-02 | 2009-04-15 | 大动力公司 | Unregulated DC-DC converter having synchronous rectification with efficient gate drives |
| CN101582637A (en) * | 2008-05-13 | 2009-11-18 | 三美电机株式会社 | Power source apparatus |
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