CN1349143A - Stable switching voltage regulator - Google Patents

Stable switching voltage regulator Download PDF

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Publication number
CN1349143A
CN1349143A CN 01113745 CN01113745A CN1349143A CN 1349143 A CN1349143 A CN 1349143A CN 01113745 CN01113745 CN 01113745 CN 01113745 A CN01113745 A CN 01113745A CN 1349143 A CN1349143 A CN 1349143A
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voltage
output
power
diode
circuit
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CN1161875C (en
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周符明
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Priority to CNB011137452A priority Critical patent/CN1161875C/en
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Priority to PCT/CN2002/000452 priority patent/WO2003005543A1/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a switch type stable power supply. It includes a convertor with steady power whose conversion is based on output inductance and a controller circuit with steady power. With imputting DC or rectified AC being received by the controller circuit, it can regulate the value of output direct current or voltage from minimum to limited value by two ways random adjusting for a load to use. The invention has features of large regulating range, high working efficiency. Only one switch tube with withstand voltage 600V is used.

Description

Stable switching voltage regulator
The present invention relates to Switching Power Supply, especially a kind of stable switching voltage regulator belongs to power technique fields.
Stable switching voltage regulator of the present invention can with the input direct current and the alternating current after the rectification is for conversion into electric current and voltage can be exported to load from minimal value to the direct current of limit value random two-way adjustment respectively, because of electric power is the product of voltage and electric current, so stable switching voltage regulator of the present invention comprises switch stabilized current supply and switching power supply, switch stabilized current supply of the present invention or switching power supply be a kind of form of expression of stable switching voltage regulator of the present invention only, here said " surely " word, except the output voltage that makes power supply is arranged, electric current and electric power are stabilized in outside the implication of a certain numerical value, make the output voltage of power supply in addition, electric current and electric power are limited to the implication of a certain numerical range, moreover, it makes the output voltage of power supply in addition, the implication that electric current and electric power change by certain funtcional relationship given in advance, therefore, also stable switching voltage regulator of the present invention can be referred to as the switch function power supply.
Switching Power Supply has independently experienced nearly half a century since the power technology appearance as one, during this period, the power supply theory relevant with switch power technology, converter design, control method, material devices, production technology, aspects such as product application have all obtained very big progress and development, yet, after furtheing investigate this technology, we find but that it still exists some problems and needs to solve, and the problem that has also has of overall importance, it is relevant below to try to list theme several and of the present invention, and the problem that is resolved substantially in stable switching voltage regulator of the present invention is done a concise and to the point elaboration.
Which feature if to being engaged in the power technology specialty and having the engineers of certain design experiences to put question to: on the basis of current material device, the power supply of " ideal " design should have? some following contents occur in " answer " possibly:
1), the working current of power supply is preferably continuous.---the working current of existing Switching Power Supply is generally all discontinuous, cause the reason of this situation relevant with the control theory of the Switching Power Supply control mode that generally adopts at present and institute's foundation thereof, as being example with present the most frequently used control mode " fixed frequency modulated PWM system ", it is with the switch fixed work period, the ON time of adjusting switch is controlled a kind of Switching Power Supply control mode of output, this control mode based on control theory think: in switch conduction that same switch periods comprised and switch two times, as long as adjust one of them---the switch conduction time, just can control the output of power supply, therefore, the control mode of all employing fixed frequency modulated PWMs is come designing power supply, all with output power when maximum required time of afterflow serve as according to reserving switch closing time, so, then just must cause the discontinuous of working current during less than the peak power output of power supply when the required power of load, be understood that, " floatless switch work period " and " reservation switch closing time " is a kind of " restrictive practice ", its essence is the corrective action of closing time to exporting of " abandoning " switch, and only utilize this portion of time of switch conduction to adjust the output of power supply, limitation just because of this " dullness " control theory and method existence, except that the working current that causes power supply is discontinuous, other many " blind spots " in the power supply design have also been caused.
2), preferably a kind of way that reduces the high-frequency transformer inverse peak voltage can be arranged, make from now on only low withstand voltagely with one, switching tube just can carry out conversion to the 220V power frequency supply as withstand voltage 600V.---this is the ubiquitous problem of present AC-DC Switching Power Supply, in decades, people are in order to solve this difficult problem, designed countless converter circuit around high-frequency transformer, but do not find a gratifying solution so far yet, why this problem " fails to solve after a long delay ", we think relevant with the control theory and the method for long-term prevailing fixed frequency modulated PWM, a design blind spot that might as well it can be regarded as causes by the control theory and the method for this " dullness ", at present, representational single-end ortho-exciting, half-bridge or full-bridge converter all are with the be together in series inverse peak voltage that bears high-frequency transformer jointly of two switching tubes, though this way " effectively " has also been brought repetition, waste, negative side such as poor efficiency and poor reliability.We know, " inverse peak voltage " is a kind of performance of magnetization energy when switch turn-offs that deposits high-frequency transformer during the switch conduction in, and magnetization energy can only, also must close at switch and dispose between the off period have no progeny, can efficiently handle the way that magnetization energy can effectively limit inverse peak voltage again exists, that will provide one " impedance path " for magnetization energy exactly in time, and for magnetization energy pass through to provide a period of time, but above " dullness " control method does not possess this condition.
3), whether the magnetization energy of single-ended forward converter medium-high frequency transformer can not fed back to the input power supply, and solve the magnetic-reset problem of high-frequency transformer with other more positive ways.---the magnetic-reset problem and the above-mentioned inverse peak voltage problem homology of high-frequency transformer, all cause by magnetization energy, and nearly three kinds of the processing approach of magnetization energy: 1, return to the input power supply; 2, export to load; 3, consume on the spot.; the single-ended forward converter that is subjected to fixed frequency modulated PWM control is except that " consuming on the spot " this processing approach; just can only select magnetization energy has been returned to a kind of practice of power supply; what the energy of importing high-frequency transformer was returned to that power supply does again is " idle work "; do the big defective of inefficiency, loss of devices such as not only causing high-frequency transformer and switching tube like this, it has gone back " waste " time of transmission of power! If the magnetization energy of a power supply is not to return to input power supply but exported to load, that just means that we can obtain following " income ": 1, the high-frequency transformer of available smaller size smaller obtains bigger output power, thereby can reduce the volume of power supply.2, switch frequency of operation that can be lower obtains bigger output power, thereby can reduce the open and close loss of switching tube.3, can the short switch conduction time obtain bigger output power, thereby can reduce the tube voltage drop loss of switching tube.4, can be the inverse peak voltage that reduces high-frequency transformer one " impedance path " is provided, and then for adopting low withstand voltage switching tube to come conversion 220V power frequency supply to create conditions.
4), a kind of new high efficiency current sampling method that is substituted in the conventional current sampling method of resistance in series in the loop of power circuit can be arranged preferably.---this problem always is a power technology, " bottleneck " of the switch power technology development of especially being good at small size, high power density, " obstacle " that its stable switching voltage regulator of the present invention especially must be forgone.
5), the output current and the voltage of what a power supply can be adjusted from minimal value to the limit value random two-way respectively.---perhaps this be that each is engaged in the idea that the professional of power supply design had, it also is the main task of stable switching voltage regulator of the present invention, from Specialized Theory and application point of view, in a single day power supply has possessed above performance, not only its purposes can greatly be expanded, and its inherent technical indicator also will be significantly improved.
6), preferably can solve the output problem synchronously in parallel of high frequency switch power, to break through the limitation of Switching Power Supply maximum design power.---at present, owing to exist multiple limiting factor, the maximum design power of a Switching Power Supply generally can only be accomplished several kilowatts, speciality circles generally acknowledge that the design power that Switching Power Supply has only realization synchronous output in parallel could finally break through Switching Power Supply limits, could satisfy such as electrolysis, electroplate the high frequency needs of a class electric current in the power supply in kilo-ampere, Wan An, the advantage of competence exertion high frequency switch power.
Above problem seems independently of one another, exist certain relevance in fact between them, go singly to address these problems if attempt, people's effort shows, perhaps, this still is a difficult and very long road, so, wheresoever be " crux " of these problems? we find when the structure of research switching power converters for a long time: no matter be the transducer that only contains single inductance, or comprise the transducer of inductance and high-frequency transformer simultaneously, they all have one " transform center ", this transform center is exactly that output terminal that is placed in transducer is pressed close to the inductor of load most, be the present invention's alleged " outputting inductance ", in the past, as if may be the cause that influenced by the AC transformer power supply, people have also treated high-frequency transformer habitually as the transform center of Switching Power Supply, actually this is not so, transformation of electrical energy, especially the transformation of electrical energy that carries out with switch power technology be unable to do without inductance, electric capacity and switch etc., but could be without transformer! About this point, the simplest single inductance converter in the Switching Power Supply that as long as we in depth investigate, just be not difficult to understand this reason, therefore, Switching Power Supply can no thing be treated as the transform center of switching power converters to begin be exactly one " misunderstanding ".Why outputting inductance can become the transform center of switching power converters, be because it " is held " on the necessary channel of transducer output current, it is unique device by whole output currents in the transducer, outputting inductance itself is just being undertaken NE BY ENERGY TRANSFER, current limliting, accumulation of energy, release and to wait key effect, no matter your subjective certain a part of characteristic of wanting to utilize outputting inductance, but objectively it also will carry out " last conversion " to all electric energy by it, comprise at the same time in the transducer of high-frequency transformer and outputting inductance, in fact electric energy has been transformed twice, once in high-frequency transformer, carry out, another time carried out in outputting inductance, the conversion that the latter is compared in twice conversion is main, the former then assists in the conversion of high-frequency transformer, less important, because outputting inductance is the transform center of Switching Power Supply, so the Switching Power Supply design should be carried out around this center, form in all multifunction devices and element circuit of Switching Power Supply at all, we have only and have handled other parts that outputting inductance just can be handled circuit well earlier well, could find the most appropriate solution for the variety of issue that Switching Power Supply occurs, and can key that handle outputting inductance well be allow it be operated in " optimum condition ", that is to say, we should subjectively not go to arrange a kind of mode of operation for outputting inductance, and the natural situation should be operated in optimum condition by outputting inductance the time is controlled in good time, we know, current waveform when outputting inductance is operated in optimum condition shows as " continuous triangle ripple ", can make the current waveform on the outputting inductance keep the continuous triangle ripple just to become design switch power controller " key " so, stable switching voltage regulator of the present invention is with " the continuous triangle ripple that keeps electric current on the outputting inductance " conduct " principle of design ", according to this principle of design: the control mode of switch power controller must be " Switching Two modulation ", this is the Switching Power Supply control mode that output is controlled in a kind of shutoff of not only having adjusted the unlatching ON time of switch but also having adjusted switch closing time, and having the control mode that Switching Two transfers only could be adaptive with the continuous triangle phase of wave of electric current on the outputting inductance; According to this principle of design: switch power controller need not to be provided with independently " oscillator ", controller itself is unlatching, ON time and shutoff, the closing time of direct determine switch not, the unlatching of switch, ON time and shutoff, closing time are to be decided by the rising of continuous triangle ripple on the outputting inductance and the time curve of decline, and the rising of continuous triangle ripple and the time curve of decline are then decided by outputting inductance and input, output parameter on the final outputting inductance.
The object of the present invention is to provide a kind of stable switching voltage regulator, this power supply can be with the direct current of input and the direct current high-level efficiency that be transformed into current limliting voltage stabilizing, pressure limiting current stabilization, voltage stabilization and current stabilization and power stabilize of the alternating current after the rectification, high power, intelligently offer load.
Another object of the present invention is to provide a kind of broad-spectrum stable switching voltage regulator, this power supply can also be designed to it seriation, modular power stabilize multiple power source except can be used in power source special fields such as electroplating power supply, electrolysis power, the source of welding current, charge power supply, DC UPS, communication power supply, ultrasonic-frequency power supply, medical power supply, instrument power supply, DC motor speed-regulating power supply.
Another purpose of the present invention is to provide that a kind of output function is many, setting range is big, workload-adaptability is strong; The power device high efficiency, loss is little, temperature rise is low; Only can carry out conversion to the 220V power frequency supply with the following switching tube of a withstand voltage 600V; Be provided with output function synchronously in parallel; Versatility is good, seriation, modular sequence are few; And the stable switching voltage regulator that machine volume is little, in light weight, cost is low.
Final purpose of the present invention is to promote by the present invention the progress and the development of power technology, power supply industry and application of power.
In order to reach the foregoing invention purpose, stable switching voltage regulator of the present invention comprises outputting inductance (L1), also comprises input circuit (Vi); Switch (U1) and trigger circuit; Fly-wheel diode (D1); Output circuit (RL and C1 parallel connection); Voltage comparator (IC1) circuit and output (OUT) thereof; By divider resistance (R2 and R3 series connection) and isolating diode (D2) and (D5) voltage sampling circuit of formation; The LRC electric current sync peaks sample circuit that constitutes by outputting inductance (L1) and sampling resistor (R1), sampling capacitance (C2) and blocking diode (D6), earial drainage diode (D3); LD on-off circuit by outputting inductance (L1) and switching diode (D4) formation; The RC that is made of accelerating resistor (R6) and speed-up capacitor (C3) quickens and shockproof circuit; The voltage that is made of operational amplifier (IC2), divider resistance (R4 and R5 series connection), current-limiting resistance (R8), filter capacitor (C5) is reference voltage circuit at random; The electric current that is made of operational amplifier (IC3), current-limiting resistance (R9), filter capacitor (C6), isolating diode (D7) is reference voltage circuit at random; CRD peak clipping buffer circuit by peak clipping electric capacity (C0), despiking resistance (D0) and buffering diode (D0) formation, in addition, it also comprises by fly-wheel diode (D1), output diode (D9) and diode (D01) and the full-wave rectifying circuit (D09) formed; Adjustable or fixed current reference voltage source (V IOR) circuit; Adjustable or fixed voltage reference voltage source (V VOR) circuit; Fixed current reference voltage (W1) circuit; By outputting inductance (L1), switching diode (D4), the LDD synchronous output switch circuit in parallel that constitutes of diode (D8) and lead-out terminal in parallel (X1) etc. synchronously.
Have letter before the title of some element circuit of the present invention, as: " RC ", " LRC ", " LDD " etc., this is a kind of expression way that this paper takes, components and parts generally only represented in each letter wherein, and according to usage: " R " represents resistance, " C " represents electric capacity, " L " represents inductance, " D " represents diode etc., take the purpose of this expression way to be the depth of indexing specificity of accentuator, circuit difference as much as possible that purposes is different and that obscure is easily come, be example for example with " LD and LDD switch " circuit, this is the height that utilizes outputting inductance (L) its terminal voltage when work, hang down variation and make a diode (D) or two diodes (DD) be operated in conducting, by a kind of on-off circuit of two states, but we can not be called " switch " simply with these two circuit and promptly are.
Leading thinking of the present invention is: be the transform center of power supply with the outputting inductance; Keeping the current waveform of outputting inductance is the continuous triangle ripple; Adjust the input and output of power supply with Switching Two regulation and control system mode; Load is exported in the magnetization energy series connection of high-frequency transformer and outputting inductance; The Low ESR that utilizes the buck converter output terminal to present reduces the inverse peak voltage of high-frequency transformer; Adopt LRC electric current synchronized sampling circuit that output current is carried out controlling of sampling; Utilize operational amplifier to produce electric current reference voltage and voltage reference voltage at random at random; Utilize the output synchronously in parallel of the continuous triangle wave-wave shape consistance realization power supply in time of each parallel connection power supply outputting inductance, the present invention has following main points:
1), transducer and controller be Switching Power Supply two basic compositions partly, at this, for the ease of narration, stable switching voltage regulator of the present invention also is divided into transducer and controller two partly, and they is called: power stabilize transducer and power stabilize controller.But, at this of particular note: because stable switching voltage regulator of the present invention does not have separate oscillators, therefore power stabilize transducer of the present invention is different with traditional transducer and controller with the power stabilize controller, some device of forming power stabilize transducer of the present invention also participates in the work of power stabilize controller simultaneously, they also are the parts of power stabilize controller simultaneously, it is exactly " a sharing " device that had not only belonged to the power stabilize transducer but also belonged to the power stabilize controller such as " outputting inductance ", therefore strictly speaking, stable switching voltage regulator of the present invention is an indivisible integral body, and its " controller " do not have " versatility ".
2), essence from " transformation of electrical energy ", form that to have only high-frequency transformer and outputting inductance in all devices of above power stabilize transducer be " energy storage means ", thereby they are transformation of electrical energy " the main transducers that make ", make how much dividing of transducer as transducer to contain the master, the power stabilize transducer both can comprise high-frequency transformer and two masters of outputting inductance make transducer so, also can only contain master of outputting inductance and make transducer, stable switching voltage regulator of the present invention is different with traditional Switching Power Supply, it is with this main transducer " central transducer " as power stabilize transducer of the present invention that make of outputting inductance, and make the transducer high-frequency transformer as " auxiliary converter " another master, its reason is touched upon in preamble, in brief, doing so only is the true colours of going back them.
3), can form two kinds of power stabilize transducers: 1, DC-DC voltage-dropping type power stabilize transducer by central transducer and auxiliary converter---with the dc high voltage or the dc high voltage after the rectification of input is the power stabilize transducer of DC low-voltage output by the direct decompression transformation of central transducer.2, pre-buck or boost DC-DC voltage-dropping type power stabilize transducer---is the power stabilize transducer of DC low-voltage output with the DC voltage or the DC voltage after the rectification of input again by the central transducer decompression transformation through the pre-buck or boost of high-frequency transformer.
More than two kinds of power stabilize transducers a common feature is arranged, be that they all finish conversion to the input power supply at last with central transducer " decompression transformation ", and auxiliary converter only provides a suitable voltage that is higher than output voltage to central transducer in this effect, and it is central transducer " voltage source ".
As single angle from " function ", as long as with second kind in above two kinds of power stabilize transducers is that pre-buck or boost DC-DC voltage-dropping type power stabilize transducer just can carry out conversion to the voltage of all inputs, and first kind of DC-DC voltage-dropping type power stabilize transducer of necessary employing, this shows that first kind of power stabilize transducer only is fit under the specified conditions of Direct Transform a kind of " simplification " to second kind of power stabilize transducer just at input voltage.
4), power stabilize transducer of the present invention is central transducer with the outputting inductance, the design of stable switching voltage regulator will be carried out around outputting inductance, and the optimum Working of outputting inductance shows as electric current " continuous triangle ripple ", therefore the present invention is defined as " the continuous triangle ripple that keeps electric current on the outputting inductance " " principle of design " of stable switching voltage regulator, take Switching Two modulated control mode suitable with it, being commonly defined as of this control mode: not only to adjust the switch conduction time but also adjust a kind of Switching Power Supply control mode that switch is controlled output closing time.In addition, the present invention takes another thought starting point of " Switching Two modulation " to be: the actual two parts that have been divided into of Switching Power Supply energy of input translator during switch conduction, a part has been exported to load through transducer, another part then has been stored in high-frequency transformer and the outputting inductance as magnetization energy, magnetization energy need be disposed between the off period at switch, and the optimal selection of handling magnetization energy is that it is exported to load, and makes switch equal magnetization energy closing time to export to the required time of load.Therefore, the Switching Two regulation and control system mode that stable switching voltage regulator of the present invention can be used is further defined as: to adjust the energy of switch conduction time control input translator, and make it closing time to equal magnetization energy is exported to a kind of Switching Power Supply control mode that the required time of load controls output to adjust switch, Switching Two regulation and control system mode of the present invention is combined by power stabilize transducer and power stabilize controller and finishes.
To sum up chat, be central transducer with the outputting inductance, keep on the outputting inductance continuous triangle ripple current waveform, do not establish independently oscillator, take Switching Two regulation and control system mode, magnetization energy is exported to load and make switch equal magnetization energy closing time that to export to the required time of load be the key character of stable switching voltage regulator of the present invention.
5), promptly there be the processing and the magnetic core reset issues of high-frequency transformer magnetization energy in the power stabilize transducer that contains high-frequency transformer, the present invention to export to load with the magnetization energy of high-frequency transformer and its magnetic core is resetted in order to realize, especially set up one group " afterflow reset winding " at the secondary of high-frequency transformer, and it and outputting inductance is together in series, be arranged in " time of afterflow " lining that switch ends the magnetization energy of high-frequency transformer is exported to load with the magnetization energy of outputting inductance, the magnetic core of high-frequency transformer and outputting inductance is resetted.
6) all be " voltage-dropping type " transducer, because of power stabilize transducer of the present invention, so the magnetization energy of high-frequency transformer is exported to load promptly to be meaned for magnetization energy one " impedance path " is provided, therefore, the present invention further the reset number of turn of the number of turn of winding and high-frequency transformer output winding of high-frequency transformer afterflow is set to equate, reduce the afterflow winding that resets with this and reflect inverse peak voltage, and then realize the purpose of only coming conversion 220V power frequency supply with the switching tube below the withstand voltage 600V to high-frequency transformer input winding.
The magnetization energy of high-frequency transformer is exported to load mean that also therefore, available lighter, less high-frequency transformer weight, volume obtain bigger output power in the utilization factor that improves high-frequency transformer; The magnetization energy of high-frequency transformer is exported to load also means the work efficiency that has improved switch, therefore can reduce switching tube loss, alleviate the heat radiation burden of power supply; In addition, the magnetization energy of high-frequency transformer is exported to load produced a kind of method of adjusting the power work parameter by the adjustment magnetization energy, we can prolong switch closing time relatively and shorten the switch conduction time by the magnetization energy that increases high-frequency transformer, and the frequency of operation that reduces power supply, thereby optimize the power supply design.
7), because Switching Two of the present invention regulation and control system mode remains the continuous triangle ripple with the current waveform of outputting inductance, thereby perseverance is keeping 1/2nd relation between the average current of the peak point current of outputting inductance output and its output, this " relation " is for the generation and the application of technology such as " samplings of LRC electric current sync peaks " provides condition.
8), the element circuit of forming power stabilize controller of the present invention has: voltage comparator circuit, RC quickens and shockproof circuit, LRC electric current sync peaks sample circuit, electric current at random reference voltage circuit, voltage sampling circuit, voltage at random element circuit such as reference voltage circuit, LD or LDD switch and the sub-X1 circuit of synchronous output end in parallel, CRD peak clipping buffer circuit, switch triggering circuit and optocoupler circuit form.Chat as preceding institute, power stabilize controller of the present invention does not have independently oscillator, the frequency of operation of power supply is by power stabilize controller and the common generation of power stabilize transducer, if " oscillator " for Switching Power Supply just as being one " heart ", each device or the circuit of forming stable switching voltage regulator of the present invention so all are subordinated to this heart, and they have all participated in the work of heart.
9), " voltage comparator " is the core circuit of power stabilize controller of the present invention, power stabilize controller of the present invention is only used a voltage comparator, the positive and negative input end that other circuit is all delivered to the signal that produces voltage comparator compares, voltage comparator is again with its relatively back high and low level signal that produces, go gauge tap by photoelectrical coupler and switch triggering circuit etc., and then the work of control power stabilize transducer.
The power stabilize controller of stable switching voltage regulator of the present invention only with a voltage comparator undoubtedly for the compressed signal transmission time has been created condition to greatest extent, facts have proved that the present invention just can bring up to the frequency of operation of power supply 1,000,000 level easily with the voltage comparator of usual speed, the stability of this setting range for the power consumption that reduces power supply, expansion of power supply, raising power work is favourable.
10), " RC quickens and shockproof circuit " is an adjunct circuit of voltage comparator, it has two effects: 1, improve the reversal rate of the high and low level signal of voltage comparator output, thereby the switching rate of raising switch is to reduce switching loss, alleviate the output overshoot and to improve control accuracy.2, with the state delay a period of time after the high voltage comparer upset preventing circuit oscillation, and for outputting inductance changes the afterflow state over to, the upset of LDD switch provides the time to guarantee.RC acceleration and shockproof circuit relationships are to the stability of power work, and it is a circuit that can not lack suddenly of stable switching voltage regulator of the present invention,
11), " LRC electric current sync peaks sample circuit " is that the current waveform that is based upon outputting inductance is always the continuous triangle ripple, and the average current perseverance of output is a kind of peak point current Sampling techniques on 1/2nd condition bases of peak point current, this technology utilization resistance and capacitances in series charging, the approximate principle that is linearity of the curve leading portion that the voltage at electric capacity two ends rises in time, with after the series connection of sampling resistor and sampling capacitance again and be connected in the two ends of outputting inductance, the other end of sampling resistor and the input end of outputting inductance link, like this, when the switch open conducting, sampling resistor charged to sampling capacitance when the input end of outputting inductance was noble potential, the voltage upcurve and the electric current upcurve on the outputting inductance at sampling capacitance two ends are synchronous, with the peak point current on the outputting inductance being transformed into simultaneously " sampled voltage " on the sampling capacitance, at the same time, this sampled voltage will with by electric current at random " the current reference voltage " of setting such as reference voltage circuit compare counteracting, the voltage that the back generation is offset in contrast will be transfused to voltage comparator and impel the voltage comparator upset, and then the control output current; In addition, also to utilize outputting inductance to turn-off the current potential that is lower than ground that occurs by the back input end, make the voltage on the sampling capacitance return to original state at switch.
12), the task of " electric current is reference voltage circuit at random " is to provide a current reference voltage for the sampling capacitance in the LRC electric current sync peaks sample circuit, different with general current reference voltage, this current reference potential circuit will provide the current reference voltage that can adjust at random for the needs that stable switching voltage regulator of the present invention is adjusted output current on a large scale at random, and this current reference potential circuit is also wanted can be suitable with LRC electric current sync peaks sample circuit, to before the input voltage comparer, finish the comparison of current sample voltage and current reference voltage, for this reason, the present invention has designed the Method and circuits of three kinds of preset current reference voltages around sampling capacitance: 1, shunt regulator tube fixed preset current reference potential circuit before the sampling capacitance.2, charging preset current reference voltage circuit behind the sampling capacitance.3, mix the preset current reference voltage circuit before and after the sampling capacitance.Wherein, the charging voltage of charging preset current reference voltage circuit can be from general fixing or manual digital and Adjustable behind the sampling capacitance, also can be from voltage sources providing with the machine such as operational amplifiers, and, the preset time of charging preset voltage was arranged between the after production period of outputting inductance behind the sampling capacitance, and it is to utilize the outputting inductance current potential that is lower than ground that input end occurs when afterflow to come to preset for the sampling capacitance reverse charging.
Stable switching voltage regulator of the present invention is with LRC electric current sync peaks sample circuit and electric current reference voltage circuit at random, replace the tradition old way that resistance in series is carried out current sample and control in loop of power circuit, following advantage is arranged: 1, eliminated the power consumption of carrying out current sample with resistance in series.2, created condition for adjusting output current at random on a large scale.3,, thereby provide technical support for stable switching voltage regulator of the present invention for only having created condition with voltage comparator control output current and voltage.
13), " voltage sampling circuit and voltage is reference voltage circuit at random " is to adjust the needs of output voltage at random on a large scale and design for satisfying stable switching voltage regulator of the present invention, the voltage wherein presentation mode and the general reference voltage presentation mode of reference voltage at random is different: it is except can be by general fixing or manually digital and Adjustable provide, it was also from voltage sources providing with the machine such as operational amplifiers.
14), " LD or LDD switch and power supply output synchronously in parallel leading-out terminal " is two circuit that are associated, the special setting of LD wherein or LDD switch in order to implement output current " continuous triangle ripple principle ", it is with at least one diode, when exporting the power supply parallel connection, needs get up with two diode series aiding connections, series connection is at the input end of outputting inductance and voltage comparator one just or between the negative input end again, utilize outputting inductance input end height, the low operating voltage that changes, make a diode or two diodes also be operated in simultaneously by or the state of conducting, reduce the current potential of voltage comparator positive input terminal or negative input end with this, and play the effect of sustaining voltage comparer output level, thereby make the time of afterflow of outputting inductance corresponding synchronously with the closing time of switch, continuous with the waveform that keeps output current.
Because diode is corresponding with the voltage of the high and low variation of outputting inductance input end by, conducting state, also be that the trough and the crest of electric current triangular wave is corresponding on switching time and the outputting inductance of shutoff, unlatching of diode, therefore, when we export some power supplys parallel connections, as long as again the tie-point of two diodes in the LDD switch of every power supply is drawn a connection terminal and with them and be linked together, like this, as long as a power supply has entered the afterflow state, all the other power supplys in parallel are just followed by also entering the afterflow state; Otherwise as long as there is the afterflow state of a power supply not finish, all the other power supplys in parallel also just can not finish the afterflow state, so, just can realize the output synchronously in parallel of power supply, reach the purpose that enlarges electric power outputting current and power.
15), " CRD peak clipping buffer circuit " be the functional circuit that stable switching voltage regulator of the present invention can not default, it has following effect in the present invention: the peak voltage that produces when 1, absorbing the switch eliminated in the power stabilize transducer, high-frequency transformer, outputting inductance, the work of fly-wheel diode constant power device.2, avoid power stabilize transducer generation self-oscillation.3, the path of a short time is provided for the inverse current after the outputting inductance afterflow end, current potential with rapid raising outputting inductance input end, impel LD or LDD switch to turn-off and keep a period of time and open conducting once more until switch, make the power stabilize transducer can be normally, stably work.
16), because stable switching voltage regulator of the present invention itself has possessed certain " the slow startup " and " short-circuit protection " function; therefore generally needn't repeat the circuit of additional slow startup or short-circuit protection again; but do not get rid of the holding circuit of considering to increase in addition a certain class for certain; because stable switching voltage regulator circuit of the present invention is " exposure " substantially; so it is generally fairly simple, convenient to add holding circuit; and form is also various, just no longer enumerates here.It needs to be noted: the result of short-circuit protection generally has two kinds, a kind of be output terminal by short circuit after no-output, another kind is that output is still had output after the short circuit, the power supply that designs with stable switching voltage regulator method for designing of the present invention is generally the latter.
Be described in detail below with reference to circuit diagram and formula structure, principle of work and technical characterictic etc. stable switching voltage regulator of the present invention.
Fig. 1 (A) to (C) is the principle of work synoptic diagram of DC-DC buck convertor at the output current consecutive hours.
Fig. 2 (B) and (C) be DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of the present invention and principle of work synoptic diagram thereof.
Fig. 3 (A) to (H) is the working waveform figure of DC-DC adjusting and voltage-reduction switch stable-power power-supply of the present invention shown in Figure 2.
Fig. 4 is the DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that the output of voltage comparator on Fig. 2 circuit base is set to high level control.
Fig. 5 increases synchronous diode D8 and lead-out terminal X1 in parallel on the basis of Fig. 2 circuit, form to have the DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of output function synchronously in parallel.
Fig. 6 is the DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that uses in parallel that some (being three) is shown in Figure 5 among the figure.
Fig. 7 is on the basis of power supply shown in Figure 6 use in parallel circuit, a power supply that keeps wherein is a primary power, most of controller circuitry etc. of deleting all the other power supplys is for from power supply, formation will some DC-DC adjusting and voltage-reduction switch stable-power power-supplies with the circuit of master and slave power supply use in parallel.
Fig. 8 is for adopting preposition fixed current benchmark of sampling capacitance and adjustable voltage benchmark, the current limliting voltage stabilizing DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of formation.
Fig. 9 utilizes the rearmounted fixed current reference voltage of low-voltage formation sampling capacitance of power supply output and adopts the adjustable voltage benchmark, the current limliting voltage stabilizing DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that has slow startup and short-circuit protection function concurrently of formation.
Figure 10 is for adopting rearmounted fixed current benchmark of sampling capacitance and adjustable voltage benchmark, the current limliting voltage stabilizing DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that has slow startup and short-circuit protection function concurrently of formation.
Figure 11 is for adopting rearmounted adjustable current benchmark of sampling capacitance and fixed voltage benchmark, the pressure limiting current stabilization DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that has slow startup and short-circuit protection function concurrently of formation.
Figure 12 is for adopting rearmounted adjustable current benchmark of sampling capacitance and adjustable voltage benchmark, the constant current constant voltage DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that has slow startup and short-circuit protection function concurrently of formation.
Figure 13 is for producing the also DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of Control current benchmark and voltage reference at random with two operational amplifiers.
Figure 14 inserts buck or boost to isolate high-frequency transformer, the pre-buck or boost DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of formation on the basis of Figure 13 circuit.
Figure 15 resets the output winding of high-frequency transformer and afterflow winding two combine into one that the back increases by two diodes on the basis of Figure 14, the another kind of pre-buck or boost DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of formation.
Referring to Fig. 1.Fig. 1 is made up of (A), (B), (C) three width of cloth figure.What three width of cloth figure painted is same DC-DC buck convertor circuit, but the symbol of expression switch U1 is different: (A) figure usefulness is N type field effect transistor symbol, expression transducer device of normal employing when real work, (B), (C) figure then used two kinds of switch symbols, U1 is in the switch conduction time T with the expression switch ONWith switch T closing time OFFTwo kinds of different operating states.Waveform shown in three width of cloth figure centres will be described hereinafter.
Among Fig. 1 by input circuit V i, switch U1, outputting inductance L1 and by the output circuit V of filter capacitor C1 and load RL parallel connection oThe order series connection forms closed loop, sustained diode 1 is connected in parallel between the input end and ground of outputting inductance L1 in addition, the circuit that the plus earth of sustained diode 1 is formed is commonly called " series connection buck DC-DC converter ", this be acknowledged as that contained element is minimum, structure is the simplest, conversion efficiency is the highest, also be one of the most frequently used basic transformation device, stable switching voltage regulator of the present invention is promptly with the circuit base of this converter circuit as power stabilize transducer of the present invention.
Referring to Fig. 1 (A), when being V with a voltage amplitude GS, the time is T ON, when the square-wave signal shown in oscillogram among the figure removed trigger switch U1, switch U1 opened and conducting, referring to Fig. 1 (B), and the input voltage V of power supply iBe added in the input end of outputting inductance L1 by switch U1, as the tube voltage drop of ignoring switch U1 disregards, and circuit has been when being in stable state, the voltage that is added in outputting inductance L1 two ends is input voltage V iAnd output voltage V OPoor, outputting inductance L1 electric current under the effect of this voltage linear rising of starting from scratch, direction of current is shown in the arrow on the line among the figure, through T ONTime, the electric current by outputting inductance L1 rises to peak I L1P, shown in the oscillogram among Fig. 1 (B), can be formulated as with co-relation:
(V i-V O) * T ON=L1*I L1P(1) V in the formula i---input voltage (V);
V O---output voltage (V);
T ON---the switch conduction time (S);
L1---outputting inductance (H);
I L1P---the peak point current (A) on the outputting inductance.
Switch U1 in conducting T ONTurn-off after time and end, at this moment, referring to Fig. 1 (C), the voltage commutation on the outputting inductance L1 continues its magnetization energy of putting aside to load output by sustained diode 1 during switch conduction, and direction of current is shown in the arrow on the line, and output current is at T OFFIn time from peak point current I L1PLinearity drops to zero, shown in the oscillogram among the figure, at the same time, the magnetic-reset of outputting inductance L1, as the tube voltage drop of ignoring sustained diode 1 disregards, and can be formulated as with co-relation:
I L1P 2* L1/2=V 0* I O* T OFF(2) I in the formula O---output current (A);
T OFF---switch closing time (S).
Since outputting inductance switch conduction and between the off period waveform of output current be linear and continuous, so the average current on the outputting inductance equals output current I O, that is:
I L1P/2＝I O (3)
In formula (2), get after the subtractive (3)
I L1P*L1＝V o*T OFF (4)
Contrast formula (1) and formula (4), " I L1P* L1 " for total, therefore have
(V i-V O)*T ON＝I L1P*L1＝V o*T OFF (5)
Formula (5) has been explained existing a kind of mathematical relation between three links of input, conversion, output of traditional series connection buck DC-DC converter concisely, with formula (3) introduction-type (5), then has:
(V i-V O)*I L1P*T ON/2
＝I L1P 2*L1/2
＝V o*I O*T OFF (6)
Formula (6) has clearly been expressed a kind of Power Conversion relation that exists between three links of input, conversion, output of traditional series connection buck DC-DC converter, the formula " I in the centre of formula (6) L1P 2* L1/2 " be the magnetization energy of outputting inductance, it is the energy of savings in outputting inductance during the switch conduction, has exported between the off period at switch then and has given load.
A kind of output current that formula (6) and above various indicated mathematical relation have disclosed traditional series connection buck DC-DC converter keeps continuous mode of operation, they also are the rely Fundamentals of Mathematics set up and the mode of operations of power stabilize transducer of the present invention of stable switching voltage regulator of the present invention, and are unique mode of operations of power stabilize transducer of the present invention.Formula (6) and above variously also show:
1), outputting inductance L1 is a tradition series connection buck DC-DC converter " transform center ", it is passage and bridge between the input and output, it is again the main transform part that intake is transformed to the output energy, the institute of transducer is free, parameter is all relevant with outputting inductance L1 with " action ", all carries out around outputting inductance L1.
2), formula (3) is the condition that formula (6) is set up, and that is to say to have only as output current I OBe constantly equal to the peak point current I on the outputting inductance L1 L1P1/2nd up-to-date styles (6) could set up, and to satisfy above condition, the current waveform on the outputting inductance L1 just must remain the continuous triangle ripple, this just becomes the principle that stable switching voltage regulator of the present invention must honor be kept naturally.
3), outputting inductance L1 normally fixes in practical power, be that the inductance value of outputting inductance L1 will be an invariant in various more than formula (6), other parameters then all are variable, and position in the analysis mode between each variable and relation are not difficult to find out: as output current I ODuring change, the peak point current I on the outputting inductance L1 L1PAlso to change, and must adjust the ON time T of switch U1 simultaneously ONWith T closing time OFFJust can make the relational expression balance; Work as output voltage V ODuring change, be added in the input voltage (V at outputting inductance two ends i-V O) also will and then become, same, also have only the ON time T that adjusts switch U1 simultaneously ONWith T closing time OFFJust can make the relational expression balance, therefore, stable switching voltage regulator of the present invention has the control method of taking Switching Two to transfer only and could control and stablize and export.
4), the ON time T of switch ONWith T closing time OFFOn outputting inductance L1, also be presented as the rise time of peak point current and the output time of magnetization energy simultaneously, outputting inductance L1 is also corresponding with two times of polarity and this that change operating voltage simultaneously, as Fig. 3 (B) and (C) in outputting inductance L1 two ends just, shown in the minus symbol, therefore, the present invention just utilizes outputting inductance L1 both end voltage height, low change with and the stream waveform that powers on be the characteristics of continuous triangle ripple, correspondence has designed the control method that Switching Two is transferred, in addition, utilize the above characteristics of outputting inductance L1 equally, designed a kind of current sample method of LRC electric current sync peaks sampling and the preset mode of current reference voltage etc.
Referring to Fig. 2.Fig. 2 is made up of (B), (C) two width of cloth figure, and the circuit of two width of cloth figure is identical, and they are corresponding with (B), (C) two width of cloth figure among Fig. 1, and expression is that same transducer is in the switch conduction time T respectively ONWith switch T closing time OFFThe different operating state, different with Fig. 1 is, increased power stabilize controller circuitry part among Fig. 2, because circuit shown in Figure 2 has possessed adjustment capability to output current and voltage, so we go out to send structure and the principle of work that progressively in depth discloses stable switching voltage regulator of the present invention from the circuit of this Fig. 2:
1), as Fig. 2, based on DC-DC voltage-dropping type power stabilize converter circuit, a voltage comparator ic 1 is set earlier on this circuit base; Input end (being positive input terminal among the figure) at voltage comparator ic 1 inserts a component piezoresistance R2 and a R3, the other end ground connection of resistance R 3, the other end one side of resistance R 2: introduce output voltage V by diode D2 O, deliver to the positive input terminal of voltage comparator ic 1 as " output voltage sampled signal "; On the other hand: resistance R 2 also will be accepted " the output current control signal " sent here by diode D5, and here, the effect of diode D2 and D5 is to prevent that mutually the signal that the other side sends here from being shunted, and therefore claim that they are isolating diode.Next, another input end (being negative input end among the figure) at voltage comparator ic 1 inserts another component piezoresistance R4 and R5 again, the other end ground connection of resistance R 5, and the other end of resistance R 4 is connected on voltage reference voltage V VOROn, purpose is to provide one " voltage reference voltage " for the negative input end of voltage comparator ic 1.When the output voltage sampled signal compares with voltage reference voltage in voltage comparator ic 1 and is higher than the latter, the output OUT of voltage comparator ic 1 is a high level, this level will remove stopcock U1 by photoelectrical coupler and switch triggering circuit (not shown), and then the output voltage of control power supply etc.The voltage signal of importing for the positive and negative input end that makes voltage comparator ic 1 has comparability, and in the ordinary course of things, the value of forming each resistance of above functional circuit should meet following relational expression:
(V O-V D2)*R3/(R2+R3)
=V VOR* V in R5/ (R4+R5) (7) formula D2---the tube voltage drop (V) of diode D2;
V VOR---voltage reference voltage (V);
R2, R3, R4, R5---resistance (Ω).
2), next, pick out a diode D4 who is called as switching diode from the negative input end of voltage comparator ic 1, the negative pole of switching diode D4 is connected on the input end of outputting inductance L1, this has promptly formed so-called " LD switch ", the LD switch utilizes the height of outputting inductance L1 its input terminal voltage when commutation, the low variation, and this voltage height, low switching time that changes and outputting inductance L1 go up the trough and the corresponding feature of crest of continuous triangle ripple electric current, current potential by reduction and recovery voltage comparer one input end (being negative input end among the figure), come the output level of switched voltage comparer IC1, thereby make T closing time of switch U1 OFFAnd keep the relation of correspondent equal between the time of afterflow of outputting inductance L1.
3), next, according to resistance and capacitances in series charging, the approximate principle that is linearity of the curve leading portion that the voltage at electric capacity two ends rises in time, the average current of its output was constantly equal to the relation of peak point current 1/2nd when the current waveform on the utilization series connection buck DC-DC converter outputting inductance L1 was the continuous triangle ripple, with resistance R 1, after capacitor C 2 and the diode D6 series connection again parallel connection on outputting inductance L1, the input end of the other end of resistance R 1 and outputting inductance L1 links, the negative pole of diode D6 is connected on the output terminal of outputting inductance L1, this has promptly formed so-called " LRC electric current sync peaks sample circuit ", we are called " sampling resistor " with the R1 in the circuit, C2 is called " sampling capacitance ", and wherein the effect of diode D6 is the blocking-up output voltage V OSampling capacitance C2 is charged.Between the resistance of the resistance of above sampling resistor R1 and resistance R 3 and R4 and they and input voltage V iAnd output voltage V OBetween relation should meet following formula:
[R1: (R3+R4)]＞[(V i-V O): V O] R1---sampling resistor (Ω) in (8) formula.
In addition, earial drainage diode D3 also need be on resistance R 1 in parallel, the positive pole of D3 and sampling capacitance C2 link, and the purpose that D3 is set is to provide for sampling capacitance C2 the quick path of a discharge and reverse charging.
4), with a stabilivolt W1 and isolating diode D5 positive pole link, the negative pole of stabilivolt W1 is connected on the tie-point of sampling resistor R1 and sampling capacitance C2, has promptly formed so-called " the preposition fixed current reference voltage of sampling capacitance C2 "; On the tie-point of sampling capacitance C2 and diode D6, insert diode D7 again, and introduce current reference voltage V by the positive pole of D7 IORThis has promptly formed so-called " the rearmounted current reference voltage of sampling capacitance C2 ", this voltage is with before to chat the preposition fixed current reference voltage of sampling capacitance C2 different, it be the current potential of " A " point among the current potential that utilizes outputting inductance L1 its input end when afterflow, the figure be lower than " " during current potential, via V IOR, D7, C2, D3 and be based upon current reference voltage V on the sampling capacitance C2 IORWhen the preposition fixed current reference voltage of sampling capacitance C2 W1 is set, should make its poor less than input voltage and output voltage, that is:
(V i-V OW1 in)＞W1 (9) formula---stabilivolt (V).
5), because the not ad hoc oscillator of stable switching voltage regulator of the present invention, the frequency of operation of complete machine promptly is to be " conversion frequency " of the power stabilize transducer at center with outputting inductance L1, produce after the signal comparison process that this conversion frequency need concentrate each element circuit to send here by voltage comparator ic 1, therefore whether the working stability of voltage comparator ic 1 will be related to the stable of complete machine, reliable and safety, for this reason, the present invention has set up one " RC quicken and shockproof circuit " especially on voltage comparator ic 1, as scheming: with terminating on the positive input terminal of voltage comparator ic 1 of capacitor C 3 that is called as " speed-up capacitor ", the output terminal of another termination voltage comparator ic 1 of speed-up capacitor C3; Again with one be called as " shockproof resistance " resistance R 6 one terminate at accessory power supply V CCOn, the other end of shockproof resistance R 6 also connects the output terminal of voltage comparator ic 1, so, then when the OUT of the output of voltage comparator ic 1 switches between high and low level, speed-up capacitor C3 is by charge and discharge, the charge and discharge voltage of speed-up capacitor C3 produces the positive feedback voltage of a short time when acting on voltage comparator ic 1 positive input terminal, the main effect of this voltage has two: 1, improves the switching rate of voltage comparator ic 1 output, and then shortens unlatching, the turn-off time of switch U1.2, prevent the output appearance vibration of voltage comparator ic 1, thereby voltage comparator ic 1 and complete machine are stably worked.
The numerical value of speed-up capacitor C3 is at accessory power supply V CCVoltage be higher than under the prerequisite of several volts of voltage comparator ic 1 positive input terminal voltage, generally get tens picofarads, accelerating resistor R6 gets several milliamperes to vagabond current.
6), next, circuit again that capacitor C 0 is in parallel with resistance R 0 and diode D0 is together in series, the other end of capacitor C 0 is connected on the tie-point of switch U1 and outputting inductance L1, the other end ground connection of resistance R 0 and diode D0, this has promptly formed so-called " CRD peak clipping buffer circuit ", capacitor C 0 is called as peak clipping electric capacity, resistance R 0 is called as despiking resistance, diode D0 is called as buffering diode, this circuit has following effect: 1, utilize its moment " absorption " effect, eliminate the due to voltage spikes that produces when devices such as switch U1 and outputting inductance L1 are worked producing at the road electric current.2,, slow down reset electric current climbing speed on the winding of high-frequency transformer afterflow, thereby reduce to be superimposed upon due to voltage spikes on the inverse peak voltage until elimination for outputting inductance L1 changes the current compensation that the afterflow state provides the short time over to.3, provide a current channel for the voltage commutation after the outputting inductance L1 afterflow end, so that the input end of outputting inductance L1, promptly noble potential in time appears in the point of " A " among the figure, and then switching diode D4 is transferred to by conducting end, recover the current potential of " C " point, impel the output level upset of voltage comparator ic 1.4, reduce the turn-off power loss of switch U1.
As above chat, DC-DC voltage-dropping type power stabilize transducer adds the power stabilize controller circuitry, comprises photoelectrical coupler, switch triggering circuit and accessory power supply V on the output OUT that is connected in voltage comparator ic 1 CCCircuit (not shown)s etc. have just formed DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of the present invention.Because photoelectrical coupler, switch triggering circuit and accessory power supply V CCCircuit has multiple circuit types, and these circuit people are also familiar, so just no longer illustrated in the accompanying drawings.
Continuation referring to Fig. 2 (B) and (C), this figure is depicted as DC-DC adjusting and voltage-reduction switch stable-power power-supply of the present invention in the switch conduction time T ONWith switch T closing time OFFThe principle of work synoptic diagram, " arrow " among the figure on line expression direction of current.
Shown in Fig. 2 (B): when " C " of voltage comparator ic 1 point current potential is higher than " B " some current potential, the output OUT of voltage comparator ic 1 is a low level, establishes that switch U1 opens when output OUT low level, conducting, as the tube voltage drop of ignoring switch U1 is disregarded, so, input voltage V iThrough switch U1 make on the one hand negative just down on the voltage on the outputting inductance L1, electric current is from the zero line rising and export to load, outputting inductance L1 savings magnetization energy simultaneously; Input voltage V on the other hand iAlso give sampling capacitance C2 charging, as having established rearmounted current reference V on the sampling capacitance C2 by sampling resistor R1 IOR, the terminal voltage of sampling capacitance C2 will rise on the occasion of, elapsed time T gradually from negative value so ONWhen the voltage on the sampling capacitance C2 rose to voltage stabilizing value above stabilivolt W1, stabilivolt W1 was breakdown, caused the current potential of " B " point to rise rapidly and was higher than the current potential of " C " point, (the output voltage V of being introduced by diode D2 at this moment, OAlso not enough so that the current potential of " B " point is higher than the current potential of " C " point, i.e. power supply current stabilization control at this moment is ahead of voltage stabilizing control, if before this, and output voltage V OTaken the lead in making the current potential of " B " point to be higher than the current potential that " C " puts, power supply will be carried out voltage stabilizing control earlier so.) output switching activity of voltage comparator ic 1 is noble potential, switch U1 turn-offs also and ends.
Next, shown in Fig. 2 (C): after switch U1 turn-offed and ends, the voltage commutation on the outputting inductance L1 transferred to and just bearing down, causes sustained diode 1 conducting, and circuit enters the afterflow state, and outputting inductance L1 exports to load with the magnetization energy of its savings; Simultaneously, outputting inductance L1 also makes switching diode D4 conducting, and promptly the current potential of " C " point has been dropped to and approaches earth potential, thereby the high level of keeping voltage comparator ic 1 output is constant, and switch U1 has also been maintained cut-off state; In addition, outputting inductance L1 also makes diode D3 and diode D7 conducting, makes sampling capacitance C2 discharge and sets up rearmounted current reference voltage V simultaneously IOROutputting inductance L1 is passing through T OFFIts magnetization energy discharges and finishes after time, and the voltage on the outputting inductance L1 commutates once more and changes into to peak clipping capacitor C 0 and the charging of despiking resistance R0 series circuit, and the current potential that " A " put rises to and equals output voltage V simultaneously OCause switching diode D4 to end, the current potential of " C " point recovers and is higher than the current potential of " B " point, the output OUT of voltage comparator ic 1 overturns again and is low level, switch U1 opens conducting once more, carry out above process again and again, constantly the high voltage electric energy of importing is transformed to low-voltage electric energy and exports to load.According to above current sample of chatting and control procedure, can list following formula:
(V i+V IOR-W1-V O)*T ON
=(W1+V IOR) V in * C2*R1 (10) formula IOR---the rearmounted current reference (V) of sampling capacitance C2;
C2---sampling capacitance (F).
As being provided with in advance: V IOR=W1.(10) formula can be rewritten as so:
(V i-V O)*T ON
＝(W1+V IOR)*C2*R1 (11)
(11) if formula explanation is with V IORBe set to equivalence with the numerical value of W1, just they can be disappeared from (10) formula equal sign preceding paragraph formula, like this, W1 and V in the consequent formula of (10) formula equal sign IORThe position since one before sampling capacitance C2 and another behind sampling capacitance C2, this just means that we can treat the voltage upcurve at sampling capacitance C2 two ends with " linear ".
As contrasting (11) formula and (1) formula again, the item formula before the equal sign is identical, therefore has:
(W1+V IOR)*C2*R1＝L1*I L1P (12)
(12) voltage (W1+V of formula from the mathematics angle explanation sampling capacitance C2 IOR) and outputting inductance L1 on peak point current I L1PBe to rise synchronously.
(11) formula and (12) formula are told us: can adjust peak point current I by adjusting sampling capacitance C2 or sampling resistor R1 L1PIn addition, increase, subtract V by equivalent IORAlso can adjust peak point current I with the numerical value of W1 L1P, because peak point current I L1PWith output current I OBetween perseverance keeping 1/2nd relation, so adjust peak point current I L1PPromptly be the output current I that has adjusted power supply OSo far, we have also realized the Linear Control to electric power outputting current when having realized the sampling of electric current linear synchronous.But should see simultaneously, though can make output current adjust to minimal value from limit value by adjusting sampling capacitance C2 or sampling resistor R1, adjust sampling capacitance C2 and sampling resistor R1 generally can only take the mode of " manually " when practical operation, be difficult to reach the requirement of " at random " control, so they can only be used for limited occasion.
In addition, here need to prove, no matter adjustment sampling capacitance C2 or adjustment sampling resistor R1 can not adjust to " zero " with the output current of stable switching voltage regulator of the present invention, because all there be " storage effect " in devices such as the voltage comparator in the circuit, diode, field effect transistor, they transmit the signal demand time, these times of transmitting signals are added up to be enough to make switch U1 to open and to export a certain amount of electric current, and Here it is, and we represent the reason of the output current lowest limit with " minimal value ".
Referring to Fig. 3.Fig. 3 (A) to (H) is the waveform synoptic diagram of DC-DC adjusting and voltage-reduction switch stable-power power-supply of the present invention when current stabilization is worked shown in Figure 2, and this figure ignores the tube voltage drop of diode.
Fig. 3 (A) is depicted as switch U1 when adopting field effect transistor to do, and is added in the trigger pip V on the field effect transistor U1 GSOscillogram, the time relationship of representing among the figure is:
T＝T ON+T OFF。(13) T in the formula---switch periods (S).
Fig. 3 (B) is depicted as leakage, the source electrode operating voltage V of field effect transistor U1 DSOscillogram.
Fig. 3 (C) is depicted as the operating voltage V on the outputting inductance L1 L1Oscillogram.
Fig. 3 (D) is depicted as the drain electrode working current I of field effect transistor U1 DOscillogram.
Fig. 3 (E) is depicted as the operating voltage oscillogram of sampling capacitance C2, and the dotted line among the figure is sampling capacitance C2 preposition fixed current reference voltage W1 and sampling capacitance C2 after-current reference voltage V IOR
Fig. 3 (F) is depicted as the output current I of outputting inductance L1 L1Oscillogram.
Fig. 3 (G) is depicted as the working current oscillogram of sustained diode 1.
Fig. 3 (H) is depicted as the output current wave figure of power supply, and the horizontal straight line among the figure is represented average output current I O
Referring to Fig. 4.Change high level into and trigger when the low level of the voltage comparator ic 1 of Fig. 2 being triggered, when promptly needing the positive and negative input end exchange with voltage comparator ic 1, as shown in Figure 4, must will speed up capacitor C 3 still places between voltage comparator ic 1 output OUT and the positive input terminal, other circuit and annexation thereof are constant, to keep the positive feedback effect of speed-up capacitor C3 to voltage comparator ic 1 output OUT.
Referring to Fig. 5.Fig. 5 has increased diode D8 and the lead-out terminal X1 in parallel that is called as synchronous diode on the tandem circuit of Fig. 2, diode D8 is inserted between the input end of switching diode D4 and outputting inductance L1 synchronously, drawing a connection terminal X1 then on the positive pole of synchronous diode D8 and node that the negative pole of D4 links is " lead-out terminal in parallel ", above outputting inductance L1, synchronous diode D8, switching diode D4 and lead-out terminal X1 in parallel etc. have formed so-called " LDD switch and synchronous output end in parallel ", when needs are exported stable switching voltage regulator parallel connection of the present invention, can be simultaneously synchronous output end in parallel of out-put supply in parallel be coupled together, just can make the output synchronously in parallel of all power supplys.
Referring to Fig. 6.Fig. 6 is the wiring diagram that some (representing with three power supplys among the figure) stable switching voltage regulators of the present invention shown in Figure 5 are together in parallel and use, except will be with the input of each power supply, outside output is together in parallel respectively, also the sub-X1 of synchronous output end in parallel of all power supplys also to be coupled together, so, following relation has just taken place in all power supplys that is connected in parallel: as long as wherein the outputting inductance rate of arbitrary power supply has been introduced into the afterflow state, will drive other all power supplys and also enter the afterflow state simultaneously, also be, as long as wherein there is the outputting inductance of a power supply also to remain on the afterflow state, it is constant the output OUT of other all power source voltage comparers will to be pinned in high level, thereby the switch U1 that makes these power supplys is remain off, otherwise, has only outputting inductance when last power supply afterflow state that is through with, the switch of other parallel connection power supply could be opened conducting, therefore, the output of above parallel connection power supply will be synchronous.
The circuit of work as shown in Figure 6 is connected in parallel some independent current sources, if fault has appearred in a power supply wherein, the possibility that involves other power supplys is less, circuit also is unlikely to integral body and receives damage, though at this moment the output current of circuit is little, but may can also continue to keep work, this is the advantage that adopts the independent current source parallel running, if we deeply observe the parallel circuit of power supply shown in Figure 8, will find that some thing in the power supply seemingly repeats, unnecessary unavoidably, can remove.
Referring to Fig. 7.Fig. 7 keeps a complete power as " primary power " on the basis of Fig. 6, and the segment controller circuit of leaving out all the other power supplys is as " from power supply ", and with all switch U1 (palpus reservation photoelectrical coupler and switch triggering circuit part from power supply, not shown) all concentrate output OUT to drive by primary power, thus the master and slave power supply parallel circuit that forms.As shown in the figure, (A) power supply among the figure is a primary power, and the output OUT (A) of its voltage comparator ic 1 will control the switch U1 of all master and slave power supplys; (A+1) among the figure and (A+2) power supply be from power supply, (A+1) part that is centered on by dotted line from power supply refers to deleted circuit part, (A+2) is depicted as from power supply and has deleted the situation behind the partial circuit.Be not difficult to find out; though be simplified from the circuit of power supply; but each parallel connection still needs the indispensable part outputting inductance L1 of stable switching voltage regulator of the present invention output synchronously in parallel from power supply; diode D8 and the sub-X1 of synchronous output end in parallel etc. remain synchronously; so master shown in Figure 7; the output relation synchronously in parallel that still can keep as shown in Figure 6 independent current source parallel circuit to be had from the power supply parallel circuit; but power supply (A) in parallel among Fig. 7 can not break down; otherwise; power source integral will have destroyed danger; therefore; no matter be the independent current source parallel circuit of Fig. 6; or the master of Fig. 7; from the power supply parallel circuit; all should take in the loop of power circuit of each parallel connection power supply protection ways such as series connection fuse in addition, at any time the power supply " isolation " from parallel circuit that damages be gone out.
Chat as preceding institute, though the circuit of Fig. 2 has possessed the ability of linear adjustment output current, but exist inconvenience owing to adjust sampling capacitance C2 and sampling resistor R2 etc., so it does not possess the condition of " at random " control output current, therefore must transform this circuit, according to resistance, capacitances in series charging, the approximate principle that is linearity of the curve leading portion that the voltage at electric capacity two ends rises in time, we need only preposition fixed current benchmark W1 and rearmounted current reference V at sampling capacitance C2 IORAdopt one of them in two, and make it much smaller than input voltage V iWith output voltage V OPoor, it is linear that the upcurve that so also sampling capacitance C2 can be gone up voltage be regarded as, that is:
W1＜＜(V i-V O) (14)
Perhaps:
V IOR＜＜(V i-V O) (15)
Adopt preposition fixed current benchmark W1 or rearmounted current reference V IOROne in two as behind the current reference, just can derive the stable switching voltage regulator circuit of multiple different output characteristics such as current limliting voltage stabilizing, pressure limiting current stabilization, constant current constant voltage and power stabilize and purposes from the DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of Fig. 5.
Referring to Fig. 8.Fig. 8 is the rearmounted current reference V of cancellation sampling capacitance C2 on the basis of Fig. 7 IOR, only adopt the preposition fixed current benchmark of sampling capacitance C2 W1, and a kind of current limliting voltage stabilizing DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that forms, voltage reference V among the figure VORSymbol on an oblique line is arranged, represent that it is a variable voltage source, adjust voltage reference V VORCan be with output voltage V OAdjust to limit value from minimal value, because the voltage stabilizing numerical value of stabilivolt W1 is fixed among the figure, therefore, when exporting by short circuit, output current will be setting value.
Referring to Fig. 9.If the output voltage V of current limliting stabilized voltage supply shown in Figure 8 OOnly need be stabilized in lower (such as 5V) magnitude of voltage, we just can directly utilize output voltage V OForm the rearmounted current reference voltage of sampling capacitance C2, can save three elements of stabilivolt W1, diode D6 and D7 like this, thereby form another kind of current limliting voltage stabilizing DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit.Because the current reference voltage of this circuit promptly is output voltage V O, therefore when power initiation, this current reference voltage will be along with output voltage V ORising gradually and rise, cause this circuit to have slow the startup and short-circuit protection function.When the output short-circuit of this circuit, because the influence of the factors such as storage effect, response speed and distribution parameter of device, the output current of this power supply is non-vanishing, but is output as minimum value.
Referring to Figure 10.Figure 10 is the preposition fixed current benchmark of cancellation sampling capacitance C2 W1 on Fig. 5 basis, only adopts the rearmounted current reference V of sampling capacitance C2 IOR, and another the current limliting voltage stabilizing DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that forms.Current reference V among the figure IORSymbol on do not have oblique line, represent that it is a fixed voltage source and since figure in current reference V IORBe connected on output voltage V by diode D7 and D6 OOn, so current reference V IORWill follow output voltage V ORise or descend, have only the output voltage V of working as ORising also exceeds current reference V IORSetting value the time, current reference V IORCould finally be established, this feature has been given the slow startup of current limliting voltage stabilizing DC-DC adjusting and voltage-reduction switch stable-power power-supply of this figure and the function of short-circuit protection.And when exporting by short circuit, owing to there are the factors such as tube voltage drop of diode D6 to exist, the output current of this power supply will maintain a less numerical value.
Referring to Figure 11.Figure 11 is the fixed current benchmark V with Figure 10 IORChange variable voltage source into, adjustable voltage benchmark V VORChange fixed voltage source into, thereby the pressure limiting current stabilization DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that forms is adjusted current reference V IORCan be with output current I OAdjust to limit value from minimum value.Because the current reference V among the figure IORBe connected on output voltage V by diode D7 and D6 OOn, so current reference V IORTo follow V ORise or descend, have only the output voltage V of working as ORising also exceeds current reference V IORSetting value the time, current reference V IORCould finally be established, therefore, the pressure limiting current stabilization DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit of Figure 11 has the function of slow startup and short-circuit protection concurrently, and when output short-circuit, the output current of power supply will maintain a less numerical value.If current reference V IORBe adjusted to zero, owing to there are the factors such as storage effect, response speed and distribution parameter of device to exist, the output current of this power supply is non-vanishing, but is output as minimum value so.
Referring to Figure 12.Figure 12 is the current reference V with above Figure 10, Figure 11 IORWith voltage reference V VORAll make variable voltage source into, and the constant current constant voltage DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit that forms, this circuit has the function of slow startup and short-circuit protection concurrently.Adjust V VORCan be from the acyclic homologically trioial to the limit value with output voltage, and adjust V IOROutput current can be transferred to limit value from minimum value, it is one and has current limliting voltage stabilizing and pressure limiting current stabilization function " bistable " power supply concurrently.
Referring to Figure 13.Figure 13 has replaced adjustable current benchmark V in Figure 12 circuit respectively with two operational amplifier IC2 and IC3 IORWith adjustable voltage benchmark V VOR, make V IORAnd V VORBreak away from the restriction of hand adjustment and had the function of " at random " adjustment, thereby finally formed " the DC-DC adjusting and voltage-reduction switch stable-power power-supply " circuit on the complete meaning, the circuit of this figure can be realized all output characteristics and the functions of power circuit shown in above each figure of 12 figure.C5 among the figure, C6 are filter capacitors.R8, R9 are current-limiting resistance.Adopt operational amplifier to control the output current and the voltage of power supply: 1, to help improving speed and the precision that changes the power supply output waveform.2, help the output waveform of power supply is carried out simple functions control.2, help the output waveform of power supply is taked complicated computer program control.3, help utilizing the Based Intelligent Control of various sensors realizations to power supply.
Up to the present, more than the stable switching voltage regulator circuit shown in each figure all be on the basis of DC-DC voltage-dropping type power stabilize transducer of the present invention, to develop and come, as the angle from Power Conversion, the Power Conversion of above DC-DC adjusting and voltage-reduction switch power stabilize transducer relation can be formulated as:
V i*T ON*I L1P/2 ＝(V i-V O)*T ON*I L1P/2+V O*T ON*I L1P/2 (16)
(16) formula shows the T at switch conduction ONIn time, the actual two parts that have been divided into of the electric energy of input, a part has been exported to load, and another part then has been stored in the outputting inductance.And the energy that is stored in the outputting inductance must be at, the T that also can only turn-off at switch OFFFlow to load in time, therefore have:
T OFF＝[(V i-V O)*T ON*I L1P/2]/[V O*T ON*I L1P/2]
＝(V i-V O)/V O (17)
(17) formula shows, input voltage V iWith output voltage V OCompare high more then required switch turn-off time T OFFJust long more, therefore, when designing power supply in order the work period T of power supply to be limited in 50 microseconds to avoid audio frequency, just need be with input voltage V iExceed output voltage V ONumerical limits in certain scope, as input voltage V iThen need to insert the high frequency voltage descending transformer when too high, as input voltage V iCrossing then needs to insert high-frequency step-up transformer when hanging down.In addition, when alternating current after being rectification of the direct current of input, also need to utilize the safety of " isolations " characteristic of transformer with the assurance power supply; Moreover, still need to insert the isolation high-frequency transformer for the safeguard protection of strengthening consumer purely sometimes." high-frequency transformer " occurs with auxiliary converter in power stabilize transducer of the present invention, but high-frequency transformer can make stable switching voltage regulator of the present invention more perfect undoubtedly.
Referring to Figure 14.Figure 14 is a formed stable switching voltage regulator circuit after inserting buck or boost on the circuit base of Figure 13 to isolate high-frequency transformer T1, we are called it " pre-buck or boost DC-DC adjusting and voltage-reduction switch stable-power power-supply ", equally, high-frequency transformer T1 also can insert among above other figure except that Figure 13, thereby forms pre-buck or boost current limliting voltage stabilizing DC-DC adjusting and voltage-reduction switch stable-power power-supply or pre-buck or boost pressure limiting current stabilization DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit.
The high-frequency transformer T1 that Figure 14 inserts contains N1, N2 and three windings of N3 altogether, and wherein: N1 is the input winding; N2 is the output winding; N3 is the afterflow winding that resets, and as its name suggests, " afterflow reset winding " is for the magnetization energy of high-frequency transformer being exported to load and magnetic core being resetted and a winding being provided with.As Figure 14, the input end of input winding N1 is connected on the source class that switch U1 is the field effect pipe " S ", output termination input voltage V iNegative pole (the another kind of connection of input winding N1 is: the input termination input voltage V that will import winding N1 iPositive pole, the leakage level " D " of the output termination field effect transistor U1 of input winding N1, the source class of field effect transistor U1 " S " then meets input voltage V iNegative pole); The end that the input end of output winding N2 and input winding N1 is of the same name is an output terminal, this output termination one is called as the positive level of the diode D9 of output diode, the negative pole of output diode D9 is connected on the input end of outputting inductance L1, the other end ground connection of output winding N2, the effect of output diode D9 is: the electric current that only allows output winding N2 is at the voltage source of switch U1 conduction period uniflux as outputting inductance L1; Afterflow the continue negative pole of stream diode D1 of winding N3 and the input end of an input winding N1 end of the same name such as figure that resets, the other end ground connection of sustained diode 1, the reset other end of winding N3 of afterflow is connected on the input end of outputting inductance L1, the effect of sustained diode 1 is: only allow reset electric current uniflux between the switch U1 off period of winding N3 of afterflow that the magnetization energy of high-frequency transformer T1 is exported to load by connecting with outputting inductance L1, in addition, also need be on sustained diode 1 and afterflow reset the tie-point of winding N3 with the negative pole reconfiguration of former synchronous diode D8, utilizing afterflow between the switch U1 off period to reset, winding N3 and sustained diode 1 connect one brings out the electric current that the existing current potential that is lower than ground absorbs voltage comparator ic 1 negative input end, high level with sustaining voltage comparer IC1 output OUT is constant, thereby keeps the afterflow output state of power supply.
After inserting high-frequency transformer T1, should remove trigger switch U1 again by a photoelectrical coupler between the output OUT of voltage comparator ic 1 and the trigger circuit of switch U1, this is not shown at circuit, though this photoelectrical coupler sees that from the angle of circuit theory it is irreplaceable or cancellation being not in the present invention, owing to there has been it will make more brief, reasonable, the reliable and safety of driving circuit.
Pre-buck or boost DC-DC adjusting and voltage-reduction switch stable-power power-supply as Figure 14 is opened at switch U1, conduction period, electric current on the input winding N1 of high-frequency transformer T1 is linear to rise, as leakage inductance and the loss of ignoring transformer are disregarded, at this moment the energy of importing high-frequency transformer T1 is divided into output energy and magnetization energy two parts, wherein, the output energy passes to outputting inductance L1 by output winding N2, and magnetization energy then has been stored among the high-frequency transformer T1, thereby following relational expression is arranged:
(V i* N2/N1-V O) * T ON=L1*I L1P(18) N1 in the formula---input winding (circle);
N2---output winding (circle).
(18) formula is compared with (1) formula, only input voltage V iTaken advantage of a coefficient " N more 2/1",
N 2/1N in=N2/N1 (19) formula 2/1---output winding and the turn ratio of importing winding.
As N 2/1Less than 1, illustrate that high-frequency transformer T1 is a step-down transformer; N 2/1Greater than 1, illustrate that then high-frequency transformer T1 is a step-up transformer.
Switch U1 in conducting T ONTurn-off after time and end, the magnetization energy that is stored among the high-frequency transformer T1 will be exported to load with the magnetization energy of outputting inductance L1, required time of afterflow T by the afterflow winding N3 that resets OFFCan draw by following formula:
T OFF＝[(V i*T ON/L N1) 2*L N1/2+
(V i* N 2/1* T ON/ L1) 2* L1/2]/V 0* I O(20) L in the formula N1---the inductance value (H) of input winding N1.
Comparison expression (20) and formula (2), the energy that formula (20) was exported between the after production period has had more whole one, and promptly high-frequency transformer T1 is at switch U1 conduction period T ONThe magnetization energy of being put aside:
W LN1=(V i* T ON/ L N1) 2* L N1W in/2 (21) formulas LN1---pass through L N1Introduce the magnetization energy (Wh) of T1.
Stable switching voltage regulator of the present invention is taked the magnetization energy W with high-frequency transformer T1 LN1Export to load and magnetic core that the mode to the input power supply that do not feed back solves T1 resets following advantage is arranged: the work efficiency that 1, can improve high-frequency transformer T1 and switch U1, as disregard device loss, then the energy by switch U1 input high-frequency transformer T1 has all obtained utilization.2, for adjusting the magnetization energy W of high-frequency transformer T1 LN1, optimizing the power supply design provides condition.3, reduce the switching loss of switch U1 for reduction complete machine frequency of operation, and then the power consumption and the temperature rise of reduction complete machine provide condition.4, for making full use of the fan-out capability of devices such as high-frequency transformer T1, provide condition with the volume and weight that reduces complete machine.5, the inverse peak voltage that is added on the switch U1 for reduction provides condition.What facts have proved switch U1 withstand voltagely generally just can be used for conversion 220V power frequency supply at 600V, so not only can reduce the cost of manufacture of AC-DC high power switching power supply significantly, and therefore the stability of power work and reliability also will be improved.
Pre-buck or boost DC-DC adjusting and voltage-reduction switch stable-power power-supply as Figure 14, after CRD peak clipping buffer circuit has been arranged, when turn-offing, ends switch U1, the afterflow of the high-frequency transformer T1 winding N3 that resets enters the afterflow state, and the afterflow inverse peak voltage that winding N3 reflection is superimposed upon on the switch U1 that resets can be tried to achieve with following formula:
V DSU1=V i+ (N 1/ N 3) * V O(22) V in the formula DSU1---the inverse peak voltage (V) on the switch U1;
N 3---the afterflow winding (circle) that resets;
N 1/ N 3---the reset turn ratio of winding of input winding and afterflow.
Because the central transducer of stable switching voltage regulator of the present invention is one " buck convertor ", the voltage that it requires output winding N3 to offer outputting inductance L1 must be higher than output voltage V all the time OAgain since usually the reset number of turn of winding N3 of our afterflow be set to equate that as to establish the output voltage of exporting winding N3 be output voltage V with the number of turn of output winding N2 OTwice, formula (22) can change into so:
V DSU1＝V i+(V i/2V O)*V O＝V i+V i/2 (23)
With input voltage V iReplace with the 220V power frequency supply after the rectification, then have: V DSU 1 = 220 V * 2 + 220 V * 2 / 2
≈311V+155V＝466V (24)
(24) formula shows, this switch U1 minimum withstand voltage be 466V, as add certain surplus, the withstand voltage 600V of having of switch U1 can meet the demands, certainly, the specific output voltage V that the voltage that we can also output winding N3 is provided with OTwice higher, further reduce requirement of withstand voltage to switching tube U1.
So far, pre-buck or boost DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit shown in Figure 14 can be realized this figure all output characteristics and the function of power circuit shown in other each figure in addition, other each only this figure a kind of " simplification " under given conditions of figure, so Figure 14 is the representative graph of stable switching voltage regulator of the present invention.
Pre-buck or boost DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit as Figure 14, equate as the reset coil turn of winding N3 and output winding N2 of afterflow, just meaning can two combine into one with them, and only serve as the output of high-frequency transformer T1 and the afterflow task that resets with a winding, this has just derived the circuit of Figure 15 again.
Referring to Figure 15.The circuit of Figure 15 is compared with the circuit of Figure 14 and has been lacked a winding N3, but two diode D01 and D09 have been used more, four diode D1, D01, D9, and D09 is inserted between winding N2 and the outputting inductance L1 as scheming to make up the form that is connected into full-wave rectification, in addition also will be on the positive pole of output diode D9 with the negative pole reconfiguration of synchronous diode D8, like this then formed winding N2 plays last figure output winding N2 when switch U1 conducting effect, then play the reset effect of winding N3 of afterflow and close to have no progeny at switch U1, from figure, the high-frequency transformer of Figure 13 is simpler really, but power supply has been used two diodes more, the power consumption that these two diodes will produce will not allowed to ignore when designing power supply, therefore this figure generally can only be used for designing the power supply of little electric current, as is used for designing big electric current, powerful power supply then is not suitable.
Power supply provides the device of electric energy, and Switching Power Supply is different with power supplys such as industrial-frequency alternating current, accumulators, it neither generates electricity and does not also store, it only serves as " bridge " between power supply and load, Switching Power Supply is a power supply for load, but it is again load for power supplys such as industrial-frequency alternating current and accumulator.
In general, the output characteristics of a power supply designs according to load characteristic, as: stabilized voltage supply and resistive load are suitable, stabilized current supply is then more suitable with capacitive or inductive load, and need to adopt the load of stable-power power-supply as if also few at present, a common example is a DC motor speed-regulating, because the torque of direct current generator is the function of electric current, rotating speed is the function of voltage, therefore need the power supply of an electric current, voltage energy bidirectional modulation to match, only in this way just can give full play to the good speed adjusting performance of direct current generator.
Broadly, to the requirement of output characteristic of power source not merely from load.For example: the capacity of lead-acid accumulator will be subjected to the influence of its discharge current, and its capacity diminished when discharge current was big, and both are inverse relation; If discharge current has surpassed certain limit, also can influence the life-span of battery.Therefore, expection capacity and life-span can be reached, just its discharge power must be limited in good time in order to make lead-acid accumulator.
Furtherly, power supply is not to be subordinated to load passively, as: we can be by the output waveform of control stable-power power-supply, make low frequency, intermediate frequency even the high-frequency DC energy of its formation except that general direct current, or the electric energy that its frequency and amplitude are changed regularly in a certain time domain, directly go to handle " peripheral hardware ", give load some function, the power supply product that exploitation is novel.

Claims (12)

1. a stable switching voltage regulator comprises outputting inductance (L1), it is characterized in that it also comprises: input circuit (Vi); Switch (U1) and trigger circuit; Fly-wheel diode (D1); Output circuit (RL and C1 parallel connection); Voltage comparator (IC1) and output (OUT) circuit thereof; By divider resistance (R2 and R3 series connection) and isolating diode (D2) and (D5) voltage sampling circuit of formation; The LRC electric current sync peaks sample circuit that constitutes by described outputting inductance (L1) and sampling resistor (R1), sampling capacitance (C2) and blocking diode (D6), earial drainage diode (D3); LD on-off circuit by described outputting inductance (L1) and switching diode (D4) formation; The RC that is made of accelerating resistor (R6) and speed-up capacitor (C3) quickens and shockproof circuit; The voltage that is made of operational amplifier (IC2), divider resistance (R4 and R5 series connection), current-limiting resistance (R8), filter capacitor (C5) is reference voltage circuit at random; The electric current that is made of operational amplifier (IC3), current-limiting resistance (R9), filter capacitor (C6), isolating diode (D7) is reference voltage circuit at random; CRD peak clipping buffer circuit by peak clipping electric capacity (C0), despiking resistance (D0) and buffering diode (D0) formation;
Described outputting inductance (L1) is in series into closed loop with described output circuit (RL and C1 parallel connection), input circuit (Vi), switch (U1), the negative pole of described fly-wheel diode (D1) connects the tie-point of described switch (U1) and outputting inductance (L1) in addition, the plus earth of described fly-wheel diode (D1) constitutes the power stabilize transducer;
Described divider resistance (R2 and R3 series connection) tie-point is connected on an input end of described voltage comparator (IC1), the other end ground connection of (R3) in the described divider resistance, the negative pole of the described isolating diode of another termination (D2) of (R2) and isolating diode (D5) in the described divider resistance, the positive pole of described isolating diode (D2) connects the anode of described output circuit (RL and C1 parallel connection), and the positive pole of described isolating diode (D5) connects the tie-point of described sampling resistor (R1) and described sampling capacitance (C2);
Described divider resistance (R4 and R5 series connection) tie-point is connected on another input end of described voltage comparator (IC1), the other end ground connection of (R5) in the described divider resistance, the tie-point of the described filter capacitor of another termination (C5) of (R4) and current-limiting resistance (R8) in the described divider resistance, the output of the described operational amplifier of another termination (IC2) of described current-limiting resistance (R8), described filter capacitor (C5) other end ground connection;
Described sampling resistor (R1) and sampling capacitance (C2) and the series connection of blocking diode (D6) order, the described switch of another termination (U1) of described sampling resistor (R1) and the tie-point of outputting inductance (L1), the negative pole of described blocking diode (D6) connects the anode of described output circuit (RL and C1 parallel connection), at the two ends of described sampling resistor (R1) described earial drainage diode (D3) in parallel, the positive pole of described earial drainage diode (D3) connects described sampling capacitance (C2) in addition;
The tie-point of described sampling capacitance (C2) and blocking diode (D6) inserts described isolating diode (D7), the positive pole of described isolating diode (D7) connects the tie-point of described filter capacitor (C6) and current-limiting resistance (R9), the output of the described operational amplifier of another termination (IC3) of described current-limiting resistance (R9), described filter capacitor (C6) other end ground connection;
Negative or the positive input terminal of described voltage comparator (IC1) picks out described switching diode (D4), and the negative pole of described switching diode (D4) connects the input end of described outputting inductance (L1);
Described accelerating resistor (R6) and described speed-up capacitor (C3) be series connection earlier, again the connect in series point is connected in the output (OUT) of described voltage comparator (IC1), the other end of described speed-up capacitor (C3) is connected on the positive input terminal of described voltage comparator (IC1), another termination accessory power supply V of described accelerating resistor (R6) CC
Described despiking resistance (D0) and the first parallel connection of described buffering diode (D0) are connected with described peak clipping electric capacity (C0) again, the plus earth of the other end of described despiking resistance (D0) and described buffering diode (D0), the other end of described peak clipping electric capacity (C0) is connected on the tie-point of described switch (U1) and outputting inductance (L1), more than constitutes the power stabilize controller;
Constitute DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit by the above power stabilize transducer and described power stabilize controller.
2. stable switching voltage regulator as claimed in claim 1 is characterized in that deleting described voltage described operational amplifier (IC2), current-limiting resistance (R8) and the filter capacitor (C5) in the reference voltage circuit at random, increases variable voltage source (V VOR) be the adjustable voltage benchmark; Delete described electric current described operational amplifier (IC3), current-limiting resistance (R9) and the filter capacitor (C6) in the reference voltage circuit at random, increase variable voltage source (V IOR) be the adjustable current benchmark, simplify forming DC-DC adjusting and voltage-reduction switch stable-power power-supply with constant current constant voltage function.
3. stable switching voltage regulator as claimed in claim 2 is characterized in that described variable voltage source (V VOR) be set to the fixed voltage benchmark, simplify forming DC-DC adjusting and voltage-reduction switch stable-power power-supply with pressure limiting current stabilization function.
4. stable switching voltage regulator as claimed in claim 2 is characterized in that described variable voltage source (V IOR) be set to the fixed current benchmark, simplify forming DC-DC adjusting and voltage-reduction switch stable-power power-supply with current limliting voltage stabilizing function.
5. stable switching voltage regulator as claimed in claim 2 is characterized in that deleting described variable voltage source (V IOR) and delete described isolating diode (D7) and blocking diode (D6), described sampling capacitance (C2) directly is connected on the anode of described output circuit (RL and C1 parallel connection), utilize the stable low-voltage of output to be the fixed current benchmark, another has the DC-DC adjusting and voltage-reduction switch stable-power power-supply of current limliting voltage stabilizing function to simplify formation.
6. stable switching voltage regulator as claimed in claim 2 is characterized in that deleting described variable voltage source (V IOR), increasing stabilivolt (W1) between described sampling capacitance (C2) and isolating diode (D5) is the fixed current reference voltage, the positive pole of described stabilivolt (W1) connects the positive pole of described isolating diode (D5), simplifies to form another DC-DC adjusting and voltage-reduction switch stable-power power-supply with current limliting voltage stabilizing function.
7. as the described stable switching voltage regulator of claim 1 to 6, it is characterized in that further comprising buck or boost isolation high-frequency transformer (T1) and output diode (D9), to constitute pre-buck or boost DC-DC adjusting and voltage-reduction switch stable-power power-supply circuit;
Described high-frequency transformer (T1) comprises input winding (N1), output winding (N2), afterflow three windings of winding (N3) that reset;
The output of the described switch of input termination (U1) of described input winding (N1) is the source electrode (S) as field effect transistor, the negative pole of the described input circuit of output termination (Vi) of described input winding (N1), the input of described switch (U1) promptly connect the positive pole of input circuit (Vi) as the drain electrode (D) of field effect transistor; Described input voltage (the V of the input termination of perhaps described input winding (N1) i) positive pole, the input of the described switch of output termination (U1) of described input winding (N1) promptly as the leakage level (D) of field effect transistor, the output of described switch (U1) is the negative pole of input circuit (Vi) as described in the source class (S) as field effect transistor connects;
The end that the input end of described output winding (N2) and described input winding (N1) is of the same name is an output terminal, this exports termination output diode (D9), the negative pole of described output diode (D9) connects the input end of described outputting inductance (L1), the other end ground connection of described output winding (N2);
The reset negative pole of winding (N3) and the input end described fly-wheel diode of a termination (D1) of the same name of input winding (N1) of described afterflow, the reset input end of the described outputting inductance of another termination (L1) of winding (N3) of the other end ground connection of fly-wheel diode (D1), described afterflow;
In addition with the negative pole reconfiguration of described switching diode (D4) on described afterflow resets winding (N3) and fly-wheel diode (D1) tie-point.
8. stable switching voltage regulator as claimed in claim 7 is characterized in that the reset number of turn of winding (N3) and described output winding (N2) of further described afterflow is set to equate.
9. stable switching voltage regulator as claimed in claim 8, it is characterized in that deleting the described afterflow winding (N3) that resets, increase by two diodes (D01) and (D09), the form that the combination of described two diodes (D01 and D09) and described fly-wheel diode (D1) and described output diode (D9) is connected into full-wave rectification is inserted between described output winding (N2) and the outputting inductance (L1), with the double described afterflow of described output winding (N2) winding (N3) that resets.
10. as claim 1 to 6 and 8,9 described stable switching voltage regulators, it is characterized in that also comprising synchronous diode (D8) and synchronous output end in parallel (X1), described synchronous diode (D8) inserts input end or the described afterflow be connected on described switching diode (D4) and outputting inductance (L1) and resets between winding (N3) and fly-wheel diode (D1) tie-point, draws synchronous output end in parallel (X1) on the tie-point of the negative pole of the positive pole of described synchronous diode (D8) and switching diode (D4).
11. stable switching voltage regulator as claimed in claim 10 is characterized in that input circuit (Vi) and output circuit (RL and C1 parallel connection) and synchronous output end in parallel (X1) as described in some power supplys of the same type in the 10 described stable switching voltage regulators are together in parallel respectively.
12. some parallel connections as claimed in claim 11 are the same type stable switching voltage regulator of output synchronously, a power supply that it is characterized in that keeping wherein is a primary power, and the power stabilize controller of other power supply is partly deleted to from power supply, and the trigger circuit of described described switch (U1) from power supply are concentrated on that described primary power is controlled and the stable switching voltage regulator another kind of of the same type that forms with the master and slave power supply structure of output synchronously in parallel.
CNB011137452A 2001-07-01 2001-07-01 Stable switching voltage regulator Expired - Fee Related CN1161875C (en)

Priority Applications (2)

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CNB011137452A CN1161875C (en) 2001-07-01 2001-07-01 Stable switching voltage regulator
PCT/CN2002/000452 WO2003005543A1 (en) 2001-07-01 2002-06-28 Switch stable power supply

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Application Number Priority Date Filing Date Title
CNB011137452A CN1161875C (en) 2001-07-01 2001-07-01 Stable switching voltage regulator

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CN1161875C CN1161875C (en) 2004-08-11

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Cited By (3)

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CN102075133A (en) * 2010-12-10 2011-05-25 李乔 Direct current motor speed regulation controller
CN107733212A (en) * 2017-10-26 2018-02-23 东莞启益电器机械有限公司 Has the direct current of power saving function with exchanging output circuit
CN115668721A (en) * 2020-05-20 2023-01-31 思睿逻辑国际半导体有限公司 Randomization of current in power converters

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KR20070026650A (en) 2004-05-27 2007-03-08 악셀레론 파마 인코포레이티드 Cerberus/coco derivatives and uses thereof

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CN87204355U (en) * 1987-06-23 1987-12-31 徐步前 Transistor dc transformer
JPH07123702A (en) * 1993-10-18 1995-05-12 Sumitomo Metal Ind Ltd Dc-dc converter
JP2001136736A (en) * 1995-10-24 2001-05-18 Rohm Co Ltd Power supply apparatus and electrical apparatus using the same
JPH10210736A (en) * 1997-01-22 1998-08-07 Yaskawa Electric Corp Step-down type dc-dc converter
JPH11215825A (en) * 1998-01-28 1999-08-06 Kenwood Corp Switching power supply

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Publication number Priority date Publication date Assignee Title
CN102075133A (en) * 2010-12-10 2011-05-25 李乔 Direct current motor speed regulation controller
CN107733212A (en) * 2017-10-26 2018-02-23 东莞启益电器机械有限公司 Has the direct current of power saving function with exchanging output circuit
CN107733212B (en) * 2017-10-26 2024-04-16 东莞启益电器机械有限公司 DC and AC output circuit with energy-saving function
CN115668721A (en) * 2020-05-20 2023-01-31 思睿逻辑国际半导体有限公司 Randomization of current in power converters
CN115668721B (en) * 2020-05-20 2023-08-15 思睿逻辑国际半导体有限公司 Randomization of current in a power converter

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