CN1314211C - Improvements in or relating to frequency-hopping modulators and demodulators - Google Patents
Improvements in or relating to frequency-hopping modulators and demodulators Download PDFInfo
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- CN1314211C CN1314211C CNB028165608A CN02816560A CN1314211C CN 1314211 C CN1314211 C CN 1314211C CN B028165608 A CNB028165608 A CN B028165608A CN 02816560 A CN02816560 A CN 02816560A CN 1314211 C CN1314211 C CN 1314211C
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/713—Spread spectrum techniques using frequency hopping
- H04B1/7136—Arrangements for generation of hop frequencies, e.g. using a bank of frequency sources, using continuous tuning or using a transform
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/22—Demodulator circuits; Receiver circuits
- H04L27/227—Demodulator circuits; Receiver circuits using coherent demodulation
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/713—Spread spectrum techniques using frequency hopping
- H04B1/7136—Arrangements for generation of hop frequencies, e.g. using a bank of frequency sources, using continuous tuning or using a transform
- H04B2001/71365—Arrangements for generation of hop frequencies, e.g. using a bank of frequency sources, using continuous tuning or using a transform using continuous tuning of a single frequency source
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Abstract
Methods and apparatus are provided for effectively shortening the set-up time of a new receive or transmit frequency in a frequency hopping transceiver. Post-rotation of received baseband signals removes a phase error caused by a local oscillator not yet being phase locked as intended. Pre-rotation of baseband signals for transmission cancels a phase error to be introduced by a local oscillator of the transmit path not yet being phase locked as intended.
Description
Technical field
The present invention relates to the frequency hopping synthesizer.More particularly, it relates to the phase modulated in the fast jumping local oscillator of the base station of mobile telephone network or the phase error correction of demodulation.
Background technology
At the base station transceiver that is used for the GSM/EDGE mobile telephone network, need possess the frequency hopping synthesizer of high switch speed, low phase noise and low parasitic component simultaneously.Phase noise is very important because baseband signal by phase encoding to the RF carrier wave.In typical carrier wave unit, need the transmission switch speed of 2-4 μ s, have usually be better than-signal of 80dBc compares performance to parasitic frequency.
The known carrier wave unit (CU) that is used for mobile telephone base station as shown in Figure 1.As shown in the figure, transmit path 10 and RX path 12 all communicate between baseband processor and controller 13 and radio set 15.Transmit path 10 and RX path 12 all require corresponding local oscillator signals TXLO, the RXLO from corresponding local oscillator 9,11.The independent synthesizer 14,16,18,20 of four separation is used for this purpose, and switched in the unoccupied place when they disposed one by one with " leapfrog ".That is to say, when a synthesizer (for example 14) just in use, its complementary synthesizer 16 be tuned to the required frequency of next time slot.When next time slot begins, switch 22 will transmit 16 output as signal RXLO, the beginning of 14 of synthesizers be tuned to the frequency of next time slot.The synthesizer 18,20 of transmit path is worked in the same manner.Baseband processor and controller 13 are to each synthesizer transmission frequency control signal 17, and reference frequency Ref also is applied on each synthesizer.
Fig. 2 explanation in the local oscillator of all frequency-hopping carrier unit as shown in Figure 1 be tuned to phase error Δ in the output signal of voltage controlled oscillator (' vco ') of required frequency and phase place.Fig. 2 also represents the typical case output of phase comparator of the phase-locked loop of the local oscillator shown in 9 among Fig. 1,11.
In the first area that is designated as 1, voltage controlled oscillator vibrates on the frequency that is different from required or reference frequency, i.e. Δ f ≠ 0.Can see the cycle phase error reach ± 180 °, expression equals the beat frequency of the difference of the frequency that reference frequency and voltage controlled oscillator produced.Along with voltage controlled oscillator through control to reach required frequency, beat frequency slows down, and finally occurs last zero crossing 25 when first interval the end.Vco is just providing required frequency and Δ f=0.But, still have phase error Δ ≠ 0 between vco output and the reference signal.
In Fig. 2, be designated as in second interval of " 2 ", the operation of local oscillator makes the reference signal of the more approaching input that makes the phase comparator that is added to local oscillator of the present invention respectively of the phase place of vco signal and the required phase place of Phase synchronization of feedback signal, as the following detailed description, reduce Δ gradually.
When finishing to second stage, the vco output signal with reference signal homophase and Δ.
For the fast frequency hopping transducer, should make first and second intervals 1,2 short as far as possible, make the vco signal can use as early as possible.But, effectively happen suddenly, be that valid data send or receive and may begin in second stage 2, at this moment still there is phase error.This can cause the interference through the baseband signal of phase modulated to its RF carrier wave.
Summary of the invention
The present invention relates to reduce as shown in Figure 2 the vco frequency and the method and apparatus of duration in second interval 2 of phase locking process.As mentioned above, the variation phase error in second interval causes the interference in the base band of received signal, because their adopt phase modulated to encode usually, and the phase error in the local oscillator signals can cause the skew in the baseband signal of detecting.Phase error also may cause sending the interference of signal, and it will comprise the phase error as the apparent modulation signal.
Therefore, the present invention reduces the duration and the influence in second interval 2 by back rotation being applied to the baseband signal in the receiver and preceding rotation being applied to baseband signal in the transmitter.
That is to say, with rightabout that the phase error of local oscillator signals in the RX path is compared on, phase shift is applied to the baseband signal that received, so that the phase error that local oscillator produced is compensated.With rightabout that the phase error of local oscillator signals in the transmit path is compared on, before sending, phase shift is applied to send baseband signal, so that the phase error that local oscillator produced is compensated.
Therefore, the invention provides a kind of method that the baseband signal of the phase modulated of frequency hopping demodulator is carried out demodulation of being used for, may further comprise the steps: the RF signal that receives the baseband signal that comprises phase modulated; Employing itself utilizes phase-locked loop to provide the local oscillator of the local oscillator signals of covert bit error when having to carry out demodulation to received signal; And the response demodulation step, generation comprises the demodulated base band signal that has been offset the baseband signal of error term owing to phase error.This method is further comprising the steps of: rotate by with the complex multiplication of phase place rotation item demodulated base band signal being carried out the back, thereby fully eliminate skew and the generation baseband signal from demodulated base band signal.
The present invention also provides a kind of being used at the frequency hopping modulator baseband signal to be carried out the method for phase modulated, and may further comprise the steps: employing itself utilizes phase-locked loop to provide the local oscillator of the local oscillator signals of covert bit error when having that baseband signal is carried out phase modulated; And the response phase modulation step, generation comprises the modulating baseband signal that has been offset the baseband signal of error term owing to phase error.This method is further comprising the steps of: before the phase modulated step, by complex multiplication baseband signal is rotated with phase place rotation item, thereby introducing the error term of introducing with phase error equates and the opposite error term of effect basically, thereby eliminate the skew that phase error is introduced basically, produce the modulating baseband signal that does not have skew basically.
Response indicates the reception of the signal of the currency of the phase error that characterizes phase-locked loop and loop parameter, can calculate phase place rotation by linear predictor.
The phase comparator of phase-locked loop can provide the signal of the currency that indicates phase error to linear predictor.The signal that indicates the currency of phase error can be sampled before being applied to linear predictor and be converted to numeral.
The loop parameter that offers linear predictor can be revised according to the required operating frequency of local oscillator signals.
The present invention also provides a kind of frequency hopping phase demodulator, comprising: local oscillator, comprising the phase-locked loop that the local oscillator signals of covert bit error when having is provided with preset frequency; RX path, be used for that the RF signal that receives is carried out phase demodulating and comprise the demodulated base band signal that has been offset corresponding to the required baseband signal of the error term of the currency of phase error with generation, phase-locked loop itself comprises the phase comparator of the phase error signal of being arranged to provide expression phase error currency.Demodulator also comprises complex multiplier, complex multiplier is configured to receive demodulated base band signal and is fit to have with error term and equates substantially and effect opposite phases rotating signal, and the complex multiplication of being arranged to carry out demodulated base band signal and phase place rotation item, thereby obtain required baseband signal.
The present invention also provides: the frequency hopping phase-modulator comprises itself comprising the local oscillator that the phase-locked loop of the local oscillator signals of covert bit error when having is provided with preset frequency; Transmit path is used for receiving baseband signal is carried out phase modulated, produces to comprise expression and be offset modulated rf signal corresponding to the modulation of the receiving baseband signal of the error term of phase error currency; Phase-locked loop itself comprises the phase comparator of being arranged to provide the phase error signal of representing the phase error currency.Modulator also comprises complex multiplier, complex multiplier is configured to receive required baseband signal and is adjusted to have and equates substantially with error term and act on the opposite phases rotating signal, and the complex multiplication of being arranged to carry out required baseband signal and phase place rotating signal, thereby in the output of modulator, obtain modulated rf signal, wherein comprise the modulation format of the required baseband signal that does not have error term substantially.
This modulator or demodulator also can comprise linear predictor and look-up table, wherein look-up table is arranged to provide to linear predictor the value of the loop parameter of expression phase-locked loop feature, and linear predictor also is configured to receive the signal of the currency that indicates phase error, and linear predictor also is arranged to correspondingly calculate the value of phase place rotating signal.
Can respond the signal that indicates the phase error currency and calculate the phase place rotating signal.Analog to digital converter can be provided, the signal that indicates the phase error currency is sampled and converted thereof into numeral, described numeral is applied to linear predictor.
Look-up table can be arranged to store many group loop parameters, and wherein each is corresponding to the specific required operating frequency of local oscillator signals, and look-up table also is configured to receive the signal which group that indicates in many group parameters should offer linear predictor.
Description of drawings
With reference to below in conjunction with accompanying drawing to some only as the explanation of the embodiment of example, above and other purpose of the present invention, feature and advantage will be fully aware of, wherein:
Fig. 1 represents a kind of known architecture of the carrier wave unit of the frequency hopping transceiver in the base station of mobile telephone network;
Fig. 2 represents to obtain the phase error of the output of the local oscillator in the frequency-hopping carrier unit of required frequency and phase place;
Fig. 3 represents the frequency hopping demodulator according to the first embodiment of the present invention;
Fig. 4 represents to be included in the signal in the operation of demodulator of Fig. 3;
Fig. 5 represents to be included in the signal in the operation of modulator of Fig. 6; And
Fig. 6 represents frequency hopping modulator according to a second embodiment of the present invention.
Embodiment
Fig. 3 represents the first embodiment of the present invention, and wherein, the back rotation is applied to the receiving baseband signal in the RX path.Have the corresponding reference label with common function shown in Figure 1.
Local oscillator 9 produces reception local oscillator frequencies RXLO for receiving path 12.Local oscillator can be any suitable type, but as shown in the figure, the phase-locked loop of the vco34 that local oscillator signals RXLO is provided that comprises reference frequency Ref and comprise loop filter 33, the transfer function Kv/s of phase comparator 32, the transfer function F (s) of transfer function K φ, wherein the counter 35 divided by N is in the feedback path of phase comparator 32.
According to an aspect of the present invention, phase error signal v (t) 36 that provided of phase comparator 32 is converted to digital form 37 by analog to digital converter (ADC) 38.
Phase error signal v (t) can be expressed as v (t)=K φ * Φ (t)/(N+K φ * F (s) * Kv/s), and wherein Φ (t) is the phase error in the output of vco, and (N+K φ * F (s) * Kv/s) is the loop gain of phase-locked loop.
Because receiving baseband signal Srx (t) is the phase place that is modulated to its RF carrier wave, so phase error Φ (t) will be demodulated into the part of baseband signal by RX path 12, and show as and be superimposed upon on the required baseband signal.Therefore, 40 of the signals that is produced in the output of RX path are Srx (t) * e
J Φ (t)
The example of the required baseband signal Srx (t) of Fig. 4 A explanation expression voice frequency tone.
Fig. 4 B explanation is according to second interval 2 of vco tuner operation shown in Figure 2, the phase error e that amplitude decays in time
J Φ (t)Example.
Fig. 4 C represents output signal 40 Srx (t) * e
J Φ (t), it adopts the baseband signal of Fig. 4 A that local oscillator signals RXLO with the decay phase error shown in Fig. 4 B decodes to produce by receiving link 12 responses usually.
According to the present invention, adopt the complex multiplier that is fit to phase displacement error in the elimination demodulated base band signal to carry out e to demodulated base band signal 40 Srx (t) *
J Φ (t)Back rotation, thereby produce required baseband signal Srx (t) shown in Fig. 4 A.This passes through demodulated base band signal Srx (t) * e
J Φ (t)With the phase place rotation 44e shown in Fig. 4 D
-j Φ (t)Multiply each other and obtain.
According to an aspect of the present invention, based on the loop parameter of being stored phase error voltage v (t) is sampled and respective phase error Φ (t) is predicted.
Though the initial value of v (t) is at random,, then between v (t) and Φ (t), there is clear and definite relation immediately as long as obtain frequency lock.
Referring again to Fig. 3, according to one embodiment of present invention, baseband processor and controller 13 have been equipped with receiving demodulation baseband signal Srx (t) * e
J Φ (t)40 and phase place rotating signal e
-j Φ (t)44 complex multiplier 42.
By linear predictor 46 responding digital phase error signals 37 and corresponding to the loop parameter (F of selected required vco frequency, Kv, K φ) value and produce phase place rotating signal 44, wherein parameter is provided by the control signal CH that look-up table LUT 48 responses indicate required vco frequency.Preferably also to each required vco frequency storage stable state vco control voltage V
0Value in the look-up table 48 is also preferably self-alignment, and the mode of understanding fully with those skilled in the art receives updating value CAL.
Phase place rotating signal 44 produces in the following manner.
Obtain after the frequency lock, in the output of vco 34, have limited phase error Φ (t).
Phase error is converted to phase error voltage v (t) 36 by phase detectors 32.Sample by 38 pairs of phase error voltages of ADC, produce digitized forms 37, then it is applied to baseband processor 13.
In baseband processor, adopt institute's stored parameter and instantaneous v (t) value, can be easily the back rotation amount e that needs of sample value ground forecasting institute one by one
-j Φ (t)This can find out from following formula:
v(t)＝Kφ*Φ(t)/(N+Kφ*F(s)*Kv/s)；
Thereby obtain Φ (t)=v (t) (N+K φ * F (s) * Kv/s)/K φ.
Signal v (t) is the input 37 to linear predictor; N is a constant; And F (s), Kv/s and K φ provide by look-up table, makes linear predictor 46 can calculate Φ (t), thereby produce phase place rotating signal e
-j Φ (t)44.Phase place rotating signal 44 should have equal with the phase error of introducing demodulated base band signal but opposite amplitude.That is, complex multiplier 42 is carried out following computing:
Srx(t)*e
jΦ(t)*e
-jΦ(t)＝Srx(t)
Thereby extract required restituted signal 50.
With reference to Fig. 4 A to 4D, the phase place rotating signal 44e shown in Fig. 4 D
-j Φ (t)The base band offset of being introduced with phase error Φ (t) shown in Fig. 4 B is equal and opposite.By demodulated base band signal 40 (Fig. 4 C) and phase place rotating signal 44 (Fig. 4 D) are multiplied each other, eliminate phase error skew (Fig. 4 B), required baseband signal 50 (Fig. 4 A) is provided.
Linear predictor calculates the value of required phase place rotating signal according to the existing sample value 37 of v (t).It carries out linear prediction to calculate phase place rotating signal e
-j Φ (t)44 appropriate value, thus the time be everlasting and use between the sample value of phase error voltage v (t).Linear predictor 46 can be replaced by the fallout predictor of other suitable type, may increase cost simultaneously.
Therefore, the invention provides compensation, allow in second interval 2 of vco tuner operation shown in Figure 2, early to communicate the phase error in the vco output.
According to another aspect of the present invention, the phase error in the vco output of the transmission local oscillator signals TXLO of transmit path 10 is afforded redress.This allows early to begin to transmit in second interval 2 of vco tuner operation shown in Figure 2.
Fig. 5 A-D explanation and the relevant signal in this aspect of the present invention.One embodiment of the present of invention are described among Fig. 6, and wherein the function corresponding to Fig. 3 has corresponding reference number.
Similar to the described embodiment of reference Fig. 3, local oscillator 11 in this case to transmit path 10 local oscillator signals is provided, here for TXLO.The phase-locked loop that comprises the divider 35 in phase comparator 32, loop filter 33, vco34 and the feedback path provides local oscillator signals TXLO by required frequency.But, as shown in Figure 2, in local oscillator output, will there be some frequency and phase deviation (Δ f, Δ), vco and phase-locked loop are arranged to required frequency and phase place simultaneously.In case phase-locked loop is worked under required frequency, then phase comparator 32 provides the phase error signal v (t) 36 that indicates current phase error Φ (t).This phase error signal is sampled, and converts numeral 37 to by analog to digital converter (ADC) 38.
As described in the embodiment of reference Fig. 3, baseband processor and controller 13 comprise and receive digital phase error signal v (t) 37 and corresponding to the loop parameter (F of selected required vco frequency, Kv, the linear predictor 46 of value K φ), these parameters are provided by the control signal CH that look-up table LUT 48 responses indicate required vco frequency.Preferably also in look-up table 48, control voltage V for each required vco frequency storage stable state vco
0Value in the look-up table 48 is also preferably self-alignment, and the mode of understanding fully with those skilled in the art receives updating value CAL.
Then, linear predictor 46 effect that produces the phase error of the vco in expection and the performed phase modulated of transmission link equates and opposite phases correction signal e
-j Φ (t)
In the embodiment of Fig. 6, complex multiplier 42 receives baseband signal Stx (t) 52 (Fig. 5 A) and the phase place rotating signal e that is used to transmit
-j Φ (t)44 (Fig. 5 B).Because baseband signal Stx (t) is not the main body of any phase error distortion, therefore the effect of this complex multiplication is that transmit path 10 is produced baseband signal 54Stx (t) the * e of distortion
-j Φ (t)(Fig. 5 C).Then, transmit path 10 is attempted baseband signal 54 is modulated on the carrier wave, transmits for transceiver 15.But, because the phase error Φ (t) among the local oscillator signals TXLO makes the baseband signal 54 (Fig. 5 C) will be by application phase error term e
J Φ (t)(Fig. 5 D) and distortion.But, according to an aspect of the present invention, the distortion that phase error term (Fig. 5 D) is produced with the distortion that primary signal produced is equated substantially and opposite that required baseband signal Stx (t) (Fig. 5 A) multiply by phase correction signal 44e
-j Φ (t)(Fig. 5 B) makes that finally be applied on the transceiver 15 signal for transmission comprises in fact phase modulated baseband signal corresponding to following formula:
Stx(t)*e
-jΦ(t)*e
jΦ(t)＝Stx(t)
What therefore, the invention provides effectively the new reception of the frequency hopping transceiver that shortens the carrier wave unit that is used for mobile telephone base station or transmission frequency is provided with time method and device.The invention provides back rotation,, thereby allow in any certain tones crack, more early can begin to receive so that eliminate also not by the phase error that vco caused of estimating phase-locked like that local oscillator to the baseband signal that receives.Equally, the invention provides preceding rotation,, thereby allow in any certain tones crack, more early to begin to transmit so that eliminate also not the phase error that vco introduced by the local oscillator of estimating phase-locked like that transmit path to the baseband signal that is used to transmit.Mass action is to allow to have between the frequency high-speed traffic of switching fast, perhaps allow simpler and easy, oscillator and existing communication speed are used cheaply.
Though invention has been described with reference to the specific example of limited quantity, can carry out many modifications and change within the scope of the present invention.For example, the invention is not restricted to mobile phone uses.On the contrary, it need to can be applicable to other communication system of the fast modulation of frequency-hopping carrier.Linear predictor described in the specific embodiment can replace with the fallout predictor of any other suitable type.Local oscillator can be the type described in the common unsettled UK patent application GB0120641.6, perhaps can be that phase error voltage v can be provided any kind of (t).
Claims (8)
1. one kind is used for the method for phase modulated baseband signal (50) being carried out demodulation at the frequency hopping demodulator, may further comprise the steps:
Receive the RF signal that (15) comprise phase modulated baseband signal (50);
Employing itself utilizes phase-locked loop (32,33,34,35) to provide the local oscillator (9) of the local oscillator signals (RXLO) of covert bit error when having (Φ (t)) that described received signal is carried out demodulation;
Respond described demodulation step, produce the demodulated base band signal (40) that comprises the described baseband signal (50) that has been offset the error term that causes by described phase error;
It is characterized in that described method is further comprising the steps of:
By carrying out complex multiplication operation described demodulated base band signal (40) is carried out the back rotation with phase place rotation (44), thereby from described demodulated base band signal (40), eliminate described skew, produce described baseband signal (50), the phase comparator of wherein said phase-locked loop (32) provides the signal (36) of the currency that indicates described phase error to described linear predictor, and the described loop parameter that wherein offers described linear predictor is made amendment according to the required operating frequency of described local oscillator signals; The described signal (36) of the currency of described phase error was sampled before being applied to described linear predictor and changed (38) becomes numeral (37); Linear predictor (46) responds described phase place rotation item is calculated in the reception of the loop parameter of the signal (37) of the currency that indicates described phase error and the described phase-locked loop feature of expression.
2. method of baseband signal (52) being carried out phase modulated in the frequency hopping modulator may further comprise the steps:
Employing itself utilizes phase-locked loop (32,33,34,35) to provide the local oscillator (11) of the local oscillator signals (TXLO) of covert bit error when having (Φ (t)) that described baseband signal (52) is carried out phase modulated (10);
Respond described phase modulated step, produce the modulating baseband signal (56) that comprises the described baseband signal (52) that has been offset the error term that causes by described phase error;
It is characterized in that described method is further comprising the steps of:
Before described phase modulated step, by carrying out complex multiplication operation (42) described baseband signal (52) is rotated with phase place rotation (44), thereby it is equal and act on opposite error term to introduce the described error term of introducing with described phase error, thereby eliminate the described skew that described phase error is introduced, produce the modulating baseband signal (56) that does not have skew, the phase comparator of wherein said phase-locked loop (32) provides the signal (36) of the currency that indicates described phase error to described linear predictor, and the described loop parameter that wherein offers described linear predictor is made amendment according to the required operating frequency of described local oscillator signals; The described signal (36) of the currency of described phase error was sampled before being applied to described linear predictor and changed (38) becomes numeral (37); Linear predictor (46) responds described phase place rotation item is calculated in the reception of the loop parameter of the signal (37) of the currency that indicates described phase error and the described phase-locked loop feature of expression.
3. frequency hopping phase demodulator comprises:
Local oscillator (9) is comprising the phase-locked loop (32,33,34,35) that the local oscillator signals (RXLO) of covert bit error and preset frequency when having is provided;
RX path (12) is used for carrying out phase demodulating to receiving the RF signal, produces the demodulated base band signal (40) of the required baseband signal (50) of the error term that comprises the currency (Φ (t)) that has been offset corresponding to described phase error,
Described phase-locked loop itself comprises the phase comparator (32) of the phase error signal (36) of the currency (Φ (t)) of being arranged to provide the described phase error of expression,
It is characterized in that described demodulator also comprises:
Complex multiplier (42), be configured to receive described demodulated base band signal and be adjusted to have and equate with described error term and act on opposite phases rotating signal (44), described complex multiplier is arranged to carry out the complex multiplication of described demodulated base band signal and described phase place rotation item, thereby obtain required baseband signal (50), described demodulator also comprises linear predictor (46) and look-up table (48), wherein said look-up table is arranged to store many groups road parameter, every group of specific required operating frequency wherein corresponding to described local oscillator signals, described look-up table also is configured to receive which group that indicates in described many group parameters is represented that the value of the loop parameter of described phase-locked loop feature should offer the signal of described linear predictor, and described linear predictor also is configured to receive the signal (37) of the currency that indicates described phase error, and described linear predictor also is arranged to correspondingly calculate the value of described phase place rotating signal (44); Analog to digital converter (38), it is set to the described signal (36) of the currency that indicates described phase error is sampled, and converts thereof into numeral (37), and described numeral is applied to described linear predictor.
4. demodulator as claimed in claim 3, it is characterized in that, described look-up table is arranged to provide to described linear predictor the value of the loop parameter of the described phase-locked loop feature of expression, and described linear predictor also is configured to receive the signal (37) of the currency (Φ (t)) that indicates described phase error, and described linear predictor also is arranged to correspondingly calculate the value of described phase place rotating signal (44).
5. as claim 3 or 4 described demodulators, it is characterized in that the described signal (36) that response indicates the currency (Φ (t)) of described phase error calculates described phase place rotating signal.
6. as claim 4 or 5 described demodulators, it is characterized in that, described look-up table is arranged to store many group loop parameters, wherein every group corresponding to described local oscillator signals (TXLO, RXLO) specific required operating frequency, described look-up table also are configured to receive the signal (CH) which group that indicates in described many group parameters should offer described linear predictor.
7. frequency hopping phase-modulator comprises:
Local oscillator (11) itself comprises the phase-locked loop (32,33,34,35) of the local oscillator signals (TXLO) that covert bit error when having (Φ (t)) and preset frequency are provided;
Transmit path (10) is used for receiving baseband signal (54) is carried out phase modulated, produces to comprise the modulated rf signal (56) of modulation of described receiving baseband signal (54) that expression has been offset the error term of the currency (Φ (t)) corresponding to described phase error,
Described phase-locked loop itself comprises the phase comparator (32) of the phase error signal (36) of the currency (Φ (t)) of being arranged to provide the described phase error of expression,
It is characterized in that described modulator also comprises:
Complex multiplier (42), be configured to receive required baseband signal (52) and be adjusted to have and equate with described error term and act on opposite phases rotating signal (44), described complex multiplier is arranged to carry out the complex multiplication of described required baseband signal and described phase place rotating signal, thereby in the output of described modulator, obtain modulated rf signal (56), wherein comprise the modulation format that does not have the required baseband signal of described error term (50), described modulator also comprises linear predictor (46) and look-up table (48), wherein said look-up table is arranged to store many groups road parameter, every group of specific required operating frequency wherein corresponding to described local oscillator signals, described look-up table also is configured to receive which group that indicates in described many group parameters is represented that the value of the loop parameter of described phase-locked loop feature should offer the signal of described linear predictor, and described linear predictor also is configured to receive the signal (37) of the currency that indicates described phase error, and described linear predictor also is arranged to correspondingly calculate the value of described phase place rotating signal (44); Analog to digital converter (38), it is set to the described signal (36) of the currency that indicates described phase error is sampled, and converts thereof into numeral (37), and described numeral is applied to described linear predictor.
8. modulator as claimed in claim 7 is characterized in that, the described signal (36) that response indicates the currency (Φ (t)) of described phase error calculates described phase place rotating signal.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| GB0120642A GB2379105B (en) | 2001-08-24 | 2001-08-24 | Improvements relating to fast frequency-hopping modulators and demodulators |
| GB0120642.4 | 2001-08-24 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1547808A CN1547808A (en) | 2004-11-17 |
| CN1314211C true CN1314211C (en) | 2007-05-02 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CNB028165608A Expired - Fee Related CN1314211C (en) | 2001-08-24 | 2002-08-15 | Improvements in or relating to frequency-hopping modulators and demodulators |
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| Country | Link |
|---|---|
| CN (1) | CN1314211C (en) |
| GB (2) | GB2379106B (en) |
| WO (1) | WO2003019809A1 (en) |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP3838230B2 (en) * | 2003-08-19 | 2006-10-25 | ソニー株式会社 | Propagation path characteristic estimation system, propagation path characteristic estimation method, communication apparatus, and communication method |
| US9847800B1 (en) * | 2016-05-25 | 2017-12-19 | Intel IP Corporation | Direct compensation of IQ samples for undesired frequency deviation in phase locked loops |
| CN110501728B (en) * | 2018-05-16 | 2022-03-29 | 清华大学 | Frequency discrimination method and device for time hopping signal of positioning base station |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5150378A (en) * | 1991-10-07 | 1992-09-22 | General Electric Company | Method and apparatus for coherent communications in non-coherent frequency-hopping system |
| CN1156923A (en) * | 1995-12-26 | 1997-08-13 | 三星电子株式会社 | Phase locked loop for communication system of frequency hopping type |
| EP0817442A2 (en) * | 1996-07-02 | 1998-01-07 | Plessey Semiconductors Limited | Carrier recovery in quadrature receivers |
| US6061389A (en) * | 1993-03-05 | 2000-05-09 | Hitachi, Ltd. | Frequency-hopping communication system and communication station |
| CN1296684A (en) * | 1998-02-12 | 2001-05-23 | 金吉斯通讯公司 | Multiple access method and system |
Family Cites Families (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH0693670B2 (en) * | 1984-12-29 | 1994-11-16 | 京セラ株式会社 | Spread spectrum communication system |
| AU6643790A (en) * | 1989-11-09 | 1991-06-13 | Roger Reed | Digital circuit for a frequency modulation and carrier synthesis in a digital radio system |
| US5353311A (en) * | 1992-01-09 | 1994-10-04 | Nec Corporation | Radio transmitter |
| GB9606114D0 (en) * | 1996-03-22 | 1996-05-22 | Digi Media Vision Ltd | Improvements in or relating to digital satellite receivers |
| JPH09266455A (en) * | 1996-03-28 | 1997-10-07 | Sanyo Electric Co Ltd | Frequency hopping modulation circuit |
| GB2314981A (en) * | 1996-07-02 | 1998-01-14 | Plessey Semiconductors Ltd | Radio receiver arrangements |
-
2001
- 2001-08-24 GB GB0220522A patent/GB2379106B/en not_active Expired - Fee Related
- 2001-08-24 GB GB0120642A patent/GB2379105B/en not_active Expired - Fee Related
-
2002
- 2002-08-15 CN CNB028165608A patent/CN1314211C/en not_active Expired - Fee Related
- 2002-08-15 WO PCT/EP2002/009116 patent/WO2003019809A1/en not_active Application Discontinuation
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5150378A (en) * | 1991-10-07 | 1992-09-22 | General Electric Company | Method and apparatus for coherent communications in non-coherent frequency-hopping system |
| US6061389A (en) * | 1993-03-05 | 2000-05-09 | Hitachi, Ltd. | Frequency-hopping communication system and communication station |
| CN1156923A (en) * | 1995-12-26 | 1997-08-13 | 三星电子株式会社 | Phase locked loop for communication system of frequency hopping type |
| EP0817442A2 (en) * | 1996-07-02 | 1998-01-07 | Plessey Semiconductors Limited | Carrier recovery in quadrature receivers |
| CN1296684A (en) * | 1998-02-12 | 2001-05-23 | 金吉斯通讯公司 | Multiple access method and system |
Also Published As
| Publication number | Publication date |
|---|---|
| GB0120642D0 (en) | 2001-10-17 |
| GB2379106A (en) | 2003-02-26 |
| CN1547808A (en) | 2004-11-17 |
| GB2379105A (en) | 2003-02-26 |
| GB2379105B (en) | 2003-07-09 |
| GB0220522D0 (en) | 2002-10-09 |
| WO2003019809A1 (en) | 2003-03-06 |
| GB2379106B (en) | 2003-07-09 |
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