CN117729624A - Duplex transceiver, wireless communication equipment and wireless communication method thereof - Google Patents
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Abstract
The invention discloses a duplex receiving and transmitting device, wireless communication equipment and a wireless communication method thereof, which relate to the field of duplex receiving and transmitting, and comprise a target receiver, wherein the target receiver is used for receiving signals; a receiving end nonlinear correction module; according to the duplex receiving and transmitting device, the wireless communication equipment and the wireless communication method thereof, the residual interference power under the condition of time-frequency synchronization errors is deduced by aiming at the imperfect time-frequency synchronization problem of distributed full duplex cooperative interference receiving and transmitting, and the influence of the time-frequency synchronization errors on the system performance is analyzed theoretically to obtain a closed expression of the receiver interference rejection ratio, the demodulation error rate and the communication capacity, wherein the receiver interference rejection ratio, the demodulation error rate and the communication capacity performance are obviously reduced along with the increase of time delay or frequency offset, and meanwhile, a receiving end nonlinear correction module is inserted into a receiving link through a training model to compensate nonlinear distortion caused by a transmitting end simulation component, so that the signal symbol quality of the receiving end is improved.
Description
Technical Field
The present invention relates to duplex transceiver technology, and in particular, to a duplex transceiver device, a wireless communication apparatus, and a wireless communication method thereof.
Background
The Fifth Generation mobile communication (5G) system, which is gradually commercialized, is greatly advanced over the long term evolution (Long Term Evolution, LTE) system, and the data rate can reach several Gbps, but still cannot meet the requirement of exponentially increasing data of future wireless communication. In particular, the transition from the "everything interconnected" to the "everything intelligent" mode is imminent, and there is a need to be able to transmit more wireless data in a faster, safer manner. As global informatization processes are driven faster, sixth Generation mobile communication (6G) technology research with enhanced spectral efficiency is evolving.
At present, when the transmitting power of the full duplex system is increased, the effective suppression of the interference of the receiving link is quite challenging due to the inherent nonlinear characteristics and memory effect of analog components such as a transmitting link power amplifier and the like. As the transmit power continues to increase, the effect of the nonlinear characteristics of analog devices such as power amplifiers will become more pronounced, further degrading the interference rejection performance of the receiver, for which corresponding digital predistortion techniques have been proposed [31]. In addition, as the frequency increases and the bandwidth increases, errors caused by imperfect synchronization of the time and frequency also obviously affect the interference suppression capability of the receiver, so that the actual interference suppression performance of the system is reduced.
Disclosure of Invention
The present invention is directed to a duplex transceiver, a wireless communication device and a wireless communication method thereof, so as to solve the above-mentioned drawbacks in the prior art.
In order to achieve the above object, the present invention provides the following technical solutions: a duplex transmitting-receiving device, a wireless communication apparatus and a wireless communication method thereof, comprising:
a target receiver for receiving a signal;
the receiving end nonlinear correction module is used for being inserted into the receiving link through a training model to compensate nonlinear distortion caused by the simulation components of the transmitting end, so that the signal symbol quality of the receiving end is improved;
a source transmitter for transmitting a signal;
the transmitting end nonlinear correction module is used for carrying out up-sampling processing on a transmitting signal before passing through the low-rate DAC and observed data after passing through the low-rate ADC module;
the broadband nonlinear transmitting link low sampling rate module is used for firstly dividing the full-band predistortion signal into three sections of frequency components in a digital mode before the transmitting link predistortion signal enters the power amplifier, wherein the three sections of frequency components correspond to an in-band part, an upper sideband part and a lower sideband part of the full-band predistortion signal respectively, and then three D/A converters with relatively low sampling rates are used for respectively converting the predistortion signal of the in-band, the lower sideband and the upper sideband from a digital domain to an analog domain, so that the hardware cost of the high sampling rate D/A is obviously reduced;
and the full duplex communication time-frequency synchronization error processing module is used for analyzing and processing the full duplex communication time-frequency synchronization error.
Further, the specific working steps of the receiving end nonlinear correction module are as follows:
a1, performing signal filtering processing by an analog low-pass filter, and filtering the obtained received signal in a digital domain v (n) can be expressed as:
in the formula, h m Representing coefficients of the anti-aliasing filter;
a2, memorizing the polynomial model and receiving signals v The integration of (n) can be given by:
a3 by using OSF as the formulaDownsampling is performed, the symbol-level manner between the received signal y (n) and the transmitted signal z (n) may be further expressed as:
wherein:
a,4, after zero-padding, the signal x (n) can be expressed as:
wherein the method comprises the steps ofIs->Vectors of zero elements;
a5, pairAfter low-pass filtering, the following formula can be obtained
Wherein I represents the maximum order of the LPF filter, gamma i Representing the filter coefficient corresponding to the ith delay
A6 by using OSF as the formulaDownsampling may be performed to obtain the following formula:
wherein, and x (n) both assume synchronous calibration in time and frequency, z (n) can be further expressed as:
the A7, y (n) nonlinear model can be represented by the source notation as:
a8, the digital nonlinear correction function u (n) at the receiving end can be expressed as:
where D represents the maximum order of the nonlinear correction model and L represents the maximum depth of its memory effect.
Further, the specific working method of the transmitting end nonlinear correction module is as follows:
at the transmitter end of the link, the modulated signal first passes through a root raised cosine filter, and DPD processing is performed on the signal at a high sampling rate. The output signal X (n) is filtered and downscaled by M times, the digital baseband signal is converted into a digital IF signal through a digital up-converter, meanwhile, the filtered downscaled signal X (n) is up-sampled and combined into an X1.25 matrix signal, then the X1.25 matrix signal is converted into a matrix signal FX1.25 through a low-pass filter to carry out correction estimation, the intermediate frequency digital signal with lower sampling rate is converted into an analog signal z (t), and finally the analog signal is sent into a power amplifier and transmitted through an antenna.
Further, the full duplex communication time-frequency synchronization error processing module includes:
in the transmitting node model, assuming that a baseband discrete signal of a transmitting node is s (n) ∈ {0,1}, after digital-to-analog conversion, the baseband discrete signal is changed into a baseband continuous signal to be denoted as s (t), and the s (t) is transmitted by a radio frequency antenna after up-conversion, wherein the transmitting signal can be expressed as follows:
wherein P is s Representing the transmitted signal power of a transmitting node of the system, f s Is the carrier frequency phi s Is the carrier primary phase;
if the baseband discrete signal of the cooperative interference node is i (n), the baseband discrete signal is converted into a baseband continuous signal i (t) after digital-to-analog conversion, the i (t) is up-converted and then transmitted through a radio frequency antenna, and the transmitting signal can be expressed as the following formula:
wherein P is i Representing the power of the transmitted signal of the cooperative interference node, f i Is the carrier frequency phi i Is the initial phase of the carrier wave;
the channel model, if the communication signal and the cooperative interference signal both experience an additive white gaussian noise channel, and are transmitted through a wireless channel, the radio frequency signal received by the receiving node can be expressed as: .
y(t)＝A s x s (t-t s )+A i x i (t-t i )+n(t)
Wherein A is s And A i The channel attenuation factors respectively representing the communication signals and the cooperative interference signals are not lost in generality, and are assumed to be 1; t is t s Representing a transmission delay of the communication signal; t is t i Representing the transmission delay of the interference signal; n (t) represents zero mean and sigma variance 2 Additive white gaussian noise of (2);
the signal model, the local transmit signal, may be expressed as:
where x (t) represents the equivalent baseband form of the local transmit signal, f c Representing the carrier frequency s z (t) and n sz (t) represents the resolved forms of the local transmit signal and noise, respectively, and in the case of self-interference, the received self-interference signal at the receiving link can be generally expressed as:
where I (t) represents an ideal self-interference signal, nr (t) represents a receiving link noise, K represents the number of paths of the self-interference channel,and->Respectively representing the channel complex coefficient and the time delay of the kth path;
interference signal I reconstructed by receiving end canceller c (t) may be represented by the formula:
wherein L is the number of taps of the canceller,and->The complex coefficient and the time delay of the 1 st tap are respectively;
thus, the residual SI signal (i.e., the cancellation error signal) can be expressed as
Further, the specific working steps of the full duplex communication time-frequency synchronization error processing module for parameter optimization are as follows:
b1, obtaining a mean square error as shown in the formula by using the interference cancellation error signal expression
In the method, in the process of the invention,is the power of the received link noise nr (t);
b2, define R (τ) =es z (t)s z (t-τ)]For the resolved signal s corresponding to the local transmit signal s (t) z The complex autocorrelation function of (t) can be expressed as:
b3, can be expressed in matrix form as:
wherein:
b4, the signal characteristics are known, and the SI channel parameters are fixed, the optimization target is carried out on each tap parameter, as shown in the formula
A wireless communication device, the wireless communication device comprising: memory, processor and duplex transceiver program stored on the memory and executable on the processor.
A wireless communication method, the wireless communication method comprising the steps of:
transmitting a signal through a source transmitter; performing transmitting end nonlinear correction on transmitting end signals; receiving the signal by the target receiver; performing receiving end nonlinear correction on the receiving end signal; setting a full duplex communication broadband nonlinear low sampling rate; and calculating the influence of the time-frequency synchronization error on the system interference suppression performance.
Compared with the prior art, the duplex receiving and transmitting device, the wireless communication equipment and the wireless communication method thereof provided by the invention aim at the imperfect time-frequency synchronization problem of distributed full duplex cooperative interference receiving and transmitting, derive the residual interference power under the condition of time-frequency synchronization error, analyze the influence of the time-frequency synchronization error on the system performance in theory, obtain the closed expression of the receiver interference rejection ratio, the demodulation error rate and the communication capacity, wherein the receiver interference rejection ratio, the demodulation error rate and the communication capacity performance are obviously reduced along with the increase of time delay or frequency offset, and meanwhile, a receiving end nonlinear correction module is inserted into a receiving link through a training model to compensate nonlinear distortion caused by a transmitting end analog component, thereby improving the signal symbol quality of a receiving end.
Drawings
In order to more clearly illustrate the embodiments of the present application or the technical solutions in the prior art, the drawings that are needed in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments described in the present invention, and other drawings may be obtained according to these drawings for a person having ordinary skill in the art.
Fig. 1 is a schematic structural diagram of a nonlinear correction module at a receiving end according to a first embodiment of the present invention;
fig. 2 is a schematic structural diagram of a nonlinear correction module at a transmitting end according to a first embodiment of the present invention;
fig. 3 is a schematic diagram of a low sampling rate module structure of a wideband nonlinear transmission link according to a first embodiment of the present invention;
fig. 4 is a schematic structural diagram of a time-frequency synchronization error processing module for full duplex communication according to an embodiment of the present invention.
Detailed Description
In order to make the technical scheme of the present invention better understood by those skilled in the art, the present invention will be further described in detail with reference to the accompanying drawings.
Embodiment one:
referring to fig. 1-4, a duplex transceiver, a wireless communication device and a wireless communication method thereof, comprising:
a target receiver for receiving a signal;
the receiving end nonlinear correction module is used for being inserted into the receiving link through a training model to compensate nonlinear distortion caused by the simulation components of the transmitting end, so that the signal symbol quality of the receiving end is improved;
a source transmitter for transmitting a signal;
the transmitting end nonlinear correction module is used for carrying out up-sampling processing on a transmitting signal before passing through the low-rate DAC and observed data after passing through the low-rate ADC module;
the broadband nonlinear transmitting link low sampling rate module is used for firstly dividing the full-band predistortion signal into three sections of frequency components in a digital mode before the transmitting link predistortion signal enters the power amplifier, wherein the three sections of frequency components correspond to an in-band part, an upper sideband part and a lower sideband part of the full-band predistortion signal respectively, and then three D/A converters with relatively low sampling rates are used for respectively converting the predistortion signal of the in-band, the lower sideband and the upper sideband from a digital domain to an analog domain, so that the hardware cost of the high sampling rate D/A is obviously reduced;
and the full duplex communication time-frequency synchronization error processing module is used for analyzing and processing the full duplex communication time-frequency synchronization error.
Further, the specific working steps of the receiving end nonlinear correction module are as follows:
a1, performing signal filtering processing through an analog low-pass filter, and in a digital domain, a received signal v (n) obtained after filtering can be expressed as:
in the formula, h m Representing coefficients of the anti-aliasing filter;
a2, integrating the memory polynomial model with the received signal v (n) can obtain:
a3 by using OSF as the formulaDownsampling is performed, the symbol-level manner between the received signal y (n) and the transmitted signal z (n) may be further expressed as:
wherein:
a,4, after zero-padding, the signal x (n) can be expressed as:
wherein the method comprises the steps ofIs->Vectors of zero elements;
a5, pairAfter low-pass filtering, the following formula can be obtained
Wherein I represents the maximum order of the LPF filter, gamma i Representing the filter coefficient corresponding to the ith delay
A6 by using OSF as the formulaDownsampling may be performed to obtain the following formula:
wherein, and x (n) both assume synchronous calibration in time and frequency, z (n) can be further expressed as:
the A7, y (n) nonlinear model can be represented by the source notation as:
a8, the digital nonlinear correction function u (n) at the receiving end can be expressed as:
where D represents the maximum order of the nonlinear correction model and L represents the maximum depth of its memory effect.
The receiving link is inserted through the training model to compensate nonlinear distortion caused by the simulation components of the transmitting end, so that the signal symbol quality of the receiving end can be obviously improved,
further, the specific working method of the transmitting end nonlinear correction module is as follows:
at the transmitter end of the link, the modulated signal first passes through a root raised cosine filter, and DPD processing is performed on the signal at a high sampling rate. The output signal X (n) is filtered and downscaled by M times, the digital baseband signal is converted into a digital IF signal through a digital up-converter, meanwhile, the filtered downscaled signal X (n) is up-sampled and combined into an X1.25 matrix signal, then the X1.25 matrix signal is converted into a matrix signal FX1.25 through a low-pass filter to carry out correction estimation, the intermediate frequency digital signal with lower sampling rate is converted into an analog signal z (t), and finally the analog signal is sent into a power amplifier and transmitted through an antenna.
Further, the full duplex communication time-frequency synchronization error processing module includes:
in the transmitting node model, assuming that a baseband discrete signal of a transmitting node is s (n) ∈ {0,1}, after digital-to-analog conversion, the baseband discrete signal is changed into a baseband continuous signal to be denoted as s (t), and the s (t) is transmitted by a radio frequency antenna after up-conversion, wherein the transmitting signal can be expressed as follows:
wherein P is s Representing the transmitted signal power of a transmitting node of the system, f s Is the carrier frequency phi s Is the carrier primary phase;
if the baseband discrete signal of the cooperative interference node is i (n), the baseband discrete signal is converted into a baseband continuous signal i (t) after digital-to-analog conversion, the i (t) is up-converted and then transmitted through a radio frequency antenna, and the transmitting signal can be expressed as the following formula:
wherein P is i Representing the power of the transmitted signal of the cooperative interference node, f i Is the carrier frequency phi i Is the initial phase of the carrier wave;
the channel model, if the communication signal and the cooperative interference signal both experience an additive white gaussian noise channel, and are transmitted through a wireless channel, the radio frequency signal received by the receiving node can be expressed as: .
y(t)＝A s x s (t-t s )+A i x i (t-t i )+n(t)
Wherein A is s And A i The channel attenuation factors respectively representing the communication signals and the cooperative interference signals are not lost in generality, and are assumed to be 1; t is t s Representing a transmission delay of the communication signal; t is t i Representing interference messages
Transmission delay of the number; n (t) represents zero mean and sigma variance 2 Additive white gaussian noise of (2);
the signal model, the local transmit signal, may be expressed as:
where x (t) represents the equivalent baseband form of the local transmit signal, f c Representing the carrier frequency s z (t) and n sz (t) represents the resolved forms of the local transmit signal and noise, respectively, and in the case of self-interference, the received self-interference signal at the receiving link can be generally expressed as:
wherein I is(t) represents an ideal self-interference signal, nr (t) represents a reception link noise, K represents the number of paths of a self-interference channel,and->Respectively representing the channel complex coefficient and the time delay of the kth path;
interference signal reconstructed by receiving end canceller I c (t) may be represented by the formula:
wherein L is the number of taps of the canceller,and->The complex coefficient and the time delay of the 1 st tap are respectively;
thus, the residual SI signal (i.e., the cancellation error signal) can be expressed as
Further, the specific working steps of the full duplex communication time-frequency synchronization error processing module for parameter optimization are as follows:
b1, obtaining a mean square error as shown in the formula by using the interference cancellation error signal expression
In the method, in the process of the invention,is the receive link noise n r The power of (t);
b2, define R (τ) =es z (t)s z (t-τ)]For the resolved signal s corresponding to the local transmit signal s (t) z The complex autocorrelation function of (t) can be expressed as:
b3, can be expressed in matrix form as:
wherein:
b4, the signal characteristics are known, and the SI channel parameters are fixed, the optimization target is carried out on each tap parameter, as shown in the formula
Aiming at the imperfect time-frequency synchronization problem of distributed full duplex cooperative interference transceiving, the residual interference power under the condition of time-frequency synchronization error is deduced, the influence of the time-frequency synchronization error on the system performance is analyzed theoretically, and a closed expression of the receiver interference suppression ratio, the demodulation error rate and the communication capacity is obtained, wherein the receiver interference suppression ratio, the demodulation error rate and the communication capacity performance are obviously reduced along with the increase of time delay or frequency offset. The research can provide theoretical support and engineering reference for the design of an actual full duplex system.
Embodiment two:
a wireless communication device, the wireless communication device comprising: memory, processor and duplex transceiver program stored on the memory and executable on the processor.
Embodiment III:
a wireless communication method, the wireless communication method comprising the steps of:
transmitting a signal through a source transmitter; performing transmitting end nonlinear correction on transmitting end signals; receiving the signal by the target receiver; performing receiving end nonlinear correction on the receiving end signal; setting a full duplex communication broadband nonlinear low sampling rate; and calculating the influence of the time-frequency synchronization error on the system interference suppression performance.
Working principle: when in use, the signal is transmitted by the information source transmitter; performing transmitting end nonlinear correction on transmitting end signals; receiving the signal by the target receiver; performing receiving end nonlinear correction on the receiving end signal; setting a full duplex communication broadband nonlinear low sampling rate; and calculating the influence of the time-frequency synchronization error on the system interference suppression performance.
While certain exemplary embodiments of the present invention have been described above by way of illustration only, it will be apparent to those of ordinary skill in the art that modifications may be made to the described embodiments in various different ways without departing from the spirit and scope of the invention. Accordingly, the drawings and description are to be regarded as illustrative in nature and not as restrictive of the scope of the invention, which is defined by the appended claims.
Claims (7)
1. A duplex transmitting-receiving apparatus, comprising:
a target receiver for receiving a signal;
the receiving end nonlinear correction module is used for being inserted into the receiving link through a training model to compensate nonlinear distortion caused by the simulation components of the transmitting end, so that the signal symbol quality of the receiving end is improved;
a source transmitter for transmitting a signal;
the transmitting end nonlinear correction module is used for carrying out up-sampling processing on a transmitting signal before passing through the low-rate DAC and observed data after passing through the low-rate ADC module;
the broadband nonlinear transmitting link low sampling rate module is used for firstly dividing the full-band predistortion signal into three sections of frequency components in a digital mode before the transmitting link predistortion signal enters the power amplifier, wherein the three sections of frequency components correspond to an in-band part, an upper sideband part and a lower sideband part of the full-band predistortion signal respectively, and then three D/A converters with relatively low sampling rates are used for respectively converting the predistortion signal of the in-band, the lower sideband and the upper sideband from a digital domain to an analog domain, so that the hardware cost of the high sampling rate D/A is obviously reduced;
and the full duplex communication time-frequency synchronization error processing module is used for analyzing and processing the full duplex communication time-frequency synchronization error.
2. The duplex transceiver according to claim 1, wherein the specific working steps of the receiving-end nonlinear correction module are as follows:
a1, performing signal filtering processing through an analog low-pass filter, and in a digital domain, the received signal upsilon (n) obtained after filtering can be expressed as:
in the formula, h m Representing coefficients of the anti-aliasing filter;
a2, integrating the memory polynomial model with the received signal v (n) can obtain:
a3 by using OSF as the formulaDownsampling is performed, the symbol-level manner between the received signal y (n) and the transmitted signal z (n) may be further expressed as:
wherein:
a,4, after zero-padding, the signal x (n) can be expressed as:
wherein the method comprises the steps ofIs->Vectors of zero elements;
a5, pairAfter low-pass filtering, the following formula can be obtained
Wherein I represents the maximum order of the LPF filter, gamma i Representing the filter coefficient corresponding to the ith delay
A6 by using OSF as the formulaDownsampling may be performed to obtain the following formula:
wherein, and x (n) both assume synchronous calibration in time and frequency, z (n) can be further expressed as:
the A7, y (n) nonlinear model can be represented by the source notation as:
a8, the digital nonlinear correction function u (n) at the receiving end can be expressed as:
where D represents the maximum order of the nonlinear correction model and L represents the maximum depth of its memory effect.
3. The duplex transceiver according to claim 1, wherein the specific working method of the transmitting-end nonlinear correction module is as follows:
at the transmitter end of the link, the modulated signal first passes through a root raised cosine filter, and DPD processing is performed on the signal at a high sampling rate. The output signal X (n) is filtered and downscaled by M times, the digital baseband signal is converted into a digital IF signal through a digital up-converter, meanwhile, the filtered downscaled signal X (n) is up-sampled and combined into an X1.25 matrix signal, then the X1.25 matrix signal is converted into a matrix signal FX1.25 through a low-pass filter to carry out correction estimation, the intermediate frequency digital signal with lower sampling rate is converted into an analog signal z (t), and finally the analog signal is sent into a power amplifier and transmitted through an antenna.
4. The duplex transceiver of claim 1, wherein the full duplex communication time-frequency synchronization error processing module comprises:
in the transmitting node model, assuming that a baseband discrete signal of a transmitting node is s (n) ∈ {0,1}, after digital-to-analog conversion, the baseband discrete signal is changed into a baseband continuous signal to be denoted as s (t), and the s (t) is transmitted by a radio frequency antenna after up-conversion, wherein the transmitting signal can be expressed as follows:
wherein P is s Representing the transmitted signal power of a transmitting node of the system, f s Is the carrier frequency, phi s Is the carrier primary phase;
if the baseband discrete signal of the cooperative interference node is i (n), the baseband discrete signal is converted into a baseband continuous signal i (t) after digital-to-analog conversion, the i (t) is up-converted and then transmitted through a radio frequency antenna, and the transmitting signal can be expressed as the following formula:
wherein P is i Representation ofThe power of the transmitted signal of the cooperative interference node, f i Is the carrier frequency, phi i Is the initial phase of the carrier wave;
the channel model, if the communication signal and the cooperative interference signal both experience an additive white gaussian noise channel, and are transmitted through a wireless channel, the radio frequency signal received by the receiving node can be expressed as: .
y(t)＝A s x s (t-t s )+A i x i (t-t i )+n(t)
Wherein A is s And A i The channel attenuation factors respectively representing the communication signals and the cooperative interference signals are not lost in generality, and are assumed to be 1; t is t s Representing a transmission delay of the communication signal; t is t i Representing the transmission delay of the interference signal; n (t) represents zero mean and sigma variance 2 Additive white gaussian noise of (2);
the signal model, the local transmit signal, may be expressed as:
where x (t) represents the equivalent baseband form of the local transmit signal, f c Representing the carrier frequency s z (t) and n sz (t) represents the resolved forms of the local transmit signal and noise, respectively, and in the case of self-interference, the received self-interference signal at the receiving link can be generally expressed as:
where I (t) represents an ideal self-interference signal, nr (t) represents a receiving link noise, K represents the number of paths of the self-interference channel,and->Respectively representing the channel complex coefficient and the time delay of the kth path;
interference signal I reconstructed by receiving end canceller c (t) may be represented by the formula:
wherein L is the number of taps of the canceller,and->The complex coefficient and the time delay of the first tap are respectively;
thus, the residual SI signal (i.e., the cancellation error signal) can be expressed as
5. The duplex transceiver according to claim 1, wherein the specific working steps of the full duplex communication time-frequency synchronization error processing module for parameter optimization are as follows:
b1, obtaining a mean square error as shown in the formula by using the interference cancellation error signal expression
In the method, in the process of the invention,is the receive link noise n r The power of (t);
b2, define R (τ) =es z (t)s z (t-τ)]For a pair of locally transmitted signals s (t)The corresponding resolved signal s z The complex autocorrelation function of (t) can be expressed as:
b3, can be expressed in matrix form as:
wherein:
b4, the signal characteristics are known, and the SI channel parameters are fixed, the optimization target is carried out on each tap parameter, as shown in the formula
6. A wireless communication device according to claim 1, characterized in that the wireless communication device comprises: memory, processor and duplex transceiver program stored on the memory and executable on the processor.
7. A wireless communication method according to claim 6, characterized in that the wireless communication method comprises the steps of:
transmitting a signal through a source transmitter; performing transmitting end nonlinear correction on transmitting end signals; receiving the signal by the target receiver; performing receiving end nonlinear correction on the receiving end signal; setting a full duplex communication broadband nonlinear low sampling rate; and calculating the influence of the time-frequency synchronization error on the system interference suppression performance.
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Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20150156003A1 (en) * | 2013-11-30 | 2015-06-04 | Amir Keyvan Khandani | Wireless Full-Duplex System and Method with Self-Interference Sampling |
| CN108111186A (en) * | 2017-12-12 | 2018-06-01 | 东南大学 | A kind of digital self-interference removing method of zero intermediate frequency full-duplex transceiver |
| CN111052599A (en) * | 2017-08-28 | 2020-04-21 | 高通股份有限公司 | Method and apparatus for digital predistortion with reduced oversampling output ratio |
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| US20150156003A1 (en) * | 2013-11-30 | 2015-06-04 | Amir Keyvan Khandani | Wireless Full-Duplex System and Method with Self-Interference Sampling |
| CN111052599A (en) * | 2017-08-28 | 2020-04-21 | 高通股份有限公司 | Method and apparatus for digital predistortion with reduced oversampling output ratio |
| CN108111186A (en) * | 2017-12-12 | 2018-06-01 | 东南大学 | A kind of digital self-interference removing method of zero intermediate frequency full-duplex transceiver |
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| 肖尚辉: "全双工通信宽带收发非线性校正及同步误差处理技术研究", 《中国博士学位论文全文数据库 信息科技辑》, 15 January 2023 (2023-01-15), pages 48 - 50 * |
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