CN117614464B - Method and device for flexibly adjusting ultra-wideband message-guiding working frequency band - Google Patents
Method and device for flexibly adjusting ultra-wideband message-guiding working frequency band Download PDFInfo
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- CN117614464B CN117614464B CN202410098086.XA CN202410098086A CN117614464B CN 117614464 B CN117614464 B CN 117614464B CN 202410098086 A CN202410098086 A CN 202410098086A CN 117614464 B CN117614464 B CN 117614464B
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- 238000004891 communication Methods 0.000 claims description 12
- 230000005855 radiation Effects 0.000 claims description 8
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- 238000006243 chemical reaction Methods 0.000 claims description 6
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
- H04B1/0067—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with one or more circuit blocks in common for different bands
- H04B1/0082—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with one or more circuit blocks in common for different bands with a common local oscillator for more than one band
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- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F42—AMMUNITION; BLASTING
- F42C—AMMUNITION FUZES; ARMING OR SAFETY MEANS THEREFOR
- F42C11/00—Electric fuzes
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
- H04B1/40—Circuits
- H04B1/401—Circuits for selecting or indicating operating mode
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
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Abstract
The invention provides a method and a device for flexibly adjusting an ultra-wideband fuse working frequency band, and belongs to the technical field of radio fuses. Selecting an ultra-wideband fuze working frequency band, an ultra-wideband narrow pulse signal working frequency band and a phase-locked loop chip, then sending and receiving radio signals according to a circuit of the device, and outputting a near-frying starting signal for the received signals; the device adopts the circuit design of mixing the carrier-free ultra-wideband signal and the local oscillation signal, breaks through the limitation of the working frequency band of the traditional ultra-wideband proximity fuse, and realizes the large-span adjustment of the working frequency band. The invention solves the problem that the conventional ultra-wideband message-guiding working frequency range is narrower, and the adversary message-guiding jammer can pertinently interfere; the ultra-wideband fuze and other radio equipment on the bullet have the problem of the risk of mutual winding, and the advantage of flexibly adjusting the working frequency band of the ultra-wideband proximity fuze is provided.
Description
Technical Field
The invention relates to the technical field of radio fuses, in particular to a method and a device for flexibly adjusting an ultra-wideband fuse working frequency band.
Background
The ultra-wideband fuze has the characteristics of high distance precision, strong anti-interference capability and low power consumption, and the ultra-wideband has become a main technical system in the radio fuze. However, due to the limitation of the device technology level, the ultra-wideband communication working frequency band is generally difficult to break through the C band.
The ultra-wideband fuze radiation signal has strong concealment, and an adversary fuze jammer is difficult to detect and intercept the ultra-wideband signal. However, the enemy fuze jammer under the use environment can pertinently implement sweep-frequency interference on a fixed frequency band range, the interference frequency range covers the working frequency band of the conventional ultra-wideband fuze, the reliability of the fuze can be affected, and the fuze can even be pre-fried.
In addition, with the improvement of the intelligent degree of ammunition, more and more radio receiving and transmitting devices such as missile-borne data chains, missile-borne telemetry, missile-borne radio stations, missile-borne Beidou receivers, missile-borne active seekers, missile-borne passive seekers and the like are provided, and the radiation signal waveforms, the working frequency bands, the radiation source angles, the modulation parameters, the polarization modes and the like of the ammunition are various, so that the intelligent ammunition is in a complex electromagnetic environment. The fuze acts as a radio radiation source, and may interfere with the receiving circuits of other subsystems on the projectile, such as Beidou receivers, passive guide heads, and the like. In order to reduce the mutual influence of the fuze and other radio receiving and transmitting equipment of the intelligent ammunition, the working frequency bands are separated from each other, and the mutual interference caused by frequency band crowding is avoided.
Secondly, electromagnetic interference faced by the fuze in a use environment and the working frequency range of the fuze may overlap, for example, the fuze strikes a large-scale radio device such as a radar, a base station and the like, and the working frequency range of the fuze should be adjusted in advance at this time, so that the fuze is prevented from working under the interference condition when blocked.
Therefore, the conventional ultra-wideband message-guiding working frequency range in the prior art is narrower, and the adversary message-guiding jammer can pertinently interfere; the ultra-wideband fuze is at risk of intertwining with other radio devices on the projectile.
Disclosure of Invention
The invention solves the technical problems that: the conventional ultra-wideband fuze has a narrower working frequency range, and an adversary fuze jammer can pertinently interfere; the ultra-wideband fuze is at risk of intertwining with other radio devices on the projectile.
In order to solve the problems, the technical scheme of the invention is as follows:
a method for flexibly adjusting an ultra-wideband pilot frequency working frequency band comprises the following steps:
s1, selecting an ultra-wideband fuze working frequency band, an ultra-wideband narrow pulse signal working frequency band and a phase-locked loop chip;
s2, the high-stability crystal oscillator clock outputs a clock signal with square wave, and the clock signal is filtered by a second-order low-pass filter to obtain a sine wave signal and output the sine wave signal to a phase-locked loop chip;
s3, after the FPGA chip configures a register in the phase-locked loop chip through the SPI interface, the phase-locked loop chip outputs local oscillation signals;
s4, the local oscillator signals are subjected to power division by a power divider to obtain two paths of signals, namely a first local oscillator signal for up-conversion of a transmitting link and a second local oscillator signal for down-conversion of a receiving link;
s5, the crystal oscillator generates an oscillation clock signal, and the oscillation clock signal is multiplied by a digital phase-locked loop in the FPGA chip to obtain a high-frequency clock and is used as a master clock in the FPGA chip; a pulse coding circuit in the FPGA chip outputs a modulated clock signal, the modulated clock signal is processed by a first narrow pulse generating circuit to obtain an impulse signal, and a first filtering circuit gates the impulse signal to obtain a first ultra-wideband signal;
s6, the pulse coding circuit outputs a modulated clock signal to be delayed through a delay circuit in the FPGA chip, and then the modulated clock signal is processed through a second narrow pulse generating circuit to obtain a sampling wave gate signal;
s7, mixing the first ultra-wideband signal and the first local oscillator signal through a first mixer, and gating through a second filter circuit to obtain a modulated signal;
s8, the modulated signal is amplified by the first amplifying circuit and radiated by the transmitting antenna, scattered by the target and received by the receiving antenna to obtain a received signal, the received signal is amplified by the second amplifying circuit and mixed with a second local oscillator signal by the second mixer, and filtered by the third filter circuit to obtain a second ultra-wideband signal;
s9, the second ultra-wideband signal and the sampling wave gate signal are received through the equivalent sampling circuit in a correlated mode to obtain a detection signal, the detection signal is amplified and filtered through the amplifying and filtering circuit and then input into the signal judging module, and the signal judging module judges that the detection signal accords with the target echo characteristic and then outputs a near-frying starting signal.
As one aspect of the present invention, selecting an ultra wideband fuze operating band, an ultra wideband narrow pulse signal operating band, and a phase locked loop chip includes the steps of:
s1-1, selecting an ultra-wideband communication operation frequency band of 1-38 GHz according to the operation frequency band, the radiation power and the use environment of the on-bullet radio equipment, wherein the bandwidth of the ultra-wideband communication operation frequency band is 500-1000 MHz;
s1-2, setting the working frequency band of the ultra-wideband narrow pulse signal to be 1-6 GHz, wherein the bandwidth of the working frequency band of the ultra-wideband narrow pulse signal is 500-1000 MHz;
s1-3, setting the working frequency of the local oscillator signal as the difference value between the ultra-wideband pilot signal working frequency band and the ultra-wideband narrow pulse signal working frequency band, and selecting a phase-locked loop chip with the output frequency covering the working frequency of the local oscillator signal.
Description: the conventional ultra-wideband signal generation method adopts a step diode scheme or an avalanche transistor scheme, which is limited by the technical level of devices, has weak energy in a frequency band above a C band, and is difficult to be applied to fuze.
As one aspect of the present invention, the truncated frequency calculation formula of the second-order low-pass filter is:in the above, the->Is the cut-off frequency of the second order low pass filter,Lin the case of an inductance,Cis a capacitor.
Description: the LC low-pass filter has low cost and is easy to realize.
As one aspect of the present invention, the relationship between the cut-off frequency of the second-order low-pass filter and the operating frequency of the high-stability crystal oscillator clock is: the working frequency of the high-stability crystal oscillator clock is recorded asf HO ，f HO ＜ ＜ 3×f HO 。
Description: the high-stability crystal oscillator outputs square wave signals, and the square wave signals comprise signals with different frequencies such as fundamental waves, third harmonic waves, fifth harmonic waves, seventh harmonic waves and the like. The second order low pass filter suppresses three or more harmonics.
As one aspect of the present invention, the operating frequency of the local oscillator signal is calculated as:in the above, the->Is the working frequency of local oscillation signal, < >>For ultra-wideband communication working frequency band +.>Is the working frequency band of ultra-wideband narrow pulse signal, +.>Is the working frequency of a high-stability crystal oscillator clock, < >>Is the prepositive frequency division coefficient of the phase-locked loop chip, < + >>Is the post frequency division coefficient of the phase-locked loop chip.
Description: local oscillation signals with different frequencies can be realized by adjusting N, R; r corresponds to an R frequency divider and N corresponds to an N frequency divider.
As one aspect of the present invention, a method for obtaining a modulated signal through a second filter circuit includes: and removing the lower local oscillator signal and reserving the upper local oscillator signal through a second filter circuit to obtain a modulated signal, wherein the lower local oscillator signal is the difference value between the working frequency of the local oscillator signal and the working frequency range of the ultra-wideband narrow pulse signal, and the upper local oscillator signal is the sum of the working frequency of the local oscillator signal and the working frequency range of the ultra-wideband narrow pulse signal.
Description: the second filter circuit suppresses the lower local oscillation signal, avoids the saturation of the first amplifying circuit at the rear stage caused by the working frequency external signal, and improves the power intensity of the useful radiation signal.
As one aspect of the present invention, the third filter circuit is identical to the passband width of the first filter circuit.
Description: the filter circuit consistently improves the modularization and generalization of the product.
As one aspect of the present invention, the method for determining that the detected signal meets the target echo characteristic by the signal determining module includes: after the detection signal is processed by the digital band-pass filtering submodule, a template matching algorithm carries out correlation operation on the processed detection signal and a template signal stored in an FPGA chip to obtain a correlation coefficientWhen the correlation coefficient-><And 0.8, the signal judgment module judges that the detection signal accords with the target echo characteristic.
Description: because the target echo is only related to the echo and is not related to the noise, the influence of the noise on the signal identification moment is reduced by the detection of the correlation coefficient peak value, and the consistency of the frying height is improved.
The invention also provides a device for flexibly adjusting the ultra-wideband message-guiding working frequency band, which is used for executing the method for flexibly adjusting the ultra-wideband message-guiding working frequency band, and comprises the following steps:
the transmitting link comprises a high-stability crystal oscillator clock, a second-order low-pass filter, a phase-locked loop chip, a power divider, a first mixer, a second filter circuit, a first amplifying circuit and a transmitting antenna, wherein the second-order low-pass filter and the phase-locked loop chip are electrically connected with the high-stability crystal oscillator clock in sequence;
the receiving link comprises a crystal oscillator, an FPGA chip electrically connected with the crystal oscillator, a second narrow pulse generating circuit electrically connected with the FPGA chip, a third filter circuit and an equivalent sampling circuit, wherein the third filter circuit is sequentially connected with a second mixer and a second amplifying circuit, the second mixer is electrically connected with a power divider, the second amplifying circuit is electrically connected with a transmitting antenna, and the equivalent sampling circuit is electrically connected with an amplifying filter circuit;
the FPGA chip is internally provided with a digital phase-locked loop, a pulse coding circuit and a delay circuit which are electrically connected in sequence, the FPGA chip is also provided with a signal judging module, the pulse coding circuit is electrically connected with a first narrow pulse generating circuit and a first filter circuit in sequence, the first filter circuit is electrically connected with a first mixer, the signal judging module is electrically connected with an amplifying filter circuit, and the FPGA chip is electrically connected with the phase-locked loop chip through an SPI interface; the digital phase-locked loop is electrically connected with the crystal oscillator, and the delay circuit is electrically connected with the second narrow pulse generating circuit.
As one aspect of the present invention, a phase-locked loop chip includes an R-divider and an N-divider; the R frequency divider and the N frequency divider are electrically connected with a phase discriminator, the phase discriminator is electrically connected with a loop filter, the loop filter is electrically connected with a voltage-controlled vibrator in the phase-locked loop chip, and the voltage-controlled vibrator is electrically connected with the N frequency divider; the R frequency divider is electrically connected with the second-order low-pass filter, and the voltage-controlled vibrator is electrically connected with the power divider.
Description: the phase-locked loop chip scheme integrating the phase discriminator and the voltage-controlled oscillator improves the system integration level and avoids the influence of circuit parasitic parameters on the performance of the high-frequency circuit.
The beneficial effects of the invention are as follows:
the method adopts the frequency mixing of the carrier-free ultra-wideband signal and the local oscillator signal, breaks through the limitation of the working frequency band of the traditional ultra-wideband proximity fuse, and realizes the large-span adjustment of the working frequency band; further, the frequency of the local oscillation signal is adjusted, so that the flexible adjustment of the working frequency band of the fuze is realized; therefore, the invention can flexibly adjust the working frequency band of the ultra-wideband proximity fuse according to the working frequency band of the electromagnetic environment of a battlefield or other radio equipment on a bullet.
Drawings
FIG. 1 is a flowchart of a method for flexibly adjusting an ultra wideband pilot frequency band according to embodiment 1 of the present invention;
fig. 2 is a circuit diagram of a device for flexibly adjusting an ultra-wideband signaling operating frequency band according to embodiment 2 of the present invention;
fig. 3 is a schematic block diagram of a phase-locked loop chip in embodiment 2 of the present invention;
fig. 4 is a schematic block diagram of a second-order low-pass filter in embodiment 2 of the present invention;
fig. 5 is a schematic block diagram of a first narrow pulse generating circuit and a second narrow pulse generating circuit in embodiment 2 of the present invention;
fig. 6 is a schematic block diagram of an equivalent sampling circuit in embodiment 2 of the present invention;
FIG. 7 is a schematic block diagram of an amplification filter circuit in embodiment 2 of the present invention;
the high-stability crystal oscillator clock, a 2-second-order low-pass filter, a 3-phase-locked loop chip, a 31-R frequency divider, a 32-N frequency divider, a 33-phase discriminator, a 34-loop filter, a 35-voltage-controlled vibrator, a 4-power divider, a 5-first mixer, a 6-second filter circuit, a 7-first amplifying circuit, an 8-transmitting antenna, a 9-crystal oscillator, a 10-digital phase-locked loop, an 11-pulse coding circuit, a 12-delay circuit, a 13-second narrow pulse generating circuit, a 14-equivalent sampling circuit, a 15-amplifying filter circuit, a 16-signal judging module, a 17-first narrow pulse generating circuit, an 18-first filter circuit, a 19-second mixer, a 20-second amplifying circuit and a 21-third filter circuit.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention will be described in further detail below with reference to the accompanying drawings, and it is apparent that the described embodiments are only some embodiments of the present invention, not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The terminology used in the embodiments of the invention is for the purpose of describing particular embodiments only and is not intended to be limiting of the invention. As used in this application and the appended claims, the singular forms "a," "an," and "the" are intended to include the plural forms as well, unless the context clearly indicates otherwise, the "plurality" generally includes at least two.
It should be understood that although the terms first, second, third, etc. may be used to describe … … in embodiments of the present invention, these … … should not be limited to these terms. These terms are only used to distinguish … …. For example, the first … … may also be referred to as the second … …, and similarly the second … … may also be referred to as the first … …, without departing from the scope of embodiments of the present invention.
Example 1: the embodiment describes a method for flexibly adjusting an ultra-wideband communication work frequency band, as shown in fig. 1, comprising the following steps:
s1, selecting an ultra-wideband fuze working frequency band, an ultra-wideband narrow pulse signal working frequency band and a phase-locked loop chip 3, wherein the method specifically comprises the following steps:
s1-1, selecting an ultra-wideband communication operation frequency band of 1-38 GHz according to the operation frequency band, the radiation power and the use environment of the on-bullet radio equipment, wherein the bandwidth of the ultra-wideband communication operation frequency band is 500-1000 MHz;
s1-2, setting the working frequency band of the ultra-wideband narrow pulse signal to be 1-6 GHz, wherein the bandwidth of the working frequency band of the ultra-wideband narrow pulse signal is 500-1000 MHz;
s1-3, setting the working frequency of the local oscillator signal as the difference value between the ultra-wideband pilot signal working frequency band and the ultra-wideband narrow pulse signal working frequency band, and selecting a phase-locked loop chip 3 with the output frequency covering the working frequency of the local oscillator signal;
it can be understood that in the present embodiment, the truncated frequency calculation formula of the second-order low-pass filter 2 is:in the above, the->Is the cut-off frequency of the second order low pass filter 2,Lin the case of an inductance,Cis a capacitor;
it can be understood that in this embodiment, the relationship between the cut-off frequency of the second-order low-pass filter 2 and the operating frequency of the high-stability crystal oscillator clock 1 is: the working frequency of the high-stability crystal oscillator clock 1 is recorded asf HO ，f HO ＜ ＜ 3×f HO The method comprises the steps of carrying out a first treatment on the surface of the For example, the number of the cells to be processed,f HO =10MHz，L=10nH，C=10nf, at this time->=15.9MHz；
S2, the high-stability crystal oscillator clock 1 outputs a clock signal with square wave, and the clock signal is filtered by the second-order low-pass filter 2 to obtain a sine wave signal and output the sine wave signal to the phase-locked loop chip 3;
it can be understood that in this embodiment, the working frequency calculation formula of the local oscillation signal is:in the above, the->Is the working frequency of local oscillation signal, < >>For ultra-wideband communication working frequency band +.>Is the working frequency band of ultra-wideband narrow pulse signal, +.>For the working frequency of the high-stability crystal oscillator clock 1, < >>Is the pre-divide coefficient of the phase-locked loop chip 3, < >>Is the post frequency division coefficient of the phase-locked loop chip 3;
s3, after the FPGA chip configures a register in the phase-locked loop chip 3 through an SPI interface, the phase-locked loop chip 3 outputs local oscillation signals;
s4, the local oscillator signals are subjected to power division by a power divider 4 to obtain two paths of signals, namely a first local oscillator signal for up-conversion of a transmitting link and a second local oscillator signal for down-conversion of a receiving link;
s5, the crystal oscillator 9 generates an oscillation clock signal, and the oscillation clock signal is multiplied by a digital phase-locked loop 10 in the FPGA chip to obtain a high-frequency clock and is used as a master clock in the FPGA chip; the pulse coding circuit 11 in the FPGA chip outputs a modulated clock signal, the modulated clock signal is processed by the first narrow pulse generating circuit 17 to obtain an impulse signal, and the impulse signal is gated by the first filtering circuit 18 to obtain a first ultra-wideband signal;
s6, the pulse coding circuit 11 outputs a modulated clock signal, delays the clock signal through the delay circuit 12 in the FPGA chip, and then processes the clock signal through the second narrow pulse generating circuit 13 to obtain a sampling wave gate signal;
s7, mixing the first ultra-wideband signal and the first local oscillator signal through a first mixer 5, and gating through a second filter circuit 6 to obtain a modulated signal;
it can be understood that in this embodiment, the method for obtaining the modulated signal through the second filter circuit 6 is as follows: removing the lower local oscillation signal and reserving the upper local oscillation signal through a second filter circuit 6 to obtain a modulated signal, wherein the lower local oscillation signal is the difference value between the working frequency of the local oscillation signal and the working frequency range of the ultra-wideband narrow pulse signal, and the upper local oscillation signal is the sum of the working frequency of the local oscillation signal and the working frequency range of the ultra-wideband narrow pulse signal;
s8, the modulated signal is amplified by the first amplifying circuit 7 and radiated by the transmitting antenna 8, scattered by a target and received by the receiving antenna to obtain a received signal, the received signal is amplified by the second amplifying circuit 20 and mixed with a second local oscillator signal by the second mixer 19, and filtered by the third filter circuit 21 to obtain a second ultra-wideband signal;
optionally, in this embodiment, the third filter circuit 21 is consistent with the passband width of the first filter circuit 18;
s9, the second ultra-wideband signal and the sampling wave gate signal are received through the equivalent sampling circuit 14 in a correlated manner to obtain a detection signal, the detection signal is amplified and filtered through the amplifying and filtering circuit 15 and then input into the signal judging module 16, and the signal judging module 16 judges that the detection signal accords with the target echo characteristic and then outputs a near-frying starting signal;
it can be understood that in this embodiment, the method for determining that the detected signal meets the target echo characteristic by the signal determining module 16 is as follows: after the detection signal is processed by the digital band-pass filtering submodule, a template matching algorithm carries out correlation operation on the processed detection signal and a template signal stored in an FPGA chip to obtain a correlation coefficientWhen the correlation coefficient-><0.8, the signal judgment module 16 judges that the detected signal accords with the target echo characteristic; it will be appreciated that in this embodiment, the correlation coefficient +.>The calculation formula of (2) is as follows: />In the above, the->For the correlation coefficient +.>For the processed detection signal, +.>Is a template signal.
Example 2: the present embodiment describes a device for flexibly adjusting an ultra-wideband signaling working frequency band, which is configured to execute a method for flexibly adjusting an ultra-wideband signaling working frequency band in embodiment 1, as shown in fig. 2, and includes:
the transmitting link comprises a high-stability crystal oscillator clock 1, a second-order low-pass filter 2, a phase-locked loop chip 3, a power divider 4, a first mixer 5, a second filter circuit 6, a first amplifying circuit 7 and a transmitting antenna 8 which are electrically connected with the high-stability crystal oscillator clock 1 in sequence;
the receiving link comprises a crystal oscillator 9, an FPGA chip electrically connected with the crystal oscillator 9, a second narrow pulse generating circuit 13 electrically connected with the FPGA chip, a third filter circuit 21 and an equivalent sampling circuit 14 electrically connected with the second narrow pulse generating circuit 13, a second mixer 19 and a second amplifying circuit 20 sequentially connected with the third filter circuit 21, the second mixer 19 is electrically connected with the power divider 4, the second amplifying circuit 20 is electrically connected with the transmitting antenna 8, and the equivalent sampling circuit 14 is electrically connected with the amplifying filter circuit 15;
the digital phase-locked loop 10, the pulse coding circuit 11 and the delay circuit 12 which are electrically connected in sequence are arranged in the FPGA chip, the signal judging module 16 is further carried on the FPGA chip, the pulse coding circuit 11 is electrically connected with the first narrow pulse generating circuit 17 and the first filter circuit 18 in sequence, the first filter circuit 18 is electrically connected with the first mixer 5, the signal judging module 16 is electrically connected with the amplifying filter circuit 15, and the FPGA chip is electrically connected with the phase-locked loop chip 3 through an SPI interface; the digital phase-locked loop 10 is electrically connected with the crystal oscillator 9, and the delay circuit 12 is electrically connected with the second narrow pulse generating circuit 13;
it is understood that FPGA chips refer to field programmable gate arrays; FPGA (Field Programmable Gate Array) is a product of further development on the basis of programmable devices such as PAL (programmable array logic), GAL (generic array logic) and the like; the programmable device is used as a semi-custom circuit in the field of Application Specific Integrated Circuits (ASICs), which not only solves the defect of custom circuits, but also overcomes the defect of limited gate circuits of the original programmable device;
as can be appreciated, as shown in fig. 4, in the present embodiment, the second-order low-pass filter 2 is composed of an inductance and a capacitance;
it can be understood that, as shown in fig. 5, in this embodiment, the circuits of the first narrow pulse generating circuit 17 and the second narrow pulse generating circuit 13 are the same, and each of the circuits is composed of a step recovery diode, a peripheral inductor and a capacitor which are electrically connected in sequence;
therefore, in step S5, the first narrow pulse generating circuit 11 generates a narrow pulse signal through a step recovery diode; the circuit utilizes the characteristics of long storage time and short fall time of reverse cut-off when the step recovery diode is forward conducted, and a large amount of stored minority charge is discharged in a very short time; in step S6, the second narrow pulse generating circuit 13 functions as it is;
it can be understood that, as shown in fig. 6, in this embodiment, the equivalent sampling circuit 14 is composed of a mixer diode and a peripheral integral differential resistance-capacitance circuit electrically connected in sequence;
as can be understood, as shown in fig. 7, in the present embodiment, the amplifying filter circuit 15 is an active low-pass filter amplifying circuit composed of two stages of operational amplifiers and resistors and capacitors;
therefore, in step S9, the amplifying and filtering circuit 15 has two functions, namely, amplifying the amplitude, filtering the frequency range, and amplifying the signal in a certain frequency range to suppress the signal in other frequency ranges;
it will be appreciated that in this embodiment, the first filter circuit 18, the second filter circuit 6 and the third filter circuit 21 are each composed of an integrated LC filter of low temperature co-fired ceramic technology, which reduces the size compared to discrete devices; the first amplifying circuit 7 is a power amplifier, and the second amplifying circuit 20 is a low noise amplifier; the pulse coding circuit 11 consists of a trigger and a lookup table in the FPGA; the delay circuit 12 is implemented by a look-up table inside the FPGA;
therefore, in step S5, the impulse signal (i.e., the extremely narrow pulse signal) is rich in spectral components, and has a strong power spectral density in the range from several tens of megahertz to several gigahertz; the first filter circuit 18 gates the frequency range of the impulse signal, frequency components outside the passband range of the first filter circuit 18 are suppressed, and only frequency components in the passband are reserved; in step S7, the second filter circuit 6 functions as it is;
it can be understood that in the present embodiment, as shown in fig. 3, the phase-locked loop chip 3 includes an R frequency divider 31 and an N frequency divider 32; the R frequency divider 31 and the N frequency divider 32 are electrically connected with a phase detector 33, the phase detector 33 is electrically connected with a loop filter 34, the loop filter 34 is electrically connected with a voltage-controlled vibrator 35 in the phase-locked loop chip 3, and the voltage-controlled vibrator 35 is electrically connected with the N frequency divider 32; the R frequency divider 31 is electrically connected to the second-order low-pass filter 2, and the voltage-controlled vibrator 35 is electrically connected to the power divider 4.
Claims (9)
1. The method for flexibly adjusting the ultra-wideband communication work frequency band is characterized by comprising the following steps:
s1, selecting an ultra-wideband fuze working frequency band, an ultra-wideband narrow pulse signal working frequency band and a phase-locked loop chip (3);
s2, outputting a clock signal with square wave waveform by the high-stability crystal oscillator clock (1), filtering higher harmonic waves by the clock signal through the second-order low-pass filter (2) to obtain a sine wave signal, and outputting the sine wave signal to the phase-locked loop chip (3);
s3, after the FPGA chip configures a register in the phase-locked loop chip (3) through the SPI interface, the phase-locked loop chip (3) outputs local oscillation signals;
s4, obtaining two paths of signals after the local oscillator signals are subjected to power division by a power divider (4), wherein the two paths of signals are respectively a first local oscillator signal for up-conversion of a transmitting link and a second local oscillator signal for down-conversion of a receiving link;
s5, the crystal oscillator (9) generates an oscillation clock signal, and the oscillation clock signal is multiplied by a digital phase-locked loop (10) in the FPGA chip to obtain a high-frequency clock and is used as a master clock in the FPGA chip; a pulse coding circuit (11) in the FPGA chip outputs a modulated clock signal, the modulated clock signal is processed by a first narrow pulse generating circuit (17) to obtain an impulse signal, and a first filtering circuit (18) gates the impulse signal to obtain a first ultra-wideband signal;
s6, the pulse coding circuit (11) outputs a modulated clock signal, delays the clock signal through a delay circuit (12) in the FPGA chip, and then processes the clock signal through the second narrow pulse generating circuit (13) to obtain a sampling wave gate signal;
s7, mixing the first ultra-wideband signal and the first local oscillator signal through a first mixer (5), and gating through a second filter circuit (6) to obtain a modulated signal;
s8, the modulated signal is amplified by a first amplifying circuit (7) and radiated by a transmitting antenna (8), then scattered by a target and received by a receiving antenna to obtain a received signal, the received signal is amplified by a second amplifying circuit (20) and mixed with a second local oscillator signal by a second mixer (19), and then filtered by a third filter circuit (21) to obtain a second ultra-wideband signal;
s9, the second ultra-wideband signal and the sampling wave gate signal are received in a correlated manner through an equivalent sampling circuit (14) to obtain a detection signal, the detection signal is amplified and filtered through an amplifying and filtering circuit (15) and then input into a signal judging module (16), and the signal judging module (16) judges that the detection signal accords with the target echo characteristic and then outputs a near-frying starting signal.
2. A method for flexibly adjusting an ultra wideband fuze operating band according to claim 1, characterized in that the selecting of the ultra wideband fuze operating band, the ultra wideband narrow pulse signal operating band and the phase locked loop chip (3) comprises the steps of:
s1-1, selecting an ultra-wideband communication working frequency band of 1-38 GHz according to the working frequency band, the radiation power and the use environment of the on-bullet radio equipment, wherein the bandwidth of the ultra-wideband communication working frequency band is 500-1000 MHz;
s1-2, setting the working frequency band of the ultra-wideband narrow pulse signal to be 1-6 GHz, wherein the bandwidth of the working frequency band of the ultra-wideband narrow pulse signal is 500-1000 MHz;
s1-3, setting the working frequency of the local oscillator signal as the difference value between the ultra-wideband pilot signal working frequency band and the ultra-wideband narrow pulse signal working frequency band, and selecting a phase-locked loop chip (3) with the output frequency covering the working frequency of the local oscillator signal.
3. The method for flexibly adjusting an ultra-wideband pilot operating frequency band according to claim 2, wherein the truncated frequency calculation formula of the second-order low-pass filter (2) is as follows:in the above, the->Is the cut-off frequency of the second order low pass filter (2),Lin the case of an inductance,Cis a capacitor.
4. A method for flexibly adjusting an ultra-wideband signaling operating frequency band according to claim 3, wherein the relationship between the cut-off frequency of the second-order low-pass filter (2) and the operating frequency of the high-stability crystal oscillator clock (1) is: the working frequency of the high-stability crystal oscillator clock (1) is recorded asf HO ，f HO ＜ ＜ 3×f HO 。
5. The method for flexibly adjusting an ultra-wideband pilot frequency operating band of claim 1, wherein the operating frequency of the local oscillator signal is calculated according to the formula:in the above, the->Is the working frequency of local oscillation signal, < >>For ultra-wideband communication working frequency band +.>Is the working frequency band of ultra-wideband narrow pulse signal, +.>For the operating frequency of a highly stable crystal oscillator clock (1)>Is the pre-division coefficient of the phase-locked loop chip (3)>Is a post-division coefficient of the phase-locked loop chip (3).
6. A method for flexibly adjusting an ultra-wideband signaling operating frequency band according to claim 1, wherein the method for obtaining the modulated signal through the second filter circuit (6) comprises: and removing the lower local oscillator signal and reserving the upper local oscillator signal through a second filter circuit (6) to obtain a modulated signal, wherein the lower local oscillator signal is the difference value between the working frequency of the local oscillator signal and the working frequency range of the ultra-wideband narrow pulse signal, and the upper local oscillator signal is the sum of the working frequency of the local oscillator signal and the working frequency range of the ultra-wideband narrow pulse signal.
7. The method for flexibly adjusting an ultra-wideband pilot frequency band according to claim 1, wherein the method for determining that the detected signal meets the target echo characteristic by the signal determining module (16) is as follows: after the detection signal is processed by the digital band-pass filtering submodule, a template matching algorithm carries out correlation operation on the processed detection signal and a template signal stored in an FPGA chip to obtain a correlation coefficientWhen the correlation coefficient-><And 0.8, the signal judgment module (16) judges that the detected signal accords with the target echo characteristic.
8. A device for flexibly adjusting an ultra-wideband signaling working frequency band, configured to perform a method for flexibly adjusting an ultra-wideband signaling working frequency band according to any one of claims 1 to 7, comprising: the transmitting link comprises a high-stability crystal oscillator clock (1), a second-order low-pass filter (2) and a phase-locked loop chip (3), a power divider (4), a first mixer (5), a second filter circuit (6), a first amplifying circuit (7) and a transmitting antenna (8) which are electrically connected with the high-stability crystal oscillator clock (1) in sequence;
the receiving link comprises a crystal oscillator (9), an FPGA chip electrically connected with the crystal oscillator (9), a second narrow pulse generating circuit (13) electrically connected with the FPGA chip, a third filter circuit (21) and an equivalent sampling circuit (14) electrically connected with the second narrow pulse generating circuit (13), a second mixer (19) and a second amplifying circuit (20) sequentially connected with the third filter circuit (21), the second mixer (19) is electrically connected with the power divider (4), the second amplifying circuit (20) is electrically connected with the transmitting antenna (8), and the equivalent sampling circuit (14) is electrically connected with an amplifying filter circuit (15);
the FPGA chip is internally provided with a digital phase-locked loop (10), a pulse coding circuit (11) and a delay circuit (12) which are electrically connected in sequence, the FPGA chip is further provided with a signal judging module (16), the pulse coding circuit (11) is electrically connected with a first narrow pulse generating circuit (17) and a first filtering circuit (18) in sequence, the first filtering circuit (18) is electrically connected with the first mixer (5), the signal judging module (16) is electrically connected with the amplifying and filtering circuit (15), and the FPGA chip is electrically connected with the phase-locked loop chip (3) through an SPI interface; the digital phase-locked loop (10) is electrically connected with the crystal oscillator (9), and the delay circuit (12) is electrically connected with the second narrow pulse generating circuit (13).
9. The device for flexibly adjusting an ultra-wideband signaling operating frequency band according to claim 8, wherein the phase-locked loop chip (3) comprises an R-divider (31) and an N-divider (32); the R frequency divider (31) and the N frequency divider (32) are electrically connected with a phase detector (33), the phase detector (33) is electrically connected with a loop filter (34), the loop filter (34) is electrically connected with a voltage-controlled vibrator (35) in the phase-locked loop chip (3), and the voltage-controlled vibrator (35) is electrically connected with the N frequency divider (32); the R frequency divider (31) is electrically connected with the second-order low-pass filter (2), and the voltage-controlled vibrator (35) is electrically connected with the power divider (4).
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Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105758269A (en) * | 2016-01-25 | 2016-07-13 | 北京宏动科技有限公司 | Wireless synchronous testing simulation system of ultra-wideband radio fuse |
| CN113311396A (en) * | 2021-05-19 | 2021-08-27 | 南京理工大学 | Interference and anti-interference digital simulation system based on millimeter wave fuse and construction method thereof |
| CN114577076A (en) * | 2022-04-07 | 2022-06-03 | 北京宏动科技股份有限公司 | Method for eliminating impulse fuse noise |
| CN116413654A (en) * | 2023-06-09 | 2023-07-11 | 北京中科睿信科技有限公司 | Ultra-wideband radio fuze target simulation device and method based on DRFM |
| CN116428922A (en) * | 2023-02-03 | 2023-07-14 | 北京宏动科技股份有限公司 | Impulse fuse modulation method and system |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7417582B2 (en) * | 2004-10-22 | 2008-08-26 | Time Domain Corporation | System and method for triggering an explosive device |
| FR3125887B1 (en) * | 2021-07-29 | 2023-08-25 | Commissariat Energie Atomique | DEVICE AND METHOD FOR RADAR MEASUREMENT WITH DUAL RADAR SIGNAL GENERATION |
-
2024
- 2024-01-24 CN CN202410098086.XA patent/CN117614464B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105758269A (en) * | 2016-01-25 | 2016-07-13 | 北京宏动科技有限公司 | Wireless synchronous testing simulation system of ultra-wideband radio fuse |
| CN113311396A (en) * | 2021-05-19 | 2021-08-27 | 南京理工大学 | Interference and anti-interference digital simulation system based on millimeter wave fuse and construction method thereof |
| CN114577076A (en) * | 2022-04-07 | 2022-06-03 | 北京宏动科技股份有限公司 | Method for eliminating impulse fuse noise |
| CN116428922A (en) * | 2023-02-03 | 2023-07-14 | 北京宏动科技股份有限公司 | Impulse fuse modulation method and system |
| CN116413654A (en) * | 2023-06-09 | 2023-07-11 | 北京中科睿信科技有限公司 | Ultra-wideband radio fuze target simulation device and method based on DRFM |
Non-Patent Citations (2)
| Title |
|---|
| 无线电近炸引信抗干扰方法;向正义 等;探测与控制学报;20091231;第31卷(增刊);第4-7页 * |
| 自适应超宽带频率捷变防空导弹PD引信;王涛;信息与电子工程;20050630;第3卷(第2期);第129-132页 * |
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