CN117394004B - Multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication - Google Patents
Multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication Download PDFInfo
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- H—ELECTRICITY
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- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
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- H—ELECTRICITY
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- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
- H01Q15/24—Polarising devices; Polarisation filters
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/0006—Particular feeding systems
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- H—ELECTRICITY
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- H01Q21/00—Antenna arrays or systems
- H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
- H01Q21/061—Two dimensional planar arrays
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Abstract
The invention belongs to the technical field of polarized reconfigurable conformal array antennas, and provides a multi-polarized reconfigurable conformal array antenna based on unmanned aerial vehicle communication. The polarized reconfigurable conformal array antenna comprises a microstrip patch antenna and a reconfigurable feed network; firstly, a miniaturized, high-efficiency and polarization-reconfigurable radiation element is designed, which is characterized in that a short-circuit needle is loaded in the center of the element to simplify the structure, and 4 grooves are formed at the corner of a patch to realize the miniaturization of the size. A reconfigurable feed network based on 4 PIN diodes is designed on the back of the circular radiation patch, and the element can flexibly switch the polarization state between two orthogonal linear polarizations and left-hand circular polarization and right-hand circular polarization modes although only four diodes and two bias lines are arranged. In addition, on the basis of the polarized reconfigurable antenna, a conformal sparse array is designed, and the gain, coverage area and directional flexibility of the unmanned aerial vehicle communication system are improved. The conformal array further improves the gain of the whole antenna system besides meeting the performance of being conformal with the unmanned aerial vehicle body, has a wide-angle beam scanning range, and meanwhile, multiple polarizations of the antenna are beneficial to reducing multipath interference, so that the channel capacity and the signal quality are improved.
Description
Technical Field
The invention belongs to the technical field of polarized reconfigurable conformal array antennas, and particularly relates to a multi-polarized reconfigurable conformal array antenna based on unmanned aerial vehicle communication.
Background
As the modern wireless communication system is used in various complex and changeable environments, various performance requirements on the wireless communication system are more and more strict, and the system is widely applied to the wireless communication system aiming at various application requirements of mountain close forest scenes, such as forest safety monitoring, forest disaster rescue, unmanned aerial vehicles because the unmanned aerial vehicles are not limited by space and topography, and has the advantages of strong effectiveness, good maneuverability, wide inspection range and the like;
Firstly, an air-to-ground communication antenna system based on an unmanned aerial vehicle must have the working characteristics which meet the operation of the unmanned aerial vehicle, and an antenna system suitable for the pneumatic characteristics of the unmanned aerial vehicle must meet the requirements of small size and light weight; secondly, in order to minimize the fading loss, multipath reflection and co-channel interference of air-to-ground wireless communication, the antenna diversity technology has been a research hotspot as a method for improving the channel capacity and the signal quality; the polarization reconfigurable antenna can switch corresponding polarization modes according to the requirements of a wireless application real-time environment and communication requirements; polarization diversity and frequency diversity are realized, and the channel capacity is improved; in addition, the multi-polarization avoids the requirement of accurate alignment required by a single polarization system, and is also beneficial to reducing signal loss caused by multipath reflection and polarization mismatch in a complex propagation environment and improving the quality of communication.
With the development of polarization reconfigurable antenna technology, three technologies for realizing polarization reconfiguration are mainly used at present:
One is to add disturbance on the radiation patch, reconstruct the current distribution of the radiation antenna by using the on-off of switches such as PIN diode, MEMS and the like to change the polarization state of the antenna; however, introducing disturbances may lead to instability in antenna performance, making precise control and stability of multi-polarization performance more difficult;
One is to integrate multiple antenna elements in an antenna structure to achieve different polarization states by adjusting the drive current or phase of each element; there are some potential disadvantages to this approach: for example, multiple antenna elements can lead to more complex systems, increased power consumption, and mutual interference between antenna elements;
Still another is to reconstruct the excitation by a feed network or phase shifter, with different current paths to achieve different polarizations; however, as the number of the pin tubes is large, the antenna efficiency is low, which is unfavorable for the efficient power management of the unmanned aerial vehicle; since there is typically a higher path loss in air-to-ground communications, the gain of the antenna is one aspect that needs to be considered with great importance; the gain of a single antenna element is often limited, and a very low gain can lead to reduced signal reception quality, reduced communication distance, and reduced signal directivity; to overcome the high path loss of air-to-ground communications, assembling antennas into high gain arrays is a simple and effective solution;
Therefore, in order to meet the performance requirements of multiple polarizations, high directivity, high gain and wide scan angle, it is highly desirable to design a conformal array antenna system with multiple polarization modes suitable for the cylindrical fuselage of a fixed-wing unmanned aerial vehicle.
Disclosure of Invention
The invention aims to provide a multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication, which aims at the problems that the conventional unmanned aerial vehicle antenna system is high in profile, low in gain and monotonous in polarization, the aerodynamic characteristics of an unmanned aerial vehicle can be influenced by a higher profile, the signal quality of a receiving end is poor due to the lower gain, the antenna array capable of conforming to an unmanned aerial vehicle body is designed, the gain of the whole antenna system is further improved by the formed array besides the performance of conforming to the unmanned aerial vehicle body, the beam scanning range of a large angle is wide, meanwhile, the multipath interference is reduced due to multiple polarizations of the antenna, and the improvement of the channel capacity and the signal quality is ensured.
The technical scheme adopted by the invention is as follows:
A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication comprises a microstrip patch antenna and a reconfigurable feed network.
The microstrip patch antenna is adhered to a reconfigurable feed network to form an antenna unit with four polarizations, wherein the length, width and height of the unit are 100mm multiplied by 5.8mm; a nine-split phase-shifting coupler is composed of microstrip lines, and the material of the medium substrate is F4BM220.
The microstrip patch antenna and the reconfigurable feed network are both combined by a design method, and the design method comprises the following steps:
Step S1: the microstrip patch antenna is designed, and specifically comprises the following steps:
Step S1.1: designing a circular radiation patch with a radius of r p1, and etching four rectangular gaps with a length of l r1 and a width of w r1 around the circular radiation patch to realize miniaturization of the whole antenna unit;
Wherein r p1 is 34mm; the length l r1 and the width w r1 of the rectangular gap are 14mm and 6mm respectively;
Step S1.2: loading a square medium substrate with a side length L and a thickness h 1 below the circular radiation patch, so that the edge of the square medium substrate keeps one tenth of free space wavelength from the edge of the circular radiation patch, and radiation energy is prevented from excessively leaking to the back surface of the medium substrate;
Wherein L is 100mm, and h 1 mm; the dielectric substrate was type F4BM220 having a dielectric constant of 2.2 and a loss tangent of 0.0009; one tenth of the free space wavelength refers to the wavelength of the electromagnetic wave corresponding in free space when the antenna resonates at the center frequency;
Step S1.3: a copper film with the thickness of 1 ounce is coated on the other surface of the dielectric substrate without the circular radiation patch to serve as a grounding plate, and the grounding plate, the dielectric and the circular radiation patch form a complete microstrip patch antenna;
Step S1.4: loading a metal short-circuit needle with the radius of r f and the length of L 2 at the position of the circle center of the circular radiation patch corresponding to the grounding plate so as to realize miniaturization of the antenna and provide grounding of direct current bias; loading two metal needles with radius r f and length L 3 at the diagonal position without gaps of the circular radiation patch and the position with distance r i1 from the center of the circle so as to provide input of alternating current signals;
Wherein r i1 and r f are 0.6mm and 9mm, respectively, and L 2 and L 3 are 5mm and 5.8mm, respectively;
S2, designing a reconfigurable feed network, which specifically comprises the following steps:
S2.1, loading a dielectric substrate with the side length L and the thickness H2 on the other surface of the grounding plate loaded in the step S1 as a dielectric substrate of a reconfigurable feed network;
the medium substrate is F4BM220 with thickness H2 of 0.8mm;
step S2: designing a circuit of a reconfigurable feed network on the other side of the dielectric substrate;
Step S2.1: one end of the microstrip line TL1 with characteristic impedance Z 1 is connected with two PIN tubes D1 and D2; ensuring that the path of an alternating current signal is changed by controlling the on-off of the PIN tube; a direct current blocking capacitor with a capacitance value of 50nF is loaded at a position, close to an input end, of the microstrip line TL1, so that a radio frequency signal is prevented from being influenced by direct current, a direct current bias line is introduced between the capacitor and a PIN diode by using an inductor with an inductance value of 1nH, the voltage of the negative electrode of the positive electrode D2 of the D1 is changed, and the input end of the direct current blocking capacitor is P v1;
One end of the TL1, which is not connected with the PIN tube, is used as an input end P1 of the alternating current signal of the whole reconfigurable feed network; z 1 is 50 ohms, and the width of the microstrip line is 3.54mm; the type of the PIN pipe is BAR64-02V;
step S2.2: the other ends of the D1 and the D2 are respectively connected with microstrip lines TL2 and TL2', so that impedance matching is realized when only one of the D1 or the D2 is conducted, and energy is not reflected;
Wherein TL2 and TL2' are microstrip lines with characteristic impedance Z 1 and length of quarter wavelength;
Step S2.3: two impedance transformation lines TL3 and TL3 'are connected at the other ends a1 and a1' of the microstrip lines TL2 and TL2', so that the impedance Z a1 and Z a2 at the a1 and a1' can be transformed to realize impedance matching;
wherein the TL3, TL3' has a characteristic impedance Z 2 and an impedance transformation line of quarter wavelength length; the size of Z 2 is:
Step S2.4: connecting two microstrip lines TL3, TL3' with characteristic impedance Z 1 and length of eighth wavelength between the a1 and a1', and loading a third PIN tube D3 between the TL3 and the TL3 '; so as to change the working mode of the reconfigurable feed network by controlling the on-off state of the D3;
Step S2.5: repeating the step S2.4 between the other ends b1, b1' of the two impedance transformation lines TL3, TL3', loading the microstrip lines TL4, TL4' and loading the PIN tube D4 therebetween; so as to change the working mode of the reconfigurable feed network by controlling the on-off state of the PIN tube D4 and the D3; introducing a direct current bias line into the middle part of the TL4 by using an inductor with the size of 1nH, wherein the input end of the direct current bias line is P v2, and the inductor isolates radio frequency signals;
Step S2.6: two microstrip lines with the same length and characteristic impedance Z 1 are connected at the positions b1 and b1' and serve as output ends P2 and P3 of the reconfigurable feed network; the P2 and the P3 are connected with two metal feed pins of the microstrip patch antenna to ensure the transmission of signals between the reconfigurable feed network and the circular radiation patch;
Step S2.7: loading a patch capacitor at the microstrip line TL6, wherein the capacitance is 50nF, and the patch capacitor plays a role in switching on an alternating current signal and isolating a direct current signal;
Step S3: the dual-port feeding microstrip patch antenna grounding plate and the reconfigurable feed network are adhered together to form a four-polarization reconfigurable antenna unit, so that two output ports of the reconfigurable feed network are connected with two input ports of the microstrip patch antenna, and the input of radio frequency signals is ensured;
Step S4: a four-polarization reconfigurable conformal array antenna for unmanned aerial vehicle communication is designed, which comprises the following steps:
Step S4.1: forming a 9-element curved square matrix by the 9 quadrupolar reconfigurable antenna units in the step S3 according to a curved surface mode, wherein the radius of a corresponding cylinder of the curved surface is r c, the distances between the antenna units and adjacent antennas along the directions of an axis and the circumference are d 1 and d 2 respectively, and the beam scanning range of the array is increased when the mutual coupling between the antenna units in the array is low;
Wherein r c is 500mm, d 1 and d 2 are 120mm and 104mm, respectively.
Step S4.2: and uniformly arranging 3 9-element curved surface arrays in the step S4.1 in a mode of rotating 60 degrees along the circumference, so that the 180-degree beam coverage area on one surface of the cylinder is realized.
The invention has the technical effects that:
compared with the conventional polarized reconfigurable antenna, the multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication has the advantages of small volume, multiple polarization modes and high efficiency against multipath influence.
Compared with other multi-polarization microstrip antennas, the multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication has the advantage that a large number of PIN tubes and aggregation elements can cause the loss of the antenna to be increased. The metal short-circuit needle is placed at the center of the circular radiation patch in an innovative manner, the complexity of the offset network structure is reduced under the condition that the radiation performance of various polarizations is not affected, and the efficiency of the antenna is improved.
According to the multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication, the reconfigurable feed network in the method is considered to be complex in structure based on the reconfigurable feed network at present, and the reconfigurable feed network branches can be multiplexed under four polarizations in the design, so that the antenna has the advantages of being low in cost and easy to manufacture.
According to the multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication, 9 polarization reconfigurable units are formed into a 9-element array conformal with a cylindrical surface, and the gain of the antenna is improved, so that the communication quality of signals is improved. Meanwhile, the whole antenna system has the beam scanning capability, and the beam scanning area can be changed in real time. And because of adopting conformal structure, can reduce the influence to the aerodynamic properties of unmanned aerial vehicle flight to a great extent. In order to further improve the coverage of the beam, the 9-element square matrix is uniformly arranged on the cylindrical surface in a sparse mode, so that a larger beam scanning range is realized. Therefore, the four-polarization reconfigurable conformal array antenna for unmanned aerial vehicle communication has a very large application prospect in the field of emergency rescue communication.
Drawings
Fig. 1 is a block diagram of a polarized reconfigurable antenna element;
FIG. 2 microstrip patch antenna scattering parameters;
Fig. 3 is a schematic diagram of a reconfigurable feed network circuit;
FIG. 4 is a PIN diode equivalent circuit diagram;
fig. 5 is a circuit diagram of the reconfigurable feed network operating in four states;
fig. 6 is an equivalent circuit diagram of a reconfigurable feed network in state 1;
FIG. 7 is a diagram of simulated scattering parameters of the reconfigurable feed network in state 1;
Fig. 8 is an equivalent circuit diagram of the reconfigurable feed network in state 3;
FIG. 9 is a graph of simulated scattering parameters versus phase for the reconfigurable feed network in state 3;
FIG. 10 is a graph of the reflection coefficient of a polarized reconfigurable antenna element operating in the-45 LP mode;
FIG. 11 is a graph of the reflection coefficient of a polarized reconfigurable antenna element operating in the +45° LP mode;
FIG. 12 is a graph of the reflection coefficient of a polarized reconfigurable antenna element operating in RHCP mode;
FIG. 13 is a graph of the reflection coefficient of a polarized reconfigurable antenna element operating in LHCP mode;
fig. 14 is a gain diagram of a polarization reconfigurable antenna element operating in two linear polarization modes;
fig. 15 is a graph of gain versus axial ratio for a polarization reconfigurable antenna element operating in two circular polarization modes;
Fig. 16 radiation pattern of the E-plane of the polarized reconfigurable antenna element operating in-45 LP mode;
Fig. 17 is a radiation pattern of the H-plane of the polarized reconfigurable antenna element operating in the-45 LP mode;
FIG. 18 is a simulation model of a cylindrical based conformal sparse array;
FIG. 19 is a schematic diagram of the phase relationship required to calculate array elements;
the conformal subarray of fig. 20 operates in an impedance profile of-45 LP mode;
the impedance profile of the conformal subarray of fig. 21 operating in RHCP mode;
FIG. 22 is a gain plot for three scan angles for the conformal subarray operating in the-45 LP mode;
FIG. 23 gain vs. axial ratio graphs for three scan angles for a conformal subarray operating in RHCP mode;
The conformal subarray of fig. 24 operates in RHCP mode E-plane radiation pattern;
FIG. 25 conformal subarray operating in RHCP mode H-plane radiation pattern;
FIG. 26 is a flow chart of a design method of the present invention.
In the drawings, the list of components represented by the various numbers is as follows:
1. A reconfigurable feed network; 2. a ground plate; 3. a dielectric substrate; 4. a circular radiating patch; 5. a metal shorting pin; 6. a metal feed pin.
Detailed Description
The present invention will be specifically described with reference to examples below in order to make the objects and advantages of the present invention more apparent. It should be understood that the following text is intended to describe only one or more specific embodiments of the invention and does not limit the scope of the invention strictly as claimed.
The four-polarization reconfigurable conformal array antenna for unmanned aerial vehicle communication comprises a miniaturized microstrip patch antenna, a feed reconfigurable circuit and a conformal array.
Embodiment one:
Referring to fig. 1-26, the present embodiment designs a miniaturized microstrip patch antenna, and the design method of the microstrip patch antenna corresponds to step S1 of the invention, as shown in fig. 26, and includes a circular radiating patch 4, a dielectric substrate 3, a metal shorting pin 5 and a ground plate 2, and the specific structure of the antenna is shown in fig. 1, a miniaturized circular radiating patch with radius r p1 and made of metal is designed on a F4BM220 dielectric substrate 3 with a thickness h 1 having a relatively low dielectric constant, the contact plane is printed on the back of the same dielectric substrate 3, and four rectangular slots with size l r1×wr1 are symmetrically cut to lengthen the current path for reducing the size for the proposed heat sink.
In order to achieve four polarization reconstruction and increase the axial ratio bandwidth of the CP mode, the antenna is excited with two feed ports P1 and P2 according to the relationship between amplitude and phase of the signal determined by the polarization reconfigurable network. For either polarization mode, the total radiation field is the vector superposition of the two orthogonal electric fields independently generated by ports P1 and P2 in FIG. 1.
Since the circular radiating patch operates in TM11 mode in both orthogonal fields, the electric field strength in the center of the patch is zero. Therefore, the metal shorting pin 5 loaded in the center of the circle has little influence on the radiation fields of all the reconfigurable polarizations, which can greatly simplify the design of the direct current bias circuit.
Loading a metal short-circuit needle 5 with the radius of r f and the length of L 2 at the position corresponding to the position of the circle center of the circular radiation patch 4 and the grounding plate 2; and loading two metal needles with radius r f and length L 3 at the diagonal position without gaps of the circular radiation patch 4 and the position with distance r i1 from the center of the circle so as to provide input of alternating current signals;
Wherein r i1 and r f are 0.6mm and 9mm, respectively, and L 2 and L 3 are 5mm and 5.8mm, respectively.
FIG. 2 is a graph of simulated scattering parameters of a radiating element when independently excited by port 1; microstrip patch antennas have a-10 dB impedance bandwidth of about 40MHz at a frequency of 1.5GHz and a port isolation of greater than 30dB over the operating band; in addition, the short pins have little effect on the antenna S11, while the loading of four rectangular slots effectively reduces the circular radiating patch size by 10%.
The working procedure of this case is as follows: when one of the two feed ports works independently, the microstrip patch antenna works in a linear polarization mode, and when the two feed ports input signals simultaneously, the amplitudes of the signals are equal and the phases are different by 90 degrees, the microstrip patch antenna works in a circular polarization mode.
Embodiment two:
In this embodiment, a reconfigurable feed network 1 for a microstrip patch antenna operating in four polarization modes is designed, and the microstrip patch antenna and the reconfigurable feed network 1 are combined into a four-polarization reconfigurable antenna unit, where the design method corresponds to step S2 of the summary of the invention, and the reconfigurable feed network 1 includes a radio frequency network and a dc offset network, and the specific layout thereof is shown in fig. 3.
The reconfigurable feed network 1 is mainly composed of two parts, namely a direct current bias circuit with two input ports (namely P v1 and P v2) and a 3-port radio frequency network (with input ports Pin and output ports P o1 and P o2), four types of BAR64-02VPIN diodes (namely D1, D2, D3 and D4) are integrated as switches, the equivalent circuit model of the OFF and ON states is shown in figure 4, the direct current bias circuit is composed of two microstrip lines with the width of w 3 (namely TL V1 and TL V2) and a series of lumped elements, the two microstrip lines comprise two 50-pF capacitors and two 1-nH inductors for DC and RF isolation, the PIN diodes are turned ON or OFF by controlling voltages V1 and V2, and the reconfigurable feed network 1 can work in four reconfigurable states as shown in figure 5.
When the PIN diode D1 is turned on and the reconfigurable feed network 1 is turned off and D2 to D4 are operated in state 1, the equivalent circuit model is shown in fig. 6, and when the radio frequency signal flows from the input port P in to the output port P o1, the equivalent circuit is composed of four transmission lines TL2, TL3, TL5, TL6 with characteristic impedance Z 50 (or 50Ω) and one transmission line TL4 with characteristic impedance Z 35.36 (or 35.36Ω), and considering that the lengths of the open parallel branches TL3 and TL5 are 1/8 of the conduction wavelength and the lengths of the serial branch TL4 are 1/4 of the conduction wavelength, the input impedances Z b and Z a2 at the nodes b and a can be calculated as:
The input impedance Z a1 at node b may be further derived as:
Obviously, with impedance matching at input port P in, fig. 6 shows simulated scattering parameters for reconfigurable feed network 1 operating in states 1 and 3, port P in、Po1、Po2 being labeled 1, 2, 3, respectively. As shown in fig. 7, at a frequency around 1.5GHz, the reflection coefficient S11 of both states is smaller than-15 dB, for the operating state 1, in the frequency range of 1.45 to 1.55GHz, the transmission coefficient S 21 is above-0.95 dB, and S 31 is lower than-15 dB in the corresponding frequency band.
When PIN diodes D1, D3 and D4 are on and D2 is off, reconfigurable feed network 1 operates in state 3, the RF signal fed from port P in flows into ports P o1 and P o2, the equivalent circuit of which is shown in fig. 8, with diode D2 off, transmission line TL2' becomes an open quarter-wavelength line; according to microstrip line transmission theory, node e acts as a virtual ground, resulting in lines TL3 and TL4' being short-ended quarter-wavelength lines.
At the same time, virtual open conditions are realized on node a and node c for lines TL3 and TL4', respectively, so that the reconfigurable feed network 1 resembles a T-junction 3db power divider, as shown in fig. 8; the branch TL4 serves as a quarter-wavelength impedance transformer, and ensures that impedance at the node a or the input end P in is well matched.
In addition, since the length of branch TL5 is one quarter of a guide wavelength, the output signals of ports P o1 and P o2 are 90 ° out of phase; when the PIN diode D2 is turned on and the PIN diodes D1, D3 and D4 are turned off, the reconfigurable feed network 1 works in a state 2; when the PIN diodes D2, D3 and D4 are on, D1 is off, and the reconfigurable feed network 1 works in a state 4; due to the symmetry of the circuit, the reconfigurable feed network 1 will operate in states 2 and 4, respectively, exhibiting similar performance as states 1 and 3.
As can be seen from fig. 9, at frequencies around 1.5GHz, the transmission coefficients S 21 and S 31 for state 3 are about 3.3dB and-3.6 dB, respectively; furthermore, the phase difference of the P o1 and P o2 port output signals is about 90 ° in the operating band.
The grounding plate 2 of the microstrip patch antenna is adhered to the reconfigurable feed network 1 through an adhesion technology, and when in adhesion, two output ports of the reconfigurable feed network 1 are required to be connected with two input ports of the microstrip patch antenna, so that radio frequency signals can be output; due to the structural symmetry of the reconfigurable feed network 1 and the antenna, the reflection coefficients of two orthogonal LP or CP modes are very similar.
And two output ports P2 and P3 of the reconfigurable feed network are respectively connected with two feed ports of the circular radiation patch through a metal feed pin 6 with the radius of r f.
As shown in FIG. 10 and FIG. 11, in both LP modes of operation, the measured impedance bandwidth for S11 is less than-10 dB at approximately 55MHz (i.e., 1.475-1.53 GHz), which is 5MHz wider than the simulation results.
On the other hand, as can be seen from fig. 12 and 13, the impedance bandwidth of the antenna in both CP modes is 75MHz (i.e., 1.465-1.54 GHz) and is also 5MHz wider than the analog bandwidth (i.e., 1.47-1.54 GHz).
As shown in fig. 14 and 15, the antenna unit operates in four polarization states, the gain is greater than 6dBi, in addition, fig. 15 shows that the bandwidth of the 3db axial ratio of the circular polarization is about 1.485 to 1.505GHz (about 1.3%), since the two linear polarizations have similarities with the radiation patterns of the two circular polarizations, fig. 16 and 17 show the simulated and measured radiation patterns of the linear polarization at 1.49GHz, respectively, and the half power beam widths of the e-plane and h-plane of the antenna are-35 ° to 35 ° in the LP mode, which is beneficial for forming a conformal array antenna of the wide beam antenna, and reducing the scanning loss.
Embodiment III:
In the four-polarization reconfigurable conformal array antenna for unmanned aerial vehicle communication, as shown in fig. 18, the proposed conformal sparse array is attached to the surface of a cylinder with a radius of r c, wherein 9 radiating units form a 3×3 conformal subarray, three nine-element conformal subarrays are uniformly arranged at intervals at the bottom of the cylinder for sparse design, subarrays with three angular intervals of 60 degrees are arranged, a wide scanning range of 180 degrees×50 degrees can be obtained through electromagnetic simulation and optimization, and the whole conformal array enables the coverage area of space-to-ground communication based on unmanned aerial vehicles to be relatively large.
For each conformal subarray, the phase relation required by all the radiating elements needs to be calculated, as shown in fig. 19, a global coordinate system is established by taking the center of the cylinder as the origin, and the parameter equation of the radiating element position can be described as follows:
Where r c is the cylinder radius, t n and θ n are the axial and angular positions of the nth radiating element, respectively, and thus the position vector of the radiating element can be expressed as:
OOn＝(tn,rc sinθn,rc cosθn)
On the other hand, the position vector of any far-field point P (θ, Φ) in the spherical coordinate system is expressed as:
dn＝OOn.rop
thus, the phase compensation required for the nth radiating element is:
Δθn＝-2πdn/λ
Through simulation software HFSS and experimental tests, the radiation performance of the reconfigurable conformal subarray is confirmed; to facilitate measurement, we use three phase shift networks to change the beam scan angle of the array; the simulated reflectance of a conformal subarray mated with three 9-way phase shifting couplers was first calculated using high frequency structure simulator software (HFSS) and Advanced Design Systems (ADS).
The specific method comprises the following steps:
Firstly, acquiring all scattering parameters of a conformal array and a phase shift network through an HFSS, and then modeling and simulating a combined network in an ADS;
as shown in FIG. 20, the measurement result shows that in the-45 DEG LP mode, the actual measured S11< -10dB operating bandwidth is about 125MHz (i.e., 1.45-1.575 GHz), which is slightly wider than the simulation result;
also, as can be seen from FIG. 21, in RHCP mode, the measured bandwidth of S11< -10dB is about 125MHz (i.e., 1.45-1.575 GHz), and the simulation result is the same as that of LP mode;
fig. 22 shows the peak gains at beam steering angles (0 °, 25 °), (0 ° ) and (90 °, 30 °) for the-45 ° LP mode of the antenna sub-o, respectively, of about 13.8dBi, 14dBi and 13.7dBi;
As can be seen from fig. 23, at beam steering angles of (0 °, 25 °), (0 ° ) and (90 °,30 °), peak gains of RHLP modes are 14.1, 14.8 and 14.2dBi, respectively;
In addition, at two beam steering angles, the bandwidth of the actually measured 3dbAR is 1.485-1.505 GHz (about 1.3%), and is shifted to the left by 5MHz than the simulation result (1.49-1.51 GHz);
FIGS. 24 and 25 show normalized measured and simulated radiation patterns of RHCP at 1.49GHz for a polarization reconfigurable conformal array, with beam steering (0, 25,), (0,) and (90, 30) directions clearly seen; in addition, the cross polarization level of the E surface and the H surface is lower than-15 dB; on both principal planes, the cross polarization of the RHCP mode in three directions is less than-18 dB; in addition, the half power lobe width of the conformal array is around 30 ° in both principal planes.
The foregoing is merely a preferred embodiment of the present invention and it should be noted that modifications and adaptations to those skilled in the art may be made without departing from the principles of the present invention, which are intended to be comprehended within the scope of the present invention. Structures, devices and methods of operation not specifically described and illustrated herein, unless otherwise indicated and limited, are implemented according to conventional means in the art.
Claims (10)
1. Multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication, its characterized in that: the antenna comprises a microstrip patch antenna, a reconfigurable feed network (1), a four-polarization reconfigurable microstrip antenna and a four-polarization reconfigurable conformal array antenna, wherein the microstrip patch antenna, the reconfigurable feed network (1), the four-polarization reconfigurable microstrip antenna and the four-polarization reconfigurable conformal array antenna are all arranged by the following steps:
Step S1: the microstrip patch antenna is arranged, and the method comprises the following steps:
Step S1.1: designing a circular radiation patch (4) with a radius of r p1, and etching four rectangular gaps with a length of l r1 and a width of w r1 around the circular radiation patch (4); wherein r p1 is 34mm; the length l r1 and the width w r1 of the rectangular gap are respectively 14mm and 6mm;
Step S1.2: loading a square dielectric substrate (3) with the side length L and the thickness h 1 below the circular radiation patch (4), and keeping the edge of the square dielectric substrate (3) at one tenth of free space wavelength from the edge of the circular radiation patch (4);
Wherein L is 100mm, and h 1 mm; the model of the dielectric substrate (3) was F4BM220, the dielectric constant thereof was 2.2, and the loss tangent thereof was 0.0009; one tenth of the free space wavelength refers to the wavelength of the electromagnetic wave corresponding in free space when the antenna resonates at the center frequency;
step S1.3: a copper film with the thickness of 1 ounce is coated on the other surface of the dielectric substrate (3) without the circular radiation patch (4) to serve as a grounding plate (2), and the grounding plate (2), the dielectric and the circular radiation patch (4) form a complete microstrip patch antenna;
Step S1.4: loading a metal short-circuit needle (5) with the radius r f and the length L 2 at the position corresponding to the center of the circular radiation patch (4) and the grounding plate (2); loading two metal needles with the radius r f and the length L 3 at the position of the diagonal line position without a gap of the circular radiation patch (4) from the circle center distance r i1 so as to provide input of alternating current signals;
Wherein r i1 and r f are 0.6mm, and L 2 and L 3 are 5mm and 5.8mm respectively;
step S2: a circuit of a reconfigurable feed network (1) is designed on the other side of the dielectric substrate (3), and comprises the following steps:
Step S2.1: one end of the microstrip line TL1 with characteristic impedance Z 1 is connected with two PIN tubes D1 and D2; the path of the alternating current signal is changed by controlling the on-off of the PIN tube; loading a direct current blocking capacitor with a capacitance value of 50nF at a position, close to an input end, of the microstrip line TL1, introducing a direct current bias line between the capacitor and a PIN diode by using an inductor with an inductance value of 1nH, and connecting the inductor with a direct current bias line TL V1 with a width of w 3 to change the voltage of the positive electrode of D1 and the negative electrode of D2;
One end of the TL1, which is not connected with the PIN tube, is used as an input end P1 of the alternating current signal of the whole reconfigurable feed network; z 1 is 50 ohms, and the width of the microstrip line is 3.54mm;
step S2.2: the other ends of the D1 and the D2 are respectively connected with microstrip lines TL2 and TL2', so that impedance matching is realized when only one of the D1 or the D2 is conducted, and energy is not reflected;
step S2.3: two impedance transformation lines TL3 and TL3 'are connected at one ends a1 and a1' of the microstrip lines TL2 and TL2', so that the impedance Z a1 and Z a2 at the a1 and a1' can be transformed to realize impedance matching;
Wherein the TL3, TL3' has a characteristic impedance Z 2 and an impedance transformation line of quarter wavelength length; the size of Z 2 is as follows:
Step S2.4: connecting two microstrip lines TL3, TL3' with characteristic impedance Z 1 and length of eighth wavelength between the a1 and a1', and loading a third PIN tube D3 between the TL3 and the TL3 '; so as to change the working mode of the reconfigurable feed network by controlling the on-off state of the D3;
Step S2.5: repeating the step S2.4 between the other ends b1, b1' of the two impedance transformation lines TL3, TL3', loading the microstrip lines TL4, TL4' and loading the PIN tube D4 therebetween; so as to change the working mode of the reconfigurable feed network by controlling the on-off state of the PIN tube D4 and the D3; a direct current bias line is led in the middle of the TL4 by using an inductor with the size of 1nH, and the input end of the direct current bias line is P v2;
Step S2.6: two microstrip lines with the same length and characteristic impedance Z 1 are connected at the positions b1 and b1' to serve as output ends P2 and P3 of the reconfigurable feed network (1); the P2 and the P3 are connected with two feed metal pins (6) of the microstrip patch antenna to ensure the transmission of signals between the reconfigurable feed network (1) and the circular radiation patch (4);
Step S2.7: loading a patch capacitor at the microstrip line TL6, wherein the capacitance is 50nF;
Step S3: the grounding plate (2) of the dual-port feed microstrip patch antenna and the reconfigurable feed network are adhered together to form a four-polarization reconfigurable antenna unit, so that two output ports of the reconfigurable feed network (1) are connected with two input ports of the microstrip patch antenna, and the input of radio frequency signals is ensured;
step S4: a four-polarization reconfigurable conformal array antenna for unmanned aerial vehicle communication, comprising the steps of:
Step S4.1: forming a 9-element curved surface square matrix by the 9 four-polarization reconfigurable antenna units in the step S3 according to a curved surface mode, wherein the radius of a corresponding cylinder of the curved surface is r c, and the distances between the antenna units and adjacent antennas along the axial line and the circumferential direction are d 1 and d 2 respectively;
Step S4.2: and uniformly arranging 3 9-element curved surface arrays in the step S4.1 in a mode of rotating 60 degrees along the circumference, so that the 180-degree beam coverage area on one surface of the cylinder is realized.
2. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: the dielectric substrate (3) of the circular radiation patch (4) in the step S1.1 is a substrate made of F4BM220 and having a thickness h 1, and the substrate includes three metallized through holes, and the positions of the three through holes correspond to two feed ports and a center of a circle of the circular radiation patch (4) respectively.
3. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: in the step S2.1, the positive and negative directions of two PIN diodes connected to one end of the microstrip line TL1 with the characteristic impedance Z 1 are identical, one positive electrode of the PIN diode D1 is connected to TL1, and the other negative electrode of the PIN diode D2 is connected to TL 1.
4. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: TL2 and TL2' in step 2.2 are microstrip lines with characteristic impedance Z 1 and length of quarter wavelength.
5. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: the other ends of TL2 and TL2 'in the step S2.3 are connected to the impedance transformers TL4 and TL4' with the length of one quarter wavelength, and the impedance thereof is Z 2.
6. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: in the step S2.5, the middle position of TL4 is connected to a dc bias line TL V2 with a width of w 3 by a 1nH inductor.
7. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: in the step S2.5, two ends of TL4 and TL4' are respectively connected with two sections of microstrip lines TL3 and TL5 with a length of one quarter wavelength and an impedance of Z 1, and two PIN diodes D2 and D3 are loaded in the middle of the microstrip lines, and the positive and negative poles of the two PIN diodes are identical.
8. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: in the step S2.6, two output ports P2 and P3 of the reconfigurable feed network (1) are respectively connected with two feed ports of the circular radiation patch (4) through a metal feed pin with the radius of r f.
9. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: the r c in the step S4.1 is 500mm, and the d 1 and d 2 are 120mm and 104mm respectively.
10. A multi-polarization reconfigurable conformal array antenna based on unmanned aerial vehicle communication according to claim 1, wherein: the 9-element curved surface arrays in the step S4.2 are uniformly arranged with 3 9-element curved surface arrays in a mode of rotating 60 degrees along the circumference.
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