CN117013831A - Hybrid ISOP-based wide input voltage range DC-DC converter and voltage regulating method - Google Patents
Hybrid ISOP-based wide input voltage range DC-DC converter and voltage regulating method Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/01—Resonant DC/DC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33573—Full-bridge at primary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
- H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
- H02M5/10—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using transformers
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
- H02M7/068—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode mounted on a transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
- H02M7/08—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode arranged for operation in parallel
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
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- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention provides a mixed ISOP-based wide input voltage range DC-DC converter and a voltage regulating method, and relates to the field of medium-high voltage direct current distribution DC-DC converters. The multi-resonant converter comprises a plurality of submodules, wherein each submodule comprises an LLC-DCX converter and k multi-resonant converters, k is more than or equal to 2, the input sides of the submodules are connected in series, and the output sides of the submodules are connected in parallel. The invention adopts a hybrid ISOP structure, and the LLC module is replaced by a multi-resonant converter module, so that when the input voltage range is wide, the converter can be switched into a D2D converter in real time, and the wide voltage gain is ensured; when the input voltage range is narrow, the switching to the DCX converter and the LLC-DCX part can improve the working efficiency. The invention solves the problems of high loss, low efficiency, wide switching frequency range, poor light load voltage regulation capability and the like of the traditional LLC as a single DC-DC module under the application scene of high input voltage and wide voltage range.
Description
Technical Field
The invention relates to the field of medium-high voltage direct current distribution DC-DC converters, in particular to a mixed ISOP-based wide input voltage range DC-DC converter and a voltage regulating method, wherein the converter is of a mixed converter topological structure formed by compounding a multi-resonant converter and LLC-DCX.
Background
With the continuous progress of new energy technology, energy storage technology and modern power electronic technology, the demand for energy conversion systems is also increasing, and in order to cope with the problems of energy crisis, environmental pollution and the like, renewable energy sources represented by solar energy, wind energy and the like are gradually the focus of development and utilization in recent years, and distributed power sources such as photovoltaic power sources, fuel cells and the like generate power in the form of direct current, so that when the direct current power distribution network is connected, a DC/DC converter is unavoidable. However, the new energy power generation mode represented by photovoltaic power generation is susceptible to the influence of factors such as environment, so that the output is unstable, and the output voltage of the photovoltaic module often fluctuates in a certain range due to the change of illumination intensity and temperature. Meanwhile, the urban rail transit power supply voltage is also increased from 600VDC and 750VDC to 1500VDC in the early stage, and the increase of the power grid voltage also puts higher demands on the voltage level of the auxiliary power supply DC-DC converter. In the field of on-board power systems, it is also desirable for the power supply to have a wide input voltage range and a good step response to meet wide-range fluctuations in input voltage caused by variations in aircraft engine speed. Therefore, the wide input range DC/DC converter has important significance in applications with larger input voltage variation ranges, such as new energy power generation, on-board power supply, on-board charger, and the like, and research and development of the wide input voltage range DC/DC converter has become one of hot spots in the power electronics field.
Under the application scene that input voltage range is wider, traditional LLC resonant converter receives the influence of own gain characteristic, can realize low output voltage under very high switching frequency, and when the gain range was wider, switching frequency range also can be wider, and this is unfavorable for the design of magnetic element, can increase the loss to single module voltage regulation ability is not enough. It is therefore proposed to use a plurality of submodules with lower input voltages in series, with the output sides of the submodules connected in parallel, whereas for submodules in an ISOP (input series, output parallel) combined structure, two general categories are known: one type is a phase-shifting double active full bridge converter (DAB), and the other type is a resonant converter, such as a Series Resonant Converter (SRC), an LLC converter, a CLLLC converter, etc. The ISOP converter taking DAB as the submodule can realize zero-voltage on, but has large current and larger turn-off loss when turned off, limits the development of the ISOP converter in high-frequency occasions, takes the LLC converter as the submodule, can realize ZVS (full name Zero Voltage Switch, zero-voltage on) and ZCS (full name Zero Current Switch, zero-current on) at the same time, has higher efficiency compared with DAB, and has simple and flexible control, can adopt frequency control and phase-shifting control, but is only suitable for the working condition of voltage ratio fixation.
Based on the foregoing, there is therefore a need to retrofit existing converters or to design new converters to meet operating conditions.
Disclosure of Invention
The invention provides a DC-DC converter with a wide input voltage range and a voltage regulating method based on a mixed ISOP, which aims to solve the problem that a traditional single LLC resonant converter is difficult to simultaneously compatible with wide voltage gain and high efficiency.
The invention is realized by the following technical scheme: a wide input voltage range DC-DC converter based on a hybrid ISOP comprises a plurality of submodules, namely an LLC-DCX converter and k multi-resonant converters, wherein k is more than or equal to 2, the input sides of the submodules are connected in series, and the output sides of the submodules are connected in parallel.
The circuit structures of k multi-resonant converters are the same, the multi-resonant converter sequentially comprises a converter switch network, a resonant cavity circuit, a transformer and a rectifying network on the secondary side of the transformer from an input end to an output end, the converter switch network of the multi-resonant converter is a full-bridge inversion structure and comprises a power switch tubeQ 1 ~Q 4 The resonant cavity circuit comprises a notch filter, an excitation branch and a resonant inductorL r Formed by series connection, the notch filter isL p AndC r tandem withC p A circuit formed by parallel connection, wherein the exciting branch circuit consists ofL m AndC m formed in series with the primary side and the secondary side passing through a turns ratio ofnThe secondary side of the transformer is a full-bridge rectification network, and is formed by diodesD 1 ~D 4 The composition is formed. Since all the multi-resonant converters have the same structure, roman numerals can be used for numbering the multi-resonant converters, and circuit elements of the subsequent multi-resonant converters can be distinguished by marks which are different from those of the multi-resonant converter circuit elements with the earlier numbers; for example: the converter switching network of the multi-resonant converter II is a full-bridge inversion structure and is composed of power switching tubesQ 1 ′~Q 4 The 'constitution', the resonant cavity circuit comprises a notch filter, an excitation branch and a resonant inductorL r ' series connection, the notch filter isL p ' sumC r ' series connected and then connected withC p ' parallel circuit, exciting branch circuit is formed byL m ' sumC m ' series connection is formed, the turn ratio between the primary side and the secondary side isnThe secondary side of the transformer is a full-bridge rectification network, and is formed by diodesD 1 ′~D 4 'constitution'. During operation, the switch tubeQ 1 ~Q 4 Or (b)Q 1 ′~Q 4 And', each bridge arm is complementarily conducted up and down with a duty ratio of 50%, the direct current input voltage is inverted into square waves, and the square waves are sent into a secondary side rectifying network, so that stable direct current output is obtained. The excitation branches of all the multi-resonant converters only take part in resonance in a short time, and the multi-resonant converters have two resonant frequencies when the rest resonant elements resonate by adding resonant tank elements, and the multi-resonant converters are divided into three modes of under resonance, quasi resonance and over resonance by taking a first resonant frequency as a boundary.
The LLC-DCX converter sequentially comprises a converter switching network, a resonant cavity circuit, a transformer and a rectifying network of the secondary side of the transformer from an input end to an output end, wherein the converter switching network is of a full-bridge inversion structure and is composed of a power switch tubeS 1 ~S 4 The resonant cavity circuit is composed of resonant inductorL r1 Resonant capacitorC r1 And excitation inductanceL m1 Is formed in series, and the turn ratio between the primary side and the secondary side isn 1 The secondary side of the transformer is a full-bridge rectification network, and is formed by diodesD R1 ~D R4 The composition is formed. During operation, the switch tubeS 1 ~S 4 Each bridge arm is conducted up and down complementarily at 50% duty ratio, the direct current input voltage is inverted into square wave, and then the square wave passes through the secondary side diodeD R1 ~D R4 Rectifying to obtain stable DC output.
The invention designs a DC-DC converter with a wide input voltage range based on a mixed ISOP, which adopts a mixed ISOP structure, and a plurality of multi-resonant converter modules are used for replacing LLC modules in the mixed ISOP structure, so that the mixed ISOP-based DC-DC converter can transmit fundamental wave energy and third harmonic energy, and can be switched into a D2D converter in real time when facing the condition of wide input voltage range, thereby ensuring wide voltage gain; when the input voltage range is narrow, the switching mode can be realized by switching the DCX converter and the LLC-DCX part together, so that the working efficiency is improved. The DCX part selects an LLC resonant converter, and the overall efficiency is increased by utilizing the high efficiency at the resonance point, so that the DC/DC converter with the output voltage regulation capability under the wide input voltage range is finally provided. The LLC-DCX converter is fixed at the resonance frequency, namely, fixed frequency control is adopted, only the voltage conversion function is completed, most of power (more than 60%) is transmitted, the LLC-DCX converter does not have the voltage regulation function, and the efficiency of the whole converter is improved by utilizing the high-efficiency performance at the resonance frequency. The multi-resonant converter provides voltage regulation capability and supports the function of a wide input voltage range; the input voltage range is further widened by utilizing a plurality of multi-resonant converters so as to achieve the purpose of supplying multi-level input voltage; typically, a wide input voltage range means that the difference between the upper and lower limits of the adjustable range exceeds 300V. The method comprises the following steps: when the input voltage is too high, the k multi-resonant converters are all used as D2D converters to cope with the high input voltage; when the input voltage is normal, one or more multi-resonant converters are used as DCX according to the condition of the load on the output side, the overall efficiency is increased together with the LLC-DCX converter, and the rest multi-resonant converters still serve as D2D to realize the voltage regulation function; when the input voltage is low, the k multi-resonant converters are all used as DCX and LLC-DCX converters to increase the overall efficiency.
Furthermore, the invention adopts three sub-modules, namely an LLC-DCX converter, a multi-resonant converter I and a multi-resonant converter II, wherein the input sides of the three sub-modules are connected in series, and the output sides of the three sub-modules are connected in parallel; when the input voltage is too high at 925V-1100V, the two multi-resonant converters are used as D2D converters to cope with the high input voltage; when the input voltage is normal and is in range of 640V-925V, the multi-resonant converter I and the multi-resonant converter II are switched between D2D and DCX in real time according to the condition of load on the output side, wherein the multi-resonant converter I is used as DCX, the overall efficiency is increased together with the LLC-DCX converter, and the multi-resonant converter II still is used as D2D to realize the voltage regulation function; when the input voltage is low, below 645V, both multi-resonant converters act as DCX together with LLC-DCX converters to increase overall efficiency.
Compared with the prior art, the invention has the following beneficial effects: the mixed ISOP-based wide input voltage range DC-DC converter and the voltage regulating method solve the problem that the voltage regulating capability of a single DC-DC module is insufficient under the condition of large-range fluctuation of input voltage, and solve the problems that the traditional LLC is used as the single DC-DC module, and the loss is high, the efficiency is low, the switching frequency range is wide, the light load voltage regulating capability is poor and the like under the application scene of high input voltage and wide voltage range; the loss of the operation of the converter is reduced, the overall efficiency of the converter is improved, and the output voltage can be regulated within a widened input voltage range, so that the output voltage is kept stable.
Drawings
Fig. 1 is a block diagram of a hybrid ISOP converter in accordance with an embodiment of the present invention.
Fig. 2 is a topological structure diagram of a hybrid ISOP converter according to an embodiment of the present invention, in which,i s 、i s ’、i s1 the low-side ac currents of the sub-module converters are respectively.
Figure 3 is a diagram of a topology of a multi-resonant converter in accordance with an embodiment of the present invention.
Figure 4 is a diagram of the topology of an LLC-DCX converter in accordance with a specific embodiment of the invention.
FIGS. 5 and 6 are waveforms of operation of a multi-resonant converter under-resonant according to an embodiment of the invention, whereinv ab Is the output voltage of the inverter bridge at the high voltage side,v cd is the output voltage of the inverter bridge at the low voltage side,i o is to output a direct current.
Figure 7 is a waveform diagram of the operation of a multi-resonant converter at quasi-resonance in accordance with an embodiment of the present invention.
Figure 8 is a waveform diagram of the operation of a multi-resonant converter in accordance with an embodiment of the present invention when overdesonant.
Figure 9 is a waveform diagram of LLC-DCX operation according to an embodiment of the present invention.
Figure 10 is a waveform diagram of the operation of a hybrid ISOP converter in accordance with an embodiment of the present invention.
Detailed Description
The invention is further illustrated below with reference to specific examples.
A wide input voltage range DC-DC converter based on a hybrid ISOP comprises a plurality of submodules, namely an LLC-DCX converter and k multi-resonant converters, wherein k is more than or equal to 2, the input sides of the submodules are connected in series, and the output sides of the submodules are connected in parallel; in this embodiment, three sub-modules are used, as shown in fig. 1 and 2: the input sides of the three sub-modules are connected in series, and the output sides of the three sub-modules are connected in parallel.
The multi-resonant converter I and the multi-resonant converter II have the same circuit structure, as shown in figure 3, the multi-resonant converter I sequentially comprises a converter switch network, a resonant cavity circuit, a transformer and a rectifying network of the secondary side of the transformer from the input end to the output end, the converter switch network of the multi-resonant converter I is a full-bridge inversion structure and is formed by a power switch tubeQ 1 ~Q 4 The resonant cavity circuit comprises a notch filter, an excitation branch and a resonant inductorL r Formed by series connection, the notch filter isL p AndC r tandem withC p A circuit formed by parallel connection, wherein the exciting branch circuit consists ofL m AndC m formed in series with the primary side and the secondary side passing through a turns ratio ofnThe secondary side of the transformer is a full-bridge rectification network, and is formed by diodesD 1 ~D 4 Constructing; the converter switching network of the multi-resonant converter II is a full-bridge inversion structure and is composed of power switching tubesQ 1 ′~Q 4 The 'constitution', the resonant cavity circuit comprises a notch filter, an excitation branch and a resonant inductorL r ' series connection, the notch filter isL p ' sumC r ' series connected and then connected withC p ' parallel circuit, exciting branch circuit is formed byL m ' sumC m ' series connection is formed, the turn ratio between the primary side and the secondary side isnThe secondary side of the transformer is a full-bridge rectification network, and is formed by diodesD 1 ′~D 4 'constitution'.
The LLC-DCX converter sequentially comprises a converter switching network, a resonant cavity circuit, a transformer and a rectifying network of the secondary side of the transformer from the input end to the output end, wherein the converter switching network is in a full-bridge inversion structure and comprises a power switch tube as shown in figure 4S 1 ~S 4 The resonant cavity circuit is composed of resonant inductorL r1 Resonant capacitorC r1 And excitation inductanceL m1 Is formed in series, and the turn ratio between the primary side and the secondary side isn 1 The secondary side of the transformer is a full-bridge rectification network, and is formed by diodesD R1 ~D R4 The composition is formed.
The LLC-DCX converter is fixedly operated at the resonance frequency to complete the voltage conversion function, transmits more than 60% of power, and does not have the voltage regulation function; the multi-resonant converters I and II provide voltage regulation capability and support the function of a wide input voltage range. The LLC-DCX converter is only used as DCX, the multi-resonant converter I and the multi-resonant converter II can be used as DCX and D2D, and the functions realized by the LLC-DCX converter and the multi-resonant converter II can be switched in real time according to the real-time value of the input voltage.
1. The multi-resonant converter I has the advantages that in one period, an excitation branch is only in resonance in a short time, through adding resonant tank elements, the converter has two resonant frequencies when the other resonant elements resonate, the first resonant frequency is used as a boundary, the multi-resonant converter I is divided into three modes of under resonance, quasi resonance and over resonance, the working modes of the three modes are the same, and the working principle of the multi-resonant converter II is similar to that of the multi-resonant converter I.
(1) The multi-resonant converter I has 6 working modes in the under resonance, the working waveforms are shown in figures 5 and 6,V gs is thatQ 1 ~Q 4 The respective gate-source voltages are as follows:
mode 1 ]t 0 ~t 1 ]：Q 1 AndQ 4 the electric conduction is carried out,Q 2 andQ 3 shut off, att 0 At the moment of time, exciting currenti Lm From negative to positive, resonant currenti Lr >i Lm Primary side to secondary side power transfer diodeD 1 、D 4 Conducting and outputting voltage of +V o . In this stage, the voltage across the excitation branch is unchanged due to the clamping of the output voltage,i Lm the linear growth is maintained, the excitation branch does not participate in resonance,L r 、C r 、L p andC p and (5) resonance together. Since the transducer delivers both the fundamental and third harmonics, the waveform approximates a saddle. To the point oft 1 At the moment of time of day,i Lr and (3) withi Lm Equal, modality 1 ends.
Mode 2[t 1 ~t 2 ]：Q 1 AndQ 4 is still in conduction with the power supply,Q 2 andQ 3 and (5) switching off. Exciting current in this stagei Lm And resonant currenti Lr Equal, the primary side does not transmit power to the secondary side,D 1 andD 4 the zero current is turned off. In the resonant cavityL r 、C r 、L p 、C p 、L m AndC m common resonance, primary side and secondary side are separated, primary side does not transfer energy to secondary side, load is formed from output capacitorC o Providing energy.
Mode 3[t 2 ~t 3 ]：Q 2 AndQ 3 still kept turned off and is turned off,Q 1 andQ 4 ready to shut down, the converter enters the dead zone. Within the dead time, the resonant currenti Lr One side charges and discharges the output capacitor of the power switch tube untilt 3 And ending the charge and discharge at the moment.Q 2 AndQ 3 drain-source voltage of (2)V ds Reduced to zero, which underlies ZVS on (zero voltage on).
Mode 4 ]t 3 ~t 4 ]：Q 1 ~Q 4 Are all in an off state.t 3 At the moment of time of day,C s1 ~C s4 charge and discharge are completed, exciting currenti Lm >Resonant currenti Lr The secondary side current is negative, thusD 2 、D 3 Conducting and outputting voltage of-V o . During this stage, the switching tubeQ 2 AndQ 3 is resonant currenti Lr A freewheel channel is provided,Q 2 andQ 3 drain-source voltageV ds And the voltage is reduced to zero, so that ZVS is switched on.
Mode 5 ]t 4 ~t 5 ]：Q 1 AndQ 4 are all turned off and are then turned off,Q 2 andQ 3 ready to conduct. At the position ofIn this stage, still satisfyi Lm >i Lr Obviouslyi s Still less than zero, therebyD 2 、D 3 Continuing to conduct and outputting voltage of-V o . Up tot 5 At the moment of time of day,i Lr decreasing to zero and mode 5 ends.
Mode 6 ]t 5 ~t 6 ]：Q 1 AndQ 4 the switch-off is performed and the switch-off is performed,Q 2 andQ 3 remain conductive. Resonant currenti Lr At the position oft 5 The time is reduced to zero, the positive is changed into negative, and the exciting currenti Lm And continuing to descend. In this stage of the process, the process is carried out,D 2 、D 3 still in the on state, the output voltage is maintainedV o Up tot 6 At the moment of time of day,i Lm down to zero, the first half cycle ends.
(2) The multi-resonant converter i operates at a first resonant frequency at quasi-resonance, i.e., the multi-resonant converter operates with a waveform as shown in fig. 7, in which,i Lr and (3) withi Lm At equal instants, the converter immediately enters the dead zone and thus there is no time in fig. 5i Lr Andi Lm approximately equal small "platforms". From the above analysis, it can be seen that mode 2[ in which the mode does not have an underresonant mode ]t 1 ~t 2 ]. The working condition of the other modes is the same as that of the underresonance.
(3) The multi-resonant converter I is in the over-resonant mode when over-resonant, i.e. when the operating frequency is greater than the first resonant frequency, and the operating waveform is as shown in FIG. 8, resulting in a short period due to the high operating frequency compared to the quasi-resonant mode, such thati Lr Andi Lm not yet equal, the converter enters the dead zone in advance, specifically as follows:
mode 1 ]t 0 ~t 1 ]: in this stage Q 1 AndQ 4 in the on-state of the device,Q 2 andQ 3 in the off-state of the device,v ab is +V in ，v ab In fig. 2 to 4, the voltage between the point a and the point b is the output voltage of the inverter bridge at the high voltage side;V in for the input voltage to be applied to the circuit,t 0 at the moment of time, exciting currenti Lm From negative to positive, resonant currenti Lr Is positive andi Lr >i Lm therefore, it isi s >0，D 1 、D 4 Is conducted and the output voltage is +V o . Due to the clamping effect of the output voltage, the voltage at two ends of the exciting branch is kept constant, therebyi Lm Maintain a linear growth, andL m andC m does not participate in resonance, byL r 、C r 、L p AndC p and (5) resonance together.i Lr Since the transducer delivers both the fundamental and third harmonics, the waveform approximates a saddle. Up tot 1 At the moment of time of day,Q 1 andQ 4 start to turn off, the converter starts to enter the dead zone, mode 1 ends, at which timei Lr Is still larger thani Lm 。
Mode 2[t 1 ~t 2 ]: at this timeQ 2 AndQ 3 the switch-off is continued to be maintained,Q 1 andQ 4 ready to enter shutdown.t 1 At that point, the converter takes over the dead zone. In dead zone, resonant currenti Lr One side is a power switch tubeQ 1 AndQ 4 output capacitance of (2)C s1 AndC s4 charging, simultaneous power switching tubeQ 2 AndQ 3 output capacitance of (2)C s2 AndC s3 by passing throughi Lr The electric discharge is carried out and, i Lr and starts to descend. Due to workThe frequency is higher, the resonance period is shorter, and thereforei Lr >i Lm . As is known from the law of KCL,i s >0, therebyD 1 、D 4 Keep on, output voltage keep +)V o 。t 2 At the moment of time of day,Q 2 andQ 3 drain-source voltage of (2)V ds Reduce to zero asQ 2 AndQ 3 lay a foundation for zero voltage turn-on. For the purpose ofQ 2 AndQ 3 the zero-voltage switching-on is smoothly realized, and the dead time is long enough and is longer than the time required by the charging and discharging process.
Mode 3[t 2 ~t 3 ]: in this stageQ 1 ~Q 4 Are all in an off state.t 2 At the moment of time of day,C s1 ~C s4 charge and discharge are completed, exciting currenti Lm And resonant currenti Lr All start to descend andi Lr speed ratio of descenti Lm Fast, therebyi Lm >i Lr As known from KCL law, the secondary side current is negative, therebyD 2 、D 3 Conducting and outputting voltage of-V o . During this stage, the switching tubeQ 2 AndQ 3 anti-parallel diode of (a)D s2 AndD s3 is resonant currenti Lr A freewheel channel is provided,Q 2 andQ 3 drain-source voltage of (2)V ds Smoothly reduces to zero, and realizes zero voltage turn-on.
Mode 4 ]t 3 ~t 4 ]: at this timeQ 1 AndQ 4 the switch-off is continued to be maintained, Q 2 andQ 3 ready to enter a conductive state. During this stage, still meeti Lm >i Lr ，i s <0, thusD 2 、D 3 Continuing to conduct, the output voltage is kept to be-V o . Up tot 4 At the moment of time of day,i Lr decreasing to zero and modality 4 ends.
Mode 5 ]t 4 ~t 5 ]: in this stageQ 1 AndQ 4 the turn-off is continued and the power is turned off,Q 2 andQ 3 has been turned on. Resonant currenti Lr At the position oft 4 The moment is reduced to zero, the positive is changed into negative, and the exciting currenti Lm And also falls. In this stage of the process, the process is carried out,D 2 、D 3 continuing to conduct and maintaining the output voltageV o . Up tot 5 At the moment of time of day,i Lm down to zero and to the end of the first half cycle.
2. LLC-DCX module: resonant inductance when LLC-DCX converterL r1 And a resonance capacitorC r1 In the series resonance, the resonance frequency can be obtainedf r Tof r LLC-DCX modes of operation can be divided into under-resonant, quasi-resonant, and over-resonant for the limits. The working modes of the converter in the three modes are the same as those of the multi-resonant converter, and the working waveforms are shown in fig. 9.
According to the voltage regulating method of the wide input voltage range DC-DC converter based on the hybrid ISOP, when the input voltage is too high and is in a range of 925V-1100V, the LLC-DCX converter still works under the highest efficiency, the multi-resonant converter I and the multi-resonant converter II are used as D2D converters, namely the voltage regulating modules, so that high input voltage is handled, output voltage can be kept constant, and the influence of high fluctuation of the input voltage is avoided. When the input voltage is normal and is in range of 640 v-925 v, the multi-resonant converter i and the multi-resonant converter ii switch between D2D and DCX in real time according to the load condition of the output side, for example: the multi-resonant converter I is used as a DCX, and the overall efficiency is improved together with the LLC-DCX converter, and the multi-resonant converter II is still used as a D2D converter, so that the voltage regulation function is realized, and the output voltage is kept stable and unchanged. When the input voltage is lower and is lower than 645V, great voltage regulation is not needed at this time, and the multi-resonant converter I and the multi-resonant converter II are used as DCX and LLC-DCX converters together to improve the overall efficiency.
Through the wide input voltage range DC-DC converter based on the mixed ISOP provided in this embodiment, the working waveform is as shown in fig. 10, and the functions of the internal multi-resonant converter can be adjusted in real time according to the condition of the input side voltage, so that the switching between D2D and DCX can be performed in real time, the running loss of the converter can be reduced, the overall efficiency of the converter is further improved, the input voltage range can be widened on the basis of ensuring the basic efficiency, and the output voltage can still be kept unchanged under the condition that the input voltage fluctuates greatly.
The scope of the present invention is not limited to the above embodiments, and various modifications and alterations of the present invention will become apparent to those skilled in the art, and any modifications, improvements and equivalents within the spirit and principle of the present invention are intended to be included in the scope of the present invention.
Claims (5)
1. A wide input voltage range DC-DC converter based on a hybrid ISOP, characterized by: the multi-resonant converter comprises a plurality of submodules, wherein each submodule comprises an LLC-DCX converter and k multi-resonant converters, k is more than or equal to 2, the input sides of the submodules are connected in series, and the output sides of the submodules are connected in parallel;
the circuit structures of k multi-resonant converters are the same, the multi-resonant converter sequentially comprises a converter switch network, a resonant cavity circuit, a transformer and a rectifying network on the secondary side of the transformer from an input end to an output end, the converter switch network of the multi-resonant converter is a full-bridge inversion structure and comprises a power switch tubeQ 1 ~Q 4 The resonant cavity circuit comprises a notch filter, an excitation branch and a resonant inductorL r Formed by series connection, the notch filter isL p AndC r tandem withC p A circuit formed by parallel connection, wherein the exciting branch circuit consists ofL m AndC m formed in series with the primary side and the secondary side passing through a turns ratio ofnThe secondary side of the transformer is a full-bridge rectification network, and is formed by diodesD 1 ~D 4 Constructing;
the LLC-DCX converter sequentially comprises a converter switching network, a resonant cavity circuit, a transformer and a rectifying network of the secondary side of the transformer from an input end to an output end, wherein the converter switching network is of a full-bridge inversion structure and is composed of a power switch tubeS 1 ~S 4 The resonant cavity circuit is composed of resonant inductorL r1 Resonant capacitorC r1 And excitation inductanceL m1 Is formed in series, and the turn ratio between the primary side and the secondary side isn 1 The secondary side of the transformer is a full-bridge rectification network, and is formed by diodesD R1 ~D R4 The composition is formed.
2. A wide input voltage range DC-DC converter based on a hybrid ISOP as claimed in claim 1, characterized in that: the LLC-DCX converter is used as DCX, k multi-resonant converters are used as DCX or D2D, and the functions realized by the multi-resonant converters are switched in real time according to the real-time value of the input voltage.
3. A wide input voltage range DC-DC converter based on a hybrid ISOP as claimed in claim 1, characterized in that: the three sub-modules are respectively an LLC-DCX converter, a multi-resonant converter I and a multi-resonant converter II, wherein the input sides of the three sub-modules are connected in series, and the output sides of the three sub-modules are connected in parallel.
4. A voltage regulating method of a wide input voltage range DC-DC converter based on a hybrid ISOP is characterized by comprising the following steps of: the method is realized by adopting the wide input voltage range DC-DC converter based on the hybrid ISOP as claimed in claim 2, wherein the LLC-DCX converter is fixedly operated at a resonant frequency to complete a voltage conversion function, transmits more than 60% of power, and does not carry out voltage regulation; the k multi-resonant converters, as DCX or D2D, provide voltage regulation capability and support regulation over a wide input voltage range.
5. The voltage regulation method of the wide input voltage range DC-DC converter based on the hybrid ISOP according to claim 4, wherein: three sub-modules, namely an LLC-DCX converter, a multi-resonant converter I and a multi-resonant converter II, are adopted, the input sides of the three sub-modules are connected in series, and the output sides of the three sub-modules are connected in parallel; when the input voltage is too high at 925V-1100V, the multi-resonant converter I and the multi-resonant converter II are used as D2D converters to cope with the high input voltage; when the input voltage is normal and is in the range of 640V-925V, the multi-resonant converter I is used as DCX according to the condition of the load on the output side, the overall efficiency is increased together with the LLC-DCX converter, and the multi-resonant converter II is still used as D2D to realize the voltage regulation function; when the input voltage is lower and is lower than 645V, the multi-resonant converter I and the multi-resonant converter II are used as DCX and LLC-DCX converters together to improve the overall efficiency.
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