CN116885941A - Switch capacitor DC-DC converter with quasi-continuous voltage conversion ratio - Google Patents

Switch capacitor DC-DC converter with quasi-continuous voltage conversion ratio Download PDF

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Publication number
CN116885941A
CN116885941A CN202310841866.4A CN202310841866A CN116885941A CN 116885941 A CN116885941 A CN 116885941A CN 202310841866 A CN202310841866 A CN 202310841866A CN 116885941 A CN116885941 A CN 116885941A
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capacitor
switch
phase
converter
polar plate
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余凯
钟永凌
李思臻
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Guangdong University of Technology
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Guangdong University of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention provides a switch capacitor DC-DC converter with quasi-continuous voltage conversion ratio, which comprises: n two-phase SC units and m-phase SC units, wherein n is more than or equal to 1, and m is more than or equal to 1; the m-phase SC unit includes: m+2 first control branches, wherein the first control branches are connected in parallel and then connected to an upper polar plate of a first capacitor, each first control branch comprises a first control switch, one end of each first control switch is connected to the upper polar plate of the first capacitor, and the other end of each first control switch is connected to the input end of an M-phase SC unit;the first control branches are connected in parallel and then connected to the lower polar plate of the first capacitor, each first control branch comprises a first control switch, one end of each first control switch is connected to the lower polar plate of the first capacitor, and the other end of each first control switch is grounded; the output end of the two-phase SC unit is connected with the input end of the m-phase SC unit;the m-phase SC unit controls the output voltage by adjusting the frequency. The invention has lower charge sharing loss and higher efficiency under the same phase.

Description

Switch capacitor DC-DC converter with quasi-continuous voltage conversion ratio
Technical Field
The invention relates to the technical field of electronics, in particular to a switch capacitor DC-DC converter with a quasi-continuous voltage conversion ratio.
Background
Currently, most portable electronic devices use a battery as a main power source, and the output voltage of the battery often cannot directly supply power to an internal chip, and a DC-DC (direct current-direct current) converter is required for voltage conversion. DC-DC conversion may be achieved using Low Dropout (LDO) voltage regulators, switched inductor DC-DC converters, and switched flying capacitor DC-DC converters. The switched flying capacitor converter is one of the main branches of the DC-DC converter, the circuit of the switched flying capacitor converter adopts a flying capacitor as an energy storage medium for energy conversion, the voltage conversion of boosting, reducing or back-pressure can be easily realized by automatically adjusting an internal MOS switch tube, and in a standard CMOS process, the switched flying capacitor converter circuit can be completely integrated in a chip because the switched flying capacitor converter circuit only uses an MOS switch and a flying capacitor. The Voltage Conversion Ratio (VCR) of the switched-flying-capacitor converter, which is the ratio of the output and input voltages of the switched-flying-capacitor converter, is discrete.
The reconfigurable SC (Switched-Capacitor) DC-DC converter constructs VCRs by performing addition and subtraction operations on the flying Capacitor voltages, and since the flying Capacitor voltages are discrete and discontinuous, only discrete VCRs can be realized, and the number of the constructed VCRs can be increased by increasing the number of flying capacitors. While the multiphase operation technique can achieve a quasi-continuous scalable VCR, it requires a large number of flying capacitors to reduce the flying capacitor voltage variation step size during charge transfer, inevitably increasing design complexity and sacrificing implementation flexibility.
For a conventional SC converter with two-phase operation, the charge sharing loss Eloss is proportional to the square of the flying capacitor charge-discharge voltage step Δv, which is limited to a relatively low value, i.e. the voltage of the flying capacitor appears to be approximately a fixed value, in order to reduce the charge sharing loss. Thus, for a topology of fixed connection, the VCR is also a fixed value, although the output voltage can be changed by increasing Δv (e.g., decreasing the switching frequency), at the cost of increasing the charge sharing loss. Since the weight of charge sharing loss is not high, the switch conduction loss must be considered at the same time. A series of switches and corresponding phases are added on the basis of the traditional two-phase flying capacitor, so that the flying capacitor is charged and discharged for many times in one period, the sum of charging and discharging voltage step length delta V is VIN, and the charge sharing loss of the traditional two-phase flying capacitor is different from the charge sharing loss of the traditional two-phase flying capacitor, wherein the charge sharing loss of the CSCR topology is far greater than the switch conduction loss and is in direct proportion to the switch conduction loss, and the charge sharing loss ratio gradually increases along with the reduction of a VCR, so that the efficiency of the VCR is drastically reduced when the VCR is smaller.
In summary, the efficiency of the reconfigurable SC converter is affected by the number of discrete VCRs, and although the reconfigurable topologies such as SAR, NSC, etc. realize more VCRs, the implementation complexity is greatly improved when the problems of optimal charge sharing loss, optimal switch conduction loss, switching between VCRs, etc. of a single VCR are specifically considered; CSCR topology does not require topology reconstruction and can achieve nearly continuous VCR conversion by switching frequency modulation alone, but its efficiency and power density are limited by the number of phases.
Disclosure of Invention
The invention aims to provide a switch capacitor DC-DC converter with a quasi-continuous voltage conversion ratio, which can solve the problem of phase number compromise in the traditional CSCR topology structure, namely the problems of large charge sharing loss ratio when the phase number is small, low power density, high complexity and the like when the phase number is large, has lower charge sharing loss compared with the traditional CSCR topology under the condition of the same phase number, and keeps a certain range of adjustable VCR frequency.
A switched capacitor DC-DC converter of quasi-continuous voltage conversion ratio, comprising: n two-phase SC units and m-phase SC units, wherein n is more than or equal to 1, and m is more than or equal to 1;
the m-phase SC unit includes: m+2 first control branches, wherein the first control branches are connected in parallel and then connected to an upper polar plate of a first capacitor, each first control branch comprises a first control switch, one end of each first control switch is connected to the upper polar plate of the first capacitor, and the other end of each first control switch is connected to the input end of an M-phase SC unit;a plurality of second control branches are connected in parallel and then connected to a lower polar plate of the first capacitor, and each second control branch comprises a second controlOne end of the second control switch is connected to the lower polar plate of the first capacitor, and the other end of the second control switch is grounded, wherein M is more than or equal to 1;
the output end of the two-phase SC unit is connected with the input end of the m-phase SC unit;
the m-phase SC unit controls the output voltage by adjusting the frequency.
Preferably, the two-phase SC unit comprises: a first switch, a second switch, a third switch, a fourth switch, and a second capacitor;
one end of the first switch is connected with the power supply end, and the other end of the first switch is connected with the upper polar plate of the second capacitor; one end of the second switch is connected with the power supply end, and the other end of the second switch is connected with the upper polar plate of the second capacitor; one end of the third switch is connected with the power supply end, and the other end of the third switch is connected with the lower polar plate of the second capacitor; one end of the fourth switch is connected with the power supply end, and the other end of the fourth switch is connected with the lower polar plate of the second capacitor; the upper polar plate of the second capacitor is connected with the first switch and the third switch, and the lower polar plate is connected with the second switch and the fourth switch.
Preferably, when a switched capacitor DC-DC converter with a quasi-continuous voltage conversion ratio is operated, the voltage step Δv of each capacitor charge and discharge is equal, Δv= (V) IN -nV OUT )/(M+N+2)；
The charge and discharge times in one working period is M+N+1, wherein the output voltage V OUT ＝V IN -nV OUT -V M ，V IN N is the number of two-phase SC cells for the input voltage; the upper polar plate of the M-phase SC unit has a connection switch number of M+2, the lower polar plate has a connection switch number of N+2, V IN For the input voltage, N is 1,2 (m+n) +2=m.
Preferably, the charge amount output by each phase of the m-phase SC units is C fly (V IN -nV OUT )/(M+N+2)，C fly Is the capacitance value of the capacitor.
Preferably, when the switched capacitor DC-DC converter with a quasi-continuous voltage conversion ratio works, the output charge in one period is as follows:
C fly is the capacitance value of the capacitor.
Preferably, when the switched capacitor DC-DC converter with a quasi-continuous voltage conversion ratio works, the charge sharing loss is:
C fly is the capacitance value of the capacitor.
Preferably, when n=2, m=18, m=n=4, the fixed load current is 2mA, the magnitude of the input voltage is changed, and the frequency is adjusted to output voltage V OUT ＝0.8V。
Preferably, when n=2, m=18, m=n=4, the fixed input voltage is V IN =3.3v, varying the magnitude of the output current, adjusting the frequency to make the output voltage V OUT ＝0.8V。
Preferably, the phase of each basic unit in the m-phase SC unit is different.
Preferably, the output ends of the two-phase SC units are output to the input ends of the m-phase SC units in a staggered manner.
The invention aims to solve the problem of phase number compromise in the traditional CSCR topological structure, namely the problems of large charge sharing loss ratio when the phase number is small, low power density and high complexity when the phase number is large, and the like. A new quasi-continuous voltage conversion ratio topology is provided, which has lower charge sharing loss than the traditional CSCR topology under the condition of the same phase number, and keeps a certain range of VCR frequency adjustable. The invention mainly comprises two basic units: the switch is composed of a two-phase SC unit controlled by a two-phase clock and an m-phase SC unit controlled by a multi-phase clock, wherein the input is connected to the m-phase SC unit of the final stage through n-stage two-phase SC units, and each of the first n-stage consists of two phase SC units with staggered phases. When the circuit is used for reducing the voltage, the VCR can be regulated within the range of 0-1/(n+1) (n is more than or equal to 1).
Drawings
The accompanying drawings, which are incorporated in and constitute a part of this specification, illustrate embodiments consistent with the invention and together with the description, serve to explain the principles of the invention.
In order to more clearly illustrate the embodiments of the invention or the technical solutions of the prior art, the drawings which are used in the description of the embodiments or the prior art will be briefly described, and it will be obvious to a person skilled in the art that other drawings can be obtained from these drawings without inventive effort.
FIG. 1 is a schematic diagram of a circuit topology of the present invention;
FIG. 2 is a schematic diagram of a two-phase SC cell circuit according to the present invention;
FIG. 3 is a schematic diagram of an m-phase SC cell circuit structure according to the present invention;
fig. 4 is a schematic circuit diagram of the present invention when n=2, m=18, and m=n=4;
FIG. 5 is a signal timing diagram of the switch signal according to the present invention;
FIG. 6 is a graph of capacitance voltage of an m-phase SC cell flying capacitor according to the present invention;
FIG. 7 is a graph showing the theoretical efficiency of the present invention versus VCR;
fig. 8 is a graph of simulated efficiency for different VCRs and load currents of the present invention.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and fully with reference to the accompanying drawings, in which it is evident that the embodiments described are only some, but not all embodiments of the invention. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
It should be noted that all directional indicators (such as up, down, left, right, front, and rear … …) in the embodiments of the present invention are merely used to explain the relative positional relationship, movement, etc. between the components in a particular posture (as shown in the drawings), and if the particular posture is changed, the directional indicator is changed accordingly.
Furthermore, the description of "first," "second," etc. in this disclosure is for descriptive purposes only and is not to be construed as indicating or implying a relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defining "a first" or "a second" may explicitly or implicitly include at least one such feature. In addition, the technical solutions of the embodiments may be combined with each other, but it is necessary to base that the technical solutions can be realized by those skilled in the art, and when the technical solutions are contradictory or cannot be realized, the combination of the technical solutions should be considered to be absent and not within the scope of protection claimed in the present invention.
The efficiency of the reconfigurable SC converter is affected by the number of discrete VCRs, while the reconfigurable topologies such as SAR, NSC and the like realize more VCRs, the realization complexity is greatly improved when the problems of optimal charge sharing loss, optimal switch conduction loss [5], switching among VCRs and the like of a single VCR are particularly considered; CSCR topology does not require topology reconstruction and can achieve nearly continuous VCR conversion by switching frequency modulation alone, but its efficiency and power density are limited by the number of phases.
The invention aims to solve the problem of phase number compromise in the traditional CSCR topological structure, namely the problems of large charge sharing loss ratio when the phase number is small, low power density and high complexity when the phase number is large, and the like. A new quasi-continuous voltage conversion ratio topology is provided, which has lower charge sharing loss than the traditional CSCR topology under the condition of the same phase number, and keeps a certain range of VCR frequency adjustable. The invention mainly comprises two basic units: the switch is composed of a two-phase SC unit controlled by a two-phase clock and an m-phase SC unit controlled by a multi-phase clock, wherein the input is connected to the m-phase SC unit of the final stage through n-stage two-phase SC units, and each of the first n-stage consists of two phase SC units with staggered phases. When the circuit is used for reducing the voltage, the VCR can be regulated within the range of 0-1/(n+1) (n is more than or equal to 1).
A switched capacitor DC-DC converter of quasi-continuous voltage conversion ratio, as in fig. 1, comprising: n two-phase SC units and m-phase SC units, wherein n is more than or equal to 1, and m is more than or equal to 1;
the m-phase SC unit includes: m+2 first control branches connected in parallel and connected to the upper electrode of the first capacitorThe first control branch circuits comprise first control switches, one ends of the first control switches are connected to the upper polar plate of the first capacitor, and the other ends of the first control switches are connected to the input ends of the m-phase SC units;the second control branches are connected in parallel and then connected to the lower polar plate of the first capacitor, each second control branch comprises a second control switch, one end of each second control switch is connected to the lower polar plate of the first capacitor, the other end of each second control switch is grounded, and M is more than or equal to 1; in the embodiment of the present invention, the first capacitor is the flying capacitor C fly 。
And 2 (M+N) +2=m is satisfied in the M-phase SC unit, wherein M and N are more than or equal to 1, the number of the upper polar plate connecting switches of the M-phase SC unit is M+2, and the number of the lower polar plate connecting switches is N+2.
The output end of the two-phase SC unit is connected with the input end of the m-phase SC unit;
the m-phase SC unit controls the output voltage by adjusting the frequency.
When the circuit is used for reducing the voltage, the VCR can be regulated within the range of 0-1/(n+1) (n is more than or equal to 1). Output voltage V OUT ＝V IN -nV OUT -V M Wherein 0 is<V M <V IN -nV OUT 。
Preferably, as shown in fig. 2, the two-phase SC unit includes: a first switch, a second switch, a third switch, a fourth switch, and a second capacitor;
one end of the first switch is connected with the power supply end, and the other end of the first switch is connected with the upper polar plate of the second capacitor; one end of the second switch is connected with the power supply end, and the other end of the second switch is connected with the upper polar plate of the second capacitor; one end of the third switch is connected with the power supply end, and the other end of the third switch is connected with the lower polar plate of the second capacitor; one end of the fourth switch is connected with the power supply end, and the other end of the fourth switch is connected with the lower polar plate of the second capacitor; the upper polar plate of the second capacitor is connected with the first switch and the third switch, and the lower polar plate is connected with the second switch and the fourth switch.
Preferably, when a switched capacitor DC-DC converter with a quasi-continuous voltage conversion ratio is operated, each time the capacitor charge-discharge voltage step Δv is equal, Δv= (V) IN -nV OUT )/(M+N+2)；
The charge and discharge times in one working period is M+N+1, wherein the output voltage V OUT ＝V IN -nV OUT -V M ，V IN N is the number of two-phase SC cells for the input voltage; the upper polar plate of the M-phase SC unit has a connection switch number of M+2, the lower polar plate has a connection switch number of N+2, V IN For the input voltage, N is 1,2 (m+n) +2=m.
Preferably, the charge amount output by each phase of the m-phase SC units is C fly (V IN -nV OUT )/(M+N+2)，C fly Is the capacitance value of the flying capacitor.
Preferably, when the switched capacitor DC-DC converter with a quasi-continuous voltage conversion ratio works, the output charge in one period is as follows:
C fly is the capacitance value of the flying capacitor.
Preferably, when the switched capacitor DC-DC converter with a quasi-continuous voltage conversion ratio works, the charge sharing loss is:
C fly is the capacitance value of the flying capacitor.
Preferably, when n=2, m=18, m=n=4, the fixed load current is 2mA, the magnitude of the input voltage is changed, and the frequency is adjusted to output voltage V OUT ＝0.8V。
When n=2, m=18, and m=n=4, the structure shown in fig. 1 can be implemented by the circuit in fig. 4. As shown in fig. 4. Since the two inputs of the m-phase SC cell require continuous charge input, the front two-phase SC cell needs to be output to the 18-phase SC cell in an interleaved manner. And the switch connection between charge sharing paths between the flying capacitors is optimized, so that only one switch is used for controlling the connection between every two flying capacitors, and extra conduction loss caused by the series connection of a plurality of switches is avoided.
Fig. 5 shows driving clock signals corresponding to the switch tube with the structure shown in fig. 4, wherein the connection relation between 18 m-phase SC units is shown in table 1, and TP1 to TP18 and BP1 to BP18 correspond to upper and lower plates of the flying capacitor in 18 units respectively. Fig. 6 is a graph showing the capacitance voltage of 18 m-phase SC cell flying capacitors over time.
Table 1: connection relationship between 18 m-phase SC units
If the port T4 of the m-phase unit 1 corresponds to TP6, that is, the port T4 is directly connected to the upper plate TP6 of the m-phase unit 6.
Table 2: topological switch and flying capacitor quantity comparison
Topology and method for generating topology information Number of switches Number of flying capacitors
CSCR(M+N＝8) 216 18
Present topology (n=1, m+n=8) 216+9 18+2
Present topology (n=2, m+n=8) 216+12 18+4
Present topology (n=3, m+n=8) 216+15 18+6
Preferably, when n=2, m=18, m=n=4, the fixed input voltage is V IN =3.3v, varying the magnitude of the output current, adjusting the frequency to make the output voltage V OUT ＝0.8V。
FIG. 8 shows simulation efficiency data for the example of the design of FIG. 4, the result of FIG. 8 (a) is to vary the magnitude of the input voltage and to adjust the magnitude of the frequency to the output voltage V at a fixed load current of 2mA OUT Data measured with 0.8V, fig. 7 shows that the efficiency at about 3.3V reaches 81% peak, and the charge-discharge voltage step of the multiphase SC cell is substantially uniform at 3.3V, where the charge sharing loss is low, and is substantially consistent with theoretical analysis. FIG. 8 (b) shows the voltage V at a fixed input voltage IN In the case of =3.3v, the magnitude of the output current is changed and the output voltage V is made by adjusting the magnitude of the frequency OUT As measured with 0.8V, it can be seen that as the output load current increases, its efficiency gradually decreases, mainly because its switching on loss increases with increasing load current.
The invention has lower charge sharing loss compared with the CSCR topology under the condition of not increasing the phase number. Because the flying capacitor voltage in the multiphase SC unit is charged and discharged by a plurality of phase control, the charge quantity carried by the flying capacitor changes along with the frequency, and the VCR can be changed within a certain range by adjusting the frequency. Since the multiphase clocked switch staggered output is used, low output voltage ripple can be achieved.
Preferably, the phase of each basic unit in the m-phase SC unit is different.
Preferably, the output ends of the two-phase SC units are output to the input ends of the m-phase SC units in a staggered manner.
The invention aims to solve the problem of phase number compromise in the traditional CSCR topological structure, namely the problems of large charge sharing loss ratio when the phase number is small, low power density and high complexity when the phase number is large, and the like. A new quasi-continuous voltage conversion ratio topology is provided, which has lower charge sharing loss than the traditional CSCR topology under the condition of the same phase number, and keeps a certain range of VCR frequency adjustable. The invention mainly comprises two basic units: the switch is composed of a two-phase SC unit controlled by a two-phase clock and an m-phase SC unit controlled by a multi-phase clock, wherein the input is connected to the m-phase SC unit of the final stage through n-stage two-phase SC units, and each of the first n-stage consists of two phase SC units with staggered phases. When the circuit is used for reducing the voltage, the VCR can be regulated within the range of 0-1/(n+1) (n is more than or equal to 1).
The foregoing is only a specific embodiment of the invention to enable those skilled in the art to understand or practice the invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

Claims (10)

1. A switched capacitor DC-DC converter of quasi-continuous voltage conversion ratio, comprising: n two-phase SC units and m-phase SC units, wherein n is more than or equal to 1, and m is more than or equal to 1;
the m-phase SC unit includes: m+2 first control branches, wherein the first control branches are connected in parallel and then connected to an upper polar plate of a first capacitor, each first control branch comprises a first control switch, one end of each first control switch is connected to the upper polar plate of the first capacitor, and the other end of each first control switch is connected to the input end of an M-phase SC unit;a plurality of second control branches are connected in parallel and then connected to a lower polar plate of the first capacitor, each second control branch comprises a second control switch, one of the second control switchesOne end of the first capacitor is connected to the lower polar plate of the first capacitor, and the other end of the first capacitor is grounded, wherein M is more than or equal to 1;
the output end of the two-phase SC unit is connected with the input end of the m-phase SC unit;
the m-phase SC unit controls the output voltage by adjusting the frequency. .
2. The switched capacitor DC-DC converter of claim 1, comprising: the two-phase SC unit comprises: a first switch, a second switch, a third switch, a fourth switch, and a second capacitor;
one end of the first switch is connected with the power supply end, and the other end of the first switch is connected with the upper polar plate of the second capacitor; one end of the second switch is connected with the power supply end, and the other end of the second switch is connected with the upper polar plate of the second capacitor; one end of the third switch is connected with the power supply end, and the other end of the third switch is connected with the lower polar plate of the second capacitor; one end of the fourth switch is connected with the power supply end, and the other end of the fourth switch is connected with the lower polar plate of the second capacitor; the upper polar plate of the second capacitor is connected with the first switch and the third switch, and the lower polar plate is connected with the second switch and the fourth switch.
3. The switched capacitor DC-DC converter of claim 1, comprising: when the switch capacitor DC-DC converter with quasi-continuous voltage conversion ratio works, the voltage step delta V of each capacitor charge and discharge is equal, delta V= (V) IN -nV OUT )/(M+N+2)；
The charge and discharge times in one working period is M+N+1, wherein the output voltage V OUT ＝V IN -nV OUT -V M ，V IN N is the number of two-phase SC cells for the input voltage; the upper polar plate of the M-phase SC unit has a connection switch number of M+2, the lower polar plate has a connection switch number of N+2, V IN For the input voltage, N is 1,2 (m+n) +2=m.
4. A switched capacitor DC-DC converter of quasi-continuous voltage conversion ratio according to claim 3, comprising: the charge amount output by each phase of the m-phase SC units is C fly (V IN -nV OUT )/(M+N+2)，C fly Is the capacitance value of the capacitor.
5. A switched capacitor DC-DC converter of quasi-continuous voltage conversion ratio according to claim 3, comprising: when the switched capacitor DC-DC converter with the quasi-continuous voltage conversion ratio works, the output charge in one period is as follows:
C fly is the capacitance value of the capacitor.
6. A switched capacitor DC-DC converter of quasi-continuous voltage conversion ratio according to claim 3, comprising: when the switch capacitor DC-DC converter with the quasi-continuous voltage conversion ratio works, the charge sharing loss is as follows:
C fly is the capacitance value of the capacitor.
7. A switched capacitor DC-DC converter of quasi-continuous voltage conversion ratio according to claim 3, comprising: when n=2, m=18, and m=n=4, the fixed load current is 2mA, the magnitude of the input voltage is changed, and the frequency is adjusted to output voltage V OUT ＝0.8V。
8. A switched capacitor DC-DC converter of quasi-continuous voltage conversion ratio according to claim 3, comprising: when n=2, m=18, m=n=4, the fixed input voltage is V IN =3.3v, varying the magnitude of the output current, adjusting the frequency to make the output voltage V OUT ＝0.8V。
9. The switched capacitor DC-DC converter of claim 1, comprising: the phase of each elementary cell in the m-phase SC cell is different.
10. The switched capacitor DC-DC converter of claim 1, comprising: the output ends of the two-phase SC units are output to the input ends of the m-phase SC units in a staggered way.
CN202310841866.4A 2023-07-10 2023-07-10 Switch capacitor DC-DC converter with quasi-continuous voltage conversion ratio Pending CN116885941A (en)

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CN202310841866.4A CN116885941A (en) 2023-07-10 2023-07-10 Switch capacitor DC-DC converter with quasi-continuous voltage conversion ratio

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