CN116865548A - Z-source inverter control method and device for optimizing switching loss under variable power factor - Google Patents

Z-source inverter control method and device for optimizing switching loss under variable power factor Download PDF

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CN116865548A
CN116865548A CN202310153360.4A CN202310153360A CN116865548A CN 116865548 A CN116865548 A CN 116865548A CN 202310153360 A CN202310153360 A CN 202310153360A CN 116865548 A CN116865548 A CN 116865548A
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vector
voltage
sector
switching
power factor
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CN116865548B (en
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姜翼展
郭志康
张经纬
王强
何凤有
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China University of Mining and Technology CUMT
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China University of Mining and Technology CUMT
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/425—Arrangements for improving power factor of AC input using a single converter stage both for correction of AC input power factor and generation of a high frequency AC output voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

The application discloses a Z source inverter control method and a device for optimizing switching loss under a variable power factor, wherein the method is based on a space vector control method, and the method comprises the following steps: by voltage reference vectorα‑βCoordinate axes in coordinate systemαIncluded angle of axesθCalculating the action time of the voltage vector and the action time of inserting the direct vector into the zero vector by combining the modulation M corresponding to the voltage reference vector and the sector where the voltage reference vector is located; determining a switching sequence according to the set switching state, a basic voltage vector, a vector acting time and a direct vector inserting zero vector acting time and a sector where a voltage reference vector is located; controlling the through vector in response to changes in load power factorAnd the insertion mode is combined with the switching sequence to determine the switching sequence after loss optimization, so that the control of the Z source inverter under the variable power factor is realized. The application realizes that the through current passing through the switching device is counteracted by the output current of the alternating current side as much as possible, so as to realize lower switching loss and conduction loss effects.

Description

Z-source inverter control method and device for optimizing switching loss under variable power factor
Technical Field
The application relates to the technical field of power electronics, in particular to a Z-source inverter control method and device for optimizing switching loss under variable power factor.
Background
In the field of fuel cells or photovoltaic power generation, due to the unstable voltage, a two-stage inverter is generally required, that is, a direct-current voltage is firstly boosted and converted, and then a traditional inverter is used for converting direct current into alternating current. The discovery of a Z Source Inverter (ZSI) can replace a two-stage structure, and the boost of a direct current link is realized by adding a Z source network and a special direct modulation mode. Furthermore, the special structure of the Z-source inverter enables the Z-source inverter to realize the straight-through of the upper bridge arm and the lower bridge arm. Therefore, the Z-source inverter can be free from dead zone consideration, and the reliability of the system is improved.
The Z source inverter modulation development follows the topology development as well. The early modulation method of the Z-source inverter generally adopts a modulation method based on carrier waves. Based on the control method, simple boost modulation, maximum constant boost modulation and the like are developed. Early modulation is mainly used for exploring topology boosting capability and device voltage and current stress. Space vector modulation was developed after that, which includes a series of modulation methods such as ZSVM6, ZSVM4, ZSVM2, and ZSVM1 among the ZSVMs (Z-source inverter space vector modulations) modulation methods. In recent years, the modulation method of the Z-source inverter has also been developed in the aspects of reducing switching loss, optimizing inductance ripple and the like. However, the new modulation method lacks a modulation method combined with power factor variation, and a better loss effect cannot be achieved under the condition of power factor variation. Therefore, it is meaningful to discuss the problems of switching loss, etc. at varying power factors.
Disclosure of Invention
The application provides a Z source inverter control method and device for optimizing switching loss under variable power factor.
The application is realized according to the following technical scheme:
in a first aspect, the present application provides a method for controlling a Z-source inverter with optimized switching loss under a variable power factor, where the method is based on a space vector control method, and includes:
setting a switching state and a basic voltage vector of a bridge arm of the three-phase two-level Z-source inverter;
setting a voltage reference vector to be modulated by a three-phase two-level Z source inverter, and judging a sector where the voltage reference vector is located;
calculating the acting time of the voltage vector and the acting time of inserting the direct vector into the zero vector by combining the included angle theta of the voltage reference vector and the coordinate axis alpha in the alpha-beta coordinate system and the modulation M corresponding to the voltage reference vector and the sector where the voltage reference vector is positioned;
determining a switching sequence according to the set switching state, a basic voltage vector, a vector acting time and a direct vector inserting zero vector acting time and a sector where a voltage reference vector is located;
calculating a load power factor by collecting current and voltage of a load alternating-current side;
and controlling the insertion mode of the through vector according to the change of the load power factor, and determining a switching sequence after loss optimization by combining the switching sequence to realize the control of the Z source inverter under the variable power factor.
In one embodiment, the setting the three-phase bridge arm switch state of the three-phase two-level Z-source inverter includes:
when the switching state is 1, the upper bridge arm switching device is turned on, and the lower bridge arm switching device is turned off;
when the switching state is 0, the upper bridge arm switching device is closed, and the lower bridge arm switching device is opened;
when the switching state is sh, the upper bridge arm switching device and the lower bridge arm switching device are simultaneously turned on.
In one embodiment, 8 basic voltage vectors are obtained according to the switching state of a three-phase bridge arm of the three-phase two-level Z-source inverter and are respectively recorded as voltage vectors V 0 、V 1 、V 2 、V 3 、V 4 、V 5 、V 6 And V 7 The method comprises the steps of carrying out a first treatment on the surface of the The specific states of the switch state combination A phase switch state, the B phase switch state and the C phase switch state corresponding to the 8 basic voltage vectors are as follows:
the switching state corresponding to the voltage vector V0 is (000);
the corresponding switch state of the voltage vector V1 is (100);
the switch state corresponding to the voltage vector V2 is (110);
the switching state corresponding to the voltage vector V3 is (010);
the switch state corresponding to the voltage vector V4 is (011);
the switch state corresponding to the voltage vector V5 is (001);
the corresponding switch state of the voltage vector V6 is (101);
the switch state corresponding to the voltage vector V7 is (111);
wherein V is 0 And V 7 The other six voltage vectors are non-zero vectors; any bridge arm of the Z-source inverter can form a through vector Vsh by adopting a through state, and a switch state combination corresponding to the through vector Vsh comprises: (shXX), (XshX) and (xxxh); wherein X represents any 1 or 0 state, and sh represents a straight-through state that the upper bridge arm switch tube and the lower bridge arm switch tube are simultaneously conducted.
In one embodiment, the determining the sector in which the voltage reference vector is located includes:
on an alpha-beta axis static coordinate system, starting from the alpha axis direction, dividing the alpha axis direction into 6 sectors of 60 degrees in the anticlockwise direction, and sequentially naming each sector as a sector 1-a sector 6 according to the serial number in the anticlockwise direction;
projecting the voltage reference vector on the coordinate axis alpha and beta, and respectively marking the components as the voltage reference vector alpha axis component V α And a voltage reference vector beta axis component V β ；
According to the alpha-axis component V of the voltage reference vector α And a voltage reference vector beta axis component V β And judging the sector where the voltage reference vector is located.
In one embodiment, the angle θ between the voltage reference vector and the axis α of the coordinate axis α in the α - β coordinate system is:
wherein V is α 、V β The components of the voltage reference vector projected on the coordinate axis alpha and beta are respectively; the modulation degree M corresponding to the voltage reference vector is as follows:
wherein V is dc Is the direct current link voltage of the Z source inverter, |V ref And I is the voltage reference vector amplitude.
In one embodiment, the voltage vector has a duration of action of:
wherein T is s For the switching period of the switch-on and switch-off period,modulation degree, i is sector number; first sector T 1 As a base voltage vector V 1 Time of action, T 2 Is the voltage vector V 2 The action time; second sector T 1 Is the voltage vector V 2 Time of action, T 2 Is the voltage vector V 3 The action time; third sector T 1 Is the voltage vector V 3 Time of action, T 2 Is the voltage vector V 4 The action time; fourth sector T 1 Is the voltage vector V 4 Time of action, T 2 Is the voltage vector V 5 The action time; fifth sector T 1 Is the voltage vector V 5 Time of action, T 2 Is the voltage vector V 6 The action time; sixth sector vector T 1 Is the voltage vector V 6 Time of action, T 2 Is the voltage vector V 1 The action time; t (T) 0 Is the voltage vector V 0 And V 7 The action time;
when the through vectors all occupy zero vector action time, the through duty ratio can be expressed as:
due to zero vector time of action T 0 The pass vector need not be used in its entirety, D is defined below 0 ，
Wherein D is 0 Representing the pass-through time and T 0 Time ratio. When D is 0 When less than 1, the zero vector acting time is not the straight-through vector acting time.
In one embodiment, the method for controlling the insertion of the through vector according to the change of the load power factor specifically includes:
when the resistive load is used, when the power factor angle is phi, the original sector switching sequence is not changed, and the sequence for generating the through vector is delayed backwards by phi angle; when the power factor angle is between 0 and phi, adopting a straight-through bridge arm as a bridge arm inserted by a straight-through vector by adopting a sixth sector in the original ZSVM2 modulation method; and when the power factor angle phi-pi/3 is between, the bridge arm is inserted through by using the first sector of the original ZSVM 2.
In one embodiment, if a resistive-capacitive load is used, the through vector generation position is moved forward accordingly if the current leads the voltage.
In a second aspect, the present application provides a Z-source inverter control device for optimizing switching loss under a variable power factor, the device comprising:
the setting module I is used for setting the switching state and the basic voltage vector of a three-phase bridge arm of the three-phase two-level Z-source inverter;
the second setting module is used for setting a voltage reference vector to be modulated by the three-phase two-level Z source inverter and judging a sector where the voltage reference vector is located;
the vector acting time calculation module is used for acquiring an included angle theta of a voltage reference vector and a coordinate axis alpha in an alpha-beta coordinate system and a modulation degree M corresponding to the voltage reference vector according to the setting of the setting module II, and calculating acting time of the voltage vector and acting time of inserting the direct vector into a zero vector by combining the sector where the voltage reference vector is located;
the switching sequence generating module is used for determining a switching sequence according to the setting of the setting module I, the action time of the voltage vector calculated by the vector action time calculating module, the action time of the direct vector inserted zero vector and the sector where the voltage reference vector is located;
the load power factor module is used for calculating a load power factor by collecting current and voltage of a load alternating-current side;
and the direct vector optimization module is used for controlling the insertion mode of the direct vector according to the change of the load power factor, and determining a switching sequence after loss optimization by combining the switching sequence to realize the control of the Z source inverter under the variable power factor.
In one embodiment, the second setting module includes a reference voltage setting module and a sector judgment module; the reference voltage giving module is used for giving a voltage reference vector to be modulated; the sector judgment module is used for judging the sector where the voltage reference vector is located; the vector acting time calculation module comprises a vector time calculation module and a straight-through time calculation module; the vector acting time calculation module is used for calculating the acting time of the voltage vector by combining the included angle theta of the voltage reference vector and the coordinate axis alpha in the alpha-beta coordinate system and the modulation degree M corresponding to the voltage reference vector and the sector where the voltage reference vector is located; and the straight-through time calculation module is used for calculating the straight-through vector acting time according to the zero vector acting time.
In a third aspect, the present application provides a Z-source inverter control system, which includes a three-phase two-level Z-source inverter module and the Z-source inverter control device for optimizing switching loss under a variable power factor according to any one of the above-mentioned aspects.
The application has the beneficial effects that:
the application is applicable to a Z source/quasi-Z source inverter which does not adopt all bridge arms to carry out a through modulation strategy in one switching period; the application changes the direct insertion mode of the switching sequence in one sector according to the change of the load power factor, and the direct current passing through the switching device is counteracted by the output current of the alternating current side as much as possible, thereby realizing lower switching loss and conduction loss effects.
Drawings
In order to more clearly illustrate the embodiments of the present application or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below.
Fig. 1 is a topological structure diagram of a three-phase two-level voltage type inverter according to the present application;
FIG. 2 is a flowchart of a method for controlling a Z-source inverter with optimized switching loss at a variable power factor according to an embodiment of the present application;
fig. 3 is a schematic diagram showing a comparison of the positions of the switching device through the ac side current and the through current according to the ZSVM2 modulation method and the ZSVM2 modulation method adjusted by the present application;
fig. 4 is a vector sequence diagram (first sector is taken as an example) of an adjusted ZSVM2 modulation method according to an embodiment of the present application;
fig. 5 is a schematic diagram of a bridge arm for generating a through vector according to the adjusted ZSVM2 modulation method according to an embodiment of the present application;
fig. 6 is a schematic structural diagram of a Z-source inverter control system with optimized switching loss under variable power factor according to an embodiment of the present application;
fig. 7 is a graph comparing ZSVM2 strategy and recommended modulation strategy efficiency at different output powers when the Z source inverter control method for switching loss optimization under variable power factor provided by the present application is used;
fig. 8 is an infrared thermal imaging diagram of an IGBT device when the Z source inverter control method for switching loss optimization under a variable power factor provided by the present application is used.
Detailed Description
For the purpose of making the objects, technical solutions and advantages of the embodiments of the present application more apparent, the technical solutions in the embodiments will be clearly and completely described with reference to the accompanying drawings in the embodiments of the present application, and the following embodiments are used to illustrate the present application, but are not intended to limit the scope of the present application.
Fig. 1 shows a three-phase two-level voltage type inverter topology structure according to the present application, and as can be seen from fig. 1, the Z-source inverter topology structure according to the present strategy includes a direct current source E, capacitors C1 and C2 forming a Z-source network topology structure, inductors L1 and L2, and a diode VD 1 The three-phase two-level inverter structure comprises 6 switching tubes with anti-parallel diodes, wherein the 6 switching tubes are respectively marked as a switching tube S1, a switching tube S2, a switching tube S3, a switching tube S4, a switching tube S5 and a switching tube S6.
The state when the upper bridge arm device and the lower bridge arm device are simultaneously opened is defined as sh; the upper bridge arm device is switched on while the lower bridge arm device is switched off, and the lower bridge arm device is switched on while the upper bridge arm device is switched off, and the state is 0. For a Z-source inverter, the a-phase leg current passing situation becomes complex when considering the through vector. Through current is subjected to the previous state I ac Is a function of (a) and (b). When the state is from (100 to sh 00), the current passing through the upper bridge arm is I under the resistive load sh The current passing through the lower bridge arm is I sh -I ac . The through current passing through the upper bridge arm is as follows:
as is clear from the above equation, the current passing through the upper arm or lower arm switching device is affected by the ac side output current at the switching time. The current that the switching device passes at the switching instant is defined as the switching current. In steady state operation, through current I sh Is basically unchanged. The larger ac side output current may cause either the upper leg device or the lower leg device to pass a lower through current. The lower through current reduces not only the switching losses when the switching state is switched, but also the conduction losses when the state is maintained. When the power factor of the load changes, the waveform of the output current at the alternating current side can relatively move with the waveform of the output alternating voltage along with the change of the power factor. Traditional Z-source inverter modulation methodThe position of the through vector generation corresponds to the output voltage of the alternating current side, and the phase shift affects the phase relationship between the output current of the alternating current side and the through current. Based on the findings, the application provides a Z source inverter control method under a variable power factor, and the modulation method is mainly based on a space vector modulation method. As shown in fig. 2, the method comprises the following specific implementation steps:
step S100: setting a switching state and a basic voltage vector of a bridge arm of the three-phase two-level Z-source inverter;
in the embodiment of the application, setting the switching state of a three-phase bridge arm of a three-phase two-level Z-source inverter comprises the following steps:
when the switching state is 1, the upper bridge arm switching device is turned on, and the lower bridge arm switching device is turned off;
when the switching state is 0, the upper bridge arm switching device is closed, and the lower bridge arm switching device is opened;
when the switching state is sh, the upper bridge arm switching device and the lower bridge arm switching device are simultaneously turned on.
Specifically, when the switching state of the a-phase bridge arm of the three-phase two-level inverter is set to be 1, the upper bridge arm switching device S1 is turned on, the lower bridge arm switching device S2 is turned off, and when the switching state of the three-phase two-level inverter is set to be 0, the upper bridge arm switching device S1 is turned off, and the lower bridge arm switching device S2 is turned on. And the definition of the state of the bridge arm of the B-phase and C-phase switch and the opening condition of the device can be known in the same way. The Z source/quasi-Z source inverter has a pass-through state. When the A-phase bridge arm switch state is set to be sh, the upper bridge arm switch device S1 and the lower bridge arm switch device S2 are simultaneously turned on. And similarly, the on condition of the B-phase and C-phase bridge arm through state devices can be set.
Further, 8 basic voltage vectors are obtained according to the switching states of the three-phase bridge arms of the three-phase two-level inverter and are respectively marked as voltage vectors V0, V1, V2, V3, V4, V5, V6 and V7. The specific states of the switch state combinations (a-phase switch state, B-phase switch state, C-phase switch state) corresponding to the 8 base voltage vectors are as follows:
the switching state corresponding to the voltage vector V0 is (000);
the corresponding switch state of the voltage vector V1 is (100);
the switch state corresponding to the voltage vector V2 is (110);
the switching state corresponding to the voltage vector V3 is (010);
the switch state corresponding to the voltage vector V4 is (011);
the switch state corresponding to the voltage vector V5 is (001);
the corresponding switch state of the voltage vector V6 is (101);
the switch state corresponding to the voltage vector V7 is (111);
where V0 and V7 are zero vectors and the other six voltage vectors are non-zero vectors. Any bridge arm of the Z-source inverter can form a through vector Vsh by adopting a through state. The application adopts a single-phase straight-through mode, namely, only one phase bridge arm is in a straight-through state. The switch state combinations corresponding to the pass vector Vsh include: (shXX), (XshX) and (XXsh). Wherein X represents any 1 or 0 state. sh represents a through state in which the upper and lower switching tubes are simultaneously turned on.
Step S200, setting a voltage reference vector to be modulated by a three-phase two-level Z source inverter, and judging a sector where the voltage reference vector is located;
in the embodiment of the application, a voltage reference vector to be modulated by a three-phase two-level Z source inverter is set, and the sector where the voltage reference vector is located is judged; the method specifically comprises the following steps:
on an alpha-beta axis static coordinate system, starting from the alpha axis direction, dividing the alpha axis direction into 6 sectors of 60 degrees in the anticlockwise direction, and sequentially naming each sector as a sector 1-a sector 6 according to the serial number in the anticlockwise direction;
projecting the voltage reference vector on the coordinate axis alpha and beta, and respectively marking the components as the voltage reference vector alpha axis component V α And a voltage reference vector beta axis component V β ；
According to the alpha-axis component V of the voltage reference vector α And a voltage reference vector beta axis component V β And judging the sector where the voltage reference vector is located.
Specifically, on the α - β axis stationary coordinate system, starting from the α -axis direction, the counterclockwise direction is divided into 6 sectors of 60 ° and follows the counterclockwise directionThe direction numbers are sequentially named as sectors 1 to 6; let the voltage reference vector to be modulated of the three-phase two-level inverter be V ref Reference vector V of voltage ref Projecting the coordinate axis alpha and beta, the components of which are respectively recorded as the voltage reference vector alpha axis component V α And a voltage reference vector beta axis component V β According to the alpha-axis component V of the voltage reference vector α And a voltage reference vector beta axis component V β Performing a voltage reference vector V ref And judging the sector where the mobile terminal is located. Voltage reference vector V ref The actual target voltage output from the ac side of the inverter is generally known.
Step S300, calculating the acting time of the voltage vector and the acting time of inserting the direct vector into the zero vector by combining the included angle theta of the voltage reference vector and the coordinate axis alpha in the alpha-beta coordinate system and the modulation degree M corresponding to the voltage reference vector and the sector where the voltage reference vector is positioned;
further, voltage reference vector V ref Included angle θ, voltage reference vector V with axis α of coordinate axis in α - β coordinate system ref The corresponding modulation M is calculated as follows:
wherein V is α 、V β The components of the voltage reference vector projected on the coordinate axis alpha and beta are respectively;
wherein V is dc Is the direct current link voltage of the Z source inverter, |V ref And I is the voltage reference vector amplitude.
According to the volt-second balance principle, the acting time of the vector is the time for keeping the corresponding three-phase bridge arm switch state.
Further, the voltage vector time may be calculated by the following formula:
wherein T is s For the switching period of the switch-on and switch-off period,modulation degree, i is sector number; first sector T 1 As a base voltage vector V 1 Time of action, T 2 Is the voltage vector V 2 The action time; second sector T 1 Is the voltage vector V 2 Time of action, T 2 Is the voltage vector V 3 The action time; third sector T 1 Is the voltage vector V 3 Time of action, T 2 Is the voltage vector V 4 The action time; fourth sector T 1 Is the voltage vector V 4 Time of action, T 2 Is the voltage vector V 5 The action time; fifth sector T 1 Is the voltage vector V 5 Time of action, T 2 Is the voltage vector V 6 The action time; sixth sector vector T 1 Is the voltage vector V 6 Time of action, T 2 Is the voltage vector V 1 The action time; t (T) 0 Is the voltage vector V 0 And V 7 The action time.
When the through vectors all occupy zero vector active time, the through duty cycle can be expressed as:
due to zero vector time of action T 0 The pass vector need not be used in its entirety, D is defined below 0 ，
Wherein D is 0 Representing the pass-through time and T 0 Time ratio. When D is 0 When less than 1, the zero vector acting time is not the straight-through vector acting time.
Step S400: determining a switching sequence according to the set switching state, a basic voltage vector, a vector acting time and a direct vector inserting zero vector acting time and a sector where a voltage reference vector is located;
step S500: calculating a load power factor by collecting current and voltage of a load alternating-current side;
step S600: and controlling the insertion mode of the through vector according to the change of the load power factor, and determining a switching sequence after loss optimization by combining the switching sequence to realize the control of the Z source inverter under the variable power factor.
In the embodiment of the application, the insertion mode of the through vector is controlled according to the change of the load power factor, and the method specifically comprises the following steps:
when the resistive load is used, when the power factor angle is phi, the original sector switching sequence is not changed, and the sequence for generating the through vector is delayed backwards by phi angle;
if the power factor angle is between 0 and phi, adopting a straight-through bridge arm as a bridge arm inserted by a straight-through vector for a sixth sector in the original ZSVM2 modulation method;
if the power factor angle phi-pi/3 is between, the bridge arm is inserted through by using the first sector of the original ZSVM 2;
if a resistive-capacitive load is used, when the power factor angle is phi, the original sector switching sequence is not changed, and the sequence for generating the through vector is moved forwards by phi.
Specifically, the following describes the adjusted ZSVM2 modulation method according to the present application by taking ZSVM2 as an example. The ZSVM2 modulation method is realized by inserting a direct vector on the basis of a traditional SVPWM modulation strategy of an inverter. The pass vector on time occupies zero vector time. The ZSVM2 modulation method does not change its pass-through insertion position due to external parameters. The direct vector insertion mode of the Z source inverter control method for optimizing the switching loss changes according to the load power factor, and the purpose of optimizing the switching loss can be achieved.
The switch on time and sequence in the first sector are shown in the following table:
in the ZSVM2 modulation method, the through vector is inserted only among the zero vectors. At this time, the straight-through vector is used by the A-phase bridge arm and the C-phase bridge arm in the first sector. If the through vector is to be changed along with the power factor angle, the through vector needs to be inserted by using the B-phase bridge arm. With this control method, it is possible to achieve that the relative phase relationship of the through current and the ac side current through the switching device is maintained at a power factor of 1, as shown in fig. 3. And when the power factor is 1, the alternating-current side current can offset the most through current, so that the optimal loss effect can be realized. As shown in fig. 4, when the power factor angle isWhen then atThe sixth sector in the original ZSVM2 modulation is adopted to use a straight-through bridge arm as a bridge arm inserted by a straight-through vectorThe bridge arm is inserted through by using the first sector of the original ZVM 2.
The following describes a direct vector insertion mode in the adjustment of the ZSVM2 modulation method according to the present application based on the ZSVM2 modulation method. In the first sectorThe switching sequence and on-time in the range are shown in the following table:
when the power factor angle of the resistive load isWhen the original sector switch sequence is not changed, the sequence for generating the through vector is delayed backward by +.>Angle. At this time, the ac side current can exactly cancel the maximum through current, and thus the minimum switching loss can be generated. For vector modulation, it is easy to generate the pass vector and the vector switching time separately. Taking the first sector as an example, when the power factor angle is between 0-pi/3, will +.>The straight-through vector between the two phases generates a bridge arm which is changed from the original A phase and the C phase into the A phase and the B phase in the sector six. At this time->The straight-through vector between the two leads to the unchanged bridge arm. When the power factor is further increased to between pi/3 and 2 pi/3, the ratio of +.>The bridge arm is produced by direct connection between the two phases B and C, and +.>The straight-through between the two is used for generating a bridge arm with A phase and B phase as shown in figure 5. The same can be generalized to other power factor angles for correction. The shift of the through vector generation position does not necessarily just lag the original modulation strategy. If a resistive-capacitive load is used, the current leads the voltage and the through vector generation position is also moved forward accordingly.
In addition, the present application determines the generation region of the through vector based on the phase of the ac output current. The insertion position of the direct vector of the conventional Z-source inverter modulation strategy is generally determined by the output voltage of the alternating current side. The method fully utilizes the offset effect of the output current of the alternating current side on the through current by optimizing the phase relation between the through current passing through the switching device and the output current of the alternating current side, so that the total average current value passing through the device in the through state is reduced. Thereby reducing the switching loss of the device. Meanwhile, the current passing through the device in the through state is reduced, so that the conduction loss is reduced by a small amount.
The application has wide application range and can be used for a modulation method of ZSVM2, ZSVM1 and the like which does not use all bridge arms to generate a direct vector in one switching period. When all bridge arms generate through vectors in one switching period, phase conversion between the through current generation area and the alternating-current side output current cannot be realized. Therefore, optimization of loss cannot be achieved. The switching loss and the conduction loss generated by the switching device under the load working condition that the power factor is not 1 can be effectively reduced.
In one embodiment, the simulation platform is implemented using matlab/Simulink in conjunction with PLECS. Simulated load power factor pf=0.866, d 0 The modulation M was 1,0.9,0.8,0.7,0.65,0.6 for each of=0.85, and the corresponding output powers were 141.32w,165.81w,205.57w,283.5w,352.83w,470.34w, respectively. When pf=0.966, r=12.5Ω, l=10.67 mH, and the corresponding output powers are 153.72w,180.96w,225.37w,380.78w,383.02w,500w, respectively. As shown in fig. 7, the ZSVM2 strategy is given in comparison with the recommended modulation strategy efficiency at different output powers. As can be seen from fig. 7, the modulation strategy of the present application can improve inverter efficiency, and efficiency optimization is more pronounced as the power factor is smaller. In addition, the embodiment also verifies the effectiveness of the modulation method adopted by the application through a thermal imager. As can be seen from fig. 8, the temperature of the IGBT device is reduced by 1 to 3 degrees celsius when using the recommended modulation, which can reduce device loss.
In one embodiment, a Z-source inverter control device for optimizing switching loss under variable power factor is provided, and referring to fig. 6, the device includes:
the setting module I is used for setting the switching state and the basic voltage vector of a three-phase bridge arm of the three-phase two-level Z-source inverter;
the second setting module is used for setting a voltage reference vector to be modulated by the three-phase two-level Z source inverter and judging a sector where the voltage reference vector is located;
the vector acting time calculation module is used for acquiring an included angle theta of a voltage reference vector and a coordinate axis alpha in an alpha-beta coordinate system and a modulation degree M corresponding to the voltage reference vector according to the setting of the setting module II, and calculating acting time of the voltage vector and acting time of inserting the direct vector into a zero vector by combining the sector where the voltage reference vector is located;
the switching sequence generating module is used for determining a switching sequence according to the setting of the setting module I, the action time of the voltage vector calculated by the vector action time calculating module, the action time of the direct vector inserted zero vector and the sector where the voltage reference vector is located;
the load power factor module is used for calculating a load power factor by collecting current and voltage of a load alternating-current side;
and the direct vector optimization module is used for controlling the insertion mode of the direct vector according to the change of the load power factor, and determining a switching sequence after loss optimization by combining the switching sequence to realize the control of the Z source inverter under the variable power factor.
Further, the second setting module comprises a reference voltage giving module and a sector judging module; a reference voltage giving module for giving a voltage reference vector to be modulated; the sector judgment module is used for judging the sector where the voltage reference vector is located; the vector acting time calculation module comprises a vector time calculation module and a straight-through time calculation module; the vector acting time calculation module is used for calculating the acting time of the voltage vector by combining the included angle theta of the voltage reference vector and the coordinate axis alpha in the alpha-beta coordinate system and the modulation degree M corresponding to the voltage reference vector and the sector where the voltage reference vector is located; and the straight-through time calculation module is used for calculating the straight-through vector acting time according to the zero vector acting time.
It should be noted that, the Z source inverter control device for optimizing switching loss under a variable power factor and the Z source inverter control method for optimizing switching loss under a variable power factor provided in the foregoing embodiments belong to the same concept, which embody the implementation process and are detailed in a Z source inverter control method for optimizing switching loss under a variable power factor, and are not described herein again.
In one embodiment, the application provides a Z-source inverter control system, as shown in fig. 6, which comprises a three-phase two-level Z-source inverter module and the Z-source inverter control device for optimizing switching loss under any one of the variable power factors. The Z source inverter control device for optimizing the switching loss under the variable power factor refers to the above description, and is not repeated here.
It should be understood that the described embodiments are merely some, but not all, embodiments of the application. All other embodiments, which can be made by those skilled in the art based on the embodiments of the application without making any inventive effort, are intended to be within the scope of the application.
In the description provided herein, numerous specific details are set forth. However, it is understood that embodiments of the application may be practiced without these specific details. In some instances, well-known methods, structures and techniques have not been shown in detail in order not to obscure an understanding of this description.
The foregoing description is only illustrative of the preferred embodiment of the present application, and is not to be construed as limiting the application, but is to be construed as limiting the application to any simple modification, equivalent variation and variation of the above embodiments according to the technical matter of the present application without departing from the scope of the application.

Claims (10)

1. The Z source inverter control method for optimizing the switching loss under the variable power factor is characterized by comprising the following steps of:
setting a switching state and a basic voltage vector of a bridge arm of the three-phase two-level Z-source inverter;
setting a voltage reference vector to be modulated by a three-phase two-level Z source inverter, and judging a sector where the voltage reference vector is located;
calculating the acting time of the voltage vector and the acting time of inserting the direct vector into the zero vector by combining the included angle theta of the voltage reference vector and the coordinate axis alpha in the alpha-beta coordinate system and the modulation M corresponding to the voltage reference vector and the sector where the voltage reference vector is positioned;
determining a switching sequence according to the set switching state, a basic voltage vector, a vector acting time and a direct vector inserting zero vector acting time and a sector where a voltage reference vector is located;
calculating a load power factor by collecting current and voltage of a load alternating-current side;
and controlling the insertion mode of the through vector according to the change of the load power factor, and determining a switching sequence after loss optimization by combining the switching sequence to realize the control of the Z source inverter under the variable power factor.
2. The method for controlling a Z-source inverter with optimized switching loss under a variable power factor according to claim 1, wherein the setting the switching state of the three-phase two-level Z-source inverter leg comprises:
when the switching state is 1, the upper bridge arm switching device is turned on, and the lower bridge arm switching device is turned off;
when the switching state is 0, the upper bridge arm switching device is closed, and the lower bridge arm switching device is opened;
when the switching state is sh, the upper bridge arm switching device and the lower bridge arm switching device are simultaneously turned on.
3. The control method for the Z-source inverter with optimized switching loss under the variable power factor according to claim 2, wherein 8 basic voltage vectors are obtained according to the switching states of the three-phase two-level Z-source inverter bridge arms and are respectively recorded as voltage vectors V 0 、V 1 、V 2 、V 3 、V 4 、V 5 、V 6 And V 7 The method comprises the steps of carrying out a first treatment on the surface of the The specific states of the switch state combination A phase switch state, the B phase switch state and the C phase switch state corresponding to the 8 basic voltage vectors are as follows:
the switching state corresponding to the voltage vector V0 is (000);
the corresponding switch state of the voltage vector V1 is (100);
the switch state corresponding to the voltage vector V2 is (110);
the switching state corresponding to the voltage vector V3 is (010);
the switch state corresponding to the voltage vector V4 is (011);
the switch state corresponding to the voltage vector V5 is (001);
the corresponding switch state of the voltage vector V6 is (101);
the switch state corresponding to the voltage vector V7 is (111);
wherein V is 0 And V 7 The other six voltage vectors are non-zero vectors;
any bridge arm of the Z-source inverter can form a through vector Vsh by adopting a through state, and a switch state combination corresponding to the through vector Vsh comprises: (shXX), (XshX) and (xxxh); wherein X represents any 1 or 0 state, and sh represents a straight-through state that the upper bridge arm switch tube and the lower bridge arm switch tube are simultaneously conducted.
4. The method for controlling a Z-source inverter with optimized switching loss under a variable power factor according to claim 1, wherein the determining the sector in which the voltage reference vector is located includes:
on an alpha-beta axis static coordinate system, starting from the alpha axis direction, dividing the alpha axis direction into 6 sectors of 60 degrees in the anticlockwise direction, and sequentially naming each sector as a sector 1-a sector 6 according to the serial number in the anticlockwise direction;
projecting the voltage reference vector on the coordinate axis alpha and beta, and respectively marking the components as the voltage reference vector alpha axis component V α And a voltage reference vector beta axis component V β ；
According to the alpha-axis component V of the voltage reference vector α And a voltage reference vector beta axis component V β And judging the sector where the voltage reference vector is located.
5. The method for controlling a Z-source inverter according to claim 4, wherein an included angle θ between the voltage reference vector and an α -axis of a coordinate axis in the α - β coordinate system is:
wherein V is α 、V β The components of the voltage reference vector projected on the coordinate axis alpha and beta are respectively;
the modulation degree M corresponding to the voltage reference vector is as follows:
wherein V is dc Is the direct current link voltage of the Z source inverter, |V ref And I is the voltage reference vector amplitude.
6. The method for controlling a Z-source inverter with switching loss optimization at a variable power factor according to claim 5, wherein the duration of the voltage vector is:
wherein T is s For the switching period of the switch-on and switch-off period,modulation degree, i is sector number; first sector T 1 As a base voltage vector V 1 Time of action, T 2 Is the voltage vector V 2 The action time; second sector T 1 Is the voltage vector V 2 Time of action, T 2 Is the voltage vector V 3 The action time; third sector T 1 Is the voltage vector V 3 Time of action, T 2 Is the voltage vector V 4 The action time; fourth sector T 1 Is the voltage vector V 4 Time of action, T 2 Is the voltage vector V 5 The action time;fifth sector T 1 Is the voltage vector V 5 Time of action, T 2 Is the voltage vector V 6 The action time; sixth sector vector T 1 Is the voltage vector V 6 Time of action, T 2 Is the voltage vector V 1 The action time; t (T) 0 Is the voltage vector V 0 And V 7 The action time;
when the through vectors all occupy zero vector action time, the through duty ratio can be expressed as:
due to zero vector time of action T 0 The pass vector need not be used in its entirety, D is defined below 0 ，
Wherein D is 0 Representing the pass-through time and T 0 Time ratio. When D is 0 When less than 1, the zero vector acting time is not the straight-through vector acting time.
7. The method for controlling a Z-source inverter with optimized switching loss under a variable power factor according to claim 1, wherein the inserting mode of the through vector is controlled according to the change of the load power factor, specifically comprising:
when using resistive load, the power factor angle isWhen the original sector switch sequence is not changed, the sequence for generating the through vector is delayed backward by +.>An angle;
if the power factor angle is between 0 and phi, adopting a straight-through bridge arm as a bridge arm inserted by a straight-through vector for a sixth sector in the original ZSVM2 modulation method;
if at its power factor angleDuring the process, the bridge arm is directly inserted by using the first sector of the original ZSVM 2;
if a resistive-capacitive load is used, the power factor angle isWhen the original sector switch sequence is not changed, the sequence for generating the through vector is moved forward +.>Angle.
8. A Z source inverter control device for switching loss optimization under a variable power factor, the device comprising:
the setting module I is used for setting the switching state and the basic voltage vector of a three-phase bridge arm of the three-phase two-level Z-source inverter;
the second setting module is used for setting a voltage reference vector to be modulated by the three-phase two-level Z source inverter and judging a sector where the voltage reference vector is located;
the vector acting time calculation module is used for acquiring an included angle theta of a voltage reference vector and a coordinate axis alpha in an alpha-beta coordinate system and a modulation degree M corresponding to the voltage reference vector according to the setting of the setting module II, and calculating acting time of the voltage vector and acting time of inserting the direct vector into a zero vector by combining the sector where the voltage reference vector is located;
the switching sequence generating module is used for determining a switching sequence according to the setting of the setting module I, the action time of the voltage vector calculated by the vector action time calculating module, the action time of the direct vector inserted zero vector and the sector where the voltage reference vector is located;
the load power factor module is used for calculating a load power factor by collecting current and voltage of a load alternating-current side;
and the direct vector optimization module is used for controlling the insertion mode of the direct vector according to the change of the load power factor, and determining a switching sequence after loss optimization by combining the switching sequence to realize the control of the Z source inverter under the variable power factor.
9. The variable power factor switching loss optimized Z-source inverter control device of claim 8, wherein: the second setting module comprises a reference voltage giving module and a sector judging module; the reference voltage giving module is used for giving a voltage reference vector to be modulated; the sector judgment module is used for judging the sector where the voltage reference vector is located; the vector acting time calculation module comprises a vector time calculation module and a straight-through time calculation module; the vector acting time calculation module is used for calculating the acting time of the voltage vector by combining the included angle theta of the voltage reference vector and the coordinate axis alpha in the alpha-beta coordinate system and the modulation degree M corresponding to the voltage reference vector and the sector where the voltage reference vector is located; and the straight-through time calculation module is used for calculating the straight-through vector acting time according to the zero vector acting time.
10. A Z source inverter control system, characterized by: the system comprises a three-phase two-level Z-source inverter module and the Z-source inverter control device for optimizing the switching loss under the variable power factor according to any one of claims 8-9.
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