CN116683662A - Two-way output independent adjustable wireless power supply device based on three-switch inverter - Google Patents
Two-way output independent adjustable wireless power supply device based on three-switch inverter Download PDFInfo
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- CN116683662A CN116683662A CN202310967094.9A CN202310967094A CN116683662A CN 116683662 A CN116683662 A CN 116683662A CN 202310967094 A CN202310967094 A CN 202310967094A CN 116683662 A CN116683662 A CN 116683662A
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
- H02J50/40—Circuit arrangements or systems for wireless supply or distribution of electric power using two or more transmitting or receiving devices
- H02J50/402—Circuit arrangements or systems for wireless supply or distribution of electric power using two or more transmitting or receiving devices the two or more transmitting or the two or more receiving devices being integrated in the same unit, e.g. power mats with several coils or antennas with several sub-antennas
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
- H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
- H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
- H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Computer Networks & Wireless Communication (AREA)
- Inverter Devices (AREA)
Abstract
The application relates to the technical field of wireless power transmission, and discloses a two-way output independent adjustable wireless power supply device based on a three-switch inverter. The high-frequency inverter in the electric energy transmitting end is formed by stacking three switching tubes in series, two independently adjustable square wave voltage excitation can be generated, and the voltage stress on each switching tube is input power supply voltage, so that the voltage stress of the switching tube and the system cost are reduced. In addition, the two paths of control duty ratios are regulated through closed loop feedback, and the control signal of the middle switching tube can be generated by utilizing a NAND logic gate, so that the implementation is simple. By means of the LC auxiliary soft switching network, soft switching in the full load range can be realized, switching loss is effectively reduced, and system transmission efficiency is improved. Meanwhile, the application is beneficial to modularization realization, the three-switch inverter is packaged into a single sub-power module, and in order to realize any even-number power transmission, only n sub-power modules are required to be connected with an input power supply in parallel.
Description
Technical Field
The application relates to the technical field of wireless power transmission, in particular to a two-way output independent adjustable wireless power supply device based on a three-switch inverter.
Background
In recent years, wireless power transmission technology is fast becoming a current research hot spot due to the characteristics of safety, convenience, flexibility and more reliable than plug-in charging under severe working conditions, and has been widely applied to industrial production and daily life. In wireless power transfer systems, it is often desirable to power multiple devices simultaneously to maximize the utilization of the transferred energy. However, multiple transmit coils require an equivalent number of high frequency inverters to generate current to energize the injection coils, resulting in a greater number of switches, increasing system cost and volume.
The common inverter of the wireless power transmission system at the present stage mainly comprises a full-bridge structure, a half-bridge structure and a single-tube structure. The full-bridge inverter needs four switching tubes, the number of the required switching tubes is the largest, and the power transmission capability is the largest. The square wave excited non-zero voltage generated by the half-bridge inverter has only half a period, so the power transmission capacity of the half-bridge inverter is only half of that of the full-bridge inverter. The voltage stress of the switching tube with the two topological structures is input voltage. The single-tube inverter is commonly provided with a Class-E inverter, and the conversion of direct-current voltage and alternating-current voltage can be realized by only one switching tube, but the voltage stress on the switching tube is very high and can reach 2-4 times of the input voltage, so that the difficulty in selecting the type of the switching device is increased, and the cost and the volume of the system are increased. In addition, the inverter structure can only realize single-path output and cannot meet the requirement of multi-path power transmission.
Disclosure of Invention
In view of the above problems, the present application aims to provide a two-way output independent adjustable wireless power supply device based on a three-switch inverter, which can reduce the number of switching tubes while meeting low voltage stress, reduce the voltage stress of the switching tubes and the system cost, and realize high-efficiency and high-power density transmission of the system. The technical proposal is as follows: a two-way output independent adjustable wireless power supply device based on a three-switch inverter comprises an electric energy transmitting end and an electric energy receiving end; wherein:
the electric energy transmitting end comprises a direct-current power supply, a three-switch inverter and a primary side series compensation capacitorC p1 AndC p2 primary side transmitting coilL p1 AndL p2 an LC-assisted soft switching network; the three-switch inverter comprises three switching tubes S with anti-parallel diodes 1 ~S 3 The method comprises the steps of carrying out a first treatment on the surface of the Switch tube S 1 Is connected to the positive electrode of the DC power supply, and a switching tube S 1 Is connected to the source of the switching tube S 2 Drain electrode of (d), switch tube S 2 Is connected to the source of the switching tube S 3 Drain electrode of (d), switch tube S 3 Is connected to the negative pole of the dc power supply.
The application is formed by stacking three switching tubes in series, can generate two independently adjustable square wave voltage excitations, and the voltage stress on each switching tube is the input power supply voltage, thereby reducing the voltage stress of the switching tube and the system cost.
The LC auxiliary soft switching network comprises an inductorL a And a capacitorC a The two are connected in series and then connected in parallel with a switch tube S 2 Is provided. The application can realize soft switching in the full load range by means of the auxiliary LC auxiliary soft switching network, effectively reduce switching loss and improve system transmission efficiency.
Primary side series compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after being connected in series are respectively connected to a switch tube S 1 Source and switching tube S of (2) 3 A source of (a); primary side series compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after being connected in series are respectively connected to a switch tube S 2 Source and switching tube S of (2) 3 Is a source of (c).
The electric energy receiving end comprises a secondary side series compensation capacitorC s1 AndC s2 secondary side receiving coilL s1 AndL s2 rectifier Re 1 And rectifier Re 2 The method comprises the steps of carrying out a first treatment on the surface of the Secondary series compensation capacitorC s1 And a secondary receiving coilL s1 The two ports after the series connection are connected to a rectifier Re 1 Rectifier Re 1 An output voltage of the power receiving terminal is outputted from the output terminal of (a)U o1 The method comprises the steps of carrying out a first treatment on the surface of the Secondary series compensation capacitorC s2 And a secondary receiving coilL s2 The two ports after the series connection are connected to a rectifier Re 2 Rectifier Re 2 Outputs another output voltage of the power receiving terminalU o2 。
Primary side only transmitting coilL p1 And a secondary receiving coilL s1 Between and primary side transmitting coilL p2 And a secondary receiving coilL s2 There is coupling between them, and mutual inductance is respectivelyM 1 AndM 2 . Specifically, primary side transmitting coilL p1 And primary side transmitting coilL p2 No cross coupling and primary side transmitting coilL p1 And a secondary receiving coilL s2 No cross coupling and primary side transmitting coilL p2 And a secondary receiving coilL s1 No cross coupling and secondary side receiving coilL s1 And a secondary receiving coilL s2 Cross-coupling between each other. Only primary transmitting coils are considered in the systemL p1 And a secondary receiving coilL s1 Mutual inductance betweenM 1 And primary side transmitting coilL p2 And a secondary receiving coilL s2 Mutual inductance betweenM 2 . The two paths of square wave excitation voltages are independently adjustable, the cross coupling effect is avoided, the voltage gain adjustment range is wide, and the wide voltage change occasions such as battery loads can be met.
Further, the primary side is connected in series with a compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Drain and source of (a), while the primary side is in series with the compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after the series connection are unchanged.
Or the primary side is connected in series with a compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Drain electrode of (d) and switching tube S 2 At the same time, the primary side is connected in series with a compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Source and switching tube S of (2) 3 Is a source of (c).
Furthermore, the parameter design of the wireless power supply device meets the following conditions:
wherein:ωfor the operating angular frequency of the system,f s switching frequency for a three-switch inverter;L p1 andL p2 the inductance values of the two primary side transmitting coils are respectively;C p1 andC p2 the capacitance values of the two primary-side series compensation capacitors are respectively;L s1 andL s2 the inductance values of the two pairs of side receiving coils are respectively;C s1 andC s2 the capacitance values of the compensation capacitors are respectively connected in series with the two secondary sides.
Further, the switch tube S 1 ~S 3 The gate signals of (2) are respectively denoted as G 1 ~G 3 The corresponding duty ratio signals are respectively D 1 ~D 3 The method comprises the steps of carrying out a first treatment on the surface of the Gate signal G 2 Falling edge of (1) and gate signal G 1 Has dead time DT1 at the rising edge of (a), gate signal G 3 Falling edge of (1) and gate signal G 2 Has dead time DT2 at the rising edge of (2), gate signal G 1 Falling edge of (1) and gate signal G 3 Dead time DT3 exists at the rising edge of (a); gate signal G 2 Is composed of G 1 And G 3 Two control signals are generated by NAND logic gate, duty cycle signalD 1 And duty cycle signalD 3 The variation ranges of (1) all belong to [0.5,1 ]]。
Further, the output voltageU o1 By changing the switching tube S 1 Duty cycle signal of (2) is regulated to output voltageU o2 By changing the switching tube S 3 Is adjusted by the duty cycle signal of (a); output voltageU o1 And output voltageU o2 The digital signal is converted by a differential sampling circuit and an analog-to-digital conversion circuit and is sent to a transmitting end by a wireless communication module, and a corresponding feedback quantity is generated into a switching tube S by a proportional-integral compensator 1 And a switch tube S 3 Duty cycle signal of (2)D 1 And duty cycle signalD 3 。
The size of the two paths of control duty ratio signals is regulated through closed loop feedback, and the control signal of the middle switching tube can be generated by utilizing a NAND logic gate, so that the implementation is simple.
Further, the switching tube S 2 The full-load range soft switch of the control circuit is realized through an LC auxiliary soft switch network; inductanceL a Value determining switch tube S 2 Soft switching range, capacitance of (2)C a For blocking DC and preventing DC bias from causing inductanceL a Magnetically saturating; inductanceL a The smaller the value is, the wider the soft switching range is, but the peak-peak value of the flowing inductive current is increased, and the conduction loss is increased; conversely, inductanceL a The larger the value is, the smaller the peak-peak value of the flowing inductive current is, the conduction loss is also reduced correspondingly, but the switching tube S 2 The soft switching range of (a) is also narrowed.
Further, the primary side transmitting coilL p1 AndL p2 coil adopting polarized structure and secondary receiving coilL s1 AndL s2 a coil with a non-polarized structure is adopted; or primary side transmitting coilL p1 AndL p2 coil adopting non-polarized structure and secondary receiving coilL s1 AndL s2 a coil with a polarized structure is used. If both sets of coils are polarized or non-polarized, cross-coupling mutual inductance can be eliminated by increasing the horizontal spacing between the two sets of coils.
Further, the coil of the non-polarized structure comprises a square coil and a round coil; the coils of the polarized structure comprise DD coil structures, namely two non-polarized coils are connected in series in opposite phases.
Compared with the prior art, the application has the beneficial effects that:
1. cost advantage: compared with the traditional full-bridge inverter and half-bridge inverter structure, the application is formed by stacking three switching tubes in series, can generate two independently adjustable square wave voltage excitations, and the voltage stress on each switching tube is the input power supply voltage, so that the voltage stress of the switching tube and the system cost are reduced.
2. Performance advantage: the size of the two paths of control duty ratio signals is regulated through closed loop feedback, the control signal of the middle switching tube can be generated by using a NAND logic gate, and the implementation method is simple; by means of an auxiliary LC auxiliary soft switching network, soft switching in a full load range can be realized, so that switching loss is effectively reduced, and system transmission efficiency is improved; the two paths of square wave excitation voltages are independently adjustable, the cross coupling effect is avoided, the voltage gain adjustment range is wide, and the wide voltage change occasions such as battery loads can be met.
3. Modularization, easy integration: the scheme provided by the application is beneficial to modularization realization, and the three-switch inverter can be packaged into a single sub-power module; to achieve any even (2 n) power transfer, only n sub-power modules need to be connected in parallel with the input voltage source.
Drawings
Fig. 1 is a schematic diagram of a two-way output independent adjustable wireless power supply device based on a three-switch inverter.
Fig. 2 (a) is a schematic diagram showing equivalent variations of different topologies of the three-switch inverter of example 1 of the present application.
Fig. 2 (b) is a schematic diagram showing equivalent variations of different topologies of the three-switch inverter of example 2 of the present application.
Fig. 2 (c) is a schematic diagram showing equivalent variations of different topologies of the three-switch inverter of example 3 of the present application.
Fig. 3 is a schematic diagram of an ac equivalent circuit of the two-output independently adjustable wireless power supply device based on the three-switch inverter of the present application.
Fig. 4 (a) is a schematic diagram of modal analysis of a two-output independently adjustable wireless power supply device based on a three-switch inverter according to the present application: modality 1.
Fig. 4 (b) is a schematic diagram of modal analysis of a two-output independently adjustable wireless power supply device based on a three-switch inverter according to the present application: modality 2.
Fig. 4 (c) is a schematic diagram of modal analysis of a two-output independently adjustable wireless power supply device based on a three-switch inverter according to the present application: modality 3.
Fig. 5 is a schematic diagram of key waveforms of the two-output independent adjustable wireless power supply system based on the three-switch inverter.
Fig. 6 is a control block diagram of a two-way output independently adjustable wireless power supply system based on a three-switch inverter of the present application.
Fig. 7 is a schematic diagram of modular integration of a two-way output independently adjustable wireless power supply device based on a three-switch inverter.
Detailed Description
The application will now be described in further detail with reference to the drawings and to specific examples.
FIG. 1 shows a schematic diagram of a two-way output independently adjustable wireless power supply device based on a three-switch inverter, comprising an electric energy transmitting end and an electric energy receiving end; wherein the electric energy transmitting end comprises a direct-current power supply, a three-switch inverter and a primary side series compensation capacitorC p1 AndC p2 primary side transmitting coilL p1 AndL p2 LC-assisted soft switching networks. The three-switch inverter consists of three switching tubes S with anti-parallel diodes 1 ~S 3 Constructing; switch tube S 1 The drain electrode of (2) is connected with the positive electrode of the direct current power supply, and the switch tube S 1 Source electrode of (C) and switch tube S 2 Is connected with the drain electrode of the switch tube S 2 Source electrode of (C) and switch tube S 3 Is connected with the drain electrode of the switch tube S 3 The source electrode of the capacitor is connected with the negative electrode of the direct current power supply; LC auxiliary soft switching network is connected in parallel to switching tube S 2 Both ends; primary side series compensation capacitorC p1 And former(s)Side transmitting coilL p1 The two ports after being connected in series are respectively connected with a switch tube S 1 Source and switching tube S of (2) 3 Is connected with the source of the voltage of the two portsu AB1 The method comprises the steps of carrying out a first treatment on the surface of the Primary side series compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after being connected in series are respectively connected with S 2 Source and S of (2) 3 Is connected with the source of the voltage of the two portsu AB2 。
The electric energy receiving end comprises a secondary side series compensation capacitorC s1 AndC s2 secondary side receiving coilL s1 AndL s2 (diode full bridge) rectifier Re 1 And (diode full bridge) rectifier Re 2 . Secondary series compensation capacitorC s1 And a secondary receiving coilL s1 The two serial ports are respectively connected with (diode full bridge) rectifier Re 1 Is connected with the middle point of two bridge arms, and a (diode full bridge) rectifier Re 1 An output voltage of the power receiving terminal is outputted from the output terminal of (a)U o1 The method comprises the steps of carrying out a first treatment on the surface of the Secondary series compensation capacitorC s2 And a secondary receiving coilL s2 The two serial ports are respectively connected with (diode full bridge) rectifier Re 2 Two bridge arm midpoints are connected, (diode full bridge) rectifier Re 2 Outputs another output voltage of the power receiving terminalU o2 . Rectifier Re in this embodiment 1 And Re (Re) 2 A diode full bridge rectifier is used.
Primary side transmitting coilL p1 And primary side transmitting coilL p2 No cross coupling and primary side transmitting coilL p1 And a secondary receiving coilL s2 No cross coupling and primary side transmitting coilL p2 And a secondary receiving coilL s1 No cross coupling and secondary side receiving coilL s1 And a secondary receiving coilL s2 Cross-coupling between each other. Only primary transmitting coils are considered in the systemL p1 And a secondary receiving coilL s1 Mutual inductance betweenM 1 And a primary sideTransmitting coilL p2 And secondary side receiving coilL s2 Mutual inductance betweenM 2 。
Besides the connection mode between the transmitting coil and the three-switch inverter, there are three other topologies, as shown in fig. 2 (a) to 2 (c). The three topologies are equivalent in output characteristics, and can generate two paths of independently adjustable square wave excitation voltages. As in fig. 2 (a), the primary side series compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Drain and source of (a), while the primary side is in series with the compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after the series connection are unchanged. As in fig. 2 (b), the primary side series compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after being connected in series are unchanged and are respectively connected to the switch tube S 1 Drain electrode of (d) and switching tube S 3 At the same time the primary side is connected in series with a compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after being connected in series are unchanged 。 Or as in FIG. 2 (c), the primary side is connected in series with a compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Drain electrode of (d) and switching tube S 2 At the same time, the primary side is connected in series with a compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Source and switching tube S of (2) 3 Is a source of (c).
From fig. 1, an ac equivalent circuit (as shown in fig. 3) of the wireless power supply device can be obtained, and a circuit model is described as follows:
（1）
wherein:U AB1 andU AB2 respectively voltages ofu AB1 Andu AB2 is used to determine the effective value of (1),I p1 andI p2 respectively, through primary side transmitting coilsL p1 AndL p2 is set to be a coil current of (a)i p1 Andi p2 is effective in terms of the effective value of (2);I s1 andI s2 respectively, flowing through the secondary receiving coilsL s1 AndL s2 is set to be a coil current of (a)i s1 Andi s2 is effective in terms of the effective value of (2);R ac1 andR ac2 is the alternating current equivalent resistance of two paths of outputs.ωIs the operating angular frequency of the system.
In order to make the system work in a complete resonance state, the parameter design of the wireless power supply device needs to satisfy:
（2）
wherein, the liquid crystal display device comprises a liquid crystal display device,f s switching frequency for a three-switch inverter;L p1 andL p2 the inductance values of the two primary side transmitting coils are respectively;C p1 andC p2 the capacitance values of the two primary-side series compensation capacitors are respectively;L s1 andL s2 the inductance values of the two pairs of side receiving coils are respectively;C s1 andC s2 the capacitance values of the compensation capacitors are respectively connected in series with the two secondary sides.
The system output voltage is obtained according to the formula (1) and the formula (2):
（3）
to change the output voltage of each channel, the effective value of the corresponding equivalent input excitation voltage can be adjustedU AB1 AndU AB2 the key control waveforms are shown in fig. 5. The operation modes of the three-switch inverter are analyzed as follows, the equivalent circuits of the modes are shown in fig. 4 (a) to 4 (c),u ds2 is a switching tube S 2 Is used for the voltage control of the drain-source voltage of the transistor,i a to assist the inductor current of the soft switching network.
Switch tube S 1 ~S 3 The gate signals of (2) are respectively denoted as G 1 ~G 3 The corresponding duty ratio signals are respectively D 1 ~D 3 (as shown in FIG. 5), gate signal G 2 Falling edge of (1) and gate signal G 1 Has dead time DT1 at the rising edge of (a), gate signal G 3 Falling edge of (1) and gate signal G 2 Has dead time DT2 at the rising edge of (2), gate signal G 1 Falling edge of (1) and gate signal G 3 There is dead time DT3 at the rising edge of (c). Gate signal G 2 Is formed by a gate signal G 1 And gate signal G 3 Two control signals are generated by NAND logic gate, duty cycle signalD 1 AndD 3 the variation ranges of (1) all belong to [0.5,1 ]]。
Mode 1 [ t ] of wireless power supply device 1 <t<t 2 ]: the equivalent circuit is shown in fig. 4 (a). In dead time DT1, switching tube S 1 And a switch tube S 2 In the off state, switch tube S 3 In an on state. Coil currenti p1 Negative, flowing through the switching tube S 1 Is provided. At this time, switch tube S 1 The drain-source voltage of (2) is zero, and zero-voltage turn-on is realized. The voltage at two ends of the LC auxiliary soft switch network is input voltage, and the inductance currenti a And linearly increases.
Mode 2 [ t ] of wireless power supply device 2 <t<t 3 ]: the equivalent circuit is shown in fig. 4 (b). In dead time DT2, switching tube S 2 And a switch tube S 3 In the off state, switch tube S 1 In an on state. Coil currenti p2 Positive, switch tube S 3 Is discharged. At the same time, inductor currenti a Positive, switch tube S 3 Is discharged. So long as the coil current is within DT2 timei p2 And inductor currenti a And the sum of the currents is positive, so that the S2 soft switching operation can be realized.
Mode 3 [ t ] of wireless power supply device 3 <t<t 4 ]: the equivalent circuit is shown in fig. 4 (c). Within dead time DT3, switching tube S 1 And a switch tube S 3 In the off state, switch tube S 2 At the position ofOn state, coil currenti p2 Negative, flowing through the switching tube S 3 Thereby ensuring the switching tube S 3 Realizing soft switching. LC-assisted soft switching network with zero voltage across the LC-assisted soft switching network, inductor currenti a The linearity decreases.
Taking into account the switching tube S 1 And a switch tube S 3 Soft switching can be naturally realized in the full load range, so the LC auxiliary soft switching network only helps the switching tube S 2 Realizing the soft switch of the full load range. Wherein the inductanceL a Value determining switch tube S 2 Soft switching range, capacitance of (2)C a Plays a role in blocking direct current and alternating current, and prevents inductance caused by direct current biasL a And (5) magnetically saturating. InductanceL a The smaller the value is, the wider the soft switching range is, but the peak-peak value of the flowing inductive current is increased, and the conduction loss is increased; conversely, inductanceL a The larger the value is, the smaller the peak-peak value of the flowing inductive current is, the conduction loss is also reduced correspondingly, but the switching tube S 2 The soft switching range of (a) is also narrowed. Thus, the inductor is designedL a The values need to be balanced against soft switching range and system conduction losses.
As can be seen from fig. 5, the switching tube S 2 The duty cycle signal of (D) 1 +D 3 -1) inductor current according to the principle of volt-second balancei a Peak current of (1) and switching tube S 2 Is a fixed value, and can be expressed as:
（4）
wherein:U in inputting a direct-current voltage for the system;L a for inductance in LC auxiliary soft switching networkL a Is a function of the inductance value of the capacitor.
On the other hand, equivalent ac input excitation voltageu AB2 The time domain expression of (2) is:
（5）
neglecting equivalent series resistance of coil, arbitraryn-the impedance of the order harmonic at the switching frequency is:
（6）
wherein: z is Z pc2 =nωL p2 ，Z sc2 =nωL s2 N=1, 3, … is an integer.Z p2n AndZ s2n the total harmonic impedance of the primary side resonance circuit and the total harmonic impedance of the secondary side resonance circuit are respectively,Z pc2 andZ sc2 the primary side resonant circuit fundamental wave impedance and the secondary side resonant circuit fundamental wave impedance are respectively.
The input impedance angle ψ can be derived as:
（7）
by combining the formulas (4) to (7), the coil current can be calculatedi p2 At the time oft 2 The amplitude at this point is:
（8）
wherein, the liquid crystal display device comprises a liquid crystal display device,βthe fitting coefficient of the equivalent impedance of the higher harmonic can be calculated by using mathematical software such as MATLAB.
The two sets of transmit and receive coils may employ a polarized and non-polarized configuration, respectively, to eliminate cross-coupling between the coils. The typical non-polarized coil comprises a square coil, a round coil and the like, and the typical polarized coil comprises a DD coil structure, namely two non-polarized coils are connected in series in opposite phases. If both sets of coils are polarized or non-polarized, cross-coupling mutual inductance can be eliminated by increasing the horizontal spacing between the two sets of coils.
Referring to FIG. 6, the output voltageU o1 And output voltageU o2 Is converted into a digital signal by a differential sampling circuit and an analog-to-digital conversion circuit, and then is transmitted by a wireless communication module (such as radio frequency communicationThe module, nRF24 L01+) is sent to the transmitting end, and the corresponding feedback quantity is passed through the proportional-integral compensator to produce a switch tube S 1 And a switch tube S 3 Duty cycle signal D of (2) 1 And duty cycle signal D 3 After that, the duty ratio signal D1 and the duty ratio signal D3 are fed into the gate driver through the PWM module unit to add dead time and phase compensation output PWM waveforms, and finally driving signals G1 to G3 of the switching transistors S1 to S3 are generated.
The application is formed by stacking three switching tubes in series, and can generate two independently adjustable square wave voltage excitations relative to the traditional full-bridge inverter and half-bridge inverter structures, and the voltage stress on each switching tube is input power supply voltage, so that the voltage stress of the switching tube and the system cost are reduced. In addition, the size of the two paths of control duty ratio signals is regulated through closed loop feedback, the control signal of the middle switching tube can be generated by utilizing a NAND logic gate, and the implementation is simple. By means of the LC auxiliary soft switching network, soft switching in the full load range can be realized, switching loss is effectively reduced, and system transmission efficiency is improved. The two paths of square wave excitation voltages are independently adjustable, the cross coupling effect is avoided, the voltage gain adjustment range is wide, and the wide voltage change occasions such as battery loads can be met. Meanwhile, the scheme provided by the application is beneficial to modularization realization, and the three-switch inverter can be packaged into a single sub-power module. To achieve any even (2 n) power transfer, only n sub-power modules need to be connected in parallel with the input power supply, and the integrated schematic diagram is modularized (as shown in fig. 7).
In summary, the application utilizes the stacked structure of three switching tubes in series to enable the system to generate two paths of independently adjustable square wave excitation voltage, and the voltage stress on each switching tube is the input power supply voltage, thereby reducing the voltage stress of the switching tube and the system cost, and a plurality of modules can be connected in parallel to realize any even-number power transmission.
Claims (7)
1. The two-way output independent adjustable wireless power supply device based on the three-switch inverter is characterized by comprising an electric energy transmitting end and an electric energy receiving end; wherein:
the electric energy transmitting end comprises a direct current power supplyThree-switch inverter and primary side series compensation capacitorC p1 AndC p2 primary side transmitting coilL p1 AndL p2 an LC-assisted soft switching network; the three-switch inverter comprises three switching tubes S with anti-parallel diodes 1 ~S 3 The method comprises the steps of carrying out a first treatment on the surface of the Switch tube S 1 Is connected to the positive electrode of the DC power supply, and a switching tube S 1 Is connected to the source of the switching tube S 2 Drain electrode of (d), switch tube S 2 Is connected to the source of the switching tube S 3 Drain electrode of (d), switch tube S 3 Is connected to the negative pole of the direct current power supply; the LC auxiliary soft switching network comprises an inductorL a And a capacitorC a The two are connected in series and then connected in parallel with a switch tube S 2 Is provided; primary side series compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after being connected in series are respectively connected to a switch tube S 1 Source and switching tube S of (2) 3 A source of (a); primary side series compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after being connected in series are respectively connected to a switch tube S 2 Source and switching tube S of (2) 3 A source of (a);
the electric energy receiving end comprises a secondary side series compensation capacitorC s1 AndC s2 secondary side receiving coilL s1 AndL s2 rectifier Re 1 And rectifier Re 2 The method comprises the steps of carrying out a first treatment on the surface of the Secondary series compensation capacitorC s1 And a secondary receiving coilL s1 The two ports after the series connection are connected to a rectifier Re 1 Rectifier Re 1 An output voltage of the power receiving terminal is outputted from the output terminal of (a)U o1 The method comprises the steps of carrying out a first treatment on the surface of the Secondary series compensation capacitorC s2 And a secondary receiving coilL s2 The two ports after the series connection are connected to a rectifier Re 2 Rectifier Re 2 Outputs another output voltage of the power receiving terminalU o2 ；
Primary side only transmitting coilL p1 And a secondary receiving coilL s1 Between and primary side transmitting coilL p2 And an auxiliaryEdge receiving coilL s2 There is coupling between them, and mutual inductance is respectivelyM 1 AndM 2 。
2. the two-output independently adjustable wireless power supply device based on three-switch inverter according to claim 1, wherein the primary side is connected in series with a compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Drain and source of (a), while the primary side is in series with the compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after being connected in series are unchanged;
or the primary side is connected in series with a compensation capacitorC p1 And primary side transmitting coilL p1 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Drain electrode of (d) and switching tube S 2 At the same time, the primary side is connected in series with a compensation capacitorC p2 And primary side transmitting coilL p2 The two ports after the series connection are replaced by being respectively connected to the switch tube S 1 Source and switching tube S of (2) 3 Is a source of (c).
3. The two-way output independently adjustable wireless power supply device based on the three-switch inverter according to claim 1, wherein the parameter design of the wireless power supply device satisfies the following conditions:
；
wherein:ωfor the operating angular frequency of the system,f s switching frequency for a three-switch inverter;L p1 andL p2 the inductance values of the two primary side transmitting coils are respectively;C p1 andC p2 the capacitance values of the two primary-side series compensation capacitors are respectively;L s1 andL s2 the inductance values of the two pairs of side receiving coils are respectively;C s1 andC s2 the capacitance values of the compensation capacitors are respectively connected in series with the two secondary sides.
4. The two-output independently adjustable wireless power supply device based on three-switch inverter according to claim 1, wherein the switching tube S is connected with a power supply circuit 1 ~S 3 The gate signals of (2) are respectively denoted as G 1 ~G 3 The corresponding duty cycle signals are respectivelyD 1 ~D 3 The method comprises the steps of carrying out a first treatment on the surface of the Gate signal G 2 Falling edge of (1) and gate signal G 1 Has dead time DT1 at the rising edge of (a), gate signal G 3 Falling edge of (1) and gate signal G 2 Has dead time DT2 at the rising edge of (2), gate signal G 1 Falling edge of (1) and gate signal G 3 Dead time DT3 exists at the rising edge of (a); gate signal G 2 Is formed by a gate signal G 1 And gate signal G 3 Two control signals are generated by NAND logic gate, duty cycle signalD 1 And duty cycle signalD 3 The variation ranges of (1) all belong to [0.5,1 ]]。
5. The two-way output independently adjustable wireless power supply device based on three-switch inverter according to claim 3, wherein the output voltageU o1 By changing the switching tube S 1 Duty cycle of (a) is adjusted to output voltageU o2 By changing the switching tube S 3 Is adjusted by the duty cycle signal of (a); output voltageU o1 And output voltageU o2 The digital signal is converted by a differential sampling circuit and an analog-to-digital conversion circuit and is sent to a transmitting end by a wireless communication module, and a corresponding feedback quantity is generated into a switching tube S by a proportional-integral compensator 1 And a switch tube S 3 Duty cycle signal of (2)D 1 And duty cycle signalD 3 。
6. The two-output independently adjustable wireless power supply device based on three-switch inverter according to claim 1, wherein the primary side transmitting coilL p1 AndL p2 coil adopting polarized structure and secondary receiving coilL s1 AndL s2 a coil with a non-polarized structure is adopted; or primary side transmitting coilL p1 AndL p2 coil adopting non-polarized structure and secondary receiving coilL s1 AndL s2 a coil with a polarized structure is used.
7. The three-switch inverter-based two-way output independently adjustable wireless power supply device of claim 6, wherein the non-polarized structured coil comprises a square coil and a circular coil; the coils of the polarized structure comprise DD coil structures, namely two non-polarized coils are connected in series in opposite phases.
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Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103648830A (en) * | 2011-06-10 | 2014-03-19 | 庞巴迪运输有限公司 | System and method for transferring electric energy to a vehicle using segments of a conductor arrangement which can be operated independently |
| CN104935172A (en) * | 2015-06-09 | 2015-09-23 | 南京邮电大学 | Three-level soft switch forward-flyback DC/DC converter circuit topology structure |
| US20170005527A1 (en) * | 2014-06-13 | 2017-01-05 | Kabushiki Kaisha Toshiba | Drive device, method thereof, and wireless power transmission device |
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Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103648830A (en) * | 2011-06-10 | 2014-03-19 | 庞巴迪运输有限公司 | System and method for transferring electric energy to a vehicle using segments of a conductor arrangement which can be operated independently |
| US20170005527A1 (en) * | 2014-06-13 | 2017-01-05 | Kabushiki Kaisha Toshiba | Drive device, method thereof, and wireless power transmission device |
| CN104935172A (en) * | 2015-06-09 | 2015-09-23 | 南京邮电大学 | Three-level soft switch forward-flyback DC/DC converter circuit topology structure |
Non-Patent Citations (2)
| Title |
|---|
| A. FATEMI, M. AZIZI, M. MOHAMADIAN, A. YAZDIAN VARJANI AND M. SHAHPARASTI: "Single-Phase Dual-Output Inverters With Three-Switch Legs", 《IEEE TRANSACTIONS ON INDUSTRIAL ELECTRONICS》, vol. 60, no. 05, pages 1769 - 1779, XP011490820, DOI: 10.1109/TIE.2012.2190952 * |
| 李海 等: "三开关三相逆变器及其模型预测控制器设计", 《电气传动》, vol. 50, no. 12, pages 64 - 71 * |
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