CN116264439A - Control method and device for high-power-factor single-phase PWM rectifier - Google Patents

Control method and device for high-power-factor single-phase PWM rectifier Download PDF

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CN116264439A
CN116264439A CN202310508695.3A CN202310508695A CN116264439A CN 116264439 A CN116264439 A CN 116264439A CN 202310508695 A CN202310508695 A CN 202310508695A CN 116264439 A CN116264439 A CN 116264439A
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current
voltage
sliding mode
axis
rectifier
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CN116264439B (en
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许昊天
周述晗
高惠珍
熊志强
贺明智
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Sichuan University
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Sichuan University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Rectifiers (AREA)

Abstract

The invention discloses a control method and a device for a high-power-factor single-phase PWM rectifier. The control method comprises the following steps: obtaining alternating current voltage and current, respectively lagging and shifting to obtain virtual orthogonal signals, and respectively performing Park conversion to obtain a d-axis voltage component, a current component, a q-axis voltage component and a current component; constructing a sliding mode switching surface by using direct current output voltage and output current; control rate of sliding mode of d-axis current loop
Figure ZY_1
And q-axis current loop slip mode control rate
Figure ZY_2
The method comprises the steps of carrying out a first treatment on the surface of the The output of the sliding mode switching surface is made to be the command value of d-axis current, and the result is obtained
Figure ZY_3
And
Figure ZY_4
the method comprises the steps of carrying out a first treatment on the surface of the Will be
Figure ZY_5
And
Figure ZY_6
after summation, the PWM signals are compared with the triangular carrier waves to obtain PWM signals, and the switching tubes of the rectifier are controlled. The invention can realize that the output voltage of the direct current side is stabilized at a specific voltage value under the condition of power frequency sinusoidal input; the current harmonic wave at the input side is small, and the power factor is high; when load steps or other large disturbances occur to the system, the system has higher transient response performance and anti-interference performance.

Description

Control method and device for high-power-factor single-phase PWM rectifier
Technical Field
The invention relates to the technical field of power electronics, in particular to a control method and a device for a high-power-factor single-phase PWM rectifier.
Background
With the power electronic equipment of the power system, any equipment connected to the power grid should be avoided as much as possible from affecting the quality of the power grid. Besides high voltage and extra-high voltage, a phase control mode mainly comprising thyristors and derivative devices thereof is reserved, and most of rectifying equipment is converted and upgraded to PWM rectifying equipment with high power factor and low current harmonic wave. At present, the control technology of the single-phase PWM rectifier is mature increasingly, for example, a voltage-current double closed loop with a network side voltage feedforward is simple and easy to realize, but the control of the input current to the network side is crossed; the voltage and current double closed loops based on synchronous rotation coordinate system decoupling solve the problem of the former, can well control the current amplitude and phase of the network side and even realize variable power factor, but the calculated amount of the control mode is larger, and the calculation force requirement on the controller is higher; the resonance control has the advantages of the former two control modes, can effectively control the current of the network side, is simpler to realize, and greatly reduces the control performance when the frequency of the network side slightly fluctuates.
Because the PWM rectifier belongs to a nonlinear system, the PWM rectifier designed by applying the traditional linear control has a certain defect in the aspect of dynamic response, and when the system is greatly disturbed, the system is very likely to be incapable of operating normally due to poor robustness.
Disclosure of Invention
The invention provides a control method and a device for a high-power-factor single-phase PWM rectifier, wherein the nonlinear control method of sliding mode control is applied to the single-phase PWM rectifier, has excellent dynamic response and robustness, and can effectively improve the anti-interference capability of a system.
The technical scheme for realizing the purpose of the invention is as follows:
a high power factor single phase PWM rectifier control method, comprising:
obtaining ac voltage measurement
Figure SMS_3
And current
Figure SMS_5
Respectively lagging behind the phase shift
Figure SMS_8
Obtaining virtual orthogonal signals
Figure SMS_2
And
Figure SMS_4
respectively performing Park conversion to obtain a d-axis voltage component under a rotating coordinate system
Figure SMS_7
Voltage component on q-axis
Figure SMS_9
And d-axis current component
Figure SMS_1
Current component on q-axis
Figure SMS_6
；
Structure sliding mode switching surface
Figure SMS_10
：
Figure SMS_11
；
wherein ,
Figure SMS_12
is the voltage at the direct-current side,
Figure SMS_13
is the direct-current side current which is the current,
Figure SMS_14
is a reference value for the dc side voltage,
Figure SMS_15
is the capacitance of the parallel capacitor at the DC side of the rectifier,
Figure SMS_16
is a static difference parameter;
control rate of sliding mode of d-axis current loop
Figure SMS_17
And q-axis current loop slip mode control rate
Figure SMS_18
：
Figure SMS_19
，
Figure SMS_20
，
Figure SMS_21
；
wherein ,
Figure SMS_22
is the phase of the ac measured voltage,
Figure SMS_23
is that the moving point does not reach the sliding mode switching surface
Figure SMS_24
The rate of movement at the time of the movement,
Figure SMS_25
is a sliding mode switching surface with a motion point approaching to
Figure SMS_26
Rate of motion at that time;
Figure SMS_27
is the command value of the d-axis current,
Figure SMS_28
is a command value of q-axis current;
order the
Figure SMS_29
And order
Figure SMS_30
Obtaining
Figure SMS_31
And
Figure SMS_32
； wherein ,
Figure SMS_33
the d-axis current component value is the d-axis current component value when the rectifier operates under the rated working condition;
will be
Figure SMS_34
、
Figure SMS_35
After summation, the PWM signals are compared with the triangular carrier waves to obtain PWM signals, and the switching tube of the rectifier is controlled.
Preferred technical proposal, order
Figure SMS_36
。
A high power factor single phase PWM rectifier control apparatus, comprising: the first voltage sampling circuit VS1, the first current detection circuit CS1, the phase-locked calculation unit PLL, the first virtual orthogonal construction unit OCU1, the second virtual orthogonal construction unit OCU2, the first coordinate transformation unit OTU1, and the second coordinate transformation unit OTU2; the first voltage sampling circuit VS1 acquires an ac side voltage
Figure SMS_44
Inputting the phase of the alternating voltage into a phase-locked calculation unit PLL to obtain the phase of the alternating voltage
Figure SMS_52
And input the first virtual orthogonal construction unit OCU1 to obtain virtual orthogonal signal of alternating-current side voltage
Figure SMS_59
The method comprises the steps of carrying out a first treatment on the surface of the The first current detection circuit CS1 obtains an ac-side current
Figure SMS_43
The second virtual orthogonal construction unit OCU2 is input to obtain virtual orthogonal signal of alternating current side current
Figure SMS_50
；
Figure SMS_58
、
Figure SMS_64
And
Figure SMS_41
inputting the d-axis voltage component into a first coordinate transformation unit OTU1 to obtain a d-axis voltage component under a rotating coordinate system
Figure SMS_48
And q-axis voltage component
Figure SMS_56
；
Figure SMS_63
、
Figure SMS_42
And
Figure SMS_51
inputting the d-axis current component into a second coordinate transformation unit OTU2 to obtain a d-axis current component under a rotating coordinate system
Figure SMS_60
And q-axis current component
Figure SMS_66
The method comprises the steps of carrying out a first treatment on the surface of the The circuit also comprises a second voltage sampling circuit VS2, a second current detection circuit CS2 and a first sliding mode calculation unit SMC1; the second voltage sampling circuit VS2 and the second current detection circuit CS2 respectively acquire dc-side voltages
Figure SMS_38
Direct current side current
Figure SMS_49
Inputting the command value of d-axis current obtained by the operation of the sliding mode switching surface of the first sliding mode computing unit SMC1
Figure SMS_57
The method comprises the steps of carrying out a first treatment on the surface of the The device further comprises a second sliding mode calculating unit SMC2 and a third sliding mode calculating unit SMC3;
Figure SMS_65
、
Figure SMS_37
and
Figure SMS_45
the input second sliding mode calculating unit SMC2 is obtained through the operation of the d-axis current loop sliding mode control rate
Figure SMS_53
；
Figure SMS_61
And
Figure SMS_40
the third sliding mode calculating unit SMC3 is input and the command value of the q-axis current is combined
Figure SMS_47
The q-axis current loop sliding mode control rate is calculated to obtain
Figure SMS_55
The method comprises the steps of carrying out a first treatment on the surface of the Command value of the q-axis current
Figure SMS_62
，
Figure SMS_39
The d-axis current component value is the d-axis current component value when the rectifier operates under the rated working condition; also included are a timer CLK, a comparator CMP and a drive circuit DR; the timer CLK outputs a triangular carrier to the comparator CMP;
Figure SMS_46
、
Figure SMS_54
inputting the PWM signals into a comparator CMP, and comparing the PWM signals with the triangular carrier after summation; the PWM signal controls the switching tube of the rectifier through the driving circuit DR.
The invention has the beneficial effects that under the condition of power frequency sine input, the output voltage of the direct current side can be stabilized at a specific voltage value; the current harmonic wave at the input side is small, and the power factor is high; when load steps or other large disturbances occur to the system, the system has higher transient response performance and anti-interference performance.
Drawings
Fig. 1 is a block diagram of the circuit configuration of the present invention.
FIG. 2a is a graph showing waveforms of voltage and current at the input side of the rectifier when the sliding mode control is added in the control circuit.
Fig. 2b is a graph of waveforms of voltage and current at the input side of the rectifier during conventional dq decoupling control.
FIG. 3a is a graph showing the voltage waveform at the output side of the rectifier when the slip mode control is added to the control circuit.
Fig. 3b is a graph of the voltage waveform at the output side of the rectifier for conventional dq decoupling mode control.
Fig. 4 is a graph comparing power factors of rectifiers when adding slip mode control and conventional dq control in a control circuit.
Fig. 5 is a graph showing the total harmonic distortion ratio of the ac current at the input side of the rectifier when the slip mode control and the conventional dq control are added to the control circuit.
Fig. 6 is a graph showing comparison of dc voltage ripple coefficients at the output side of a rectifier when a sliding mode control and a conventional dq control are added to a control circuit.
Detailed Description
The invention will be further described with reference to the drawings and specific examples.
A control method of a high-power-factor single-phase PWM rectifier comprises the following steps:
1. obtaining network side AC voltage instantaneous value in real time
Figure SMS_67
Obtaining phase signals of grid voltage through a phase-locked loop
Figure SMS_68
The method comprises the steps of carrying out a first treatment on the surface of the Detecting input current at AC input side
Figure SMS_69
Hysteresis phase shifting it
Figure SMS_70
Obtaining virtual orthogonal signals
Figure SMS_71
Obtaining a d-axis current component under a rotating coordinate system through Park conversion
Figure SMS_72
And q-axis current component
Figure SMS_73
。
wherein
Figure SMS_74
For AC voltage signals
Figure SMS_75
Performing Park conversion to obtain
Figure SMS_76
And
Figure SMS_77
. Is of the same kind
Figure SMS_78
wherein
Figure SMS_79
Is also a hysteresis
Figure SMS_80
Is a virtual orthogonal signal of (a).
Using dc output voltage
Figure SMS_81
And an output current on the DC side
Figure SMS_82
Construction of sliding mode switching surface
Figure SMS_83
：
Figure SMS_84
wherein ,
Figure SMS_85
is a reference value for the dc output voltage,
Figure SMS_86
is the capacitance of the parallel capacitor at the output side of the rectifier,
Figure SMS_87
is a static difference parameter, i.e. parameter
Figure SMS_88
The value of (2) determines the error value between the output voltage and the reference output voltage under stable conditions.
2. Control rate of sliding mode of d-axis current loop
Figure SMS_89
And q-axis current loop slip mode control rate
Figure SMS_90
：
Figure SMS_91
；
Selecting an exponential approach law
Figure SMS_92
；
Wherein the parameters are
Figure SMS_93
Representing the movement rate of the movement point when the movement point does not reach the sliding mode switching surface, the parameter
Figure SMS_94
Representing the movement rate when the movement point approaches the sliding mode switching surface; in the method, in the process of the invention,
Figure SMS_95
Figure SMS_96
is a command value of the d-axis current, and represents an active current component of the input-side current. In the invention, the output of the sliding mode switching surface is taken as the command value of d-axis current
Figure SMS_97
。
Figure SMS_98
Is a command value of q-axis current, and represents a reactive current component of input-side alternating current. Setting up
Figure SMS_99
，
Figure SMS_100
The d-axis current component value is used for the rated working condition operation of the rectifier.
Figure SMS_101
Different values of (2) can realize different high power factors when
Figure SMS_102
An optimally high power factor can be achieved while having excellent interference immunity.
3. Will be
Figure SMS_103
And
Figure SMS_104
after summation, the PWM signals are compared with the triangular carrier waves to obtain PWM signals for driving the switching tube.
As shown in fig. 1, the control device includes a first voltage sampling circuit VS1, a second voltage sampling circuit VS2, a first current detection circuit CS1, a second current detection circuit CS2, a phase-locked calculation unit PLL, a first virtual orthogonal construction unit OCU1, a second virtual orthogonal construction unit OCU2, a first coordinate transformation unit OTU1, a second coordinate transformation unit OTU2, a first slip-form calculation unit SMC1, a second slip-form calculation unit SMC2, a third slip-form calculation unit SMC3, a comparator CMP, a timer CLK, and a drive circuit DR. The first voltage sampling circuit VS1 is used for detecting an input voltage of the ac side of the rectifier and obtaining a voltage phase angle in real time, the second voltage sampling circuit VS2 is used for detecting an output voltage of the dc side of the rectifier, the first current detection circuit CS1 is used for detecting an input current of the ac side of the rectifier, and the second current detection circuit CS2 is used for detecting a load current of the dc side. The output end of the first voltage sampling circuit VS1 is connected with the input end of the phase-locked computing unit PLL and the input end of the first virtual orthogonal construction unit OCU1, and the output end of the first voltage sampling circuit VS1, the output end of the phase-locked computing unit PLL and the output end of the first virtual orthogonal construction unit OCU1 are connected with the first coordinate transformation unit OTU1, so that input voltage under a synchronous rotation coordinate system is obtained; the output end of the first current detection circuit CS1 is connected with the input end of the second virtual orthogonal construction unit OCU2, and the output end of the phase-locked calculation unit PLL, the output end of the first current detection circuit CS1 and the output end of the second virtual orthogonal construction unit OCU2 are connected with the second coordinate transformation unit OTU2, so that input current under a synchronous rotation coordinate system is obtained; the output end of the second voltage sampling circuit VS2 and the output end of the second current detection circuit CS2 are connected with the first sliding mode computing unit SMC1, and the output end of the first sliding mode computing unit SMC1, the first output end of the first coordinate transformation unit OTU1 and the first output end of the second coordinate transformation unit OTU2 are connected with the second sliding mode computing unit SMC2; the second output end of the first coordinate transformation unit OTU1 and the second output end of the second coordinate transformation unit OTU2 are connected with a third sliding mode calculation unit SMC3; the output end of the second sliding mode calculating unit SMC2, the output end of the third sliding mode calculating unit SMC3 and the output end of the timer CLK are connected with a comparator CMP; the comparator CMP outputs a PWM signal to be driven by the driving circuit DR, thereby controlling the on and off of the main loop switching tube.
The working process of the device is as follows: the first voltage sampling circuit VS1 measures the instantaneous value of the ac voltage on the ac side of the rectifier during each switching cycle
Figure SMS_106
The second voltage sampling circuit VS2 measures the dc output voltage of the dc side of the rectifier
Figure SMS_109
The first current detection circuit CS1 detects an input current on the ac side of the rectifier
Figure SMS_112
The second current detection circuit CS2 detects a load current on the dc side
Figure SMS_107
. To detect analog signals
Figure SMS_110
Sending the first virtual orthogonal construction unit OCU1 to obtain an orthogonal input voltage OVI; analog signal
Figure SMS_113
The second virtual orthogonal construction unit OCU2 is fed to obtain the orthogonal input current OCI. To be analog signals
Figure SMS_114
The orthogonal input voltage OVI is sent to a first coordinate transformation unit OTU1 to obtain a d-axis input voltage DVI and a q-axis input voltage QVI; analog signal
Figure SMS_105
And the orthogonal input current OCI is fed into a second coordinate transformation unit OTU2 to obtain a d-axis input current DCI and a q-axis input current QCI. At the same time direct current side voltage
Figure SMS_108
And load current
Figure SMS_111
Into a first slip form calculation unit SMC1. The output of the first sliding mode calculating unit SMC1, the d-axis input voltage DVI and the d-axis input current DCI are sent to the second sliding mode calculating unit SMC2; the q-axis input voltage QVI and the q-axis input current QCI are fed to the third sliding mode calculating unit SMC3. The sum of the output results of the second sliding mode calculating unit SMC2 and the third sliding mode calculating unit SMC3 is taken as a modulation wave, and the modulation wave and the triangular wave which is taken as a carrier wave are sent into a comparator CMP to generate PWM signals, and the PWM signals are controlled to be turned on and off by a driving circuit DR.
The specific implementation mode is that the direct-current voltage signal is obtained according to the second voltage sampling circuit VS2
Figure SMS_116
Load current obtained with the second current detection circuit CS2
Figure SMS_118
The d-axis current reference value is obtained by being sent to a first sliding mode computing unit SMC1 together
Figure SMS_120
The d-axis input current error at this time is calculated
Figure SMS_117
Input current of q-axis
Figure SMS_119
D-axis input voltage
Figure SMS_121
Together with the second slip form calculation unit SMC2. Error of q-axis reactive current
Figure SMS_122
D-axis active current and q-axis current
Figure SMS_115
And feeding into a third sliding mode calculating unit SMC3. The outputs of the second sliding mode calculating unit SMC2 and the third sliding mode calculating unit SMC3 are synthesized to form a modulated wave, and the modulated wave and the triangular wave which is output by the timer CLK and serves as a carrier wave are sent to the comparator CMP to generate a PWM signal for controlling the on-off of the switching tube.
Simulation test:
setting up power frequency sinusoidal voltage with input voltage amplitude of 311V in MATLAB/Simulink, and inputting side inductor
Figure SMS_123
Load resistor
Figure SMS_124
Reference output voltage
Figure SMS_125
At 0.11s the load step is
Figure SMS_126
。
In fig. 2a and 2b, the solid and dashed lines are the input current and input voltage of the rectifier, respectively. Both with and without slip mode control (fig. 2 a) and with approximately 0.01s, the voltage and current phases can be achieved. At 0.11s of simulation, the load step was 2 times. After a load step, the input current to the rectifier that is added to the slip mode can enter steady state faster. It can be seen that rectifiers based on slip-mode control have excellent transient response performance.
As shown in fig. 3a and 3b, steady state is achieved at about 0.06s with and without slip mode control (fig. 3 a) and an output voltage of 800V is achieved. At 0.11s of simulation, the load step was 2 times. After slight jitter occurs in the output voltage of the rectifier controlled by adding the sliding mode, the output voltage is still stable at 800V; the output voltage of the rectifier without slip mode control drops firstly after the load step, and the output voltage is restored to 800V after 0.24 s. It can be seen that the rectifier has significantly superior tamper resistance after addition of slip mode control.
As shown in fig. 4, the solid line and the dotted line are the rectifier power factors when the slip mode control is added and when the dq control is conventional, respectively. At 0.11s of simulation, the load step was 2 times. Under the two conditions of adding the sliding mode control and not adding the sliding mode control, the power factor can be kept above 0.985 all the time. Although the fluctuation of the power factor of the rectifier added with the sliding mode control is larger than that of the rectifier without the sliding mode control when the load is stepped, the power factor is kept above 0.985 and is within the engineering acceptable range, so that the single-phase rectification circuit based on the sliding mode control has the characteristic of high power factor.
As shown in fig. 5, the solid line and the dotted line are the total harmonic distortion of the ac current at the input side of the rectifier when the slip mode control is added and the conventional dq control is performed, respectively. At 0.11s of simulation, the load step was 2 times. Under the two conditions of adding the sliding mode control and not adding the sliding mode control, the harmonic distortion rate of the input current before the rectifier reaches a steady state is gradually reduced, and the difference between the two is not great, but after the load is stepped, the total harmonic distortion rate THDi of the input current of the rectifier after the sliding mode control is added is obviously lower than the input current distortion rate of the rectifier without the sliding mode control.
As shown in fig. 6, the solid line and the dotted line are the dc voltage ripple coefficients at the output side of the rectifier when the sliding mode control is added and when the dq control is conventional, respectively. At 0.11s of simulation, the load step was 2 times. Under the two conditions of adding the sliding mode control and not adding the sliding mode control, the ripple coefficient of the output voltage is not greatly different, but after the load is stepped, the ripple coefficient of the output voltage of the rectifier added with the sliding mode control is obviously lower than that of the rectifier without the sliding mode control.
From the simulation results, the single-phase rectifier added with the sliding mode control has the performance of high power factor and high robustness.

Claims (3)

1. A method for controlling a high power factor single phase PWM rectifier, comprising:
obtaining ac voltage measurement
Figure QLYQS_2
And current->
Figure QLYQS_6
Respectively lagging phase shift->
Figure QLYQS_7
Obtain virtual orthogonal signal->
Figure QLYQS_3
and />
Figure QLYQS_5
Respectively performing Park conversion to obtain d-axis voltage component +.>
Figure QLYQS_8
Q-axis voltage component->
Figure QLYQS_9
And d-axis current component->
Figure QLYQS_1
Q-axis current component->
Figure QLYQS_4
；
Structure sliding mode switching surface
Figure QLYQS_10
：
Figure QLYQS_11
；
wherein ,
Figure QLYQS_12
is a DC side voltage, ">
Figure QLYQS_13
Is a direct current side current, ">
Figure QLYQS_14
Is a reference value for the DC side voltage, +.>
Figure QLYQS_15
Is the capacitance of the parallel capacitor on the DC side of the rectifier,/>
Figure QLYQS_16
Is a static difference parameter;
control rate of sliding mode of d-axis current loop
Figure QLYQS_17
And q-axis current loop slip mode control rate +.>
Figure QLYQS_18
：
Figure QLYQS_19
，
Figure QLYQS_20
，
Figure QLYQS_21
；
wherein ,
Figure QLYQS_22
is the phase of the ac voltage,/-, of the test signal>
Figure QLYQS_23
Is that the movement point does not reach the sliding mode switching surface +.>
Figure QLYQS_24
Rate of movement at time,/->
Figure QLYQS_25
Is the sliding mode switching surface of the motion point approaching>
Figure QLYQS_26
Rate of motion at that time; />
Figure QLYQS_27
Is the command value of d-axis current, +.>
Figure QLYQS_28
Is a command value of q-axis current;
order the
Figure QLYQS_29
And let->
Figure QLYQS_30
Find +.>
Figure QLYQS_31
and />
Figure QLYQS_32
； wherein ,/>
Figure QLYQS_33
The d-axis current component value is the d-axis current component value when the rectifier operates under the rated working condition;
will be
Figure QLYQS_34
、/>
Figure QLYQS_35
After summation, the PWM signals are compared with the triangular carrier waves to obtain PWM signals, and the switching tube of the rectifier is controlled.
2. The method for controlling a high power factor single phase PWM rectifier according to claim 1, wherein
Figure QLYQS_36
。
3. A high power factor single phase PWM rectifier control apparatus, comprising:
the first voltage sampling circuit VS1, the first current detection circuit CS1, the phase-locked calculation unit PLL, the first virtual orthogonal construction unit OCU1, the second virtual orthogonal construction unit OCU2, the first coordinate transformation unit OTU1, and the second coordinate transformation unit OTU2; the first voltage sampling circuit VS1 acquires an ac side voltage
Figure QLYQS_40
Inputting the phase of the alternating voltage into a phase-locked calculation unit PLL to obtain the phase of the alternating voltage
Figure QLYQS_42
And input a virtual orthogonal signal +.f. of the first virtual orthogonal construction unit OCU1 to obtain an alternating side voltage>
Figure QLYQS_46
The method comprises the steps of carrying out a first treatment on the surface of the The first current detection circuit CS1 acquires an alternating-side current +.>
Figure QLYQS_39
A virtual orthogonal signal of alternating-current side current is obtained by inputting a second virtual orthogonal construction unit OCU2>
Figure QLYQS_44
；/>
Figure QLYQS_48
、/>
Figure QLYQS_51
and />
Figure QLYQS_37
Inputting the d-axis voltage component into a first coordinate transformation unit OTU1 to obtain a d-axis voltage component under a rotating coordinate system
Figure QLYQS_41
And q-axis voltage component->
Figure QLYQS_45
；/>
Figure QLYQS_49
、/>
Figure QLYQS_38
and />
Figure QLYQS_43
The d-axis current component +.f under the rotation coordinate system is obtained by inputting the second coordinate transformation unit OTU2>
Figure QLYQS_47
And q-axis current component->
Figure QLYQS_50
；
The circuit also comprises a second voltage sampling circuit VS2, a second current detection circuit CS2 and a first sliding mode calculation unit SMC1; the second voltage sampling circuit VS2 and the second current detection circuit CS2 respectively acquire dc-side voltages
Figure QLYQS_52
DC side current->
Figure QLYQS_53
The first sliding mode calculating unit SMC1 is input to obtain the command value of d-axis current through sliding mode switching surface operation>
Figure QLYQS_54
；
The device further comprises a second sliding mode calculating unit SMC2 and a third sliding mode calculating unit SMC3;
Figure QLYQS_57
、/>
Figure QLYQS_59
and />
Figure QLYQS_62
Inputting into a second sliding mode calculating unit SMC2 to obtain +.>
Figure QLYQS_56
；/>
Figure QLYQS_60
and />
Figure QLYQS_63
The third sliding mode calculating unit SMC3 is input, and the command value of q-axis current is combined +.>
Figure QLYQS_64
Obtaining +.>
Figure QLYQS_55
The method comprises the steps of carrying out a first treatment on the surface of the Command value of the q-axis current
Figure QLYQS_58
，/>
Figure QLYQS_61
The d-axis current component value is the d-axis current component value when the rectifier operates under the rated working condition;
also included are a timer CLK, a comparator CMP and a drive circuit DR; the timer CLK outputs a triangular carrier to the comparator CMP;
Figure QLYQS_65
、/>
Figure QLYQS_66
inputting the PWM signals into a comparator CMP, and comparing the PWM signals with the triangular carrier after summation; the PWM signal controls the switching tube of the rectifier through the driving circuit DR.
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