CN116247953A - Control method of six-switch matrix converter - Google Patents

Control method of six-switch matrix converter Download PDF

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Publication number
CN116247953A
CN116247953A CN202310416752.5A CN202310416752A CN116247953A CN 116247953 A CN116247953 A CN 116247953A CN 202310416752 A CN202310416752 A CN 202310416752A CN 116247953 A CN116247953 A CN 116247953A
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diode
voltage
switching tube
converter
tube
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Inventor
李磊
伍星宇
张善路
焦龙腾
刘博睿
王恒力
李璐璐
汪诚
曾志勇
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Nanjing University of Science and Technology
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Nanjing University of Science and Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Ac-Ac Conversion (AREA)

Abstract

The invention discloses a control method of a six-switch matrix converter, which is characterized in that different PWM signals are applied to six switching tubes of the six-switch matrix converter in the time division stage of outputting forward voltage and reverse voltage of an alternating current power supply so that the six-switch matrix converter is in different modes for the voltage regulation and frequency modulation requirements of an ACAC converter and the characteristics of the six-switch matrix converter. The voltage gain is increased and decreased by adjusting the duty ratio of the PWM signal, and the voltage and the input voltage can be adjusted to be in-phase or out-phase so as to adjust the frequency, so that the frequency modulation function required by the ACAC converter is realized, the control mode is simple, the operation is easy, and the application occasion of the six-switch matrix converter is widened.

Description

Control method of six-switch matrix converter
Technical Field
The invention belongs to the field of power electronic converters, and particularly relates to a control method of a six-switch matrix converter.
Background
With the development of society, the problems of energy crisis and environmental pollution are becoming serious, so topics such as new energy power generation and electric automobiles become research hotspots, and power electronic converters are the core technology behind the topics and are the key research objects of people in related fields. AC-AC converters, which are important parts of power electronics, are the cores of AC power sources, transformers, and new energy power generation devices, and have been widely studied.
With the development of AC-AC converters, the AC-AC converters can be classified into AC-dc-AC converters and AC-AC converters according to the presence or absence of an intermediate energy storage link. For an ac-dc-ac converter, the overall size of the converter is large because of the presence of a large energy storage element, and the converter is not suitable for high-power occasions. Compared with an AC-DC-AC converter, the traditional AC-AC converter has the advantages of no intermediate energy storage link, small volume, low cost, easy integration and the like, and the matrix converter, as one of the AC-AC converters, also has the advantages of adjustable power factor, bidirectional energy flow, high power density and the like.
As global requirements for energy utilization rate, energy saving and the like are continuously improved in recent years, the performance of a switching tube is continuously improved, and requirements for power electronic converters in various application occasions are continuously improved, a matrix converter serving as a converter with excellent performance is becoming a research hot spot. At present, the direct-change traditional AC-AC type converter can regulate the voltage of the alternating current in a step-up and step-down manner, but the frequency cannot be changed, and the indirect-change AC-DC-AC type converter can change the frequency but has larger volume, so that the problem cannot be solved. For matrix converters, the adjustment of voltage and frequency of a part of matrix converters can still have the defects of complicated control strategy, limited voltage transmission ratio and serious commutation problem.
Disclosure of Invention
The invention aims to provide a control method based on a six-switch matrix converter, which is used for realizing the conversion of alternating current, and can directly realize the functions of voltage and frequency by changing the duty ratio of PWM control waveforms.
To achieve the above object, the present invention provides a control method of a six-switch matrix converter, which includes a first switching tube S 1 Second switch tube S 2 Third switch tube S 3 Fourth switching tube S 4 Fifth switch tube S 5 And a sixth switching tube S 6 First diode D 1 Second diode D 2 Third diode D 3 Fourth diode D 4 Fifth diode D 5 And a sixth diode D 6 Input AC voltage source V in Input filter capacitor C in Inductance L and output filter capacitor C o Load R L ；
The first switch tube S 1 Source of (C) and first diode D 1 Anode connection of first diode D 1 Cathode of (a) and third switch tube S 3 Drain electrode connection of the third switch tube S 3 Source electrode of (D) and third diode D 3 Anode connection of third diode D 3 Cathode of (a) and fifth switch tube S 5 Drain electrode connection of fifth switch tube S 5 Source of (D) and fifth diode D 5 Anode connection of a second switching tube S 2 Source electrode of (C) and second diode D 2 Anode connection of second diode D 2 Cathode and fourth switching tube S 4 Drain electrode connection of fourth switching tube S 4 Source electrode of (D) and fourth diode D 4 Anode connection of fourth diode D 4 Cathode and sixth switching tube S 6 Is connected with the drain electrode of a sixth switching tube S 6 Source electrode of (D) and sixth diode D 6 Is connected with the anode of the battery;
first switching tube S 1 Drain and second switch of (2)Closing tube S 2 Is connected with the drain electrode of the fifth diode D 5 Cathode and sixth diode D of (2) 6 Is connected with the cathode of the first switch tube S 1 And a second switching tube S 2 Is connected with the fifth diode D 5 And a sixth diode D 6 The connection points of the inductor L are respectively connected with two ends of the inductor L;
third switch tube S 3 With a first diode D 1 Is connected with a fourth switching tube S 4 And a second diode D 2 Respectively with the input filter capacitor C in Is connected with two ends of input AC voltage source V in And input filter capacitor C in Parallel connection;
third diode D 3 And a fifth switch tube S 5 Is connected with the fourth diode D 4 And a sixth switching tube S 6 Respectively with the output filter capacitor C o Is connected with the two ends of the load R L And output filter capacitor C o Parallel connection;
the control method specifically comprises the following steps:
defining a third switching tube S 3 With a first diode D 1 The connection point of (2) is high potential, the fourth switch tube S 4 And a second diode D 2 When the connection point of the voltage source is at low potential, the voltage input by the input voltage source is forward voltage, and conversely, reverse voltage;
for the converter duty cycle T when the input voltage is the forward voltage, the duty cycle of the PWM signal is set to d 1 Divided into two time periods 0 to d 1 T and d 1 T to T;
when the input voltage is the forward voltage, the second switch tube S 2 Maintain the on state for the third switch tube S 3 And a sixth switching tube S 6 With duty cycle d 1 For the fourth switching tube S 4 And a fifth switching tube S 5 Applying and third switching tube S 3 And a sixth switching tube S 6 Complementary duty cycle of 1-d 1 PWM on signal of (b);
for the inverter duty cycle T when the input voltage is the reverse voltage, the duty cycle of the PWM signal is set to d 2 Divided into two time periods 0 to d 2 T and d 2 T to T;
when the input voltage is the reverse voltage, the first switch tube S 1 Maintaining the on state for the fourth switching tube S 4 And a fifth switching tube S 5 With duty cycle d 2 For the third switch tube S 3 And a sixth switching tube S 6 Applying and fourth switching tube S 4 And a fifth switching tube S 5 Complementary duty cycle of 1-d 2 Is provided.
Preferably, when the converter is operated at 0 to d 1 At T, the converter is powered by an input AC voltage source V in Third switch tube S 3 Third diode D 3 Output filter capacitor C o Sixth switching tube S 6 Sixth diode D 6 An inductor L and a second switch tube S 2 And a second diode D 2 Forming a loop;
when the converter is operated at d 1 The T-to-T converter consists of an output filter capacitor C o Fifth switch tube S 5 Fifth diode D 5 An inductor L and a second switch tube S 2 Second diode D 2 Fourth switching tube S 4 And a fourth diode D 4 Forming a loop;
when the converter is operated at 0 to d 2 The T-time converter is powered by an input AC voltage source V in Fourth switching tube S 4 Fourth diode D 4 Output filter capacitor C o Fifth switch tube S 5 Fifth diode D 5 An inductor L and a first switch tube S 1 And a first diode D 1 Forming a loop;
when the converter is operated at d 2 The T-to-T converter consists of an output filter capacitor C o Sixth switching tube S 6 Sixth diode D 6 An inductor L and a first switch tube S 1 First diode D 1 Third switch tube S 3 And a third diode D 3 Forming a loop.
Preferably, when the converter is operated at 0 to d 1 At the time of T, the input voltage is positive, and the power is regulatedSense both ends first switch tube S 1 And a second switching tube S 2 Is at high potential, fifth diode D 5 And a sixth diode D 6 The junction point of (2) is low potential, the output voltage is in phase with the input voltage, namely a third diode D 3 And a fifth switch tube S 5 The junction point of (2) is at high potential, the fourth diode D 4 And a sixth switching tube S 6 The junction of (2) is at a low potential, and the volt-second product of the inductance L is d 1 T(V in -V o ) When the converter is operated at d 1 At T to T, the volt-second product of the inductance is (1-d 1 )TV o Then balance d according to volt-seconds in one period 1 T(V in -V o )+(1-d 1 )TV o =0, then the gain M of the converter at this time is expressed as:
Figure BDA0004185267690000031
when the converter is operated at 0 to d 2 T, the input voltage is reversed, and the first switching tube S at the two ends of the inductor is still regulated 1 And a second switching tube S 2 Is at high potential, fifth diode D 5 And a sixth diode D 6 The junction point of (2) is low potential, the output voltage is in phase with the input voltage, namely a third diode D 3 And a fifth switch tube S 5 Is low potential, the fourth diode D 4 And a sixth switching tube S 6 The junction of (2) is at high potential, the volt-second product of the inductance L is d 2 T(V in -V o ) When the converter is operated at d 2 At T to T, the volt-second product of the inductance is (1-d 2 )TV o Then balance d according to volt-seconds in one period 2 T(V in -V o )+(1-d 2 )TV o =0, then the gain M of the converter at this time is expressed as:
Figure BDA0004185267690000032
preferably, when a forward voltage is input, the duty cycle d 1 At 0.When 5 to 1, the voltage gain M is positive, the output voltage is positive, and is in phase with the input voltage, and the output voltage belongs to a positive voltage in-phase output mode, and the duty ratio d 1 When the voltage gain M is negative and the output voltage is reverse and is opposite to the input voltage, the voltage gain M belongs to a forward voltage opposite-phase output mode when the voltage gain M is 0 to 0.5;
when reverse voltage is input, duty ratio d 2 When the voltage gain M is positive and the output voltage is negative and is in phase with the input voltage, the voltage gain M is 0.5 to 1, and the voltage gain M belongs to a reverse voltage in-phase output mode and has a duty ratio d 1 When the voltage gain M is negative and the output voltage is negative in the range of 0 to 0.5, the voltage gain M is opposite to the input voltage and belongs to a reverse voltage opposite phase output mode.
Preferably, when the working mode of the converter belongs to in-phase output, no matter the input voltage is forward or reverse, the duty ratio is in the range of 0.5 to 1, and the range of the voltage gain M is 1 to positive infinity, so that different levels of boosting are realized;
when the working mode of the converter belongs to the reverse output, no matter the input voltage is positive or negative, the duty ratio is in the range of 0 to 0.5, and the range of the voltage gain M is minus infinity to 0, so that the voltage is increased and decreased at different grades.
Compared with the prior art, the invention has the remarkable advantages that: (1) Aiming at the characteristics of the six-open-tube matrix converter, the proposed control strategy is matched with the symmetry of the six-switch matrix converter, the needed switch tube driving is also symmetrical, and the control scheme is simple; (2) The invention can realize the adjustment of the magnitude and frequency of the alternating voltage at the same time, and can be suitable for occasions needing to change the magnitude and frequency of the alternating voltage at the same time, such as controlling the speed of a fan, driving an induction motor and the like; (3) Compared with a control strategy commonly used for a six-switch matrix converter, eight modes of the converter need to be considered, only four modes of the converter need to be considered, and voltage and frequency regulation can be completed simultaneously by changing one variable of the duty ratio.
Drawings
Fig. 1 is a basic circuit topology of a six-switch matrix converter.
FIG. 2 shows the input voltage being positive and the converter operating at 0 to d 1 Circuit mode diagram at T.
FIG. 3 shows the input voltage being positive and the converter operating at d 1 Circuit mode diagram at T to T.
FIG. 4 shows the input voltage being negative and the converter operating at 0 to d 2 Circuit mode diagram at T.
FIG. 5 is a graph of input voltage negative and converter operating at d 2 Circuit mode diagram at T to T.
Fig. 6 is a graph of the duty cycle versus voltage gain.
FIG. 7 is a waveform diagram of the converter operation with an input voltage of 100V/50Hz and an output voltage of 200V/25 Hz.
FIG. 8 is a simulated waveform of an output voltage of 200V/25Hz for an input voltage of 100V/50 Hz.
FIG. 9 is a diagram of the converter operation waveforms for an input voltage of 100V/50Hz and an output voltage of 200V/16.7 Hz.
FIG. 10 is a simulated waveform of an output voltage of 200V/16.7Hz for an input voltage of 100V/50 Hz.
Detailed Description
A control method of a six-switch matrix converter, the specific topological structure of which is shown in figure 1, comprises six switch tubes, six diodes and an input alternating voltage source V in Input filter capacitor C in Inductance L and output filter capacitor C o Load R L The mentioned six-switch matrix converter is symmetrical in structure, so that the converter working modes in the positive and negative directions of the input voltage are symmetrical.
For the mentioned control method, the voltage input by the input voltage source is specified to be positive voltage when the voltage is positive or negative, and is conversely reverse voltage; for the converter duty cycle T when the input voltage is the forward voltage, the duty cycle of the PWM signal is set to d 1 Divided into two time periods 0 to d 1 T and d 1 T to T; for the inverter duty cycle T when the input voltage is the reverse voltage, the duty cycle of the PWM signal is set to d 2 Divided into two time periods 0 to d 2 T and d 2 T to T; four modes of operation of the converter and four periods of operationConcerning, i.e. mention 0 to d 1 T、d 1 T to T, 0 to d 2 T and d 2 T to T.
When the input voltage is the forward voltage, the second switch tube S 2 Maintain the on state for the third switch tube S 3 And a sixth switching tube S 6 With duty cycle d 1 The corresponding converter mode diagram is shown in fig. 2; for the fourth switching tube S 4 And a fifth switching tube S 5 Applying and third switching tube S 3 And a sixth switching tube S 6 Complementary duty cycle of 1-d 1 The corresponding converter mode diagram is shown in fig. 3; when the converter is operated at 0 to d 1 The T-time converter is powered by an input AC voltage source V in Third switch tube S 3 Third diode D 3 Output filter capacitor C o Sixth switching tube S 6 Sixth diode D 6 An inductor L and a second switch tube S 2 And a second diode D 2 Form a loop when the converter is operated at d 1 The T-to-T converter consists of an output filter capacitor C o Fifth switch tube S 5 Fifth diode D 5 An inductor L and a second switch tube S 2 Second diode D 2 Fourth switching tube S 4 And a fourth diode D 4 Forming a loop.
When the input voltage is the reverse voltage, the first switch tube S 1 Maintaining the on state for the fourth switching tube S 4 And a fifth switching tube S 5 With duty cycle d 2 The corresponding converter mode diagram is shown in fig. 4; for the third switch tube S 3 And a sixth switching tube S 6 Applying and fourth switching tube S 4 And a fifth switching tube S 5 Complementary duty cycle of 1-d 2 The corresponding converter mode diagram is shown in fig. 5; when the converter is operated at 0 to d 2 The T-time converter is powered by an input AC voltage source V in Fourth switching tube S 4 Fourth diode D 4 Output filter capacitor C o Fifth switch tube S 5 Fifth diode D 5 An inductor L and a first switch tube S 1 And a first diode D 1 Form a loop when the converter is operated at d 2 The T-to-T converter consists of an output filter capacitor C o Sixth switching tube S 6 Sixth diode D 6 An inductor L and a first switch tube S 1 First diode D 1 Third switch tube S 3 And a third diode D 3 Forming a loop.
When the control method provided by the invention is adopted, the voltage gain is fixed no matter the converter works under the condition of inputting forward voltage or reverse voltage, and the voltage gain is fixed as follows:
Figure BDA0004185267690000051
wherein d is the duty cycle, d is when the forward voltage is input 1 D is the input of reverse voltage 2 。
The relation diagram of the voltage gain M and the duty ratio d is shown in fig. 6, no matter the input voltage is forward or reverse, when the duty ratio is in the range of 0.5 to 1, the range of the voltage gain M is 1 to positive infinity, the working mode of the converter belongs to in-phase output, and the boosting of different levels can be realized; the duty ratio is in the range of 0 to 0.5, and the range of the voltage gain M is minus infinity to 0, and the working mode of the converter belongs to the reverse output, so that the voltage can be increased and decreased at different grades.
The present invention will be further described with reference to the drawings and the specific embodiments.
The input voltage waveform is specified to be a sine wave with the amplitude of 100V and the frequency of 50Hz, and the output voltage waveform is controlled to be respectively in the amplitude of 200V, the frequency of 25Hz and the amplitude of 200V and the frequency of 16.7Hz by taking two examples.
If a waveform with 200V of voltage amplitude and 25Hz of frequency is to be output, firstly, considering the amplitude of the output voltage, when the output voltage is in phase, the voltage gain M is 2, at the moment, the duty ratio can be reversely solved to be 0.67 through a voltage gain formula, when the output voltage is in phase, the voltage gain M is-2, and the duty ratio can be reversely solved to be 0.4 through the voltage gain formula. For a 50Hz sine wave, with a sine period of 0.02 seconds, it is necessary to consider which parts are output in phase and which parts are output in antiphase. To adjust the output frequency to 25Hz, i.e., to double the period to 0.04 seconds, there are two complete sinusoidal periods during which the forward voltage of 0 to 0.01 seconds and the reverse voltage of 0.03 to 0.04 seconds are output in phase, the reverse voltage of 0.01 to 0.02 seconds and the forward voltage of 0.02 to 0.03 seconds are output in phase.
For each large period of 0.04 seconds, the corresponding switching tube operation waveforms are shown in fig. 7:
0 to 0.01 seconds, a second switching tube S 2 Constant conduction to the third switch tube S 3 And a sixth switching tube S 6 Applying PWM wave with duty ratio of 0.67 to fourth switch tube S 4 And a fifth switching tube S 5 Applying and third switching tube S 3 And a sixth switching tube S 6 A PWM wave with complementary control waveforms;
0.01 to 0.02 seconds, a first switching tube S 1 Constant conduction to fourth switch tube S 4 And a fifth switching tube S 5 Applying PWM wave with duty ratio of 0.4 to the third switch tube S 3 And a sixth switching tube S 6 Applying and fourth switching tube S 4 And a fifth switching tube S 5 A PWM wave with complementary control waveforms;
0.02 to 0.03 seconds, a second switching tube S 2 Constant conduction to the third switch tube S 3 And a sixth switching tube S 6 Applying PWM wave with duty ratio of 0.4 to fourth switch tube S 4 And a fifth switching tube S 5 Applying and third switching tube S 3 And a sixth switching tube S 6 A PWM wave with complementary control waveforms;
0.03 to 0.04 seconds, a first switching tube S 1 Constant conduction to fourth switch tube S 4 And a fifth switching tube S 5 Applying PWM wave with duty ratio of 0.67 to the third switch tube S 3 And a sixth switching tube S 6 Applying and fourth switching tube S 4 And a fifth switching tube S 5 And controlling PWM waves with complementary waveforms.
An output voltage simulation waveform diagram for converting an input voltage of 100V/50Hz to an output voltage of 200V/25Hz is shown in FIG. 8.
If a waveform of 200V in frequency 16.7Hz is to be outputted, the case of calculating the duty cycle of the voltage amplitude is the same as that of the waveform of 200V in frequency 25 Hz. Considering that the 50Hz waveform is adjusted to a 16.7Hz waveform, the original period is 0.02 seconds, and the output frequency is adjusted to 16.7Hz, i.e., the period becomes 3 times the original period, i.e., 0.06 seconds, and there are three complete sinusoidal periods. It is necessary to output the forward voltage of 0 seconds to 0.01 seconds, 0.02 seconds to 0.03 seconds, and the reverse voltage of 0.03 seconds to 0.04 seconds, 0.05 to 0.06 seconds in phase, and the reverse voltage of 0.01 seconds to 0.02 seconds and the forward voltage of 0.04 seconds to 0.05 seconds in phase in this period.
For each large period of 0.06 seconds, the corresponding switching tube operation waveforms are as shown in fig. 9:
0 to 0.01 seconds, a second switching tube S 2 Constant conduction to the third switch tube S 3 And a sixth switching tube S 6 Applying PWM wave with duty ratio of 0.67 to fourth switch tube S 4 And a fifth switching tube S 5 Applying and third switching tube S 3 And a sixth switching tube S 6 A PWM wave with complementary control waveforms;
0.01 to 0.02 seconds, a first switching tube S 1 Constant conduction to fourth switch tube S 4 And a fifth switching tube S 5 Applying PWM wave with duty ratio of 0.4 to the third switch tube S 3 And a sixth switching tube S 6 Applying and fourth switching tube S 4 And a fifth switching tube S 5 A PWM wave with complementary control waveforms;
the control waveforms of 0.02 to 0.03 seconds are the same as those of 0 to 0.01 seconds;
0.03 to 0.04 seconds, a first switching tube S 1 Constant conduction to fourth switch tube S 4 And a fifth switching tube S 5 Applying PWM wave with duty ratio of 0.67 to the third switch tube S 3 And a sixth switching tube S 6 Applying and fourth switching tube S 4 And a fifth switching tube S 5 A PWM wave with complementary control waveforms;
0.04 to 0.05 second, a second switching tube S 2 Constant conduction to the third switch tube S 3 And a sixth switching tube S 6 Applying PWM wave with duty ratio of 0.4 to the firstFour-switch tube S 4 And a fifth switching tube S 5 Applying and third switching tube S 3 And a sixth switching tube S 6 A PWM wave with complementary control waveforms;
the control waveforms of 0.05 seconds to 0.06 seconds are the same as those of 0.03 seconds to 0.04 seconds.
An output voltage simulation waveform diagram for converting an input voltage of 100V/50Hz to an output voltage of 200V/16.7Hz is shown in FIG. 10.
The above two examples are only two cases where the control method has a good use effect, and the function of the control method is not limited to the two cases of variable voltage and variable frequency.

Claims (5)

1. A control method of a six-switch matrix converter is characterized in that the six-switch matrix converter comprises a first switch tube S 1 Second switch tube S 2 Third switch tube S 3 Fourth switching tube S 4 Fifth switch tube S 5 And a sixth switching tube S 6 First diode D 1 Second diode D 2 Third diode D 3 Fourth diode D 4 Fifth diode D 5 And a sixth diode D 6 Input AC voltage source V in Input filter capacitor C in Inductance L and output filter capacitor C o Load R L ；
The first switch tube S 1 Source of (C) and first diode D 1 Anode connection of first diode D 1 Cathode of (a) and third switch tube S 3 Drain electrode connection of the third switch tube S 3 Source electrode of (D) and third diode D 3 Anode connection of third diode D 3 Cathode of (a) and fifth switch tube S 5 Drain electrode connection of fifth switch tube S 5 Source of (D) and fifth diode D 5 Anode connection of a second switching tube S 2 Source electrode of (C) and second diode D 2 Anode connection of second diode D 2 Cathode and fourth switching tube S 4 Drain electrode connection of fourth switching tube S 4 Source electrode of (D) and fourth diode D 4 Anode connection of fourth diode D 4 Cathode and sixth switching tube S 6 Is connected with the drain electrode of a sixth switching tube S 6 Source electrode of (D) and sixth diode D 6 Is connected with the anode of the battery;
first switching tube S 1 Drain electrode of (d) and second switch tube S 2 Is connected with the drain electrode of the fifth diode D 5 Cathode and sixth diode D of (2) 6 Is connected with the cathode of the first switch tube S 1 And a second switching tube S 2 Is connected with the fifth diode D 5 And a sixth diode D 6 The connection points of the inductor L are respectively connected with two ends of the inductor L;
third switch tube S 3 With a first diode D 1 Is connected with a fourth switching tube S 4 And a second diode D 2 Respectively with the input filter capacitor C in Is connected with two ends of input AC voltage source V in And input filter capacitor C in Parallel connection;
third diode D 3 And a fifth switch tube S 5 Is connected with the fourth diode D 4 And a sixth switching tube S 6 Respectively with the output filter capacitor C o Is connected with the two ends of the load R L And output filter capacitor C o Parallel connection;
the control method specifically comprises the following steps:
defining a third switching tube S 3 With a first diode D 1 The connection point of (2) is high potential, the fourth switch tube S 4 And a second diode D 2 When the connection point of the voltage source is at low potential, the voltage input by the input voltage source is forward voltage, and conversely, reverse voltage;
for the converter duty cycle T when the input voltage is the forward voltage, the duty cycle of the PWM signal is set to d 1 Divided into two time periods 0 to d 1 T and d 1 T to T;
when the input voltage is the forward voltage, the second switch tube S 2 Maintain the on state for the third switch tube S 3 And a sixth switching tube S 6 With duty cycle d 1 For the fourth switching tube S 4 And a fifth switching tube S 5 Applying and third switching tube S 3 And sixth openingClosing tube S 6 Complementary duty cycle of 1-d 1 PWM on signal of (b);
for the inverter duty cycle T when the input voltage is the reverse voltage, the duty cycle of the PWM signal is set to d 2 Divided into two time periods 0 to d 2 T and d 2 T to T;
when the input voltage is the reverse voltage, the first switch tube S 1 Maintaining the on state for the fourth switching tube S 4 And a fifth switching tube S 5 With duty cycle d 2 For the third switch tube S 3 And a sixth switching tube S 6 Applying and fourth switching tube S 4 And a fifth switching tube S 5 Complementary duty cycle of 1-d 2 Is provided.
2. The method of controlling a six-switch matrix converter according to claim 1, wherein when the converter is operated at 0 to d 1 At T, the converter is powered by an input AC voltage source V in Third switch tube S 3 Third diode D 3 Output filter capacitor C o Sixth switching tube S 6 Sixth diode D 6 An inductor L and a second switch tube S 2 And a second diode D 2 Forming a loop;
when the converter is operated at d 1 The T-to-T converter consists of an output filter capacitor C o Fifth switch tube S 5 Fifth diode D 5 An inductor L and a second switch tube S 2 Second diode D 2 Fourth switching tube S 4 And a fourth diode D 4 Forming a loop;
when the converter is operated at 0 to d 2 The T-time converter is powered by an input AC voltage source V in Fourth switching tube S 4 Fourth diode D 4 Output filter capacitor C o Fifth switch tube S 5 Fifth diode D 5 An inductor L and a first switch tube S 1 And a first diode D 1 Forming a loop;
when the converter is operated at d 2 The T-to-T converter consists of an output filter capacitor C o Sixth openingClosing tube S 6 Sixth diode D 6 An inductor L and a first switch tube S 1 First diode D 1 Third switch tube S 3 And a third diode D 3 Forming a loop.
3. The control method of a six-switch matrix converter according to claim 2, wherein when the converter is operated at 0 to d 1 T, the input voltage is positive, the first switch tube S at two ends of the prescribed inductance 1 And a second switching tube S 2 Is at high potential, fifth diode D 5 And a sixth diode D 6 The junction point of (2) is low potential, the output voltage is in phase with the input voltage, namely a third diode D 3 And a fifth switch tube S 5 The junction point of (2) is at high potential, the fourth diode D 4 And a sixth switching tube S 6 The junction of (2) is at a low potential, and the volt-second product of the inductance L is d 1 T(V in -V o ) When the converter is operated at d 1 At T to T, the volt-second product of the inductance is (1-d 1 )TV o Then balance d according to volt-seconds in one period 1 T(V in -V o )+(1-d 1 )TV o =0, then the gain M of the converter at this time is expressed as:
Figure FDA0004185267650000021
when the converter is operated at 0 to d 2 T, the input voltage is reversed, and the first switching tube S at the two ends of the inductor is still regulated 1 And a second switching tube S 2 Is at high potential, fifth diode D 5 And a sixth diode D 6 The junction point of (2) is low potential, the output voltage is in phase with the input voltage, namely a third diode D 3 And a fifth switch tube S 5 Is low potential, the fourth diode D 4 And a sixth switching tube S 6 The junction of (2) is at high potential, the volt-second product of the inductance L is d 2 T(V in -V o ) When the converter is operated at d 2 At T to T, the volt-second product of the inductance is (1-d 2 )TV o Then balance d according to volt-seconds in one period 2 T(V in -V o )+(1-d 2 )TV o =0, then the gain M of the converter at this time is expressed as:
Figure FDA0004185267650000022
4. the control method of a six-switch matrix converter according to claim 2, wherein the duty ratio d when the forward voltage is input 1 When the voltage gain M is positive and the output voltage is positive and is in phase with the input voltage, the voltage gain M belongs to a positive voltage in-phase output mode, and the duty ratio d 1 When the voltage gain M is negative and the output voltage is reverse and is opposite to the input voltage, the voltage gain M belongs to a forward voltage opposite-phase output mode when the voltage gain M is 0 to 0.5;
when reverse voltage is input, duty ratio d 2 When the voltage gain M is positive and the output voltage is negative and is in phase with the input voltage, the voltage gain M is 0.5 to 1, and the voltage gain M belongs to a reverse voltage in-phase output mode and has a duty ratio d 1 When the voltage gain M is negative and the output voltage is negative in the range of 0 to 0.5, the voltage gain M is opposite to the input voltage and belongs to a reverse voltage opposite phase output mode.
5. The control method of a six-switch matrix converter according to claim 4, wherein when the converter operation mode belongs to in-phase output, the duty ratio is in the range of 0.5 to 1 no matter whether the input voltage is forward or reverse, and the range of the voltage gain M is 1 to positive infinity, so as to realize boosting of different levels;
when the working mode of the converter belongs to the reverse output, no matter the input voltage is positive or negative, the duty ratio is in the range of 0 to 0.5, and the range of the voltage gain M is minus infinity to 0, so that the voltage is increased and decreased at different grades.
CN202310416752.5A 2023-04-19 2023-04-19 Control method of six-switch matrix converter Pending CN116247953A (en)

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