CN115941078A - Receiver multichannel consistency calibration method based on intermediate frequency processing unit - Google Patents
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Abstract
The invention discloses a receiver multichannel consistency calibration method based on an intermediate frequency processing unit, which comprises the steps of firstly setting a reference signal to be composed of two types of signals in a staggered mode, then respectively carrying out nonlinear mismatch detection and calibration, group delay mismatch detection and calibration and amplitude-frequency/phase-frequency response mismatch detection and calibration on the reference signal, then transmitting the results of the nonlinear mismatch detection and calibration, the group delay mismatch detection and calibration and the amplitude-frequency/phase-frequency response mismatch detection and calibration to a calibration network to complete calibration, setting a reference source in the intermediate frequency processing unit, and realizing channel error detection and calibration network by using a digital signal processing algorithm to process the multichannel inconsistency problem of a radio frequency system.
Description
Technical Field
The invention relates to the technical field of channel calibration, in particular to a receiver multichannel consistency calibration method based on an intermediate frequency processing unit.
Background
In a receiver of a radar, communication, electronic countermeasure system using an array antenna or a MIMO multi-antenna, the original parameter characteristics should ideally be completely identical between signal channels. However, in addition to the channel difference of the antenna unit itself, parameters mismatch between different receiving channels is caused by different factors such as T/R component gain, device nonlinearity, filter group delay characteristics, sampling clock desynchronization of multiple parallel ADC devices, etc., which will cause array antenna pattern distortion or loss of orthogonality between streams of MIMO signals, and finally cause the problems of poor overall performance of the receiver, low energy consumption ratio of the device, high cost, etc. Therefore, for the receiver of the radar, communication and electronic countermeasure system with multiple parallel radio frequency channels, the consistency calibration between multiple channels must be carried out, especially considering that the parameters of the multiple channels are often related to the working conditions of the device, and the calibration needs to be carried out in real time or dynamically in the field.
Considering that the above-mentioned radar/communication receiver generally starts with digitization from an intermediate frequency, the main functional digital signal processing processes (such as radar target signal detection, communication signal demodulation and decoding) are performed at the baseband. A special intermediate frequency signal processing unit is often arranged between the analog-to-digital conversion device and the baseband processing unit, and is used for realizing real-time processing of intermediate frequency signal sampling point streams such as frequency spectrum shifting, filtering, sampling point rate conversion, received signal strength detection and the like.
Disclosure of Invention
The invention aims to provide a receiver multichannel consistency calibration method based on an intermediate frequency processing unit, so as to solve the problems of low energy consumption ratio, high cost and the like of channel parameter calibration equipment in the prior art.
In order to achieve the purpose, the invention provides the following technical scheme:
a receiver multi-channel consistency calibration method based on an intermediate frequency processing unit comprises the following steps:
the method comprises the steps of setting a reference signal to be composed of two types of signals in a staggered mode, respectively carrying out nonlinear mismatch detection calibration, group delay mismatch detection calibration and amplitude-frequency/phase-frequency response mismatch detection calibration on the reference signal, transmitting results of the nonlinear mismatch detection and calibration, the group delay mismatch detection and calibration and the amplitude-frequency/phase-frequency response mismatch detection and calibration to a calibration network, and completing calibration.
Preferably, the two types of signals in the reference signal are an LFM signal and a non-linear detection signal, and the non-linear detection signal is composed of a group of single tone signals or two tone sinusoidal signals with frequency point variation.
Preferably, the formula for the LFM signal is:
wherein t is time phi 0 Is a random initial phase and is a complex vector of the random initial phase, a is a linear frequency modulation control factor, T is a modulation symbol period, M is a symbol period number 1/2, and p (T) is a power mask function.
Preferably, the monophonic signal formula is:
x 2,k (t)＝A k cos(2πf k t+θ k )
wherein A is k 、f k And theta k Respectively, the amplitude, frequency and initial phase of the kth tone signal.
Preferably, the two-tone sinusoidal signal is formulated as:
x 3,l (t)＝A′ l [cos(2πf 1,l t+θ 1,l )+cos(2πf 2,l t+θ 2,l )]
wherein, A' l Is the amplitude of the first diphone signal, f 1,l And f 2,l Frequency 1 and frequency 2, theta, respectively, of the first diphone signal 1,l And theta 2,l Initial phase 1 and initial phase 2 of the l-th biphone signal, respectively.
Preferably, the detection target in the detection calibration of the nonlinear mismatch is a nonlinear model, and the nonlinear model is represented as follows:
y(t)＝a 0 +a 1 x+a 2 x 2 +a 3 x 3 +…
where x is the input signal, y is the nonlinear signal, x k For the non-linearly induced k-th order component, a k k =0.1.2.3 \8230andis a coefficient of each order.
Preferably, the purpose of the nonlinear detection is to calculate each order coefficient in the nonlinear model, and after calculating each order coefficient, calibrating the signal y (t) into y' (t) according to the following formula;
preferably, the group delay mismatch detection specifically includes performing sliding correlation on the received signals of each channel, comparing time positions of correlation results, detecting a group delay parameter of each channel, selecting a channel with a maximum group delay value as a reference channel, and performing group delay calibration on other channels by using the reference channel as a reference.
Preferably, the detection and calibration of the mismatch of the amplitude-frequency/phase-frequency response specifically includes detecting a system function related to the body, calculating a frequency domain system function of the channel to be calibrated and the reference channel through the system function related to the body, calculating a frequency domain system function of the filter in the calibration network according to a calculation result, converting the frequency domain system function of the filter into each tap coefficient through IFFT, and placing the tap coefficients into the filter to realize the calibration of the amplitude-frequency/phase-frequency response.
Preferably, the detection and calibration specific formula of the amplitude/phase/frequency response mismatch is as follows:
|H err,k (j ω) | is the amplitude-frequency mismatch characteristic of the kth channel, θ err,k (j ω) is the phase-frequency mismatch characteristic of the kth channel, X ref (j ω) is the signal spectrum after passing through the reference channel, X k (j omega) is a reference signalThe signal spectrum after the kth mismatched channel.
Compared with the prior art, the invention has the following beneficial effects: the invention provides a receiver multichannel consistency calibration method based on an intermediate frequency processing unit, which comprises the steps of firstly setting a reference signal as two types of signals which are formed by interlacing, then respectively carrying out nonlinear mismatch detection and calibration, group delay mismatch detection and calibration and amplitude-frequency/phase-frequency response mismatch detection and calibration on the reference signal, and then transmitting the results of the nonlinear mismatch detection and calibration, the group delay mismatch detection and calibration and the amplitude-frequency/phase-frequency response mismatch detection and calibration to a calibration network to finish calibration.
Drawings
FIG. 1 is a schematic block diagram of the multi-channel consistency calibration of the present invention;
FIG. 2 is a diagram of a reference signal structure according to the present invention;
FIG. 3 is a diagram of FFT spectrum after nonlinear distortion of single-tone signal in accordance with the present invention;
FIG. 4 illustrates the group delay detection principle of the present invention;
FIG. 5 is a schematic diagram of amplitude/phase frequency response mismatch detection and calibration in accordance with the present invention;
fig. 6 is an example of a receiver employing a multi-channel uniformity calibration method.
Detailed Description
The present invention will now be described in further detail with reference to specific examples, which are intended to be illustrative, but not limiting, of the invention.
As shown in FIGS. 1-5, the present invention provides a receiver multi-channel consistency calibration method based on an IF processing unit
(1) Multichannel intermediate frequency processing unit structure with consistency calibration capability
The receiver multichannel consistency calibration method based on the intermediate frequency processing unit adopts a closed loop feedback loop structure adopting a reference signal-mismatch detection-calibration network, and a schematic block diagram of the method is shown in figure 1. A special reference signal source is arranged in the intermediate frequency processing unit, a reference signal passes through a certain transmitter channel and then is connected to each channel of a receiver through a distribution network, and the transmission process of the reference signal does not pass through a transceiving antenna. The reference signal is specially designed, so that the gain, phase, group delay and nonlinear mismatch condition of each channel can be detected. The mismatch detection module and the intermediate frequency processing channel work in parallel, matching parameters of the calibration network can be calculated according to mismatch errors, and the mismatch detection module and the intermediate frequency processing channel feed back the matching parameters to the calibration network. The calibration network is divided into a calibration network 1 and a calibration network 2, and the calibration network 1 is positioned after analog-to-digital conversion and carries out nonlinear calibration on input digital sampling points; the calibration network 2 is located after the conventional intermediate frequency processing path and is constituted by an FIR filter. The FIR filter can complete calibration of various mismatch characteristics such as group delay, amplitude, phase and the like.
(2) Dedicated reference signal design
The multi-channel mismatch condition consists of four characteristics of group delay, amplitude, phase and nonlinearity, and considering that in a broadband receiver, the amplitude and phase characteristics change along with frequency, the amplitude and phase characteristics of the channel are not constants any more, but an amplitude-frequency response curve and a phase-frequency response curve. The reference signal has a sufficient length and consists of two types of signal interleaving. The first type is an LFM signal, which has a good autocorrelation characteristic, is convenient for detecting the group delay characteristic of channels, and has a sufficient frequency width, so that the amplitude frequency and phase frequency response in the whole passband range can be fully scanned. The second signal is a nonlinear detection signal which is composed of a group of single-tone or double-tone sinusoidal signals with frequency point variation and is used for exciting the nonlinear characteristics on a plurality of preset frequency points in the passband range. Fig. 2 is a schematic diagram of a reference signal.
Formula for LFM signal:
wherein phi is 0 The method is a random initial phase, T is a modulation symbol period, M is a symbol period number 1/2, and is a power mask function, and mainly aims to prevent sudden change of burst power so that the burst power rises or falls to meet a power template.
Single tone signal formula:
x 2,k (t)＝A k cos(2πf k t+θ k )
wherein A is k 、f k And theta k Respectively, the amplitude, frequency and initial phase of the kth tone signal.
Two-tone signal formula:
x 3,l (t)＝A′ l [cos(2πf 1,l t+θ 1,l )+cos(2πf 2,l t+θ 2,l )]
wherein, A' l Is the amplitude of the first diphone signal, f 1,l And f 2,l Frequency 1 and frequency 2, theta, respectively, of the first diphone signal 1,l And theta 2,l Respectively, the initial phase.
(3) Detection and calibration of nonlinear mismatch
In an actual ADC, there are not only gain errors and offset errors, but also nonlinearity, and the nonlinear model of the device can be represented by a taylor series as follows:
y(t)＝a 0 +a 1 x+a 2 x 2 +a 3 x 3 +…
where x is the input signal, y is the nonlinear signal, x k Is a non-linearly induced k-th order component, a k Are coefficients of each order. On the premise that the performance is satisfied, it is sufficient that k takes 3, that is, only the nonlinear components below 3 th order of the signal are concerned. The purpose of the non-linear detection is to calculate each a in the model k 。
In the prior art are knownReference signal x, and calculate each a k The input signal y (t) can then be calibrated to y' (t) according to the above formula. To simplify the process, the following formula can be used:
to a is to k The estimation can be obtained by spectral analysis, taking the monophonic reference signal as an example, to illustrate that a k The method of (4). When a monophonic sinusoidal signal is input, the output order-2 component caused by the nonlinearity is the order-2 harmonic component of the monophonic reference signal. Similarly, the output 3 < rd > order component caused by the non-linearity is the 3 < rd > harmonic component of the monophonic reference signal. Performing spectrum analysis on the single-tone signal after nonlinear distortion by FFT, and counting the power of each subharmonic component to estimate a k . Because the nonlinear characteristic of the broadband signal receiver is related to the amplitude and the frequency of an input signal, a group of reference signals covering the frequency range and the amplitude dynamic range of a passband are adopted to carry out multiple estimation, and finally the most accurate a is estimated by fitting k . Fig. 3 is a graph of the FFT spectrum after nonlinear distortion of a single tone signal.
(4) Group delay mismatch detection and calibration
Since the LFM signal in the reference signal has a good autocorrelation characteristic, the group delay parameter of each channel can be detected by performing sliding correlation on the received signal of each channel and comparing the time positions of the correlation results. In order to achieve physical realizability of the FIR filter in (5), the channel with the largest group delay value needs to be selected as the reference channel, and the other channels are subjected to group delay calibration based on the reference channel. In fact, the reference signal is provided with a cyclic prefix for the LFM signal, which ensures that the length of the reference signal is longer than the maximum group delay difference of each channel, so that the calibration of the group delay can be performed in the calibration network 2 together with the amplitude/phase frequency response calibration. Fig. 4 is a single-channel group delay detection method. In the group delay detection, due to the existence of the cyclic prefix in the reference signal, the frequency domain correlation can be used for replacing the time domain sliding correlation, and the operation complexity can be reduced. In particular, considering that the nonlinear mismatch detection in (3) and the FIR coefficient calculation in (5) both use FFT, resource multiplexing is fully possible.
(5) Detection and calibration of amplitude/phase frequency response mismatch
In wideband reception, both the amplitude and frequency response of the radio frequency channel are frequency dependent, i.e. its spectral characteristics are not flat, and the "amplitude-frequency" and "phase-frequency" response curves of the channel must be detected. In consideration of the system function of the detected channel, the amplitude/phase/frequency response is naturally obtained, and the mismatch detection is converted into the system function estimation and the error detection with the system function of the reference channel. Fig. 5 is a schematic diagram of amplitude/phase frequency response mismatch detection. The present invention employs an LFM reference signal that has sufficient frequency width to adequately scan the frequency response over the entire passband. The received LFM signal is locally correlated in the if processing unit to detect its system function. In order to reduce the operation complexity, the local LFM correlation is performed in the frequency domain by adopting FFT, and the system functions of the channel to be calibrated and the reference channel are in the frequency domain. The FIR filter correction coefficient calculation module calculates the frequency domain system function of the FIR filter in the calibration network 2 according to the frequency domain system functions of the channel to be calibrated and the reference channel, changes the frequency domain system function into each tap coefficient through IFFT, and puts the tap coefficients into the FIR filter to realize the calibration of the amplitude-frequency/phase-frequency response. Since the FIR filter has the group delay characteristic, the generated calibration filter coefficient can also complete the calibration of the group delay. The reference channel is typically selected from a certain channel of the multichannel receiver, and in order to ensure causal feasibility of calibrating the FIR filters in the network 2, the channel with the largest group delay must be selected. The reference channel does not need to be calibrated, and the FIR filter can only be equivalent to one delay network by setting proper parameters so as to be consistent with the group delay of each calibrated channel.
Let reference signal be x 0 (t) having a frequency spectrum X 0 (j ω) through a reference channel (with a system function of H) 0 (j ω)) the frequency spectrum of the signal after (j ω)) is X ref (jω)。
X ref (jω)＝X 0 (jω)H 0 (jω)
Then the reference signal x 0 (t) passing through the kth mismatched channel (with a system function of H) k (j ω)) the signal spectrum after (j ω)) is X k (jω)。
X k (jω)＝X 0 (jω)H k (jω)
The mismatch characteristic H of the kth channel with respect to the reference channel err,k (j ω) can be found by:
|H err,k (j ω) | is the amplitude-frequency mismatch characteristic of the kth channel, θ err,k (j ω) is the phase-frequency mismatch characteristic of the kth channel. When the frequency domain system function of the kth FIR filter in the calibration network 2 is made H err,k (j ω), the corrected equivalent frequency domain system function of the kth channel is H 0 And (j omega) is the same as the reference channel, so that the aim of calibration is fulfilled.
Working process of receiver multichannel consistency calibration method based on intermediate frequency processing unit
The workflow of the multi-channel consistency calibration method is composed of a plurality of steps.
a. After the multichannel digital intermediate frequency processing unit is started, initial values (no calibration) are set for a calibration network 1 and a calibration network 2, and an LFM signal correlation detection module starts to carry out local correlation detection on a reference signal;
b. when the correlation peak of the local correlation exceeds the threshold, confirming that the reference signal is detected, and sending a starting signal to the nonlinear detection module by the LFM signal correlation detection module;
c. the nonlinear detection module performs FFT spectrum analysis on the single-tone/double-tone reference signals, and calculates each order coefficient of the nonlinear model according to harmonic energy;
d. putting the coefficient of the nonlinear model into a calibration network 1, and calibrating nonlinear mismatch;
detecting a next reference signal frame by the LFM signal correlation detection circuit, comparing the group delay values of all channels, and selecting the channel with the maximum group delay value as a reference channel;
f. obtaining mismatch calibration parameters of FIR filters of each channel by comparing correlation functions of LFM signals of each channel with reference channels, and putting the mismatch calibration parameters into a calibration network 2;
g. iterating the above process until all the reference signal frames are received;
h. and finishing calibration, switching the distribution network to a normal working mode, and starting normal work of the multi-channel receiver.
The embodiment is as follows:
an example of a receiver employing the multi-channel consistency calibration method of the present invention is given. The receiver has the following characteristics:
1) The receiver mainly comprises a radio frequency unit, an intermediate frequency processing unit and a baseband processing unit;
2) The intermediate frequency processing unit mainly comprises an ADC (analog to digital converter), a DAC (digital to analog converter) and an FPGA (field programmable gate array), wherein the main body (signal processing related part) of the multichannel consistency calibration method is positioned in the FPGA, and the DAC is used for digital to analog conversion of baseband signals;
3) The multichannel consistency calibration method is an off-line method using self reference signals, so that the integral cooperation of all units of a receiver is needed, and the cooperation is controlled by an embedded processor of the receiver;
4) The receiver firstly enters a calibration mode after being powered on and started up, multi-channel consistency calibration is carried out, and a normal working mode is switched to after the calibration is finished. According to the application scene of the receiver, the method can periodically cycle in a calibration mode and a normal working mode when the condition allows, so that the time dynamic multi-channel inconsistency can be corrected;
5) Bottom layer digital signal processing modules such as FFT, FIR filter and the like adopted by the method are common modules in the conventional intermediate frequency processing, and considering that consistency calibration and normal receiving are carried out in a time-sharing way, the method can multiplex the conventional digital signal processing resources with the conventional intermediate frequency processing, so that the method can not remarkably increase the complexity of an intermediate frequency unit;
6) In the receiver example shown in fig. 6, compared with a conventional receiver, only one DAC device, one rf signal distribution network, and one rf reference signal transmission channel are added to the digital if unit. In a typical radar and communication system, a receiver and a transmitter are coupled to form a transceiver. At this time, one path of transmitting channel in the transmitter can be used as the radio frequency reference signal transmitting channel, so that the complexity increment caused by the adoption of the invention can be further reduced.
The invention is widely applied to multi-channel receivers of radar and communication systems, and can obviously improve the coherence among channels and finally improve the system performance. The method can also be applied to other multi-channel systems for improving the channel consistency. Such as sensor arrays, multi-channel stereo systems, multi-channel CT machines, etc., can calibrate and compensate for group delay, nonlinearity, amplitude and phase differences of the channels.
Although the embodiments of the present invention have been described above with reference to the accompanying drawings, the present invention is not limited to the above-described embodiments and application fields, and the above-described embodiments are illustrative, instructive, and not restrictive. Those skilled in the art, having the benefit of this disclosure, may effect numerous modifications thereto without departing from the scope of the invention as defined by the appended claims.
Claims (10)
1. A receiver multi-channel consistency calibration method based on an intermediate frequency processing unit is characterized by comprising the following steps:
the method comprises the steps of setting a reference signal to be composed of two types of signals in a staggered mode, respectively carrying out nonlinear mismatch detection calibration, group delay mismatch detection calibration and amplitude-frequency/phase-frequency response mismatch detection calibration on the reference signal, transmitting results of the nonlinear mismatch detection and calibration, the group delay mismatch detection and calibration and the amplitude-frequency/phase-frequency response mismatch detection and calibration to a calibration network, and completing calibration.
2. The method as claimed in claim 1, wherein the two types of signals in the reference signal are LFM signals and nonlinear detection signals, and the nonlinear detection signals are a group of mono-tone signals or bi-tone sinusoidal signals with frequency variation.
3. The method as claimed in claim 2, wherein the LFM signal has a formula of:
wherein t is time phi 0 The method is characterized in that the method is a random initial phase and a complex vector of the random initial phase, a is a linear frequency modulation control factor, T is a modulation symbol period, M is a symbol period number 1/2, and p (T) is a power mask function.
4. The method of claim 2, wherein the single tone signal formula is as follows:
x 2,k (t)＝A k cos(2πf k t+θ k )
wherein, A k 、f k And theta k Respectively, the amplitude, frequency and initial phase of the kth tone signal.
5. The method as claimed in claim 2, wherein the bi-tone sinusoidal signal formula is:
x 3,l (t)＝A′ l [cos(2πf 1,l t+θ 1,l )+cos(2πf 2,l t+θ 2,l )]
wherein, A' l Is the amplitude of the first two-tone signal, f 1,l And f 2,l Frequency 1 and frequency 2, theta, respectively, of the first diphone signal 1,l And theta 2,l Initial phase 1 and initial phase 2 of the l-th biphone signal, respectively.
6. The method according to claim 1, wherein the detection target in the calibration for detecting the nonlinear mismatch is a nonlinear model represented as follows:
y(t)＝a 0 +a 1 x+a 2 x 2 +a 3 x 3 +…
where x is the input signal, y is the nonlinear signal, x k Is a non-linearly induced k-th order component, a k k =0.1.2.3 \8230andis a coefficient of each order.
7. The method for calibrating the multichannel consistency of the receiver based on the intermediate frequency processing unit as claimed in claim 6, characterized in that the purpose of the nonlinear detection is to calculate coefficients of each order in a nonlinear model, and after calculating the coefficients of each order, calibrate the signal y (t) into y' (t) according to the following formula;
8. the method according to claim 1, wherein the detection of the group delay mismatch specifically comprises performing sliding correlation on the received signals of each channel, comparing time positions of correlation results, detecting a group delay parameter of each channel, selecting a channel with a maximum group delay value as a reference channel, and performing group delay calibration on other channels with the reference channel as a reference.
9. The receiver multichannel consistency calibration method based on the intermediate frequency processing unit as claimed in claim 1, wherein the detection and calibration of the mismatch of the amplitude-frequency/phase-frequency response are specifically that a system function related to the body is detected first, then a frequency domain system function of the channel to be calibrated and a reference channel is calculated through the system function related to the body, then a frequency domain system function of a filter in the calibration network is calculated according to a calculation result, the frequency domain system function of the filter is changed into each tap coefficient through IFFT transformation, and the tap coefficients are placed in the filter, so that the calibration of the amplitude-frequency/phase-frequency response is realized.
10. The method for calibrating the multichannel consistency of the receiver based on the intermediate frequency processing unit as claimed in claim 9, wherein the specific formula for detecting and calibrating the mismatch of the amplitude-frequency/phase-frequency response is as follows:
|H err,k (j ω) | is the amplitude-frequency mismatch characteristic of the kth channel, θ err,k (j ω) is the phase-frequency mismatch characteristic of the kth channel, X ref (j ω) is the signal spectrum after passing through the reference channel, X k And (j omega) is a signal spectrum of the reference signal after passing through the kth mismatched channel.
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