CN115833592A - Control method of resonant converter - Google Patents
Control method of resonant converter Download PDFInfo
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- CN115833592A CN115833592A CN202111104034.1A CN202111104034A CN115833592A CN 115833592 A CN115833592 A CN 115833592A CN 202111104034 A CN202111104034 A CN 202111104034A CN 115833592 A CN115833592 A CN 115833592A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a control method of a resonant converter, wherein the resonant converter comprises an inverter circuit, a resonant cavity, a clamping branch, a transformer and a secondary side rectifying and filtering circuit, and is characterized in that: dividing the input voltage into three intervals by a first set voltage and a second set voltage, wherein the first set voltage is less than the second set voltage; when the input voltage is less than the first set voltage and less than or equal to the second set voltage, the resonant converter works in an asymmetric PWM mode: the proportion of one of the positive voltage and the negative voltage of the midpoint voltage Vab of the left bridge arm and the right bridge arm of the inverter circuit is 50 percent, and the proportion of the other one of the positive voltage and the negative voltage of the left bridge arm and the right bridge arm is less than 50 percent, and the gain of the converter is controlled by adjusting the proportion of the midpoint voltage Vab to be the positive voltage and the negative voltage. The invention can ensure that the voltage gain of the resonant converter is continuous in the whole input voltage range, has no voltage jump, does not need to increase the transition process, and has narrower frequency change range.
Description
Technical Field
The present invention relates to switching converter control, and more particularly to closed loop control of a resonant converter.
Background
Because the resonance can realize ZVS (zero voltage switching) and quasi ZCS (zero current switching), it is often used in high frequency high power density converters. When the input voltage or output voltage range is wide, if the traditional PFM mode is adopted to perform closed-loop control on the resonance, the frequency conversion in a wide range is required, which is not beneficial to the design of the filter.
Milan M.
In the paper "On-the-Fly Topology-tuning Control Optimization Method for resonating resonance transducers Operating in Win the ide Input-and/or Output-Voltage Range, a half-bridge-full-bridge switching scheme is adopted for a traditional resonance topology, so that resonance can work at the highest Input Voltage: the lowest input voltage is 4.
FIG. 1 is a schematic diagram of a typical clamped resonant converter including an inverter circuit, a resonant circuit, a clamping branch, a transformer, and a secondary rectifier filter circuit; the inverter circuit comprises a switching tube Q1, a switching tube Q2, a switching tube Q3 and a switching tube Q4, wherein the drain electrode of the switching tube Q1 is simultaneously connected with the drain electrode of the switching tube Q3 and the positive end of an input voltage, the source electrode of the switching tube Q1 is connected with the drain electrode of the switching tube Q2, the connection point is the midpoint of a left bridge arm and is marked as a, the source electrode of the switching tube Q3 is connected with the drain electrode of the switching tube Q4, the connection point is the midpoint of a right bridge arm and is marked as b, and the source electrode of the switching tube Q2 is simultaneously connected with the source electrode of the switching tube Q4 and the negative end of the input voltage; the resonant circuit comprises a resonant inductor Lr, an excitation inductor Lm and a capacitor Cr, wherein one end of the capacitor Cr is connected with a point a, the other end of the capacitor Cr is connected with one end of the resonant inductor Lr, the other end of the resonant inductor Lr is simultaneously connected with one end of the excitation inductor Lm and one end of a primary winding of the transformer, and the other end of the excitation inductor Lm and the other end of the primary winding of the transformer are simultaneously connected with a point b; the clamping branch comprises a switching tube Q5 and a switching tube Q6, the drain electrode of the switching tube Q5 is connected with the other end of the capacitor Cr, the source electrode of the switching tube Q5 is connected with the source electrode of the switching tube Q6, the drain electrode of the switching tube Q6 is connected with a point b, and the clamping branch is used for clamping current in the resonant inductor Lr, so that zero-voltage switching-on of the switching tube in the inverter circuit in the soft starting process is realized.
The clamped resonant converter shown in fig. 1 can operate in a narrower frequency range than conventional resonance over the same input voltage range. In patent document CN110768535A, a wide gain control method for a variable topology resonant converter, the following operation modes are proposed for a clamping resonant converter to improve efficiency:
the low-voltage input works in a full-bridge PFM mode; the medium-voltage input works in a full-bridge PWM mode; the high voltage input operates in a half bridge PWM mode. The control method is schematically shown in fig. 2, the driving of the switching tube Q1 is consistent with that of the switching tube Q4, the driving of the switching tube Q2 is consistent with that of the switching tube Q3, the driving of the switching tube Q1 is complementary with that of the switching tube Q2, the duty ratio of each switching tube is 50%, and the switching tubes Q5 and Q6 are turned off.
Fig. 2 can widen the input voltage range or the output voltage range of the clamped resonant converter within a relatively narrow frequency variation range, but a transient transition process still needs to be introduced between the full-bridge PWM mode and the half-bridge PWM mode, and the control complexity is still relatively high.
In summary, in the clamped resonant converter, various control methods can be adopted for the same input and output voltages, and how to set the control methods in a wide range of the input voltage currently leaves a wide range of the input voltage or the output voltage to be researched and innovated.
Disclosure of Invention
In view of the above, the technical problems to be solved by the present invention are: the control method of the resonant converter is provided, under the condition that the output voltage gain range of the clamping resonant converter is ensured to be wide, control signal mutation does not exist among all input voltage points in steady-state control, a dynamic transition process does not need to be introduced among modes, and the control complexity is reduced.
The technical scheme adopted by the invention is as follows:
a control method of a resonant converter comprises an inverter circuit, a resonant circuit, a clamping branch circuit, a transformer and a secondary side rectifying and filtering circuit, and is characterized in that:
dividing the input voltage into three intervals by a first set voltage and a second set voltage, wherein the first set voltage is less than the second set voltage;
when the input voltage is less than the first set voltage and less than or equal to the second set voltage, the resonant converter works in an asymmetric PWM mode: the proportion of one of the positive voltage and the negative voltage of the midpoint voltage Vab of the left bridge arm and the right bridge arm of the inverter circuit is 50 percent, and the proportion of the other one of the positive voltage and the negative voltage of the left bridge arm and the right bridge arm is less than 50 percent, and the gain of the converter is controlled by adjusting the proportion of the midpoint voltage Vab to be the positive voltage and the negative voltage.
Further, the ratio of the midpoint voltage Vab to the positive voltage is 50%, and the method for adjusting the ratio of the midpoint voltage Vab to the positive voltage and the negative voltage includes: the proportion of the midpoint voltage Vab to the positive voltage is kept constant, and the proportion of the midpoint voltage Vab to the negative voltage is changed.
One of the methods for changing the ratio of the midpoint voltage Vab to the negative voltage is: the midpoint voltage Vab is a positive voltage at the beginning of each cycle, then becomes a negative voltage, and finally becomes a zero voltage, and the duty ratio of the midpoint voltage Vab is changed to a negative voltage by changing the position of the rising edge of the midpoint voltage Vab from the negative voltage to the zero voltage.
The second method for changing the ratio of the midpoint voltage Vab to the negative voltage is: the midpoint voltage Vab is a positive voltage, then a zero voltage, then a negative voltage, and finally a zero voltage at the beginning of each cycle, and the midpoint voltage Vab is changed to a negative voltage by changing the positions of the falling edge of the midpoint voltage Vab from the zero voltage to the negative voltage and the rising edge of the midpoint voltage Vab from the negative voltage to the zero voltage at the same time while keeping the center position of the midpoint voltage Vab constant.
The third method for changing the ratio of the midpoint voltage Vab to the negative voltage is: the midpoint voltage Vab becomes a positive voltage at the beginning of each period, then becomes a zero voltage, and finally becomes a negative voltage, and the duty ratio of zero to the negative voltage is changed by changing the midpoint voltage Vab to the position of the falling edge of the zero voltage to the negative voltage.
Further, the proportion of the midpoint voltage Vab as a negative voltage is 50%, and the method for adjusting the proportion of the midpoint voltage Vab as a positive voltage and a negative voltage is as follows: the proportion of the midpoint voltage Vab being a negative voltage is kept constant, and the proportion of the midpoint voltage Vab being a positive voltage is changed.
Preferably, the first setting voltage is NVo, the second setting voltage is 2nvo, n is the turn ratio of the primary winding and the secondary winding of the transformer, and Vo is the output voltage of the resonant converter.
Further, when the input voltage is less than or equal to the first setting voltage, the resonant converter works in a full-bridge PFM mode: the ratio of the positive voltage to the negative voltage of the midpoint voltage Vab of the left bridge arm and the right bridge arm of the inverter circuit is respectively 50%, and the gain of the converter is controlled by adjusting the switching frequency.
Further, when the "input voltage > the second set voltage", the clamping resonant converter operates in the half-bridge PWM mode: one switching tube in one of the left bridge arm and the right bridge arm of the inverter circuit is constantly switched on, and the other switching tube is constantly switched off; the other bridge arm is a working bridge arm, the driving phases of two switching tubes are different by 180 degrees, the duty ratios are the same, and both the duty ratios are less than 50 percent; the working time sequence of the clamping branch circuit is that when any one switching tube of the working bridge arm is switched on, the clamping branch circuit is switched off, and when both switching tubes of the working bridge arm are switched off, the clamping branch circuit is switched on; the gain of the converter is controlled by adjusting the duty ratio of the two switching tubes of the working bridge arm.
Preferably, the inverter circuit includes a switching tube Q1, a switching tube Q2, a switching tube Q3 and a switching tube Q4, a drain of the switching tube Q1 is connected to a drain of the switching tube Q3 and a positive end of the input voltage, a source of the switching tube Q1 is connected to a drain of the switching tube Q2, the connection point is a midpoint of a left arm and is denoted as a, a source of the switching tube Q3 is connected to a drain of the switching tube Q4, the connection point is a midpoint of a right arm and is denoted as b, and a source of the switching tube Q2 is connected to a source of the switching tube Q4 and a negative end of the input voltage; the resonant circuit comprises a resonant inductor Lr, an excitation inductor Lm and a capacitor Cr, wherein one end of the capacitor Cr is connected with a point a, the other end of the capacitor Cr is connected with one end of the resonant inductor Lr, the other end of the resonant inductor Lr is simultaneously connected with one end of the excitation inductor Lm and one end of a primary winding of a transformer, and the other end of the excitation inductor Lm and the other end of the primary winding of the transformer are simultaneously connected with a point b; the clamping branch comprises a switching tube Q5 and a switching tube Q6, the drain electrode of the switching tube Q5 is connected with the other end of the capacitor Cr, the source electrode of the switching tube Q5 is connected with the source electrode of the switching tube Q6, and the drain electrode of the switching tube Q6 is connected with a point b.
Based on the technical scheme, compared with the prior art, the invention has the following beneficial effects:
(1) The input voltage is divided into three intervals, the clamping resonant converter works in an asymmetric PWM mode when the input voltage is in a medium-voltage section, and the gain of the converter is controlled by adjusting the proportion of positive and negative voltages of the midpoint voltage of a bridge arm, so that the clamping resonant converter can work in the occasions with a wider input voltage range or a wider output voltage range;
(2) The gain of the clamping resonant converter in three input voltage intervals is continuous, the working mode switching does not need transition, and the control complexity is low.
Drawings
The invention is further illustrated by means of the attached drawings, but the embodiments in the drawings do not constitute any limitation to the invention, and for a person skilled in the art, other drawings can be obtained on the basis of the following drawings without inventive effort.
FIG. 1 is a schematic diagram of a typical clamped resonant converter;
FIG. 2 is a driving curve of each switching tube of the clamping resonant converter in the full-bridge PFM mode;
FIG. 3 is a midpoint voltage curve of two bridge arms of three implementation methods of the clamped resonant converter in an asymmetric PWM mode;
FIG. 4 is a driving curve of each switching tube in a third implementation method of the clamping resonant converter in the asymmetric PWM mode;
FIG. 5 is a driving curve of each switching tube of the clamped resonant converter in the half-bridge PWM mode;
FIG. 6 is an output voltage gain curve of a clamped resonant converter.
Detailed Description
The principle diagram of the clamping resonant converter related by the invention is the prior art shown in fig. 1, and the innovation point of the invention is that the following control method is provided for the steady-state control of the clamping resonant converter:
dividing the input voltage into three intervals by a first set voltage and a second set voltage, wherein the first set voltage is less than the second set voltage;
when the input voltage is less than or equal to the first set voltage, no requirement is made on the working mode of the clamping resonant converter, and because the efficiency of the clamping resonant converter in the region working in the full-bridge PFM mode is higher, the invention preferably works in the full-bridge PFM mode in the voltage interval: when fs = fr, fs is a switching frequency, fr is a resonant frequency, the driving of each switching tube is the same as that in fig. 2, the positive voltage and the negative voltage of the midpoint of the two bridge arms on the primary side relative to the voltage Vab account for 50% respectively, the gain of the converter is controlled by adjusting the switching frequency, and under the control mode, the clamping branch composed of the switching tubes Q5 and Q6 is always in an off state. In addition, the clamp resonant converter works in a full-bridge PFM mode, when fs = fr, the gain G = Vo/Vin =1/N of the clamp resonant converter, therefore Vin = NVo, and therefore the first setting voltage is preferably NVo.
When the input voltage is less than the first set voltage and less than or equal to the second set voltage, the invention requires the clamping resonant converter to work in an asymmetric PWM mode: the positive and negative asymmetry of the midpoint voltages Vab of the two bridge arms on the primary side includes the following two situations:
(1) The proportion of positive voltage is 50%, the proportion of negative voltage is less than 50%, the proportion of positive voltage is kept unchanged, and the gain of the converter is changed by changing the proportion of negative voltage. Fig. 3 shows three implementation methods for maintaining 50% of the positive voltage proportion and changing the negative voltage proportion: the method I is characterized in that the midpoint voltage Vab of the bridge arm is positive voltage at the beginning of each period, then becomes negative voltage, finally becomes zero voltage, and the proportion of the midpoint voltage Vab as the negative voltage to the negative voltage is changed by changing the midpoint voltage Vab as the position of the rising edge of the negative voltage to the zero voltage, so that the gain of the converter is changed; the method II comprises the steps that the midpoint voltage Vab of the bridge arm is positive voltage at the beginning of each period, then becomes zero voltage, then becomes negative voltage, finally becomes zero voltage, the midpoint voltage Vab is kept to be the central position of the negative voltage, the position of the falling edge of the midpoint voltage Vab changing into the negative voltage and the position of the rising edge of the midpoint voltage Vab changing into the negative voltage are changed simultaneously, so that the proportion of the midpoint voltage Vab changing into the negative voltage is changed, and the gain of the converter is changed; changing the midpoint voltage Vab of the bridge arm into a positive voltage, then changing the midpoint voltage Vab into a zero voltage, finally changing the midpoint voltage Vab into a negative voltage, changing the midpoint voltage Vab into the proportion of the negative voltage by changing the midpoint voltage Vab into the position of a falling edge of the negative voltage, and changing the gain of the converter; fig. 4 shows a driving curve of the switching tube in the third implementation method, in which the switching tube Q1 and the switching tube Q2 are driven complementarily, the duty ratios are respectively 50%, the rising edge of the switching tube Q4 is identical to the switching tube Q1, the duty ratio of the switching tube Q4 is greater than 50%, and the switching tube Q3 and the switching tube Q4 are driven complementarily. By adjusting the duty ratio of the switching tubes Q3 and Q4, the duty ratio of the arm midpoint voltage Vab to the negative voltage can be adjusted, thereby changing the gain of the converter.
(2) The proportion of positive voltage is less than 50%, the proportion of negative voltage is kept unchanged, and the gain of the converter is changed by changing the proportion of positive voltage.
When the input voltage is larger than the second set voltage, the working mode of the clamping resonant converter is not required, and the efficiency of the clamping resonant converter in the area working in the half-bridge PWM mode is higher, so the invention preferably works in the half-bridge PWM mode in the voltage interval: one switching tube in one of the two bridge arms on the primary side is constantly conducted, the other switching tube is constantly turned off, the other bridge arm is a working bridge arm, the driving phases of the upper tube and the lower tube are different by 180 degrees, the duty ratios are the same and are less than 50 percent, the clamping branch and the two tubes of the working bridge arm work complementarily, namely when any one switching tube of the working bridge arm is conducted, the clamping branch is disconnected, and when the two tubes of the working bridge arm are both turned off, the clamping branch is conducted. The gain of the converter is adjusted by adjusting the duty ratio of two switching tubes of the working bridge arm. The driving of each switching tube is as shown in fig. 5, wherein the driving duty ratios of the switching tube Q1 and the switching tube Q2 are the same, the phase difference is 180 degrees, the switching tube Q3 is turned off constantly, the switching tube Q4 is turned on constantly, the driving of the switching tube Q5 is complementary to the driving of the switching tube Q1, and the driving of the switching tube Q6 is complementary to the driving of the switching tube Q1. The converter gain is adjusted by adjusting the duty ratio of the switching tube Q1. In addition, the clamped resonant converter operates in a half-bridge PWM mode, and when fs = fr, G = Vo/Vin =1/2N, so Vin = NVo, and therefore the second setting voltage is preferably 2NVo.
Fig. 6 is a gain curve of the control method, where the abscissa axis represents the switching frequency fs and the ordinate axis represents the gain G, and it can be seen from fig. 6 that, when the switching frequency fs is smaller than the resonant frequency fr of the resonant inductor Lr and the capacitor Cr, the converter operates in the low-voltage full-bridge PFM mode, and the gain is adjusted by adjusting the operating frequency; when the switching frequency fs is equal to the resonance frequency fr and the duty ratio of the switching tube Q1 is 50%, the converter works in an asymmetric PWM (pulse-width modulation) working mode, and the gain is adjusted by adjusting the duty ratio D4 of the switching tube Q4; when the switching frequency fs is equal to the resonant frequency fr and the duty ratio of the switching tube Q4 is 100%, the converter works in a half-bridge PWM mode, and the gain is adjusted by adjusting the duty ratio D1 of the switching tube Q1. As can be seen from fig. 6, the gains of the three control modes are continuous and have no jump, so that the switching process between the full bridge and the half bridge is not required to be set in the full-input voltage control process, thereby reducing the control complexity.
It should be noted that the clamping resonant converter shown in fig. 1 should not be considered as a limitation to the specific circuit to which the present invention is applied, and other types of resonant converters with clamping branches also have the problems described in the background art, and the present invention is also applicable, for example, the resonant inductor Lr in fig. 1 is moved to a position between the center tap of the secondary winding and the connection point of the output filter capacitor Co and the output negative terminal Vo — and, for example, the transformer adopts a structure in which the primary side is connected in series and the secondary side is connected in parallel.
The above embodiments are only for the understanding of the inventive concept of the present application and are not intended to limit the present invention, and any modification, equivalent replacement, improvement, etc. made by those skilled in the art without departing from the principle of the present invention should be included in the protection scope of the present invention.
Claims (10)
1. A control method of a resonant converter comprises an inverter circuit, a resonant circuit, a clamping branch circuit, a transformer and a secondary side rectifying and filtering circuit, and is characterized in that:
dividing the input voltage into three intervals by a first set voltage and a second set voltage, wherein the first set voltage is less than the second set voltage;
when the input voltage is less than the first set voltage and less than or equal to the second set voltage, the resonant converter works in an asymmetric PWM mode: the proportion of one of the positive voltage and the negative voltage of the midpoint voltage Vab of the left bridge arm and the right bridge arm of the inverter circuit is 50 percent, and the proportion of the other one of the positive voltage and the negative voltage of the left bridge arm and the right bridge arm is less than 50 percent, and the gain of the converter is controlled by adjusting the proportion of the midpoint voltage Vab to be the positive voltage and the negative voltage.
2. The method for controlling a resonant converter according to claim 1, wherein the ratio of the midpoint voltage Vab to the positive voltage is 50%, and the method for adjusting the midpoint voltage Vab to the ratio of the positive voltage to the negative voltage is: the proportion of the midpoint voltage Vab to the positive voltage is kept constant, and the proportion of the midpoint voltage Vab to the negative voltage is changed.
3. The method of controlling the resonant converter according to claim 2, wherein the method of changing the ratio of the midpoint voltage Vab to the negative voltage is: the midpoint voltage Vab is a positive voltage at the beginning of each cycle, then becomes a negative voltage, and finally becomes a zero voltage, and the duty ratio of the midpoint voltage Vab is changed to a negative voltage by changing the position of the rising edge of the midpoint voltage Vab from the negative voltage to the zero voltage.
4. The method of controlling the resonant converter according to claim 2, wherein the method of changing the ratio of the midpoint voltage Vab to the negative voltage is: the midpoint voltage Vab is a positive voltage, then a zero voltage, then a negative voltage, and finally a zero voltage at the beginning of each cycle, and the midpoint voltage Vab is changed to a negative voltage by changing the positions of the falling edge of the midpoint voltage Vab from the zero voltage to the negative voltage and the rising edge of the midpoint voltage Vab from the negative voltage to the zero voltage at the same time while keeping the center position of the midpoint voltage Vab constant.
5. The method of controlling the resonant converter according to claim 2, wherein the method of changing the ratio of the midpoint voltage Vab to the negative voltage is: the midpoint voltage Vab becomes a positive voltage at the beginning of each period, then becomes a zero voltage, and finally becomes a negative voltage, and the duty ratio of zero to the negative voltage is changed by changing the midpoint voltage Vab to the position of the falling edge of the zero voltage to the negative voltage.
6. The method for controlling a resonant converter according to claim 1, wherein the ratio of the midpoint voltage Vab to the negative voltage is 50%, and the method for adjusting the midpoint voltage Vab to the ratio of the positive voltage to the negative voltage comprises: the proportion of the midpoint voltage Vab being a negative voltage is kept constant, and the proportion of the midpoint voltage Vab being a positive voltage is changed.
7. The method of controlling a resonant converter according to claim 1, wherein: the first set voltage is NVo, the second set voltage is 2NVo, N is the turn ratio of a primary winding and a secondary winding of the transformer, and Vo is the output voltage of the resonant converter.
8. The method of controlling a resonant converter according to claim 1, wherein: when the input voltage is less than or equal to the first set voltage, the resonant converter works in a full-bridge PFM mode: the ratio of the positive voltage to the negative voltage of the midpoint voltage Vab of the left bridge arm and the right bridge arm of the inverter circuit is respectively 50%, and the gain of the converter is controlled by adjusting the switching frequency.
9. The method of controlling a resonant converter according to claim 1, wherein: when the input voltage is larger than the second set voltage, the clamping resonant converter works in a half-bridge PWM mode: one switching tube in one of the left bridge arm and the right bridge arm of the inverter circuit is constantly switched on, and the other switching tube is constantly switched off; the other bridge arm is a working bridge arm, the driving phases of two switching tubes are different by 180 degrees, the duty ratios are the same, and both the duty ratios are less than 50 percent; the working time sequence of the clamping branch circuit is that when any one switching tube of the working bridge arm is switched on, the clamping branch circuit is switched off, and when two switching tubes of the working bridge arm are switched off, the clamping branch circuit is switched on; the gain of the converter is controlled by adjusting the duty ratio of the two switching tubes of the working bridge arm.
10. The method of controlling a resonant converter according to claim 1, wherein:
the inverter circuit comprises a switching tube Q1, a switching tube Q2, a switching tube Q3 and a switching tube Q4, wherein the drain electrode of the switching tube Q1 is simultaneously connected with the drain electrode of the switching tube Q3 and the positive end of an input voltage, the source electrode of the switching tube Q1 is connected with the drain electrode of the switching tube Q2, the connection point is the midpoint of a left bridge arm and is marked as a, the source electrode of the switching tube Q3 is connected with the drain electrode of the switching tube Q4, the connection point is the midpoint of a right bridge arm and is marked as b, and the source electrode of the switching tube Q2 is simultaneously connected with the source electrode of the switching tube Q4 and the negative end of the input voltage;
the resonant circuit comprises a resonant inductor Lr, an excitation inductor Lm and a capacitor Cr, wherein one end of the capacitor Cr is connected with a point a, the other end of the capacitor Cr is connected with one end of the resonant inductor Lr, the other end of the resonant inductor Lr is simultaneously connected with one end of the excitation inductor Lm and one end of a primary winding of a transformer, and the other end of the excitation inductor Lm and the other end of the primary winding of the transformer are simultaneously connected with a point b;
the clamping branch comprises a switching tube Q5 and a switching tube Q6, the drain electrode of the switching tube Q5 is connected with the other end of the capacitor Cr, the source electrode of the switching tube Q5 is connected with the source electrode of the switching tube Q6, and the drain electrode of the switching tube Q6 is connected with a point b.
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|---|---|---|---|
| CN202111104034.1A CN115833592A (en) | 2021-09-18 | 2021-09-18 | Control method of resonant converter |
| PCT/CN2022/119255 WO2023041023A1 (en) | 2021-09-18 | 2022-09-16 | Control method for resonant converter |
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| CN202111104034.1A CN115833592A (en) | 2021-09-18 | 2021-09-18 | Control method of resonant converter |
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| CN102723876A (en) * | 2012-06-08 | 2012-10-10 | 上海市电力公司 | Full-bridge series resonant converter topological structure |
| US9281753B2 (en) * | 2012-07-31 | 2016-03-08 | General Electric Company | LLC converter with dynamic gain transformation for wide input and output range |
| CN105978356A (en) * | 2016-07-05 | 2016-09-28 | 陕西科技大学 | Active clamp in series and parallel connection to full bridge DC/DC converter |
| CN110768535B (en) * | 2019-10-22 | 2021-09-14 | 广州金升阳科技有限公司 | Wide gain control method of variable topology LLC resonant converter |
| CN112087147B (en) * | 2020-09-28 | 2022-05-20 | 广州金升阳科技有限公司 | Converter wide gain control method and application thereof |
| CN112713780B (en) * | 2020-12-30 | 2022-03-11 | 江苏南自通华智慧能源股份有限公司 | Asymmetric voltage matching phase-shifting control method for double-active-bridge converter |
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2021
- 2021-09-18 CN CN202111104034.1A patent/CN115833592A/en active Pending
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2022
- 2022-09-16 WO PCT/CN2022/119255 patent/WO2023041023A1/en unknown
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| WO2023041023A1 (en) | 2023-03-23 |
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