CN115685076A - Low sidelobe transceiving beam forming method based on cylindrical array - Google Patents
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Abstract
The invention relates to a low sidelobe transceiving beam forming method based on a cylindrical array, which is used for solving the defect that the sidelobe level of transmitting and receiving beams of the existing cylindrical phased array radar is too high. The invention decouples the cylindrical array into a pitching uniform linear array and an azimuth uniform circular array or an arc array when the cylindrical array points at a certain wave beam, and respectively carries out low side lobe processing on the pitching dimension and the azimuth dimension when transmitting and receiving wave beams are formed, thereby finally realizing the low side lobe effect of the whole array, wherein the transmitting wave beam adopts unique phase weighting, and the receiving wave beam adopts amplitude-phase weighting.
Description
Technical Field
The invention particularly relates to a low sidelobe beam forming method based on a cylindrical phased array radar, which simultaneously comprises the formation of transmitting and receiving low sidelobe beams and belongs to the field of phased array radar beam forming.
Background
Conformal arrays not only have good aerodynamic properties, can save carrier space and achieve wide-angle scanning, but also can reduce the interaction between the RCS (radar scattering cross-sectional area) and the antenna/radome. Therefore, the conformal array has wide development and application prospects in the field of phased array radars.
The cylindrical array is taken as a typical conformal array, and the advantages of the circular array and the linear array are combined. Therefore, the method can inherit the non-distortion of the omni-directional electric scanning directional diagram of the circular array, and can also make up for the defect that the target resolution of the circular array is lost due to the fact that the wave beam of the pitch dimension is too wide.
However, the cylindrical array combines the advantages of the circular array and the linear array, and inherits the disadvantages of the circular array, which is mainly reflected in the overhigh azimuth dimension sidelobe level. The side lobe of the transmitted wave beam is too high, so that the wave beam is easy to irradiate the ground, and the intensity of the ground clutter is greatly improved; when the side lobe of the receive beam is too high, the target echo entering from the side lobe is detected, causing a false alarm. However, most methods of reducing side lobes involve density weighting or amplitude weighting. For the transmitting beam, although the density weighting is adopted, the side lobe can be effectively reduced, the complexity of the array layout and the feed network is greatly increased, and the amplitude weighting is adopted, although the array layout is simple and easy to implement, the difficulty is caused when the system is physically realized, such as:
1. the phased array radar usually needs to carry out fast wave position scanning, and frequent and fast control of the size of excitation current not only has extremely high cost, but also is difficult to realize in engineering;
2. the amplitude weighting can cause the excitation current to be reduced, the transmitting power cannot reach full bias, and the detection distance of the radar and the detection capability of a weak target are reduced.
Therefore, it is very important to design a low sidelobe transmit-receive beamforming scheme suitable for the cylindrical phased array radar.
Disclosure of Invention
In order to solve the defect that the sidelobe level of the transmitting and receiving wave beams of the existing cylindrical phased array radar is too high, the invention provides a transmitting and receiving low sidelobe wave beam forming method based on a cylindrical array. The invention decouples the cylindrical array into a pitching uniform linear array and an azimuth uniform circular array or an arc array when the cylindrical array points at a certain wave beam, and respectively carries out low side lobe processing on the pitching dimension and the azimuth dimension when transmitting and receiving the wave beam, and finally realizes the low side lobe effect of the whole array, wherein the transmitting wave beam adopts unique phase weighting, and the receiving wave beam adopts amplitude-phase weighting. The low sidelobe of the transmitting and receiving wave beams is realized, the problem of complex array distribution and feed network caused by density weighting and amplitude weighting is solved, and the problem of transmission gain reduction caused by amplitude weighting is solved.
Further, in the process of forming a receiving beam, when low sidelobe processing is performed on an azimuth dimension, an improved virtual interference method is adopted to search the weight of each array element, the improved virtual interference method is characterized in that K virtual interferences are uniformly arranged in a region outside the 3dB beam width of a receiving beam azimuth dimension directional diagram by constructing a cost function, the interference intensity of the K virtual interferences is iterated continuously to update the autocorrelation matrix of interference receiving signals, the autocorrelation matrix of non-ideal receiving signals is recalculated through the updated autocorrelation matrix of the interference receiving signals, and then the weight W corresponding to each iteration is calculated according to the ADBF principle t And the directional diagram enables the directional diagram to be continuously approximate to the ideal low-sidelobe directional diagram, and when the cost function meets the requirement, an expected weight W is obtained t And the corresponding directional diagram is the directional diagram which finally meets the requirements.
Further, the interference strength Γ of the kth virtual interference is iterated for the tth time t,k The calculation process of (2) is as follows: firstly, at the kth virtual interference position, calculating the sidelobe level of the ideal directional diagram Pattern0 and the directional diagram obtained by the t-1 th iteration respectively, and making a difference to obtain the sidelobe level difference D at the kth virtual interference position of the current tth iteration t,k K =1 … K; then, using D t,k Correcting the interference strength gamma of the kth virtual interference obtained in the previous iteration t-1,k Selecting a non-negative correction value as the disturbance intensity gamma of the kth virtual disturbance in the tth iteration t,k 。
Further, the weight W corresponding to each iteration t And multiplying a steering vector which is equal to the direction of the expected beam by an inverse matrix of an autocorrelation matrix of the non-ideal received signal, wherein the autocorrelation matrix of the non-ideal received signal comprises an autocorrelation matrix of the interference received signal and an autocorrelation matrix of the noise received signal, the two autocorrelation matrices comprise square matrices of L rows and L columns, L is the number of array elements adopted in azimuth beam forming, and the noise is unchanged.
Go toStep (b), the weight W is updated t times t The latter cost function is weight W t Highest side lobe SLL of lower obtained directional diagram 1 With desired integral sidelobe level SLL 0 The difference of (a).
Further, in the process of forming a receiving beam, the pitching dimension adopts a Dolph-Chebyshev synthesis method to carry out low side lobe processing; in the process of forming the transmitting wave beam, when low sidelobe processing is respectively carried out on the pitch dimension and the azimuth dimension, the phase weight of each array element is searched by adopting a particle swarm algorithm.
Advantageous effects
Compared with the prior application, the invention has the following advantages:
1. when the transmitting and receiving wave beams are formed, the low sidelobe processing is respectively carried out on the pitching dimension and the azimuth dimension, so that the process of forming the cylindrical array wave beams can be greatly simplified;
2. the transmitting beam adopts a phase-only weighting mode, and compared with a conventional amplitude-phase weighting mode, the transmitting beam can realize low sidelobe of the transmitting beam without losing transmitting gain, and the power of the radar is ensured;
3. the receiving beam adopts an improved virtual interference method in the azimuth dimension, and because the improved virtual interference method uniformly sets a large amount of virtual interference in a region outside the 3dB beam width and carries out repeated iterative optimization on the intensity of the virtual interference to enable the virtual interference to continuously approach an ideal low side lobe directional diagram, the low side lobe beam forming is realized, the problem that the side lobe of a uniform circular/circular arc array directional diagram is too high can be effectively solved, and the side lobe level can generally reach about-30 dB in practical application.
Drawings
FIG. 1 is a schematic diagram of a cylindrical phased array radar array element layout according to the present invention;
figure 2-transmit beam elevation dimension 16-element linear array unweighted directional pattern;
figure 3-low sidelobe pattern from transmit beam elevation dimension 16-element array unique phase weighting;
4-the unweighted pattern of 22 adjacent array elements in the azimuth dimension 66 array element circular array is activated at a time;
fig. 5-low sidelobe directional diagram obtained by activating only phase weighting of 22 adjacent array elements in the azimuth dimension 66 array element circular array at a time;
6-low sidelobe directional diagrams obtained by a virtual interference method of 22 adjacent array elements are activated at a time in an azimuth dimension 66 array element circular array;
FIG. 7-low sidelobe patterns obtained with Dolph-Chebyshev synthesis for pitch dimension 16 wire arrays;
FIG. 8-schematic of the process of the invention.
Detailed Description
The beam forming method according to the present invention will be explained in detail with reference to the accompanying drawings.
The cylindrical array of the invention has M multiplied by N array elements, all the array elements are uniformly distributed on the cylindrical array surface, and the distribution of the array elements is shown in figure 1. The whole cylindrical array comprises M circular rings from top to bottom, each circular ring corresponds to an N-element uniform circular array, and the adjacent circular rings are uniformly spaced. If the curved surface of the cylindrical array is seen, the N M-element uniform linear arrays are uniformly arranged on the curved surface of the cylindrical array.
The cylindrical array beam forming process follows the following steps:
s01: the arrangement of the cylindrical array is shown in figure 1, and M uniform circular arrays of the array from bottom to top are numbered, namely number 1, 2 and 3 … … M circular rings. As can be seen from the foregoing description, the M uniform circular arrays are completely the same, so that for a single uniform circular array, N array elements in the circular array are numbered, which are respectively number 1, 2, and 3 … … N array elements. Similarly, the cylindrical arrays may be numbered as N M-element uniform linear arrays, which are No. 1, 2, and 3 … … N linear arrays, respectively. The internal parts of the uniform linear arrays are numbered as array elements No. 1, 2 and 3 … … M respectively.
S02: when the cylindrical array transmitting wave beam is formed, in order to conveniently solve the weight of each array element, the wave beam is decoupled into two dimensions of azimuth and pitching, the azimuth wave beam is formed by a circular array, and the pitching wave beam is formed by a linear array. Considering the shielding effect of the cylindrical array, that is, when a beam is formed in a certain direction, the array elements on the back cannot provide help for the beam and can raise the side lobe of the beam, and assuming that when a transmitted waveform is formed, the number of the array elements participating in the beam formation in the azimuth dimension is P, and the number of the array elements participating in the beam formation in the pitch dimension is M, the azimuth beam is formed by a uniform circular arc array formed by P array elements on the circular array, and the pitch beam is formed by all M array elements in the pitch dimension.
S03: and forming a cylindrical array transmitting beam. In order to ensure that the gain of the transmitting beam is not reduced, the forming of the transmitting beam abandons the common amplitude weighting and amplitude-phase weighting and adopts a phase-only weighting mode. The weighting method can reduce the beam sidelobe while keeping the beam width and the array antenna gain basically unchanged. In order to obtain a phase-fed value of an array element, firstly, a cylindrical array is decoupled into a pitching M-element uniform linear array and an N-element uniform circular array, and then a phase weight value of each array element is obtained by respectively adopting a phase weight value searching method based on a particle swarm algorithm, and the method specifically comprises the following steps:
s03-1: the desired side lobe level DSLL is set first. For the pitch dimension, the array is a uniform linear array, for the azimuth dimension, the array is a uniform circular array, and simultaneously the multi-beam time is a circular arc array. The specific desired side lobe level DSLL is related to the array type and the number of array elements, the more array elements the lower the DSLL. For example, the minimum DSLL of a 16-element uniform linear array is about-15.4 dB, the DSLL is reduced by 2dB compared with the actual side lobe level ASLL when the weighting is not carried out, and a beam is formed by every 22 adjacent array elements of a uniform circular array of 66 array elements, and the minimum DSLL is-12 dB at the moment, and the DSLL is reduced by 1.6dB compared with the ASLL when the weighting is not carried out.
S03-2: and searching the solved phase weight by adopting a particle swarm algorithm. Taking an equivalent uniform linear array of a pitch dimension as an example:
a) And constructing L particles, wherein each particle has M dimensions, namely each particle comprises the phase weights of M array elements, and one dimension represents the phase weight of one array element. If the array beam points to the normal direction, then each particle has M/2 dimensions according to the symmetry of the phase;
b) Carrying out initialization random assignment on M dimensions of each particle, namely, carrying out initial phase weight, and ensuring that the phase weight is between-pi and pi;
c) And constructing a fitness function. The fitness function used in the present invention is constructed as F = DSLL-ASLL (note that the side lobe power here is averaged to take a common logarithm value);
d) Setting parameters of the particle swarm optimization algorithm, such as learning rates c1 and c2, which can be generally set to be between 1 and 2, a weighting coefficient w is set to be between 0.1 and 0.9, and the speed can be set to be between-1 and 1;
e) Searching by using a particle swarm algorithm, calculating a current fitness function value in each iteration, paying attention to whether the speed and the position of the current particle are out of range, wherein the lower boundary of the speed is set to be-1, the upper boundary of the speed is set to be 1, the boundary of the position is-pi, if the out-of-range occurs, the boundary is limited to be a boundary value, when the fitness function meets the requirement (if F is less than 0.1 dB), a loop is skipped out to obtain a final phase weight, and if the loop frequency set by the algorithm is not skipped out of the loop, searching is carried out after an expected side lobe level (ASLL) is reduced;
the speed represents the speed of the change of the position of the particle in the particle swarm optimization, and the position is the phase weight.
S03-3: and (4) carrying out beam synthesis by using the phase weight meeting the condition in the step 2, and obtaining the directional diagram.
Fig. 3 and 5 show low sidelobe transmission patterns obtained by the above method, and it can be seen that the sidelobes of the transmitted beams are effectively suppressed compared to the unweighted patterns of fig. 2 and 4.
S04: and (5) forming a cylindrical array receiving beam. Since the reception can employ more flexible DBF digital beamforming techniques, the receive beams employ amplitude weighting or amplitude-phase weighting to achieve lower side lobe levels. For the uniform linear array of the pitch dimension, the invention adopts a Dolph-Chebyshev method to synthesize the directional diagram, and the method can ensure that the main lobe is spread to the minimum while the directional diagram reaches the designated side lobe level. For the azimuth dimension, the azimuth dimension is a circular arc array in which L array elements are uniformly distributed when forming a beam, so that the common linear array and planar array low sidelobe method cannot be adopted. Assuming that the array has Q lobes including 1 main lobe and Q-1 side lobes, according to the principle of ADBF adaptive beamforming, when there are R interference (R) in different directions in the space domain<Q-1) incident patternIn time, ADBF may generate adaptive zeros in R directions, with the depth of the zeros being positively correlated to the strength of the interference in that direction. The present invention derives its heuristic from ADBF adaptive beamforming. That is, if more than Q-1 virtual interferences are set in the directional diagram, the ADBF will not form an adaptive zero in each interference direction, but minimize the interference received by the entire array, and when the number of virtual interferences is much larger than the number of array elements, the directional diagram of the array can obtain the overall low side lobe effect. The intensity of the virtual interference is continuously adjusted through iteration so as to reach the expected side lobe level. The improved virtual interference method provided by the invention specifically comprises the following steps: by constructing a cost function, uniformly setting a large number of virtual interferences in a region outside the 3dB beam width of a receiving beam azimuth dimension directional diagram, wherein the large number of the virtual interferences is more than 4 (Q-1), continuously iterating the virtual interference strength to update an autocorrelation matrix of an interference receiving signal, and calculating a weight W corresponding to each iteration t Gradually making the cost function approach 0 value, thereby obtaining the expected weight W t Finally obtaining a directional diagram meeting the requirements, wherein the weight W is updated for the t time t The latter cost function is equal to the weight W t Highest side lobe SLL of the lower obtained directional diagram 1 With desired integral sidelobe level SLL 0 The difference of (a).
Now, assuming that the echo signal frequency is an S-band narrowband signal of 2.9 to 3.1GHz, the radius of the uniform circular array is 0.55 m, the number of array elements is N =66, and the specific steps are described by using L =22 adjacent array elements to form a receiving beam:
s04-1: first determining the desired beam pointing theta 0 And 3dB beamwidth BW 0 Then preset a desired overall sidelobe level SLL 0 (e.g., SLL 0 = 30 dB), according to θ 0 、BW 0 And SLL 0 Setting an ideal directional diagram, and marking as Pattern0;
s04-2: at 3dB beamwidth SLL 0 Placing K initial virtual interferences gamma in the other region k K =1 … K, K being the size and spatial sampling interval d 1 Related to the number of array elements, taken in general
Wherein T is the total number of iterations, and the initial virtual interference intensity can be generally set to 0,3dB beam width BW 0 The inner zone does not place any interference. It should be noted here that, with the subsequent continuous iterative optimization, while the sidelobe level is gradually reduced, the main lobe width is expanded, so that the 3dB beam width needs to be determined again after each iteration, and the interference intensity within the 3dB beam width is set to zero;
s04-3: according to the ADBF principle, obtaining the weight W without virtual interference 0 The formula is as follows:
W 0 i.e. the initial weight at t =0, then W 0 To form an initial Pattern, denoted Pattern1, where S 0 For the steering vector to which the beam is desired to be directed,
an autocorrelation matrix U representing the initial non-ideal received signal 0 Inversion, U t For non-ideal received signals t Including autocorrelation matrices of interfering received signals and autocorrelation matrices of noisy received signals, U t The two autocorrelation matrixes are square matrixes of L rows and L columns, wherein L is the number of array elements adopted in the formation of azimuth beams, the noise is unchanged, and the autocorrelation matrix of the initial interference receiving signal can be set to be an all-0 matrix;
s04-4: the interference strength of each virtual interference is iterated,
wherein, the interference intensity Γ of the kth (K =1 … K) virtual interference is iterated for the tth (T =1 … T) time t , k The update process of (2) is as follows: at the kth virtual interference position, calculating the sidelobe level of the ideal directional diagram Pattern0 and the directional diagram obtained by the t-1 th iteration respectively, and performing difference to obtain a sidelobe level difference D t,k When t is iterated for the first time, the ideal directional diagram Pattern is respectively calculatedThe side lobe level of 0 and the initial directional diagram Pattern1 is subtracted;
then, the side lobe level difference D is used t,k Interference strength gamma to the k-th virtual interference at the previous iteration t-1,k Since the corrected value may be negative, a non-negative correction value is selected as the disturbance intensity Γ of the updated k-th virtual disturbance t,k The specific calculation formula is as follows:
σ t，k ＝Γ t-1，k +u*D t，k
Γ t，k ＝max(σ t，k ，0)
wherein for Γ t-1,k When t =1, namely, during the first iteration, the initial value is 0,u which is a constant, generally takes a value between 1 and 10, and the size of u can be adjusted according to the actual situation to make the iteration result converge more quickly;
then, the autocorrelation matrix of the interfering received signal is updated by the interference strength of the K virtual interferences which are iterated continuously, and the autocorrelation matrix of the non-ideal received signal is recalculated by the updated autocorrelation matrix of the interfering received signal, which is a common knowledge, and the process is as follows:
using updated latest interference strength Γ of the kth virtual interference t,k Recalculating autocorrelation matrix R of interference received signal calculated at kth virtual interference during the t-th iteration t,k And obtaining the autocorrelation matrix R of the interference receiving signal calculated at the Kth virtual interference position during the t-th iteration through iterative calculation t,K In, R t,k The calculation formula of (a) is as follows:
in the above formula, V k The array manifold matrix representing L rows and K columns corresponds to a vector at the K-th virtual interference position, namely the K-th column of the array manifold matrix is L rows and 1 columns, and R t,k L rows and L columns;
by R t,K Obtaining the self of the non-ideal received signal under the current t-th iterationCorrelation matrix U t The concrete formula is as follows:
U t ＝R t,K +R n
in the above formula, R n The size of the autocorrelation matrix of the noise receiving signal is L rows and L columns.
To obtain U t Then, calculating the weight W corresponding to the t iteration through the formula in S04-3 t (ii) a Then according to the weight W t The current directional diagram is calculated.
S04-5: constructing a cost function F and updating the weight W each time t Calculating a cost function, and when the cost function meets the requirement (for example, F is less than or equal to 0.2 dB) in a certain cycle, jumping out of the cycle, wherein the weight value obtained through iteration is the required weight value; if the iteration cycle times reach the set times and the side lobe is not jumped out, the set level of the side lobe is too low or the iteration times are too few, the iteration times can be increased or the requirement on the side lobe level can be relaxed until the cost function reaches the requirement, and the weight W obtained at the moment t The formed directional diagram meets the requirement. The cost function F is the highest side lobe SLL of the directional diagram obtained under the weight W 1 With desired integral sidelobe level SLL 0 The closer F is to 0, the closer the current directional diagram is to the expected directional diagram, and the t-th updating weight W t The latter cost function is equal to the weight W t Highest side lobe SLL of lower obtained directional diagram 1 With desired integral sidelobe level SLL 0 The difference of (a).
Fig. 6 and 7 show low sidelobe patterns of azimuth and elevation dimension reception beams obtained by the above method, and compared with fig. 4 and 2, the reception pattern and the transmission pattern are the same without weighting, and the sidelobes are both greatly reduced.
Claims (6)
1. A low sidelobe transmit-receive beam forming method based on a cylindrical array is characterized in that: when a cylindrical array is utilized to point at a certain wave beam, the cylindrical array is decoupled into a pitching uniform linear array and an azimuth uniform circular array or an arc array, and when a transmitting wave beam and a receiving wave beam are formed, low side lobe processing is respectively carried out on the pitching dimension and the azimuth dimension, and finally the low side lobe effect of the whole array is realized, wherein the transmitting wave beam adopts phase-only weighting, and the receiving wave beam adopts amplitude-phase weighting.
2. The method according to claim 1, wherein the low sidelobe transmit-receive beamforming method based on the cylindrical array comprises: in the process of forming a receiving wave beam, when low sidelobe processing is carried out on an azimuth dimension, an improved virtual interference method is adopted to search the weight of each array element, the improved virtual interference method is characterized in that the improved virtual interference method is that through constructing a cost function, K virtual interferences are uniformly arranged in a region outside the 3dB wave beam width of a receiving wave beam azimuth dimension directional diagram, the interference intensity of the K virtual interferences is iterated continuously to update the autocorrelation matrix of an interference receiving signal, the autocorrelation matrix of a non-ideal receiving signal is recalculated through the updated autocorrelation matrix of the interference receiving signal, and then the weight W corresponding to each iteration is calculated according to the ADBF principle t And the directional diagram enables the directional diagram to be continuously approximate to the ideal low-sidelobe directional diagram, and when the cost function meets the requirement, an expected weight W is obtained t And the corresponding directional diagram is the directional diagram which finally meets the requirements.
3. The method according to claim 2, wherein the low sidelobe transmit-receive beamforming method based on the cylindrical array comprises: interference strength Γ of kth virtual interference of the tth iteration t,k The calculation process of (2) is as follows: firstly, at the kth virtual interference position, calculating the sidelobe level of the ideal directional diagram Pattern0 and the directional diagram obtained by the t-1 th iteration respectively, and making a difference to obtain the sidelobe level difference D at the kth virtual interference position of the current tth iteration t,k K =1 … K; then, using D t,k Correcting the interference strength gamma of the kth virtual interference obtained in the previous iteration t-1,k Selecting a non-negative correction value as the disturbance intensity gamma of the kth virtual disturbance in the tth iteration t,k 。
4. The method for forming low sidelobe transceiving beams based on the cylindrical array according to claim 2 or 3, wherein: the weight W corresponding to each iteration t And multiplying a steering vector which is equal to the direction of the expected beam by an inverse matrix of an autocorrelation matrix of the non-ideal received signal, wherein the autocorrelation matrix of the non-ideal received signal comprises an autocorrelation matrix of the interference received signal and an autocorrelation matrix of the noise received signal, the two autocorrelation matrices comprise square matrices of L rows and L columns, L is the number of array elements adopted in azimuth beam forming, and the noise is unchanged.
5. The method according to claim 4, wherein the low sidelobe transmit-receive beamforming method based on the cylindrical array comprises: t time update weight W t The latter cost function is weight W t Highest side lobe SLL of lower obtained directional diagram 1 With desired integral sidelobe level SLL 0 The difference of (a).
6. The method according to claim 1, wherein the low sidelobe transmit-receive beamforming method based on the cylindrical array comprises: in the process of receiving beam forming, the pitching dimension adopts a Dolph-Chebyshev synthesis method to carry out low side lobe processing; in the process of forming the transmitting wave beam, when low sidelobe processing is respectively carried out on the pitch dimension and the azimuth dimension, the phase weight of each array element is searched by adopting a particle swarm algorithm.
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