CN115333485A - Dynamic power supply system for radio frequency power amplifier and control method - Google Patents
Dynamic power supply system for radio frequency power amplifier and control method Download PDFInfo
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Abstract
The invention relates to a dynamic power supply system for a radio frequency power amplifier and a control method thereof. The envelope mapping module converts the envelope of the transmitting signal into a control voltage according to the mapping relation, the S-type power amplifier efficiently generates a dynamic power supply voltage which is in direct proportion to the control voltage, power is supplied to the radio frequency power amplifier, and the efficiency of the radio frequency power amplifier is improved. The envelope mapping relationship is provided by a mapping establishment module. The mapping establishing module can make the radio frequency power amplifier work in a preset compression state by combining and adjusting the gain of a transmitting path and the highest power supply voltage, and establishes an envelope mapping relation by a constant gain rule on the basis. The invention can provide dynamic power supply for the radio frequency power amplifier under large working bandwidth and complex working environment, effectively improves the efficiency of the radio frequency power amplifier, and has excellent stray and near carrier noise inhibition capability.
Description
Technical Field
The invention belongs to the technical field of radio frequency high-power transmission, and particularly relates to a dynamic power supply system for a radio frequency power amplifier and a control method.
Background
A radio frequency power amplifier (hereinafter, referred to as a radio frequency power amplifier) is an important component of a radio transmission system, and is used for enhancing the power of a transmitted radio frequency signal to achieve a required transmission distance and transmission quality. For a wireless information transmitting system related to envelope modulation, the signal amplitude changes along with time, and in order to ensure that the highest amplitude does not generate distortion, a power amplifier needs to reserve corresponding output capacity to meet the output power of a peak envelope, so that the linearity of power amplification is ensured, but the power amplifier has lower power conversion efficiency because the power amplifier does not reach full power output in the time outside the peak envelope. The reduction of the power amplifier efficiency not only increases the power consumption (thereby increasing the operation cost), but also brings a series of problems of high heat dissipation requirement, large volume, reduced reliability and the like. Reducing the output capability of the rf power amplifier will increase efficiency but will also reduce linearity.
In recent years, with the development of wireless communication technology, the contradiction between the linearity and the efficiency of a radio frequency power amplifier is more and more prominent, and the requirement for solving the contradiction is more and more urgent. At present, a Doherty technology and an Envelope Tracking (ET) technology are used for improving the efficiency of a radio frequency power amplifier, the linearity is improved by combining a Digital Predistortion (DPD) technology, and the Doherty technology and the DPD technology are mature and applied in the fields of mobile communication, wireless internet, satellite communication and the like, for example, a design method of a high-efficiency dual-frequency power amplifier based on the envelope tracking technology is disclosed in the patent publication number CN 102299689B. The two technical systems have advantages and disadvantages respectively: the Doherty system is relatively simple in composition and large in power capacity, but the operable bandwidth is limited (typically, the relative bandwidth is about 10%), and the Doherty system is mostly used for a base station transmitting end with the power level of hundreds of watts; the envelope tracking technology is mainly used for mobile terminals with the transmitting power below watt level, the performance of the envelope tracking technology is not limited by carrier frequency in principle, the envelope tracking technology has wide working bandwidth, a complex envelope modulation power supply is needed, when the signal bandwidth reaches above MHz, the envelope modulation power supply needs a linear amplifier to provide high-frequency response, the efficiency of the linear amplifier is low, and the improvement of the overall efficiency of a power amplifier system is influenced.
Envelope tracking belongs to one of the dynamic power supply technologies. The dynamic power supply technology improves the efficiency of the radio frequency power amplifier by providing dynamically changing power supply voltage for the radio frequency power amplifier. According to the influence degree of the power supply on the output amplitude of the radio frequency power amplifier, the dynamic power supply technology can be subdivided into different types: when the output amplitude of the radio frequency power amplifier basically does not depend on the dynamic power supply voltage, the method is an envelope tracking technology; when the output amplitude of the radio frequency power amplifier is completely determined by the dynamic power supply voltage, the technology is an Envelope Elimination and Restoration (EER) technology; in between, it may be referred to as a dynamic power supply technique. In fact, in part of the "ET" technology used in current engineering, the output amplitude of the radio frequency power amplifier is affected by the power supply voltage to a certain extent, so that the technology called dynamic power supply is more accurate.
At present, the existing ET (or dynamic power supply) technology is mainly applied to UHF, L and S frequency bands, and is less applied to the field of short-wave wireless transmission. One important reason is that the performance of dynamic power supply technology is related to the gain compression state of the rf power amplifier at the peak envelope input. In the existing application, the working bandwidth of the radio frequency power amplifier is relatively small, the characteristics in the frequency band are basically stable, and the antenna load condition is good, so that the power amplifier compression point corresponding to the peak envelope can be preliminarily selected in the design stage and factory setting, and even if the working point is deviated due to the change of the environmental conditions in the working process, the performance of the dynamic power supply technology is not seriously influenced. The short wave emission frequency range is 1.6 MHz-30 MHz, spans 4 octaves, the power amplification characteristic and the antenna load standing wave ratio in the large bandwidth are changed violently along with the frequency (for example, the fluctuation of the antenna standing wave ratio in the full frequency band can reach 2.5), the system characteristic is also influenced by the surrounding electromagnetic environment and weather conditions, the gain compression condition can obviously change along with the frequency and the working state, if the short wave emission frequency range can not be automatically adjusted according to the working condition, the performance of the dynamic power supply system can be deteriorated, and the engineering practicability is not achieved.
In addition, the switching power amplifier of the existing dynamic power supply technology mostly adopts a fixed-frequency PWM scheme, stray distribution quantity related to switching frequency exists, and near carrier noise is not easy to control. Because the lowest carrier frequency of the short wave frequency band is low, the distance between the short wave frequency band and the power supply switching frequency is small, the stray difficulty of the switching frequency is large, and the near carrier noise can cause negative influence on the communication performance of the remote ionized layer. Some approaches that employ switching frequency randomization are highly complex and do not address the near-carrier noise problem.
On the other hand, broadband high-power short-wave communication systems have an urgent need to adopt dynamic power supply technology. Because a large proportion of the signal systems adopt amplitude modulation, the traditional AB class power amplifier has low efficiency, large system power consumption and high energy consumption, and equipment is difficult to miniaturize. The Doherty technology cannot meet the requirement of working bandwidth, and the dynamic power technology is the best choice. In addition, because the signal of the short-wave communication system has a small relative bandwidth (not more than dozens of kHz), the dynamic power supply system can be free from a linear amplifier aiming at high-frequency envelope, and the improvement of the system efficiency is more facilitated.
Therefore, the dynamic power supply technology is applied to a broadband high-power radio frequency power amplification system, and the power amplification efficiency is stably improved.
Disclosure of Invention
The invention aims to provide a dynamic power supply system for a radio frequency power amplifier, which can improve the efficiency of the radio frequency power amplifier under large working bandwidth and complex environment and has excellent stray and near carrier noise performance.
In order to achieve the purpose, the invention adopts the following technical scheme:
a dynamic power supply system for a radio frequency power amplifier, comprising:
an envelope detection module having an in-phase-quadrature (I/Q) baseband signal input terminal connected with an external baseband signal generator and configured to detect an amplitude of the I/Q input baseband signal and to output a baseband signal amplitude value V e An output terminal (i.e., envelope signal);
an envelope mapping module having an envelope signal input terminal connected to the envelope detection module output terminal, and a class-S power amplifier control voltage inputA control voltage output terminal with an input terminal connected; the envelope mapping module is configured to map an input envelope signal V e Conversion to control voltage V of class S power amplifier c The V is e To V c The mapping relation ensures that the radio frequency power amplifier which adopts the S-type power amplifier as a power supply has a V-shaped envelope e A varying constant gain;
the system comprises an S-type power amplifier and a radio frequency power amplifier, wherein the S-type power amplifier is provided with a control voltage input terminal, the control voltage input terminal is connected with a control voltage output terminal of an envelope mapping module, a direct current power supply input terminal connected with an external direct current power supply, and a dynamic power supply output terminal connected with a power supply input end of the radio frequency power amplifier; the class-S power amplifier is configured to efficiently convert a DC supply voltage to a dynamic output voltage V that varies with an input control voltage using a Delta-Sigma modulator d Supplying power to the radio frequency power amplifier; the dynamic power supply output terminal is directly connected with a drain electrode or a collector electrode of the radio frequency power amplifier power tube;
a mapping establishment module including an original I/Q signal input terminal connected to the external baseband signal generator, a feedback I/Q signal input terminal connected to a demodulation output terminal of the feedback demodulation module, and a gain control output terminal connected to the transmit path gain adjustment unit; the mapping module is configured to, on the one hand, adjust and determine the dynamic output voltage V d Maximum value of (V) dmax And gain G of the RF path p On one hand, the gain of the radio frequency power amplifier is calculated according to the feedback signal, and the envelope signal V is adjusted e Control voltage V of S-class power amplifier c The gain of the radio frequency power amplifier is kept constant by the mapping relation;
the feedback demodulation module comprises a radio frequency feedback input terminal, a local oscillator signal input terminal and a feedback I/Q signal output terminal; the radio frequency feedback input terminal is connected with a directional coupler at the output end of an external radio frequency power amplifier, the local oscillation signal input terminal is connected with a local oscillation source of an external transmitting channel, and the feedback I/Q signal output terminal is connected with the feedback I/Q signal input terminal of the mapping establishment module; the feedback demodulation module is configured to quadrature down-convert the radio frequency feedback signal to a baseband I/Q signal.
Further, the envelope signal output by the envelope detection module
Further, the envelope mapping module uses a polynomial function to map the input envelope signal V e Converting to control signal V of class S power amplifier c The polynomial can be expressed as
Wherein M is an integer of M ≧ 1, representing the polynomial order, b m Is a polynomial coefficient and is provided by a mapping establishing module.
Further, the envelope mapping module uses a look-up table (LUT) to map the input envelope signal V e Converting to control signal V of class S power amplifier c (ii) a The LUT mode comprises a plurality of data pairs, each data pair consisting of an index number and a control signal V c Composition is carried out; the LUT mode converts the envelope signal V e Scaling and rounding according to a certain proportion, taking the rounded result as an index number, and controlling a signal V corresponding to the index number c I.e. the control signal to be output to the class-S power amplifier.
Further, the envelope mapping module comprises a digital-to-analog converter (DAC) for mapping the generated control signal V in the digital domain c And converting the signal into an analog signal for output.
Further, the class-S power amplifier includes:
an interpolation filter configured to map the received control signal V generated by the envelope mapping module c Carrying out sampling rate conversion to obtain a sampling rate f s Control signal V of c ', the frequency is f s The sampling clock signal of (a) is provided by a sampling clock circuit;
Delta-Sigma modulator, the Delta-Sigma modulatorThe controller is configured to receive the control signal V output by the interpolation filter c ', and a feedback signal V from the feedback path f (ii) a The Delta-Sigma modulator is further configured to calculate a control signal V c ' AND feedback signal V f Integral of difference L = ∑ Σ n [V c ′(n)-V f (n)]Outputting V when L > threshold sw =1, otherwise output V sw =0; the V is sw As output signal of Delta-Sigma modulator, fed to the post-stage switching power amplifier;
a switching power amplifier including a switching signal input terminal for receiving the signal V output by the Delta-Sigma modulator sw A dc power supply input terminal connected to an external dc power supply, and a switching power output terminal; the switching power amplifier is configured to receive a switching signal V sw Under the control, the direct current power input by the direct current power supply input terminal is discontinuously transmitted to the switch power output terminal through the switch device;
a feedback path including a voltage sampling network connected to the switching power output terminal of the switching power amplifier and converting the analog sampled voltage to a digital feedback signal V f The ADC of (1); the feedback signal V f Is transmitted to the feedback input end of the Delta-Sigma modulator;
the input end of the low-pass filter is connected with the output end of the switching power amplifier, receives the switching power output by the low-pass filter, filters the switching frequency and each subharmonic component thereof, and outputs a signal proportional to the control signal V c The dynamic power supply power signal of (1); the output terminal of the low-pass filter is used as the power supply output end of the dynamic power supply and is connected with an external radio frequency power amplifier;
a sampling clock circuit configured to provide a frequency f s To the interpolation filter and to the ADC of the feedback path.
Further, when the control signal V outputted by the envelope mapping module c When the analog signal is an analog signal, the S-class power amplifier further comprises an ADC and an interpolation filter; the ADC is configured to receive an analog control signal V c Converted into a digital quantity.
Further, the switching power amplifier employs a BUCK-type switching power conversion circuit (i.e., BUCK-type circuit), including a switch driver configured to receive a switching input signal V sw And generates and outputs and V sw In-phase, but different level, drive signals Q + And V sw Inverted and different level driving signal Q - And two N-channel metal oxide field effect transistors (MOSFETs) V1 and V2; the grid of the first MOSFET V1 is connected with the in-phase driving signal Q output by the driver + The drain electrode of the V1 is connected with the direct current power supply terminal and receives external direct current power supply, the source electrode of the V1 is connected with the drain electrode of the second MOSFET V2, and the connection point is used as a switching power output terminal of the switching power amplifier; the grid electrode of the second MOSFET V2 and the inverted drive signal Q output by the driver - And the source of V2 is grounded.
Furthermore, the low-pass filter consists of K inductors and K-1 capacitors, wherein K is an integer more than or equal to 2; the K inductors are connected in series in sequence, namely an inductor L k (K is more than or equal to 2 and less than or equal to K-1) and an inductor L k-1 Is connected to the second terminal of, the inductance L k Second terminal of (2) and inductor L k+1 The first terminal of (a) is connected; first inductor L 1 As an input terminal of the low-pass filter, connected to a switching power output of the switching power amplifier; last inductance L K As the output terminal of the low-pass filter, i.e. the dynamic power supply output terminal, outputs a dynamic voltage V d (ii) a The connection mode of the K-1 capacitors is that the kth (K is more than or equal to 1 and less than or equal to K-1) capacitor C k First terminal of and the inductance L k 、L k+1 The connection between the terminals, the capacitor C k Is grounded.
Further, the last inductor L of the low-pass filter K And the low-pass filter is arranged at the drain electrode or the collector electrode of the external radio frequency power amplifier power tube, and is configured to provide the inductance required by the low-pass filter and is also configured as the radio frequency choking inductance of the external radio frequency power amplifier power tube.
Further, the last inductor L of the low-pass filter K Comprises two parts, respectively an inductor L K1 And an inductance L K2 (ii) a The inductance L K2 Is mounted at the drain or collector of the external RF power amplifier power transistor, the L K2 Through the power supply lead and the inductor L K1 Are connected in series; inductor L K1 Inductance L K2 And the power supply conductors connecting the two are jointly configured to provide the low-pass filter final inductance L K Equivalent inductive reactance; the inductance L K2 While also being configured as the rf choke inductance of the external rf power amplifier power tube.
Further, the mapping establishing module outputs a gain control signal G p Is an analog voltage configured to control the gain of a variable gain amplifier on the external radio frequency transmit path.
Further, the mapping establishing module outputs a gain control signal G p Is a digital quantity configured to be multiplied by a digital signal on the transmit path to vary the input signal amplitude of the radio frequency power amplifier.
Further, the mapping establishing module further comprises an enabling end, and the enabling end is controlled by a controller of the transmitting system; when the enable signal is at a high level (1), the mapping establishing module starts to work, otherwise, the mapping establishing module stops working, or when the enable signal is at a low level (0), the mapping establishing module starts to work, otherwise, the mapping establishing module stops working.
Further, the feedback demodulation module includes an ADC, which converts the input rf feedback signal into a digital rf signal; the local oscillator input terminal is connected with a local oscillator source on an external transmission path and inputs two orthogonal digital local oscillator signals; and multiplying the digital radio frequency signals by the two paths of orthogonal digital local oscillator signals respectively, and obtaining feedback I/Q signals after the multiplied output signals pass through a low-pass filter.
Another objective of the present invention is to provide a control method based on the above dynamic power supply system, which includes the following steps:
s1) judging whether a new mapping relation is to be established or not, if so, executing a step S2), otherwise, executing a step S3);
s2) establishing an envelope mapping relation, which comprises the following steps:
s21) outputting a control voltage signal V by the S-type power amplifier c Set to a constant value;
s22) by means of a gain control signal G p Adjusting the gain of a transmitting channel to enable the output of the radio frequency power amplifier to reach a set power value;
s23) calculating the gain of the radio frequency power amplifier according to the feedback I/Q baseband signal and the original I/Q baseband signal to obtain the gain compression amount during peak envelope power;
s24) if the gain compression reaches the target value, recording the current mapping output V c A value of V dmax The gain value at peak envelope power is denoted as G R_pk And step S25) is performed; if the gain compression does not reach the target value, adjusting the envelope mapping output value V c Repeating steps S21) to S24);
s25) amplifying gain G according to current radio frequency R Envelope dependent signal V e Change relationship G of R (V e ) According to
Establishing a mapping relation, and updating an envelope mapping module;
s26) under the updated envelope mapping relation, calculating the gain G of the radio frequency power amplifier according to the feedback I/Q baseband signal and the original I/Q baseband signal R (V e ) (ii) a If G is R (V e ) Is a constant G R_pk If not, the envelope mapping establishing process is exited, otherwise, the steps S25) to S26) are repeated;
s3) closing the mapping establishing module through an enabling signal;
s4) at each sampling moment n, the envelope detection module calculates an envelope signal according to the I/Q baseband signal generated by the external baseband signal generator
Wherein I is the in-phase component of the I/Q baseband signal; q is the quadrature component of the I/Q baseband signal;
s5) the envelope mapping module inputs the envelope signal V according to the mapping relation established by the mapping establishing module e (n) mapping to obtain a control voltage signal V of the S-class power amplifier c (n)；
S6) Delta-Sigma modulator in class S Power Amplifier with V c (n) as reference value, generating square wave switching signal, and adjusting frequency and duty ratio of the square wave switching signal by feedback loop to make the low frequency average value of the square wave switching signal equal to V c (n)；
S7) controlling a switching power amplifier to amplify through the square wave switching signal, and converting the direct current supply voltage into a high-power switching signal;
s8) filtering the switching frequency of the high-power switching signal by a low-pass filter to obtain a signal proportional to the control signal V c Dynamic supply voltage V d Will supply the voltage V dynamically d And the output is transmitted to an external radio frequency power amplifier to supply power to the external radio frequency power amplifier.
Further, in step S1), when the transmitting system is powered on for the first time, or the radio frequency carrier frequency is changed, or the output power deviation exceeds the threshold, or the change of the load standing wave ratio exceeds the threshold, a new mapping relationship needs to be established.
Further, the adjusted transmission path gain control amount in the step S22) is
P o For the current output power, P t Is the target output power.
Further, the method for calculating the gain compression amount at the time of peak envelope power in step S23) includes:
s231) envelope value V of original I/Q baseband signal e The radio frequency power amplifier gain G corresponding to the envelope value R (V e ) Set of compositions { V e (n)，G R (V e (N)) | N =1,2.. N } employsFitting a polynomial to obtain a polynomial
Wherein M is an integer of 1 or more and represents a polynomial order, a m Is a polynomial coefficient;
s232) calculating V e ∈[0，V emax ]G within the range R (V e ) Maximum value of G Rmax In which V is emax For envelope peak, and calculating gain G corresponding to envelope of peak R_pk ＝G R (V emax )；
S234) calculating the peak envelope power, the amount of gain compression being dG = G Rmax -G R_pk 。
Further, in the step S24), when the gain compression amount does not reach the target value, the envelope mapping output value is adjusted
Where dG _ tgt is a target value of the gain compression amount.
Further, the step S25) further includes: amplifying gain G according to current radio frequency R Envelope V e Change relationship G of R (V e ) According to
After the mapping relation is established, V is set c (V e ) Fitting by a polynomial to obtain
Wherein M is an integer of 1 or more and represents the polynomial order, b m The envelope mapping module is updated with the polynomial coefficients for the polynomial coefficients.
Further, the step S25) further includes: amplifying gain G according to current radio frequency R Envelope V e Change relationship G of R (V e ) According to
After the mapping relation is established, at V e ∈[0，V emax ]Selecting a plurality of points, and calculating each V e Corresponding V c (V e ) A V is measured e Scaling and rounding according to a set proportion, taking the rounded result as an index number and the index number and a control signal V corresponding to the index number c And forming a data pair, and using the data pair as a table updating envelope mapping module in a lookup table mode.
Further, the step S26) further includes: under the updated envelope mapping relation, calculating the gain G of the radio frequency power amplifier by the feedback I/Q baseband signal and the original I/Q baseband signal R (V e ) And calculating the relative mean square error of the amplitudes of the feedback I/Q baseband signal and the original I/Q baseband signal
Wherein N is the number of statistical sampling points; relative mean square error Err 2 And if the value is smaller than the set threshold value, the envelope mapping establishment process is exited, and otherwise, the steps S25) to S26) are repeated.
Due to the application of the technical scheme, compared with the prior art, the dynamic power supply system for the radio frequency power amplifier and the control method have the advantages that: the envelope mapping module generates a mapping relation to convert the envelope of the transmitting signal into a control voltage, the S-type power amplifier efficiently generates a dynamic power supply voltage which is in direct proportion to the control voltage, and the dynamic power supply voltage supplies power to the radio frequency power amplifier, so that the efficiency of the radio frequency power amplifier is improved; the envelope mapping relation is provided by a mapping establishing module, the mapping establishing module can enable the radio frequency power amplifier to work in a preset compression state by adjusting the gain of a transmitting channel and the highest power supply voltage in a combined mode, and the envelope mapping relation is established according to a constant gain rule on the basis; by automatically adjusting the compression state of the radio frequency power amplifier, the efficiency of the radio frequency power amplifier in a large working bandwidth and in a complex working environment can be effectively improved, and the practicability and the adaptability of the technology are improved; the S-type power amplifier based on the Delta-Sigma modulator is used as an output power amplifier of the dynamic power supply, so that fixed-frequency spurs are effectively reduced and eliminated, the near carrier noise introduced by the power supply is reduced, and the problem of engineering practicability of the application of the dynamic power supply technology in a broadband high-power communication system is solved.
Drawings
FIG. 1 is a graph of gain of a radio frequency power amplifier as a function of input power and supply voltage;
FIG. 2 is a block diagram of the system components of an embodiment of the present invention;
fig. 3 is a table diagram illustrating an implementation of envelope mapping using the LUT method according to an embodiment of the present invention;
FIG. 4 is a block diagram of a class S power amplifier according to an embodiment of the present invention;
FIG. 5a is a schematic diagram of the operating principle of the Delta-Sigma modulator according to the embodiment of the invention;
FIG. 5b is a mathematical model of a Delta-Sigma modulator of an embodiment of the invention;
FIG. 5c is an error noise frequency response of the Delta-Sigma modulator of an embodiment of the present invention;
FIG. 5d is another implementation of a Delta-Sigma modulator of an embodiment of the invention;
FIG. 6 is a schematic diagram of a switching power amplifier in a class S power amplifier according to an embodiment of the present invention;
FIG. 7a is a schematic diagram of a low pass filter in a class S power amplifier according to an embodiment of the present invention;
fig. 7b is another implementation of the low pass filter in the class-S power amplifier according to the embodiment of the present invention;
fig. 8a is a gain control manner of the mapping setup module for the transmission path according to the embodiment of the present invention;
FIG. 8b is a diagram illustrating another gain control of the mapping module for the transmit path according to an embodiment of the present invention;
FIG. 9 is a schematic diagram of a feedback demodulation module according to an embodiment of the present invention;
FIG. 10 is another embodiment of the present invention;
FIG. 11 is a flow chart of a dynamic power method of an embodiment of the present invention;
FIG. 12 is a flowchart of a mapping setup process according to an embodiment of the invention;
FIG. 13 is a flowchart of another mapping process of the present invention;
FIG. 14 is a flow chart of a dynamic voltage generation process of an embodiment of the present invention.
Detailed Description
The first embodiment is as follows:
the dynamic power supply system and method for a radio frequency power amplifier according to the present invention are described in detail below with reference to the accompanying drawings and embodiments. First, the relationship between the performance of the dynamic power supply technology and the compression state of the radio frequency power amplifier is described with reference to fig. 1. The horizontal axis of FIG. 1 is the input power P of the RF power amplifier in (unit is dBm), the vertical axis is the gain G (unit is dB) of the radio frequency power amplifier, and the curve family 11 is different drain electrode DC supply voltage V d Variation of lower gain with input power, in which the drain voltage V d The interval 2V varies between 19V and 35V. The trend in curve 11 is that at the high end of the input power there is a drop (i.e. gain compression) and at the same input power there is an increase with increasing drain voltage.
The design of the dynamic power supply system needs to select the working point of the radio frequency power amplifier when the peak envelope is input, namely the highest drain voltage V adopted when the rated peak envelope output power is reached dmax And thus the gain at the peak packet power point and the gain compression case. For a certain constant output power P out (e.g., 53 dBm), from P out ＝G+P in The iso-output power line is a straight line with a slope of-1, such as line 12 in fig. 1. It can be seen that the straight line 12 (i.e. the same output power) has a plurality of intersections with the family of gain curves 11, each intersection corresponding to a selectable V dmax 。
For example, the corresponding drain voltage at the intersection 13 is 33V if this is taken as the maximum value of the dynamic supply voltage, i.e., V dmax =33V, the gain of the rf power amplifier at the peak envelope is G pk =23.8dB, where the corresponding gain compression dG ≈ 1dB. Similarly, V corresponding to the intersection 14 d_max =31V, gain G pk =21.5dB, the gain compression dG ≈ 3dB; v corresponding to the intersection point 15 d_max =29V, gain G pk =19.2dB, and the gain compression amount dG ≈ 5dB.
All the three intersection points can be selected as V of the dynamic power supply dmax And the final performances of the corresponding radio frequency power amplifiers are obviously different. According to the design in the prior artMethod, the envelope mapping should eventually be guaranteed at all input signal amplitudes (corresponding to different P) in ) The gain of the lower power amplifier should be kept constant, and if the intersection point 13 is selected as the peak envelope working point, P needs to be ensured in The gain in the dynamic range is a constant straight line 16, as can be seen by the intersection of the straight line 16 with the family of curves 11, with P in The compression amount corresponding to each gain curve intersection point is reduced to the left side of the intersection point 13, so that the radio frequency power amplifier works in a state of lighter compression, and the final average efficiency is lower. If the intersection point 14 is selected as the peak envelope operating point, the power amplifier is in a saturated state at the intersection point 14, and each point on the gain straight line 17 on the left side of the intersection point 14 and the like is compressed greatly, so that the final average efficiency of the power amplifier is far higher than that of the intersection point 13. It is clear that the intersection point 15 is in a deep saturation state and the corresponding constant gain line 18 will achieve a higher efficiency than in the first two cases.
On the other hand, the power amplifier enters deep saturation to bring the risk of over-excitation of the grid electrode of the power tube or over-voltage of the drain electrode. Therefore, as a technical scheme with engineering practicability, the power amplifier efficiency and the power tube safety need to be balanced, a proper gain compression point is selected, and the maximum voltage V of the dynamic power supply is determined according to the selected gain compression point dmax 。
In the application field of the existing dynamic power supply technology (or "ET"), the working bandwidth of the radio frequency power amplifier is relatively small, the load standing wave ratio is relatively good, the working environment is relatively simple, the power amplifier characteristic shown in fig. 1 changes little with the frequency and the environment, and the initial value of the working point is generally selected at the initial design and factory setting stage of the dynamic power supply system, or the system performance is ensured by a method of presetting and storing a plurality of initial values according to the working conditions.
In an application (for example, a short-wave high-power transmitting system) with a wide operating bandwidth, a large load condition change and a complex operating environment, the characteristic of the radio frequency power amplifier changes drastically with frequency and environment, and a preset operating point (for example, a point 14 in fig. 1) may drift to other operating points (for example, a point 13 in fig. 1) under different antenna load conditions, so that the efficiency of the radio frequency power amplifier is reduced sharply, and not only is the power consumption of the system increased, but also a reliability risk is brought.
In order to solve the above problems, the dynamic power supply system for an rf power amplifier of the present invention adopts the technical solution of the embodiment shown in fig. 2.
The present embodiment includes a transmit path 21 and a dynamic power supply system 22. Wherein the transmission path 21 is a typical wireless transmission system, it is only shown here for illustrating the principle of the embodiment of the present invention, the transmission path 21 does not belong to the scope of the present invention, and the transmission path scheme different from that shown in 21 is adopted without departing from the scope of the present invention.
The transmission path 21 includes a baseband signal generator 211, a delay module 212, a quadrature modulator 213, a DAC 214, a Variable Gain Amplifier (VGA) 215, a Radio Frequency Power Amplifier (RFPA) 216, and an output coupler 217, which are sequentially arranged in series.
The baseband signal generator 211 digitizes, modulates and filters an original signal (not shown in the figure) to be transmitted to form an original I/Q baseband signal; the original I/Q baseband signal is input into the delay module 212 for delay, so as to ensure the envelope of the RF signal at the output of the RF power amplifier 216 and the dynamic supply voltage V provided by the dynamic power system 22 d The time alignment, I/Q baseband signal output by the delay module 212 is received by the quadrature modulator 213, and is converted to the required radio frequency by the action of the quadrature local oscillator signal in the quadrature modulator 213, and the digital radio frequency signal after frequency conversion is output, and the quadrature local oscillator signal LO is also output to the feedback demodulation module 225 in the dynamic power system 22; the digital RF signal is converted into an analog RF signal by the DAC 214, and then amplified by the variable gain amplifier 215, wherein the gain of the variable gain amplifier 215 is controlled by the gain control G provided by the mapping establishing module 224 p Determining; the amplified radio frequency signal excites a radio frequency power amplifier 216; supply voltage V of RF power amplifier 216 d Provided by a dynamic power supply system 22; the signal amplified by the radio frequency power amplifier 216 is transmitted to the output terminal 218 through the coupler 217, and further transmitted to the transmitting antenna to complete transmission; the coupled output port 2171 of the coupler 217 provides a path of rf power amplifier output signal with attenuated power to the feedback demodulation module 225 of the dynamic power system 22.
The dynamic power supply system 22 of the present embodiment includes an envelope detection module 221, an envelope mapping module 222, an S-class power amplifier 223, a mapping establishment module 224, and a feedback demodulation module 225;
the input end of the envelope detection module 221 is connected to the baseband signal generator 211 of the external transmission path 21, receives the I/Q baseband signal, and the output end is connected to the input end of the envelope mapping module 222, and detects the obtained envelope signal V e Into the envelope mapping module 222;
the envelope mapping module 222 receives an envelope signal V e And the mapping relation provided by the mapping establishing module 224, V e Mapped control signal V c Output to the S class power amplifier 223;
one terminal of the S-type power amplifier 223 receives a control signal V c The other terminal receives an external DC supply + Vsp and generates a voltage proportional to the control signal V c Dynamic supply voltage V d The radio frequency power amplifier 216 is powered through the output port;
a pair of input terminals of the mapping establishing module 224 is connected to the output terminal of the baseband signal generator 211 of the external transmission path 21 to receive the original I/Q baseband signal, and another pair of input terminals is connected to the output terminal of the feedback demodulation module 225 to receive the feedback I/Q baseband signal; the mapping module 224 further includes an enable terminal, connected to an external controller (not shown), for receiving an enable control signal Enb; the mapping establishing module 224 outputs the mapping relation to the envelope mapping module 222 and outputs the gain control G to the VGA215 of the transmitting path p ；
The feedback demodulation module receives the power amplifier output coupling signal from the coupling output terminal 2171 of the transmission path coupler 217 and the quadrature local oscillation signal LO from the transmission path quadrature modulator 213, and outputs the feedback I/Q baseband signal obtained by quadrature down-conversion to the mapping establishment module 224.
The envelope detection module 221 of the present embodiment obtains the envelope signal V according to the following relationship e : let the original I/Q baseband signal input at the nth (n =1,2.., n is a positive integer) time be I/Q baseband signal n +jQ n Then the corresponding envelope signal
One implementation of the above-described root-opening calculation is to use the well-established CORDIC algorithm.
One implementation of the envelope mapping module 222 of the present embodiment is to use a polynomial to calculate the envelope signal V e To the control signal V c Is mapped, i.e.
Wherein M is an integer of M ≧ 1, representing the polynomial order, b m Is a polynomial coefficient. In this embodiment, the mapping building block 224 provides polynomial coefficients b m To the envelope mapping module 222.
Another embodiment of the envelope mapping module 222 is a look-up table (LUT) method, and the mapping relationship is defined by a stored data table, as shown in FIG. 3, the data table includes two columns, the first column 31 is an index number K (K is greater than or equal to 1 and less than or equal to K), and the second column 32 is a control voltage V corresponding to the index number ck (ii) a The envelope mapping module 222 derives the input envelope signal V from the input envelope signal V e Calculating index numbers
Wherein
Represents rounding down, Δ being the scaling unit; the first column 31 of the table is searched for the index number k, in which index and the second column 32 of the corresponding row the control voltage V is obtained ck . The envelope mapping module 222 of this embodiment may be implemented by an FPGA, a DSP program, or a platform based on FPGA + DSP.
The class-S power amplifier 223 of the present embodiment is shown in fig. 4 and includes an interpolation filter 41, a Dleta-Sigma modulator 42, a switching power amplifier 43, a low-pass filter 44, a feedback path 45, and a sampling clock circuit 46. The interpolation filter 41, the Delta Sigma modulator 42, the switching power amplifier 43 and the low pass filter are connected in series, and the input terminal 411 of the interpolation filter 41 receives the control voltage V provided by the envelope mapping module 222 c The output terminal 411 of the low-pass filter 44 is the power output terminal of the dynamic voltage system 22, and outputs the dynamic supply voltage V d . The switching power amplifier 43 further has an external DC power supply terminal 432 connected to an external DC power supply + V sp And (4) connecting.
The feedback path 45 includes a voltage sampling circuit 451 and an analog-to-digital converter (ADC) 452; the input terminal of the voltage sampling circuit 451 is connected to the output terminal 431 of the switching power amplifier 43, and the output terminal is connected to the input terminal of the analog-to-digital converter 452; the output of the analog-to-digital converter 452 is connected to the feedback input 421 of the Delta Sigma modulator 42 for providing a feedback signal V f Input to a Delta Sigma modulator 42.
The sampling clock circuit 45 provides the frequency f to the interpolation filter 41 and the analog-to-digital converter 452 of the feedback path, respectively s The clock of (2).
The operating principle of the class-S power amplifier 223 of this embodiment is:
1) Control signal V received by the S-type power amplifier c Is interpolated by said interpolation filter 41 according to a clock f provided by a sampling clock circuit 46 s Adjusting the sampling rate to generate a control signal V c ' Retention V c Of the sampling rate to f s 。
2) Control signal V c ' is received by a Delta-Sigma modulator 42, the operating principle of which is illustrated in FIGS. 5 a-5 d. A functional block diagram of a Delta-Sigma modulator is shown in FIG. 5a, comprising: a subtractor 421 for receiving the control signal V c ' AND feedback signal V f Subtracting; an integrator 422 for integrating and accumulating the output of the subtractor 421 and outputting an accumulation result L = [ V' c (n)-V f (n)](ii) a A comparator 423 having a positive terminal receiving the integrator output signal L and a negative terminal connected to a threshold value V th When L is not less than V th Output V of time comparator sw =1, otherwise comparator output V sw ＝0。
3) Output signal V of the comparator 423 sw Controlling the working state of the switching power amplifier 43 and outputting a high-power switching signal V h (ii) a Feedback feed-throughWay 45 is to V h Scaled down and converted into a digital feedback signal V f Forming a closed negative feedback loop. When the negative feedback loop reaches a steady state, the switching signal V can be ensured h Of the low frequency component of (c) and the control signal V' c The error therebetween approaches 0. When V is h Is less than V' c Then, the accumulated error L output by the integrator 422 will be greater than the threshold V for more time th Result in V h The accumulation time at high level is increased, thereby increasing V h Amplitude of low frequency component of (V) h Is close to V' c (ii) a And vice versa.
Since the integrator 422 has a certain delay, resulting in a lag of the accumulated error L, the adjustment process of the feedback loop oscillates between positive and negative errors, thereby causing the output signal V of the Delta Sigma modulator 42 sw Oscillating between high and low levels. Frequency, duty cycle and feedback loop delay of oscillation and V h And V' c With respect to the error therebetween. When the signal V' c The oscillation frequency of the Delta Sigma modulator 42 also varies rather than being constant over time.
Fig. 5b is an equivalent mathematical model of the Delta Sigma modulator 42. Wherein the transfer characteristic 51 of the integrator in the Z-transform domain is
The quantization noise and the switching waveform error introduced by the comparator 423 and the post-stage switching power amplifier 43 are represented by noise E (z), and are added to the integrated error signal L (z) by the adder 52; according to the model shown in fig. 5b, the signal relationships in the Z transform domain are:
the output signal of the switching power amplifier 43 is thus obtained as:
V h (z)＝V′ c (Z)Z -1 +E(z)(1-Z -1 )
it can be seen that the noise term is E (Z) (1-Z) -1 ) The item appears obviousThe high-pass characteristic, i.e. approaching 0 at low frequencies, increases with increasing frequency and the typical noise frequency response is shown in fig. 5 c. V is satisfied at the low frequency side after the high frequency noise component is filtered out by the action of the low pass filter 44 h (z)≈V′ c (Z)Z -1 (Z -1 Representing a delay) so V is output after the low pass filter 44 d Is proportional to the control signal V' c 。
FIG. 5d is another embodiment of the Delta-Sigma modulator 42 of this example, in which a delay element 424 is added to the feedback loop for the feedback signal V, as compared to the embodiment shown in FIG. 5a f Increasing the delay t d The range of the oscillation frequency of the Delta Sigma modulator 42 is adjusted with a change in the loop delay. The Delta Sigma modulator 42 of this embodiment may be implemented by an FPGA, a DSP program, or a platform based on FPGA + DSP.
The switching power amplifier 43 in the class-S power amplifier 233 of the present embodiment employs a BUCK-type switching circuit as shown in fig. 6, and includes a switching driver 432 and two N-type MOSFETs V1 and V2, and an input port 431 of the switching driver 432 is configured to receive a switching signal V sw And output and V sw Drive signal Q with same phase and different levels + 4321 and sw inverted and different level driving signal Q - 4322. The gate of the MOSFET V1 and the in-phase drive signal Q + 4321, the drain of V1 is connected to the dc supply terminal 433 and receives external dc supply, the source of V1 is connected to the drain of V2, and this connection point is the switching power output terminal 434 of the switching power amplifier 43; v2 grid and inverted drive signal Q output by driver - 4322 and the source of V2 is grounded. When the switching signal V is input sw When the voltage is high, V1 is turned on, V2 is turned off, and the dc power supply terminal 433 is connected to the switching power output terminal 434; when V is sw When the voltage is low, V1 is off, V2 is on, and the switching power output terminal 434 is short-circuited to ground.
The low pass filter 44 in the class-S power amplifier of the present embodiment is shown in fig. 7a, and is composed of K inductors and K-1 capacitors, where K ≧ 2 is an integer; inductor L 1 ～L K Sequentially connected in series; inductor L 1 As an input terminal of the low-pass filter 44, receives the switching power signal V output from the switching power amplifier 43 h Inductance L K As an output terminal of the low-pass filter 44, i.e. a power supply output terminal of the dynamic power supply system 22, outputs a dynamic supply voltage V d . Said C is 1 ～C K-1 The k-th capacitor C in k Its first terminal and the inductance L k 、L k+1 The second terminal is grounded. Inductor L of the present embodiment K Is mounted on the drain of the power tube V0 of the external RF power amplifier, and L K And is also configured as the rf choke inductance of the rf power amplifier power tube V0. In other embodiments, the Kth inductor is divided into two parts, L respectively K1 And L K2 As shown in fig. 7 b. Wherein L is K2 A drain electrode L of a power tube V0 of the external radio frequency power amplifier K1 And L K2 Are pulled far and connected in series through a power supply lead 443; inductor L K1 Inductor L K2 And the supply conductor 443 connecting the two are together configured to provide the final inductance L of the low-pass filter 44 K Equivalent inductive reactance; the inductance L K2 And also configured as a radio frequency choke inductance of the external radio frequency power amplifier power transistor.
The mapping establishing method executed by the mapping establishing module 224 in this embodiment will be described in detail later, and the method may be implemented by using an FPGA, a DSP program, or a platform based on FPGA + DSP.
The mapping module 224 shown in FIG. 2 outputs the gain control signal G p Acting on a Variable Gain Amplifier (VGA) 215 in the transmit path 21, the gain control signal G p Either an analog voltage or a digital value, depending on the particular form of VGA.
In another embodiment as shown in fig. 8a, the gain control of the transmission path 21 by the mapping establishment module 224 may also be the control of the attenuation of the variable attenuator 81, the gain control signal G p May be an analog voltageAnd can also be a digital quantity; to counteract the signal attenuation introduced by the variable attenuator 81, the main transmit path typically includes one or more boost amplifiers 82 to ensure the strength of the rf power amplifier's driving signal.
In another embodiment as shown in fig. 8b, the mapping module 224 applies a gain control signal G to the transmit path 21 p 2241 is a digital quantity; a multiplier 83 is used between the quadrature modulator 213 and the DAC 214 in the transmission path 21, one multiplier of the multiplier is the digital rf signal output by the quadrature modulator 213, and the other multiplier is the digital gain control signal G p 2241, adjusting the amplitude of the digital radio frequency signal by the multiplication operation of the multiplier 83; one or more stages of the push amplifier 84 are employed after the DAC 214 to ensure the strength of the rf power amplifier's driving signal.
The mapping module 224 of this embodiment further includes an enable terminal Enb (as shown in fig. 2) connected to an external controller (not shown); when the condition of establishing a new mapping relation is met, the external controller starts a mapping establishing process through the enabling end Enb; otherwise the mapping module does not work.
An embodiment of the feedback demodulation module 225 of this embodiment is shown in fig. 9, and includes: an ADC 92 configured to receive the radio frequency feedback signal 91 and convert it to the digital domain; multipliers 93 and 94, each having an input for receiving the digital rf signal output by the ADC 92, the other input of the multiplier 93 receiving the in-phase component cos (·) of the quadrature local oscillator signal LO provided by the transmit path 21, and the other input of the multiplier 94 receiving the quadrature component sin (·) of the quadrature local oscillator signal LO; the outputs of the multipliers 93 and 94 are respectively connected with low-pass filters 95 and 96, and the two low-pass filters have the same configuration and are used for filtering high-frequency components generated by multiplication operation, and performing interpolation at the same time to reduce the sampling rate; the output of the low pass filters 95, 96 is the I/Q baseband signal 97. The feedback demodulation module 225 of this embodiment may be implemented in an FPGA, may also be implemented by using a DSP program, and may also be implemented on a platform based on an FPGA + DSP.
The present invention also provides a dynamic power control method for a radio frequency power amplifier, as shown in fig. 11. The method comprises the following steps:
step 1101: and judging whether a new mapping relation needs to be established or not.
Specifically, the determination operation is performed by a controller external to the dynamic power supply system 22; the controller monitors the working state and working condition of the transmitting system through control software and a sensor, and judges that a new mapping relation needs to be established when the following events occur: the transmitting system is powered up for the first time, the radio frequency carrier frequency is changed, the output power deviation exceeds the threshold, and the load standing wave ratio change exceeds the threshold.
Step 1102: and setting up mapping establishment module to enable, and executing the mapping establishment process.
And when the condition that a new mapping relation needs to be established is met, the external controller starts the module through the enabling end of the mapping establishing module to execute the mapping establishing process.
Step 1103: a dynamic supply voltage generation process is performed.
When the execution of the mapping establishment process is finished or the condition for establishing a new mapping relation is not met, the process of generating the dynamic power supply voltage according to the envelope signal is executed.
Fig. 12 is a specific flow of mapping establishment in this embodiment, which includes the following steps:
step 1201: control signal V output by envelope mapping c Set to a constant value.
The setting operation is realized by updating the mapping relation of the envelope mapping module, namely, for all input envelope signals V e All output a control signal V of a constant value c 。
Step 1202: by means of a gain control signal G p And adjusting the gain of the transmitting path to make the output of the radio frequency power amplifier reach the set power value.
Specifically, the output power of the current radio frequency power amplifier is measured by an external detection system and is set as P o And the target output power of the radio frequency power amplifier is P t Then the newly adjusted RF path gain control quantity is
Step 1203: calculating the gain G of the radio frequency power amplifier by the feedback I/Q signal and the original I/Q signal R And obtaining the corresponding gain compression amount when the peak envelope power is obtained.
The radio frequency power gain is calculated according to the following formula:
wherein (I, Q) is the original I/Q signal, (I' f ，Q′ f ) Is a feedback I/Q signal.
Calculating envelope signal V corresponding to each original I/Q signal sampling point e And a gain GR, which can be the gain G R Viewed as V e A function of, i.e. G R (V e )＝f(V e ) And f (-) is the function to be determined. Data composition set V for accumulating N sampling points e (n)，G R (V e (N)) | N =1,2.. N }, where N should be large enough to guarantee N V e The samples cover the dynamic range of the original signal.
Further fitting the sets by a polynomial to obtain a polynomial function relation
M is a polynomial order, a m Is a polynomial coefficient. Calculating V using the functional relationship e ∈[0，V emax ]G within the range R (V e ) Maximum value of G Rmax In which V is emax For envelope peak, and calculating gain G corresponding to envelope of peak R_pk ＝G R (V emax ) Then the gain compression amount can be calculated as follows:
dG＝G Rmax -G R_pk 。
step 1204: and judging whether the gain compression amount reaches a target value or not.
The target of the compression amount of the gain is related to specific application, the target of the improvement of the total efficiency of the transmitting system and the reliability design of the radio frequency power tube, different design schemes can be selected differently, and therefore the target amount of the gain compression can be optimally adjusted in engineering implementation. In this embodiment, the target compression amount may be selected as 3dB by default.
Whether the gain compression target value is reached or not can be judged by adopting an inequality | dG-dG _ tgt | < epsilon, wherein dG _ tgt is the gain compression target value, for example, dG _ tgt =3dB, and epsilon is an error tolerance, for example, epsilon =0.2dB. If the inequality is true, the gain compression target is considered to be reached.
Step 1205: record the current control signal value V c For a maximum supply voltage V dmax The gain corresponding to the peak packet power is G R_pk 。
Obtaining V dmax 、G R_pk I.e. the selection of the gain compression operating point shown in fig. 1 is completed. Wherein V dmax Is the maximum value of the output voltage of the dynamic power supply, G R_pk A constant gain target value that needs to be achieved for the envelope mapping.
Step 1206: adjusting control signal V of envelope mapping output c 。
When the gain compression amount is not up to the standard, the control signal V is adjusted c Changing the output voltage V of a dynamic power supply d The gain compression amount is made to approach the target value. When the gain compression amount is smaller, the power amplifier is not compressed enough, the power supply voltage is further reduced, otherwise, the power supply voltage is increased. According to this rule, the adjusted control signals are:
step 1207: according to G R And V e Corresponding relation between them, establishing V e And V c And updating the envelope mapping module with the mapping.
Specifically, G has been established at step 1202 R And V e Functional relationship G between R (V e ) The ideal mapping is G R (V e ) Is a constant G R_pk I.e. G R (V e )＝G R_pk . And the gain and the supply voltage V d Is a positive correlation, i.e. V d The gain is increased, so that the current G can be adjusted R (V e ) And a target gain value G R_pk Making a comparison if G R (V e ) If larger, then lower the V e Control signal V of c Thereby reducing the supply voltage V d And vice versa.
According to the above principle, V is established e And V c The mapping relationship between the two is as follows:
the method for updating the envelope mapping module with the mapping relation comprises the following steps: will V c (V e ) Fitting by a polynomial to obtain
Where M is a polynomial order, b m The envelope mapping module is updated with the polynomial coefficients for the polynomial coefficients.
The envelope mapping module is updated with the mapping relationship, and the method can also be adopted as follows: at V e ∈[0，V emax ]Selecting a plurality of points, each V e Calculate the corresponding V c (V e ) Will V e Scaling and rounding according to a certain proportion, taking the rounded result as an index number, and the index number and a control signal V corresponding to the index number c The envelope mapping module is updated as a table of LUTs, making up the data pairs.
Step 1208: computing updated G R And an envelope V e The corresponding relation between them.
After the envelope mapping is updated, a process similar to step 1203 is performed to obtain G in the new envelope mapping relationship R Following V e A change in (c).
Step 1209: judgment G R Whether or not it is constantly equal to G R_pk 。
In particular, according to the current G R And V e In a functional relationship of V e ∈[0，V emax ]Selecting a plurality of points, each V e Calculate the corresponding G R (V e ) Judging the inequality G R (V e )-G R_pk If | is < δ (δ is the error margin, e.g., δ =0.2 dB), the inequality holds, and a constant gain condition is reached.
Step 1210: the mapping establishment procedure is ended.
Fig. 13 is another embodiment of a mapping establishment procedure, which is different from the embodiment shown in fig. 12 in that steps 1208 and 1209 are performed, and other steps are the same, and fig. 13 omits the same steps, and only shows alternative steps 1308 and 1309, specifically:
step 1308: computing updated G R And an envelope V e The corresponding relation between the feedback I/Q signals and the relative mean square error Err between the feedback I/Q signals and the original I/Q signals 2 。
In particular, the updated G R And an envelope V e The calculation of the correspondence between them is the same as step 1208; the relative mean square error Err 2 Calculated as follows:
wherein N is the number of statistical sample points, and (I, Q) is the original I/Q signal, (I' f ，Q′ f ) Is a feedback I/Q signal.
The relative mean square error Err 2 The AM-AM distortion condition, err of the radio frequency power amplifier is represented 2 The smaller the distortion.
Step 1309: determination of Err 2 Whether it is less than a set threshold.
The judgment operation is equivalent to the judgment inequality Err 2 If < δ holds, where δ is the relative mean square error margin, e.g., δ =0.001.
Fig. 14 is a flowchart of the dynamic power supply voltage generation of this embodiment, which specifically includes:
step 1401: the mapping setup module is turned off by an enable signal Enb.
When the envelope mapping relation does not need to be established newly, the external controller closes the mapping establishing module by setting the enable signal Enb, so as to ensure that the dynamic voltage generating process operates normally without interference.
Step 1402: the envelope signal is calculated from the original I/Q signal at each sampling instant:
step 1403: according to the established envelope mapping relation, the envelope mapping relation is formed by V e (n) mapping to obtain the control signal V c (n)。
When the envelope mapping relationship is expressed in a polynomial manner,
wherein M is an integer of M ≧ 1 and represents polynomial order, b m Is a polynomial coefficient, M and b m Are provided by an envelope mapping module.
When the envelope mapping relation adopts an LUT mode, the index number is calculated
Wherein
Expressing rounding down, delta is a scaling unit, index number k is searched in an LUT table, and a control voltage V is obtained from a table item corresponding to the index number ck As the current V c (n)。
Step 1404: delta-Sigma modulator to control signal V c And (n) is a reference value, and a square wave switching signal is generated.
Specifically, the Delta-Sigma modulator first adds V with an adder c (n) and a feedback signal V f Subtracting; and accumulating the difference by an integrator to obtain an accumulated error L = ∑ [ V ] c (n)-V f (n)](ii) a The accumulated error L is compared with a threshold value V th By comparison, if L ≧ V th Time comparator output V sw =1, otherwise comparator output V sw And =0. Since the feedback signal is derived from the switching power output by the switching power amplifierSignal, the above-mentioned process forms negative feedback loop, the loop is formed from V c (n) as a target reference value, trying to set V f Is adjusted to V c (n)。
Because the integrator causes a certain delay of the feedback signal, the adjustment process oscillates between positive and negative errors, and further the output of the Delta-Sigma modulator is a switching signal oscillating between high and low levels. The frequency, duty cycle of the oscillation is related to the feedback loop delay and the error between the control signal and the feedback signal. When the control signal varies with time, the oscillation frequency of the Delta Sigma modulator also varies rather than being constant.
Step 1405: and the switching signal generated by the Delta-Sigma modulator controls the switching power amplifier to obtain a switching power signal.
And converting a switching signal generated by the Delta-Sigma modulator into two paths of reverse driving signals, and respectively controlling two switches of the BUCK type switching power amplifier. When a switching signal generated by the Delta-Sigma modulator is in a high level, the first switch is used for conducting external direct current power supply to a switching power signal output end, and the second switch is cut off; when the switching signal generated by the Delta-Sigma modulator is in a low level, the first switch is turned off, the second switch is turned on, and the switching power signal output end is grounded.
Step 1406: after the switching power signal passes through the low-pass filter, the dynamic power supply voltage V is obtained d 。
Since the switching waveform of the switching power signal is the same as the switching signal generated by the Delta-Sigma modulator, the low frequency component of the signal approaches the control signal V with little error c Therefore, the dynamic supply voltage V obtained after the low-pass filter is adopted to filter the high-frequency component d Is proportional to the control signal V c 。
Example two:
as shown in fig. 10, the present embodiment is different from the embodiment shown in fig. 2 in that: the digital domain control signal output by the envelope mapping module 222 is converted into an analog signal V by the DAC 101 c At the output of the class-S power amplifier 223, pulled out by the transmission cable 103An ADC 102 is added at the input end for receiving the analog control signal V c And converted to the digital domain and input to the class-S power amplifier 223. Other parts of the present embodiment are the same as those of the embodiment shown in fig. 2 in terms of composition and operation principle, and are omitted here. The embodiment has the advantages that: when the S-class power amplifier 223 is far away from the envelope mapping module (e.g., distributed in two different units), the engineering implementation using analog signal transmission is simpler.
The above are only exemplary embodiments of the present invention, and all technical solutions formed by using the equivalent principle or the equivalent transformation fall within the protection scope of the present invention.
Claims (21)
1. A dynamic power supply system for a radio frequency power amplifier, for use in a transmit path including the radio frequency power amplifier, the dynamic power supply system comprising: the system comprises an envelope detection module, an envelope mapping module, an S-type power amplifier, a mapping establishment module and a feedback demodulation module;
the input end of the envelope detection module receives the I/Q baseband signal of the transmitting path, detects the amplitude of the I/Q baseband signal, and detects the envelope signal V obtained by detection e Output to the envelope mapping module;
the feedback demodulation module receives a power amplifier output coupling signal and an orthogonal local oscillator signal LO of the transmitting channel, and outputs the feedback I/Q baseband signal obtained by orthogonal down-conversion to the mapping establishment module;
the input end of the mapping establishing module receives the I/Q baseband signal and the feedback I/Q baseband signal, outputs a mapping relation to the envelope mapping module, and outputs a gain control signal G to the variable gain amplifier of the transmitting path p Enabling the radio frequency power amplifier to meet the set gain compression condition at the rated peak power and have constant gain;
the envelope mapping module receives the envelope signal V e And the mapping relation, will V e Control voltage signal V obtained by mapping c Outputting the signal to the S-type power amplifier;
said class SThe power amplifier is used for generating a signal proportional to the control voltage V c Dynamic supply voltage V d And supplying power to the radio frequency power amplifier.
2. The dynamic power supply system for a radio frequency power amplifier as claimed in claim 1, wherein: envelope signal output by the envelope detection module
Wherein I is the in-phase component of the I/Q baseband signal; q is the quadrature component of the I/Q baseband signal.
3. The dynamic power supply system for a radio frequency power amplifier as claimed in claim 1, wherein: the envelope mapping module employs a polynomial function to map the envelope signal V e Is converted into the control voltage signal V c The polynomial function is:
wherein M is an integer of M ≧ 1, representing the polynomial order, b m Is a polynomial coefficient, is provided by the mapping building block.
4. The dynamic power supply system for a radio frequency power amplifier as claimed in claim 1, wherein: the envelope mapping module adopts a lookup table mode to map the envelope signal V e Is converted into the control voltage signal V c (ii) a The lookup table mode comprises a plurality of data pairs, and each data pair comprises an index number and a control signal; in the search, the index number is calculated as the envelope signal V e Scaling according to a set proportion and rounding to obtain a control signal corresponding to the index number, namely a control voltage signal V to be output to the S-type power amplifier c 。
5. The dynamic power supply system for a radio frequency power amplifier as claimed in claim 1, wherein: the S-type power amplifier comprises an interpolation filter, a Dleta-Sigma modulator, a switching power amplifier, a low-pass filter, a feedback path and a sampling clock circuit;
the interpolation filter is used for converting the control voltage signal V c Carrying out sampling rate conversion to obtain a sampling rate f s Control signal V of c ' and output to the Dleta-Sigma modulator at the frequency f s Provided by the sampling clock circuit;
the Delta-Sigma modulator receives the control signal V c ' and a feedback signal V output by the feedback path f Output switching signal V after internal calculation sw To the switching power amplifier; the internal calculation includes: calculating a control signal V' c And a feedback signal V f Integral of difference = ∑ [ V = c ′(n)-V f (n)]When L is present>Output at threshold V sw =1, otherwise output V sw ＝0；
The switching power amplifier is connected with an external direct current power supply and is used for generating a switching signal V sw Under the control, the DC power input by the external DC power supply is intermittently output through the switching device, and a switching signal V is formed h Output into the low pass filter and the feedback path;
the feedback path comprises a voltage sampling circuit for collecting the voltage at the output end of the switching power amplifier and an ADC (analog to digital converter), wherein the ADC converts the sampling voltage collected by the voltage sampling circuit into a digital feedback signal V f And transmitting to the Delta-Sigma modulator;
the low-pass filter receives a switching signal V h After the switching frequency and each harmonic component thereof are filtered, the output is proportional to the control voltage signal V c Dynamic supply voltage V d ；
The sampling clock circuit provides a frequency of f s To the interpolation filter and to the ADC of the feedback path.
6. The dynamic power supply system for a radio frequency power amplifier as claimed in any one of claims 1 to 5, wherein: the envelope mappingThe emitting module comprises a digital-to-analog converter, and a digital domain control signal V generated by mapping c Converting the signal into an analog signal and outputting the analog signal; the class-S power amplifier further comprises an ADC for converting the analog signal to a digital quantity.
7. The dynamic power supply system for a radio frequency power amplifier as set out in claim 5, wherein: the switching power amplifier adopts a BUCK type circuit and comprises a switching driver and two MOSFET tubes V1 and V2;
the switch driver receives the switch signal V sw Generating an and V sw Drive signals Q of the same phase but different levels + And V sw Inverted and different level driving signal Q - ；
The grid electrode of the MOSFET V1 is connected to the driving signal Q + The drain electrode of V1 is connected with the external direct current power supply to receive external direct current power supply, the source electrode of V1 is connected with the drain electrode of the MOSFET V2, and the connection point is used as a switching power output terminal of the switching power amplifier to output a switching signal V h ；
The gate of the second MOSFET V2 is connected to the driving signal Q - And the source of V2 is grounded.
8. The dynamic power supply system for a radio frequency power amplifier as claimed in claim 5, wherein: the low-pass filter comprises K inductors and K-1 capacitors, wherein K is more than or equal to 2 and is an integer; the K inductors are sequentially connected in series; first inductor L 1 The first terminal of the low-pass filter is used as the input end of the low-pass filter and is connected with the switching power output end of the switching power amplifier; the Kth inductor L K As an output of said low-pass filter, outputs a dynamic supply voltage V d (ii) a The connection mode of the K-1 capacitors is as follows: the kth (K is more than or equal to 1 and less than or equal to K-1) capacitor C k First terminal of (2) and kth inductance L k K +1 th L k+1 The k-th capacitor C k Is grounded.
9. The dynamic power supply system for a radio frequency power amplifier of claim 8, wherein: the Kth inductor L of the low-pass filter K And the low-pass filter is arranged at the drain electrode or the collector electrode of the radio-frequency power amplifier power tube, provides required inductive reactance for the low-pass filter, and provides radio-frequency choking inductance for the radio-frequency power amplifier power tube.
10. The dynamic power supply system for a radio frequency power amplifier as set out in claim 8, wherein: the Kth inductor L of the low-pass filter K Comprises two parts, respectively an inductor L K1 And an inductance L K2 (ii) a The inductance L K2 Is mounted at the drain or collector of the RF power amplifier power tube, and the L K2 Through the power supply lead and the inductor L K1 Are connected in series; inductor L K1 Inductor L K2 The power supply lead provides required inductive reactance for the low-pass filter; the inductance L K2 And simultaneously, a radio frequency choke inductor is provided for the radio frequency power amplifier power tube.
11. The dynamic power supply system for a radio frequency power amplifier as claimed in claim 1, wherein: the gain control signal G output by the mapping establishment module p Is an analog voltage configured to control the gain of a variable gain amplifier in the transmit path; or
The gain control signal G output by the mapping establishment module p Is a digital quantity configured to multiply a digital signal on the transmit path, changing the input signal amplitude of the radio frequency power amplifier.
12. The dynamic power supply system for a radio frequency power amplifier as claimed in claim 1 or 11, wherein: the mapping establishing module is provided with an enabling end, and the enabling end is controlled by an enabling signal input by an external controller;
when the enabling signal is in a high level, the mapping establishing module starts to work, otherwise, the mapping establishing module stops working; or
And when the enabling signal is in a low level, the mapping establishing module starts to work, otherwise, the mapping establishing module stops working.
13. The dynamic power supply system for a radio frequency power amplifier as claimed in claim 1, wherein: the feedback demodulation module comprises an ADC, a multiplier and a low-pass filter, wherein the ADC converts a power amplifier output coupling signal of the transmitting access into a digital radio-frequency signal; and multiplying the digital radio frequency signal by the orthogonal component and the in-phase component of the orthogonal local oscillator signal LO through the two multipliers respectively, and obtaining the feedback I/Q signal after the multiplied output signals pass through the two low-pass filters respectively.
14. A control method for a dynamic power supply system according to any one of claims 1 to 5, wherein: which comprises the following steps:
s1) judging whether a new mapping relation is to be established or not, if so, executing a step S2), otherwise, executing a step S3);
s2) establishing an envelope mapping relation, which comprises the following steps:
s21) outputting a control voltage signal V by the S-type power amplifier c Set to a constant value;
s22) by means of a gain control signal G p Adjusting the gain of a transmitting channel to enable the output of the radio frequency power amplifier to reach a set power value;
s23) calculating the gain of the radio frequency power amplifier according to the feedback I/Q baseband signal and the original I/Q baseband signal to obtain the gain compression amount during peak envelope power;
s24) if the gain compression reaches the target value, recording the current mapping output V c A value of V dmax The gain value at peak envelope power is denoted as G R_pk And step S25) is performed; if the gain compression does not reach the target value, adjusting the envelope mapping output value V c Repeating steps S21) to S24);
s25) according to the current radio frequency power amplifier gain G R Envelope dependent signal V e Change relationship G of R (V e ) According to
Establishing a mapping relation, and updating an envelope mapping module;
s26) under the updated envelope mapping relation, calculating the gain G of the radio frequency power amplifier according to the feedback I/Q baseband signal and the original I/Q baseband signal R (V e ) (ii) a If G is R (V e ) Is a constant G R_pk If not, the envelope mapping establishing process is exited, otherwise, the steps S25) to S26) are repeated;
s3) closing the mapping establishing module through an enabling signal;
s4) at each sampling moment n, the envelope detection module calculates an envelope signal according to the I/Q baseband signal generated by the external baseband signal generator
Wherein I is the in-phase component of the I/Q baseband signal; q is the quadrature component of the I/Q baseband signal;
s5) the envelope mapping module inputs the envelope signal V according to the mapping relation established by the mapping establishing module e (n) mapping to obtain a control voltage signal V of the S-type power amplifier c (n)；
S6) Delta-Sigma modulator in class S Power Amplifier with V c (n) as reference value, generating square wave switching signal, and adjusting frequency and duty ratio of the square wave switching signal by feedback loop to make the low frequency average value of the square wave switching signal equal to V c (n)；
S7) controlling a switching power amplifier to amplify through the square wave switching signal, and obtaining a high-power switching signal according to the direct-current power supply voltage;
s8) filtering the switching frequency of the high-power switching signal by a low-pass filter to obtain a signal proportional to the control signal V c Dynamic supply voltage V d Will supply the voltage V dynamically d And outputting the signal to an external radio frequency power amplifier to supply power to the external radio frequency power amplifier.
15. The control method of a dynamic power supply system according to claim 14, characterized in that: in the step S1), when the transmitting system is powered on for the first time, or the radio frequency carrier frequency is changed, or the output power deviation exceeds the threshold, or the load standing wave ratio change exceeds the threshold, a new mapping relationship needs to be established.
16. The control method of a dynamic power supply system according to claim 14, characterized in that: the gain control amount of the transmission path adjusted in the step S22) is
P o For the current output power, P t Is the target output power.
17. The control method of a dynamic power supply system according to claim 14, characterized in that: the method for calculating the gain compression amount at the time of peak envelope power in step S23) includes:
s231) envelope value V of original I/Q baseband signal e The radio frequency power amplifier gain G corresponding to the envelope value R (V e ) Set of compositions { V e (n),G R (V e (N)) | N =1,2.. N } is fitted by a polynomial to obtain a polynomial
Wherein M is an integer of 1 or more and represents a polynomial order, a m Is a polynomial coefficient;
s232) calculating V e ∈[0,V emax ]G within the range R (V e ) Maximum value of G Rmax In which V is emax For envelope peak, and calculating gain G corresponding to envelope of peak R_pk ＝G R (V emax )；
S234) calculating the peak envelope power, the amount of gain compression being dG = G Rmax -G R_pk 。
18. The control method of a dynamic power supply system according to claim 14, characterized in that: in the step S24), whenWhen the gain compression amount does not reach the target value, the output value of the envelope mapping is adjusted
Where dG _ tgt is a target value of the gain compression amount.
19. The control method of a dynamic power supply system according to claim 14, characterized in that: the step S25) further includes: amplifying gain G according to current radio frequency R Envelope V e Change relation G of R (V e ) According to
After the mapping relation is established, V is set c (V e ) Fitting by a polynomial to obtain
Wherein M is an integer of 1 or more and represents the polynomial order, b m The envelope mapping module is updated with the polynomial coefficients for the polynomial coefficients.
20. The control method of a dynamic power supply system according to claim 14, characterized in that: the step S25) further includes: amplifying gain G according to current radio frequency R Envelope V e Change relationship G of R (V e ) According to
After the mapping relation is established, at V e ∈[0,V emax ]Selecting a plurality of points, and calculating each V e Corresponding V c (V e ) A V is measured e Scaling and rounding according to a set proportion, and taking the rounded result asIndex number, the index number and the control signal V corresponding to the index number c And forming a data pair, and updating the envelope mapping module by using the table in a lookup table mode.
21. The control method of a dynamic power supply system according to claim 14, characterized in that: the step S26) further includes: under the updated envelope mapping relation, calculating the gain G of the radio frequency power amplifier by the feedback I/Q baseband signal and the original I/Q baseband signal R (V e ) And calculating the relative mean square error of the amplitudes of the feedback I/Q baseband signal and the original I/Q baseband signal
Wherein N is the number of statistical sampling points; relative mean square error Err 2 And if the value is smaller than the set threshold value, the envelope mapping establishment process is exited, and otherwise, the steps S25) to S26) are repeated.
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN116595927A (en) * | 2023-07-17 | 2023-08-15 | 昆山九华电子设备厂 | Voltage mapping establishment method for dynamic power supply power amplification system |
| CN116633383A (en) * | 2023-07-18 | 2023-08-22 | 唯捷创芯(天津)电子技术股份有限公司 | Radio frequency front-end module for optimizing DEVM (digital video memory) and electronic equipment |
| CN117674752A (en) * | 2023-10-19 | 2024-03-08 | 四川鸿创电子科技有限公司 | Automatic gain control method, device and equipment for frequency agile chip |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116595927A (en) * | 2023-07-17 | 2023-08-15 | 昆山九华电子设备厂 | Voltage mapping establishment method for dynamic power supply power amplification system |
| CN116595927B (en) * | 2023-07-17 | 2023-10-13 | 昆山九华电子设备厂 | Voltage mapping establishment method for dynamic power supply power amplification system |
| CN116633383A (en) * | 2023-07-18 | 2023-08-22 | 唯捷创芯(天津)电子技术股份有限公司 | Radio frequency front-end module for optimizing DEVM (digital video memory) and electronic equipment |
| CN116633383B (en) * | 2023-07-18 | 2023-10-17 | 唯捷创芯(天津)电子技术股份有限公司 | Radio frequency front-end module for optimizing dynamic error vector amplitude and electronic equipment |
| CN117674752A (en) * | 2023-10-19 | 2024-03-08 | 四川鸿创电子科技有限公司 | Automatic gain control method, device and equipment for frequency agile chip |
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