CN115117634A - High-gain circularly polarized beam scanning antenna with transmission super surface - Google Patents
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Abstract
The invention discloses a high-gain circularly polarized beam scanning antenna with a transmission super surface. The whole structure of the antenna is a radial line slot antenna RLSA, a super surface TM1 and a super surface TM2 from bottom to top; the super-surface TM1 and TM2 are the same, the super-surface units have 45-degree phase delay in the + X direction, and the super-surface units are arranged in the same way in the Y direction. The RLSA adopts a traditional design method, four probes are used for feeding clockwise with a-90-degree phase difference, the gap arrangement mode is annular arrangement, the RLSA can radiate circularly polarized pencil-shaped beams, and two-dimensional beam scanning is realized by rotating the pair of super surfaces. The beam scanning antenna provided by the invention has circular polarization, low loss and low cost aiming at the reflector antenna and the continuous transverse branch antenna, and can realize scanning at a larger angle only by controlling a pair of low-power motors.
Description
Technical Field
The invention belongs to the technical field of antennas, and relates to a high-gain circularly polarized beam scanning antenna with a transmission super surface.
Technical Field
In different communication systems such as high-speed wireless local area networks, backhaul networks, televisions, direct broadcast systems, satellite reception, mobile communication, etc., there are strong demands for microwave and millimeter wave antennas. Various antennas such as a parabolic reflector antenna, a microstrip patch antenna, and an array antenna are widely used in satellite communication. Compared with a parabolic reflector antenna, the flat antenna has the advantages of high efficiency, strong applicability, small profile and the like, so that the flat antenna is often used for replacing the parabolic antenna. A Radial Line Slot Antenna (RLSA) is a typical non-resonant planar Slot Antenna, and the RLSA has the following advantages for a conventional planar Antenna: 1) the structure is simple, the cost is low, and the processing and the conformation are easy; 2) high gain, high efficiency and small waveguide feed loss; 3) the axial ratio performance of circular polarization is good.
In modern radio communication systems, beam scanning becomes a key technology in high capacity communication systems, which can increase signal coverage and minimize interference to other areas while enhancing signal strength through fast deflection of narrow beams. The current modes for high-directivity beam rotation can be divided into two categories: the first type is mechanical scanning mode, and the second type is electrical scanning. The first category can be divided into two categories according to the scanning mode, 1, rotating and tilting antennas; 2. rotating but not tilting the antenna; the mechanical scanning of the first method is mainly used in parabolic reflector systems, which perform well due to the overall rotation and tilting of the antenna, but are high in profile, too bulky and expensive to control the rotating motor, and are not suitable for use in aircraft and the like. The second method is applied to Continuous Transverse Stubs (CTS), which requires three or more rotating antennas, and the antenna system is complicated and expensive, but has a lower profile than the first parabolic antenna system. The second type of electric scanning antenna adopts electric control, the electric control can accurately and quickly realize beam scanning, and compared with the first and second mechanical scanning antenna systems, the scanning is more accurate and faster, and the second type of electric scanning antenna system is more suitable for the field of radar military operation, but too many T/R components exist, and the price of the antenna is high. Therefore, it is important to design a beam scanning antenna with low cost, low profile and high gain.
Disclosure of Invention
The invention mainly aims to overcome the defects of the prior art and provides a high-gain circularly polarized beam scanning antenna based on a transmission super surface, aiming at realizing two-dimensional beam regulation and control of a high-gain beam and circular polarization of the antenna.
In order to achieve the purpose of the invention, the technical scheme of the invention is as follows;
a high-gain circularly polarized beam scanning antenna with a transmission super surface comprises a radial line slot antenna 1, a phase gradient super surface TM1 and a phase gradient super surface TM2, wherein the radial line slot antenna 1, the phase gradient super surface TM1 and the phase gradient super surface TM2 are concentrically arranged relative to a central axis from bottom to top and are parallel to each other;
radial line slot antenna 1, comprising: the device comprises a lower-layer metal supporting plate, a single-layer radial line waveguide fixed above the metal supporting plate, and a copper-clad radiation slot array, wherein the upper surface of the radial line waveguide penetrates through the surface of the waveguide;
the copper-clad radiation slot array comprises a plurality of circles of concentric annular slots 5, each circle of annular slot is obtained by copying a pair of circularly polarized slots which rotate in the same direction and the same angle relative to the circle center of the array, the slot pairs of the same circle are uniformly arranged on the corresponding circle, the angle of the adjacent slot pairs which rotate in sequence is equal to 360 degrees divided by the number of the slot pairs of each circle, and the length of the slot pairs of the copper-clad radiation slot array is sequentially increased from the circle center of the array to the outside along the radial direction;
the four coaxial probe feeds 4 are transmitted in the waveguide from the lower metal support plate through a medium, an open-circuit probe is adopted for feeding, and the four coaxial probe feeds 4 are fed clockwise according to an equiamplitude phase difference of-90 degrees;
the phase gradient super surface TM1 and the phase gradient super surface TM2 are arrays formed by the phase gradient super surface units 6 according to a certain rule;
the phase gradient super-surface unit 6 comprises two layers of dielectric substrates 7 and three layers of metal, wherein the metal and the dielectric substrates 7 are alternately arranged from bottom to top, each layer of metal comprises an outermost square ring and two identical crossed rectangular metal patches at the center inside the square ring, and the phase gradient super-surface TM1 and the phase gradient super-surface TM2 have the same structure;
the beam deflection is realized through the rotation of the phase gradient super surface TM1 and the phase gradient super surface TM2 around the central axis;
the central axis of the antenna is in the Z direction upwards, the plane parallel to the radial line slot antenna 1 is an XOY plane, the direction from the center of a circle to the outside in the radial direction on the XOY plane is X, and the Y axis is perpendicular to the X axis.
Preferably, the annular gap 5 comprises 3 concentric annular gaps. The 3-turn slot array is provided to obtain the required gain of around 23 dBi.
Preferably, the period P of the phase gradient super surface unit 6 is 10mm or 0.4 λ 0 ，λ 0 The center frequency is 12GHz, which is the wavelength in free space.
Preferably, the length of the square ring of the phase gradient super-surface unit 6 is 10mm, the width t is 0.3mm, and the size of the cross rectangular metal patch at the center is determined based on the phase difference.
Preferably, the phase gradient super-surface TM1 and the phase gradient super-surface TM2 are arranged along the + X axis in a decreasing manner with a phase Δ Φ equal to 45 °, and the units having the same size are arranged along the Y axis.
Preferably, the phase gradient super-surface unit 6 needs to realize the phases of 0 °, -45 °, -90 °, -135 °, -180 °, -225 °, -270 °, -315 ° in sequence.
Preferably, the phase gradient super-surfaces TM1 and TM2 can realize deflection of a single beam, and the deflection angle is calculated by the following formula:
where Δ Φ is the phase difference of adjacent cells, P is the cell period, δ is the beam deflection angle, λ 0 Is the wavelength in free space.
Preferably, the maximum deflection is calculated by the formula:
sinθ max ＝sinδ 1 +sinδ 2
wherein, theta max At the maximum beam deflection angle, δ 1 Beam deflection angle, δ, achieved for TM1 2 For the beam deflection angle achieved by TM2, if TM1 and TM2 are the same, then δ 1 ＝δ 2 。
Preferably, the beam finally realized by the antenna can be at an angle of 2 θ max The beam scanning is performed in the cone range, and the calculation formula of the beam direction is as follows:
where θ is the elevation angle of the beam, φ is the azimuth angle of the beam, k 0 Is a propagation constant in free space, p 1 Is a phase gradient of TM1, p 2 Is a phase gradient of TM2, alpha 1 Is the angle of the phase retardation axis of TM1 with the X direction, alpha 2 Is the angle of the phase retardation axis of TM2 with the X direction.
Furthermore, the relative dielectric constant of the filling medium in the single-layer radial line waveguide is 1.55, the dielectric loss tangent angle is 0.001, and the thickness H of the medium is RLSA ＝5mm。
Preferably, the interval between each circle of adjacent annular slots is 0.6 wavelengths of the radial line waveguide, and the interval is the distance between each slot and the center. The spacing of 0.6 wavelengths is to avoid grating lobes and to reduce mutual coupling between the slots.
Preferably, the 4 coaxial probes are uniformly distributed on the circumference of the RLSA with an inner radius of 4.1 mm. The stable field mode needed for excitation in the radial line waveguide can be ensured.
The phase gradient super-surface antenna is characterized in that 8 super-surface units are sequentially arranged in the + X direction in a 45-degree decreasing mode according to phases, the same unit structure is adopted in the Y direction, and a two-dimensional phase gradient super-surface structure is formed.
Furthermore, the structural period of the super-surface unit is p equal to 10mm, the length of the metal square ring is L equal to 10mm, the width t is 0.3mm, the length of the crossed rectangular metal is Ln, and the width is Wn (Ln/2), and different phase differences of the super-surface unit can be realized only by changing Ln.
Further, the distance between the super-surface TM1 and the TM2 is HTM 15mm, and the distance between the super-surface TM1 and the RLSA is HTR 15 mm.
Furthermore, the super-surface unit adopts two layers of dielectric substrates and three layers of metal layers, the material of the dielectric substrate is F4BM, and the relative dielectric constant epsilon r 2.2, loss tangent tan delta 0.001, thickness H F4B ＝1.5mm。
Furthermore, the super-surface TM1 and the TM2 have the same structure, are round calibers, have the same calibers as those of the RLSA, have a calibre radius Rmax of 65mm, and have a total height H all ＝41mm(1.64λ 0 )
Furthermore, the number of the super-surface units is 112, and the super-surface units are distributed in a phase from left to right in sequence of-180 degrees, -225 degrees, -270 degrees, -315 degrees, -0 degrees, -45 degrees, -90 degrees, -135 degrees, -180 degrees, -225 degrees, -270 degrees and-315 degrees. And only eight super-surface units with different structure sizes are needed, the phase distribution is from 0 to 315 degrees, and the cross rectangular metal lengths Ln are as follows in sequence: 1mm, 4.3mm, 6.1mm, 7.25mm, 7.74mm, 8.1mm, 8.34mm, 8.45 mm.
The invention has the beneficial effects that:
the invention adopts RLSA and super surface antenna to realize directional radiation of antenna high gain beam, and realizes scanning in larger angle only by controlling a pair of low power motors. The invention can be realized in azimuth
The beam with the pitching angle theta of +/-39 degrees is pointed, the loss of the antenna in scanning is within 3dB, and the axial ratio is lower than 3dBHas good circular polarization performance.
For a mechanically controlled large-reflector antenna, the invention does not need a huge rotating device and has the characteristic of plane low profile. For the motor-controlled array antenna, the antenna only needs very low power when working, has lower power loss, has low whole radio frequency loss, does not need heat dissipation treatment, and has the potential of realizing a high-power antenna. The RLSA is completely stationary, so no powerful motors or rotary joints are required, nor are active electronics required for the super-surface.
Drawings
FIG. 1 is a schematic structural view of example 1 of the present invention;
fig. 2 is a top view of embodiment 1 of the present invention: FIG. 2(a) is a schematic view of an RLSA structure according to example 1 of the present invention; FIG. 2(b) schematic diagram of the super-surface TM1 and TM2 array arrangement of example 1 of the present invention
FIG. 3 is a schematic view of a super-surface unit in embodiment 2 of the present invention: FIG. 3(a) is a three-dimensional block diagram of a super-surface unit; FIG. 3(b) is a top view of a super surface unit; FIG. 3(c) is a side view of a super surface unit;
FIG. 4 is a side view of example 1 of the present invention;
fig. 5 is a diagram illustrating a far-field simulation result of the RLSA antenna according to embodiment 2 of the present invention: FIG. 5(a) is a diagram illustrating a far-field two-dimensional gain simulation result; FIG. 5(b) is a diagram illustrating the far-field axial ratio simulation results;
FIG. 6 is a schematic diagram of the transmission amplitude and the transmission phase of the simulation of the super-surface unit in embodiment 2 of the present invention;
FIG. 7 is a graph showing the reflection coefficient results of the RLSA antenna according to embodiment 2 of the present invention;
fig. 8 is a far-field two-dimensional gain pattern of the high-gain beam scanning antenna according to embodiment 2 of the present invention;
fig. 9 is an enlarged view of the far-field two-dimensional gain direction of the high-gain beam scanning antenna according to embodiment 2 of the present invention;
FIG. 10 is a normalized far field two-dimensional gain and axial ratio plot of example 2 of the present invention;
the antenna comprises a radial line slot antenna 1, a phase gradient super surface TM 12, a phase gradient super surface TM 23, a four-coaxial probe feed 4, an annular slot 5, a phase gradient super surface unit 6 and a dielectric substrate 7.
Detailed Description
The embodiments of the present invention are described below with reference to specific embodiments, and other advantages and effects of the present invention will be easily understood by those skilled in the art from the disclosure of the present specification. The invention is capable of other and different embodiments and of being practiced or of being carried out in various ways, and its several details are capable of modification in various respects, all without departing from the spirit and scope of the present invention.
Example 1
As shown in fig. 1 to fig. 3, the present embodiment provides a high-gain circularly polarized beam scanning antenna with transmissive super-surface, which is characterized by including a radial line slot antenna 1, a phase gradient super-surface TM1, and a phase gradient super-surface TM2, which are concentrically arranged about a central axis from bottom to top and are parallel to each other;
radial line slot antenna 1, comprising: the device comprises a lower-layer metal supporting plate, a single-layer radial line waveguide fixed above the metal supporting plate, and a copper-clad radiation slot array, wherein the upper surface of the radial line waveguide penetrates through the surface of the waveguide;
the copper-clad radiation slot array comprises a plurality of circles of concentric annular slots 5, each circle of annular slot is obtained by copying a pair of circularly polarized slots which rotate in the same direction and the same angle relative to the circle center of the array, the slot pairs of the same circle are uniformly arranged on the corresponding circle, the angle of the adjacent slot pairs which rotate in sequence is equal to 360 degrees divided by the number of the slot pairs of each circle, and the length of the slot pairs of the copper-clad radiation slot array is sequentially increased from the circle center of the array to the outside along the radial direction;
the four coaxial probe feeds 4 are transmitted in the waveguide from the lower metal support plate through a medium, an open-circuit probe is adopted for feeding, and the four coaxial probe feeds 4 are fed clockwise according to an equiamplitude phase difference of-90 degrees;
the phase gradient super surface TM1 and the phase gradient super surface TM2 are arrays formed by the phase gradient super surface units 6 according to a certain rule;
the phase gradient super-surface unit 6 comprises two layers of dielectric substrates 7 and three layers of metal, wherein the metal and the dielectric substrates 7 are alternately arranged from bottom to top, each layer of metal comprises an outermost square ring and two identical crossed rectangular metal patches at the center inside the square ring, and the phase gradient super-surface TM1 and the phase gradient super-surface TM2 have the same structure;
the beam deflection is realized through the rotation of the phase gradient super surface TM1 and the phase gradient super surface TM2 around the central axis;
the central axis of the antenna is in the Z direction, the plane parallel to the radial line slot antenna 1 is an XOY plane, the direction from the center of the circle to the outside along the radial direction on the XOY plane is X, and the Y axis is perpendicular to the X axis.
Example 2
The present embodiment provides a high-gain circularly polarized beam scanning antenna with transmission super-surface, which is different from embodiment 1 in that: the annular gap 5 comprises 3 concentric annular gaps.
The period P of the phase gradient super surface unit 6 is 10mm and 0.4 lambda 0 ，λ 0 The center frequency is 12GHz, which is the wavelength in free space.
The length of the square ring of the phase gradient super-surface unit 6 is 10mm, the width thereof is 0.3mm, and the size of the central cross rectangular metal patch is determined based on the phase difference.
The phase gradient super surface TM1 and the phase gradient super surface TM2 are arranged along the + X axis in a descending manner according to the phase delta phi of 45 degrees, and the units with the same size are arranged along the Y axis.
The phases required to be realized by the phase gradient super-surface unit 6 are 0 degrees, 45 degrees, 90 degrees, 135 degrees, 180 degrees, 225 degrees, 270 degrees and 315 degrees in sequence.
The phase gradient super-surface TM1 and TM2 can realize deflection of a single beam, and the calculation formula of the deflection angle is as follows:
where Δ Φ is the phase difference of adjacent cells, P is the cell period, δ is the beam deflection angle, λ 0 Is the wavelength in free space.
The maximum deflection is calculated as:
sinθ max ＝sinδ 1 +sinδ 2
wherein, theta max At the maximum beam deflection angle, δ 1 Beam deflection angle, δ, achieved for TM1 2 For the beam deflection angle achieved by TM2, if TM1 and TM2 are the same, then δ 1 ＝δ 2 。
The final realized beam of the antenna can be at an angle of 2 theta max The beam scanning is performed in the conical range of (a), and the calculation formula of the beam direction is as follows:
where θ is the elevation angle of the beam, φ is the azimuth angle of the beam, k 0 Is a propagation constant in free space, p 1 Is a phase gradient of TM1, p 2 Is a phase gradient of the TM2 and,
α 1 is the angle of the phase retardation axis of TM1 with the X direction, alpha 2 Is the angle of the phase retardation axis of TM2 with the X direction.
The relative dielectric constant of the medium filled in the single-layer radial line waveguide is 1.55, the dielectric loss tangent angle is 0.001, and the thickness H of the medium RLSA ＝5mm。
The interval between each circle of adjacent annular gaps is the wavelength of 0.6 radial line waveguides, and the interval is the distance between each gap and a center. The spacing of 0.6 wavelengths is to avoid grating lobes and to reduce mutual coupling between the slots.
The 4 coaxial probes are evenly distributed on the circumference of the RLSA with the inner radius of 4.1 mm. The stable field mode needed for excitation in the radial line waveguide can be ensured.
The phase gradient super-surface antenna is characterized in that 8 super-surface units are sequentially arranged in the + X direction in a 45-degree decreasing mode according to phases, the same unit structure is adopted in the Y direction, and a two-dimensional phase gradient super-surface structure is formed.
The structural period of the super-surface unit is 10mm, the length of the metal square ring is 10mm, the width t is 0.3mm, the length of the crossed rectangular metal is Ln, the width of the crossed rectangular metal is Wn (Ln/2), and different phase differences of the super-surface unit can be realized only by changing Ln.
The distance between the TM1 and the TM2 of the super surface is H TM 15mm, distance between the super-surface TM1 and RLSA TR ＝15mm。
The super-surface unit adopts two layers of dielectric substrates and three layers of metal layers, the material of the dielectric substrate is F4BM, and the relative dielectric constant epsilon r 2.2, loss tangent tan delta 0.001, thickness H F4B ＝1.5mm。
The super-surface TM1 and the TM2 have the same structure, are round calibers and have the same calibers as those of the RLSA, the calibre radius Rmax is 65mm, and the total height of the antenna is H all ＝41mm(1.64λ 0 )
The super-surface units are 112 in number, and are distributed in a phase from left to right in sequence of-180 degrees, -225 degrees, -270 degrees, -315 degrees, -0 degrees, -45 degrees, -90 degrees, -135 degrees, -180 degrees, -225 degrees, -270 degrees and-315 degrees. And only eight super-surface units with different structure sizes are needed, the phase distribution is from 0 to 315 degrees, and the cross rectangular metal lengths Ln are as follows in sequence: 1mm, 4.3mm, 6.1mm, 7.25mm, 7.74mm, 8.1mm, 8.34mm, 8.45 mm.
The working principle of the embodiment is as follows:
1. the phase gradient super-surface units are arranged according to a phase difference of 45 degrees, and then the delta phi is 45 degrees, and the p is 10mm
One can get δ to 18.21 °, then the phase gradient metasurfaces TM1 and TM2 are able to achieve a beam deflection of 18.21 °.
2. Firstly, the radial line slot antenna RLSA and the phase gradient super surface TM1 are fixed and the phase ladder is rotatedSuper surface TM2, then alpha 1 ＝0°，α 2 As the angle of rotation changes. Suppose alpha 2 With a step change of 30 deg., the final beam pointing direction can be calculated as shown in table 1:
TABLE 1 fixed TM1, rotating TM2 beam pointing
When TM2 is rotated and TM1 is fixed, the beam moves in an arc between two extreme positions (θ, Φ) (37 °,0 °) to (θ, Φ) (0 ° )
3. Secondly, when TM1 and TM2 rotate synchronously in the same direction, if the beam elevation angle is fixed at 37.14 °, and the phase delay axis directions of TM1 and TM2 are different by 30 °, α 1 -α 2 30 °, the final beam pointing can be calculated as shown in table 2:
TABLE 2 beam pointing with synchronous in-phase rotation of TM1 and TM2
By rotating the super-surface synchronously in the same direction, the azimuth phi of the beam changes and the beam can be directed in any direction within the cone with an apex angle of 4 delta.
In practice, the beam may be tilted to the desired elevation angle (θ) by first rotating either TM1 or TM2, as described at 0. The beam is then steered to the desired azimuth angle (phi) without affecting the pitch angle (theta) by the synergistic effect of TM1 and TM 2.
4. Finally, when TM1 and TM2 rotate in synchronous reverse, assume α 1 ＝α 2 And 0 deg., the beam direction is 38.68 deg.. And phi is 0 deg. Alpha is alpha 1 Decrease in amplitude of 15 deg., alpha 2 Increasing in magnitude by 15 deg.. The corresponding beam directions are listed in table 3. The fixed rotation angles are the same, the two super-surfaces rotate towards opposite directions, and the radiation beams can move in an elevation plane without changing the azimuth angle.
TABLE 3 TM1 and TM2 synchronized counter-rotating beam pointing
In practice, TM1 and TM2 can be rotated synchronously in the same direction to change the beam azimuth φ to the desired angle, and then rotated synchronously in opposite directions to change the beam elevation θ to the desired angle without changing the previously set azimuth φ. Thus, in conjunction with the rotation of the two super-surfaces, the beam can move in any direction within the cone of apex angle 4 δ.
The technical effect of this embodiment is further explained by HFSS simulation experiments.
And (3) simulation result analysis:
referring to fig. 5(a), the far field two-dimensional gain pattern of the RLSA has very symmetric E-plane and H-plane, with a gain of 23.95B at normal and a aperture efficiency of 93%. Referring to fig. 5(b), the left-hand circular polarization axial ratio of the RLSA is 0.12dB, and thus it can be seen that the RLSA has a high gain and a very good axial ratio performance.
Referring to FIG. 6, in the range of Ln 0-8.5 mm, the transmission amplitude is greater than-3 dB, the transmission phase is between 0 DEG and-334 DEG, and TM is 00 And TE 00 The electromagnetic waves polarized in two directions are consistent, which shows that the unit has high transmission performance for X-polarized waves and Y-polarized waves and is suitable for the incidence of circularly polarized waves.
Referring to FIG. 7, the reflection coefficient S11 of the antenna is shown, S11< -10dB and the relative bandwidth is 19.45% under the frequency of 11 GHz-13.37 GHz.
Referring to fig. 8, a far-field two-dimensional gain pattern of the high-gain beam scanning antenna transmitting through the super-surface is shown, and a comparison between a simulation result and a prediction result is shown in table 4, and it can be seen from table 4 that the predicted direction of the beam is very close to the simulation result, and the error range is within ± 2 °.
TABLE 4 predicted and simulated results Beam pointing comparison
Referring to fig. 9, the two-dimensional gain curve of fig. 8 is amplified, so that it can be seen more intuitively that the gain drop in the whole scanning range is not more than 3dB, and the aperture efficiency of the antenna is 42% -21.6%.
Referring to fig. 10, normalized gain and axial ratio of the high-gain beam scanning antenna transmitting through the super-surface are shown, and the axial ratio in the radiation direction is less than-3 dB, so that the circularly polarized antenna index is satisfied. Table 5 shows the beam pointing gain and axial ratio results:
TABLE 5 gain and axial ratio results for beam pointing
The foregoing embodiments are merely illustrative of the principles and utilities of the present invention and are not intended to limit the invention. Any person skilled in the art can modify or change the above-mentioned embodiments without departing from the spirit and scope of the present invention. Accordingly, it is intended that all equivalent modifications or changes which can be made by those skilled in the art without departing from the spirit and technical spirit of the present invention be covered by the claims of the present invention.
Claims (9)
1. A high-gain circularly polarized beam scanning antenna with a transmission super surface is characterized by comprising a radial line slot antenna (1), a phase gradient super surface TM1(2) and a phase gradient super surface TM2(3), wherein the radial line slot antenna (1), the phase gradient super surface TM1(2) and the phase gradient super surface TM2 are concentrically arranged relative to a central axis and are parallel to each other from bottom to top;
radial line slot antenna (1) comprising: the device comprises a lower-layer metal supporting plate, a single-layer radial line waveguide fixed above the metal supporting plate, and a copper-clad radiation slot array, wherein the upper surface of the radial line waveguide penetrates through the surface of the waveguide;
the copper-clad radiation slot array comprises a plurality of circles of concentric annular slots (5), each circle of annular slot is obtained by copying a pair of circularly polarized slots which rotate in the same direction and the same angle relative to the circle center of the array, the slot pairs of the same circle are uniformly arranged on the corresponding circle, the angle of the adjacent slot pairs which rotate in sequence is equal to 360 degrees divided by the number of the slot pairs of each circle, and the length of the slot pairs of the copper-clad radiation slot array is sequentially increased from the circle center of the array to the outside along the radial direction;
the four coaxial probe feeds (4) are transmitted in the waveguide from the lower metal support plate through a medium, an open-circuit probe is adopted for feeding, and the four coaxial probe feeds (4) are fed clockwise according to an equi-radiation phase difference of-90 degrees;
the phase gradient super surface TM1(2) and the phase gradient super surface TM2(3) are arrays formed by the phase gradient super surface units (6) according to a certain rule;
the phase gradient super-surface unit (6) comprises two layers of dielectric substrates (7) and three layers of metal, the two layers of metal and the dielectric substrates (7) are alternately arranged from bottom to top, each layer of metal comprises an outermost square ring and two identical crossed rectangular metal patches in the center of the inside of the square ring, and the phase gradient super-surface TM1(2) and the phase gradient super-surface TM2(3) are identical in structure;
the beam deflection is realized through the rotation of the phase gradient super surface TM1(2) and the phase gradient super surface TM2(3) around the central axis;
the central axis of the antenna is in the Z direction, the plane parallel to the radial line slot antenna (1) is an XOY plane, the direction from the center of a circle to the outside along the radial direction on the XOY plane is X, and the Y axis is perpendicular to the X axis.
2. The high-gain circularly polarized beam scanning antenna with transmission super-surface as claimed in claim 1, wherein: the annular gap (5) comprises 3 concentric annular gaps.
3. The high-gain circularly polarized beam scanning antenna with transmission super-surface as claimed in claim 1, wherein: the period P of the phase gradient super surface unit (6) is 10mm and 0.4 lambda 0 ，λ 0 The center frequency is 12GHz, which is the wavelength in free space.
4. The high-gain circularly polarized beam scanning antenna with transmission super-surface as claimed in claim 1, wherein: the length of a square ring of the phase gradient super-surface unit (6) is 10mm, the width of the square ring is 0.3mm, and the size of the central cross rectangular metal patch is determined based on the phase difference.
5. The high-gain circularly polarized beam scanning antenna with transmission super-surface as claimed in claim 1, wherein: the phase gradient super-surface TM1(2) and the phase gradient super-surface TM2(3) are arranged along the + X axis in a descending manner according to the phase delta phi of 45 degrees, and units with the same size are arranged along the Y axis.
6. The high-gain circularly polarized beam scanning antenna with transmission super-surface as claimed in claim 5, wherein: the phases required to be realized by the phase gradient super-surface unit (6) are 0 degree, 45 degree, 90 degree, 135 degree, 180 degree, 225 degree, 270 degree and 315 degree in sequence.
7. The super-surface transmissive high-gain circularly polarized beam scanning antenna as claimed in claim 5, wherein the phase gradient super-surfaces TM1 and TM2 are capable of realizing single beam deflection, and the deflection angle is calculated as:
where Δ Φ is the phase difference of adjacent cells, P is the cell period, δ is the beam deflection angle, λ 0 Is the wavelength in free space.
8. The high-gain circularly polarized beam scanning antenna with transmission super-surface as claimed in claim 1, wherein the maximum deflection is calculated by the formula:
sinθ max ＝sinδ 1 +sinδ 2
wherein, theta max At the maximum beam deflection angle, δ 1 Beam deflection angle, δ, achieved for TM1 2 For the beam deflection angle achieved by TM2, if TM1 and TM2 are the same, then δ 1 ＝δ 2 。
9. The high-gain circularly polarized beam scanning antenna with transmission super-surface as claimed in claim 1, wherein: the final realized beam of the antenna can be at an angle of 2 theta max The beam scanning is performed in the cone range, and the calculation formula of the beam direction is as follows:
where θ is the elevation angle of the beam, φ is the azimuth angle of the beam, k 0 Is a propagation constant in free space, p 1 Is a phase gradient of TM1, p 2 Is a phase gradient of TM2, alpha 1 A phase delay axis of TM1 andangle in X direction, α 2 Is the angle of the phase retardation axis of TM2 with the X direction.
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