CN115085608A - MTPA control method based on permanent magnet synchronous motor - Google Patents

MTPA control method based on permanent magnet synchronous motor Download PDF

Info

Publication number
CN115085608A
CN115085608A CN202210853521.6A CN202210853521A CN115085608A CN 115085608 A CN115085608 A CN 115085608A CN 202210853521 A CN202210853521 A CN 202210853521A CN 115085608 A CN115085608 A CN 115085608A
Authority
CN
China
Prior art keywords
mtpa
stator
permanent magnet
frequency signal
current
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
CN202210853521.6A
Other languages
Chinese (zh)
Inventor
金宁治
陈洪超
巫志强
张龙
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Harbin University of Science and Technology
Original Assignee
Harbin University of Science and Technology
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Harbin University of Science and Technology filed Critical Harbin University of Science and Technology
Priority to CN202210853521.6A priority Critical patent/CN115085608A/en
Publication of CN115085608A publication Critical patent/CN115085608A/en
Pending legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
    • H02P21/0017—Model reference adaptation, e.g. MRAS or MRAC, useful for control or parameter estimation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H02P21/18—Estimation of position or speed
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H02P21/20—Estimation of torque
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/14—Electronic commutators
    • H02P6/16—Circuit arrangements for detecting position
    • H02P6/18—Circuit arrangements for detecting position without separate position detecting elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
    • H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/72—Electric energy management in electromobility

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

An MTPA control method based on a permanent magnet synchronous motor relates to the field of motor control. The invention aims to solve the problem that the MTPA control method in the prior art ignores parameter change, so that the MTPA is difficult to realize accurate control. The invention obtains the direct axis inductance L according to the model reference self-adaptive system d And a stator resistance R; according to the direct axis inductance L d Establishing a torque equation with the stator resistor R; injecting a virtual high-frequency signal to further obtain a current angle of an MTPA working point; and obtaining quadrature axis current and direct axis current when the MTPA operates according to the current angle of the MTPA working point and the stator current vector. The invention obtains a new torque estimation equation with higher precision through the parameter and the high-frequency signal injection construction, and realizes the high precision of the motorAnd (5) controlling the degree.

Description

MTPA control method based on permanent magnet synchronous motor
Technical Field
The invention relates to the field of motor control, in particular to an MTPA control method based on a permanent magnet synchronous motor.
Background
With the rapid development of the automobile industry, environmental protection and resource shortage problems are accompanied. Therefore, electric vehicles have received attention. In an electric vehicle, a permanent magnet synchronous motor has the advantages of high power density, small size, light weight and the like, and is gradually one of the mainstream of a traction drive motor of the electric vehicle. MTPA is widely applied as an efficient control mode of a permanent magnet synchronous motor, and can output maximum torque under certain stator current, so that the operating efficiency of the whole system is improved. The main MTPA control methods include: formula method, parameter identification method, table look-up method, automatic search method and high-frequency signal injection method.
The equation method derives the MTPA solution by differentiating the partial differential of the motor torque with respect to the current angle to 0. However, this method cannot obtain an accurate MTPA solution because parameter variations are ignored. The parameter identification method is combined with online parameter identification on the basis of a formula method, so that accurate motor parameters can be obtained in real time, and the operation accuracy of the motor is improved. This method relies on tedious parameter monitoring and estimation, thus requiring the controller to have high computational power and the addition of additional hardware. The table look-up method needs to find the MTPA point of the motor in advance through an experiment or simulation mode, and then the motor works at the MTPA point through a table look-up mode. However, this method requires a lot of resources and time to find the MTPA point in advance. The automatic search method is a control strategy for adjusting the vector angle of the stator current to achieve the optimal MTPA by continuously giving a small step angle under the steady state operation of the system. However, the method has low convergence rate and low torque control precision. The high-frequency signal injection method is to observe the feedback quantity of the high-frequency signal of the injection system and calculate and analyze the feedback quantity to obtain the optimal working state. However, the high-frequency current injected by the method increases system torque ripple and additional power loss, and the torque equation constructed in the virtual signal injection method in the prior art ignores the internal parameters of the motor, so that the error is large.
The existing parameter identification method comprises a ground-inferred lowest second multiplication method, an extended Kalman filtering method and a neural network method, wherein the recursive least square method is to correct data obtained in the last step according to currently obtained data on the basis of a last model parameter estimation value so as to obtain an estimation value of a current moment model parameter. In the recursive operation process, the recursive least square method has a data saturation phenomenon and has high requirements on system hardware and software programming. The extended kalman filtering method incorporates a discrete space model into the filtering algorithm, and achieves optimal estimation of the system state by minimizing the estimated covariance. When a plurality of parameters are identified simultaneously, the method has a complex operation process, so that the difficulty is high. The neural network method can obtain better convergence characteristics, but the algorithm is very complex, so that the method is limited in practical application.
Therefore, those skilled in the art have been devoted to developing a MTPA control method based on a permanent magnet synchronous motor.
Disclosure of Invention
In view of the above defects in the prior art, the invention provides an MTPA control method based on a permanent magnet synchronous motor, which constructs a torque estimation equation with higher precision, obtains a more accurate MTPA working point, and has higher robustness and response speed.
In order to achieve the above object, the present invention provides a MTPA control method based on a permanent magnet synchronous motor, including:
s1, obtaining the direct axis inductance L according to the model reference self-adaptive system d And a stator resistance R;
s2, according to the direct axis inductance L d Establishing a torque equation with the stator resistor R;
s3, injecting a virtual high-frequency signal to further obtain a current angle of an MTPA working point;
and S4, obtaining quadrature axis current and direct axis current when the MTPA is operated according to the current angle of the MTPA working point and the stator current vector.
Further, the reference model of the model reference adaptive system is:
Figure BDA0003738223210000021
wherein:
Figure BDA0003738223210000022
i. u is stator current and voltage, respectively; l is d ，L q Are respectively stator d-q axis inductors; r is a stator resistor; psi f A permanent magnet flux linkage; omega is the electrical angular velocity;
the adjustable model of the model reference adaptive system is as follows:
Figure BDA0003738223210000023
wherein:
Figure BDA0003738223210000024
m is a gain matrix, and M is a gain matrix,
Figure BDA0003738223210000025
e is the error of the adjustable model and the reference model.
Further, the torque equation in step S2 is:
Figure BDA0003738223210000026
wherein the content of the first and second substances,
Figure BDA0003738223210000027
is a quadrature axis inductor, and is characterized in that,
Figure BDA0003738223210000028
is a permanent magnet flux linkage, T e Representing electromagnetic torque, P being the number of pole pairs, i d 、i q ，u d 、u q Stator d-q axis currents and voltages, respectively.
Further, step S3 includes:
s31, injecting the virtual high-frequency signal delta beta to obtain a torque equation after the virtual high-frequency signal is injected;
s32, the torque equation of the step S31 is combined with sin (omega) h t) multiplication;
s33, filtering the high-frequency term by a low-pass filter to obtain the electromagnetic torqueFirst partial derivative of
Figure BDA0003738223210000031
Make it
Figure BDA0003738223210000032
The current angle of the MTPA operating point is obtained by integration.
Further, the torque equation after the injection of the virtual high-frequency signal is as follows:
Figure BDA0003738223210000033
wherein Δ β ═ Asin (ω) h t) is a high frequency current angle signal;
Figure BDA0003738223210000034
representing the torque after the injection of the high-frequency signal;
Figure BDA0003738223210000035
the stator d-q axis currents after high-frequency signal injection are respectively.
Compared with the prior art, the method has the following technical effects:
1. the method fully considers the influence of the parameter change condition in the motor operation, adopts a model reference adaptive parameter identification method, and obtains the direct axis inductance L of the motor in real time d And a stator resistor R, and injecting the parameter and a high-frequency signal to construct a new torque estimation equation with higher precision;
2. in the signal extraction process, only the low-pass filter is adopted, so that a more accurate MTPA working point is obtained, and the method has higher robustness and response speed.
The conception, the specific structure and the technical effects of the present invention will be further described with reference to the accompanying drawings to fully understand the objects, the features and the effects of the present invention.
Drawings
FIG. 1 is a basic flowchart of a parameter-identified MTPA control method;
FIG. 2 is a graph comparing conventional and improved signal extraction according to the present invention;
FIG. 3 is a system control block diagram of the present invention;
FIG. 4 is a block diagram of the virtual signal module control of the present invention.
Detailed Description
The following embodiments of the present invention are provided by way of specific examples, and other advantages and effects of the present invention will be readily apparent to those skilled in the art from the disclosure herein. The invention is capable of other and different embodiments and of being practiced or of being carried out in various ways, and its several details are capable of modification in various respects, all without departing from the spirit and scope of the present invention. It is to be noted that the features in the following embodiments and examples may be combined with each other without conflict.
It should be noted that the drawings provided in the following embodiments are only for illustrating the basic idea of the present invention, and the drawings only show the components related to the present invention rather than being drawn according to the number, shape and size of the components in actual implementation, and the type, quantity and proportion of each component in actual implementation may be changed arbitrarily, and the layout of the components may be more complicated.
Some exemplary embodiments of the invention have been described for illustrative purposes, and it is to be understood that the invention may be practiced otherwise than as specifically described.
In order to achieve the above object, the present invention provides a method for controlling MTPA based on a permanent magnet synchronous motor, as shown in fig. 1 and 3, including:
s1, obtaining the direct axis inductance L according to the model reference self-adaptive system d And a stator resistance R;
due to the parameter L in the torque equation after the injection of the virtual high-frequency signal d And R will vary with temperature and magnetic saturation, affecting control system accuracy, so L is selected d And R two parameters are identified.
The model reference adaptive method is to adjust the parameters of the adjustable model and to make the model gradually converge to the actual parameters in the reference model through the pre-designed adaptive law. In comparison, the model reference adaptive algorithm is simple in principle, accurate in identification and capable of fast convergence.
In this embodiment, in the model reference adaptive system, the input quantity u ═ u is input d u q ] T The output of the reference model is y ═ i d i q ] T Adjusting the output of the model
Figure BDA0003738223210000041
Error in output
Figure BDA0003738223210000042
The reference model of the model reference adaptive system is as follows:
Figure BDA0003738223210000043
wherein:
Figure BDA0003738223210000044
i. u is stator current and voltage, respectively; l is d 、L q Are respectively stator d-q axis inductors; r is a stator resistor; psi f A permanent magnet flux linkage; ω is the electrical angular velocity.
The adjustable model of the model reference adaptive system is as follows:
Figure BDA0003738223210000045
wherein:
Figure BDA0003738223210000046
m is a gain matrix, and M is a gain matrix,
Figure BDA0003738223210000047
subtracting the adjustable model from the reference model to obtain an error equation of the model reference adaptive system, namely a parameter identification model equation is as follows:
Figure BDA0003738223210000048
Figure BDA0003738223210000049
the gain matrix determination method comprises the following steps: and selecting a proper gain matrix to enable each pole of the adjustable model to have a negative real part so as to ensure that the designed identifier has good asymptotic stability and satisfactory dynamic response.
Order to
Figure BDA0003738223210000051
Converting the parameter identification model equation into:
Figure BDA0003738223210000052
the Popov integral inequality is:
Figure BDA0003738223210000053
where γ is a finite normal independent of t for any t ≧ 0.
Mixing L with d R is used as an identification object, and w is substituted into the formula to obtain:
Figure BDA0003738223210000054
equation (3) can be decomposed into two equations as follows:
Figure BDA0003738223210000055
Figure BDA0003738223210000056
due to L d The PI adaptation law of (a) is generally expressed as:
Figure BDA0003738223210000057
firstly, only the adaptive law of direct axis inductance identification is analyzed, and the derivation process of the adaptive law of the stator resistance R is similar. Substitution of formula (6) for formula (4) (. eta.) 1 (0,t 1 ) Can be further decomposed into two sub-inequalities:
Figure BDA0003738223210000058
Figure BDA0003738223210000059
the parameter L can be obtained from the above formula d The PI adaptation law of (PI) is:
Figure BDA00037382232100000510
wherein: k is a radical of 1 、τ 1 Are respectively L d Proportional and integral coefficients of the adaptive law.
Similarly, the self-adaptation law of the stator resistance R obtained by the above calculation is:
Figure BDA0003738223210000061
wherein: k is a radical of 2 、τ 2 Respectively the proportional and integral coefficients of the R adaptive law.
S2, according to the direct axis inductance L d Establishing a torque equation with the stator resistor R;
the torque equation is:
Figure BDA0003738223210000062
wherein, the first and the second end of the pipe are connected with each other,
Figure BDA0003738223210000063
is a quadrature axis inductor, and is characterized in that,
Figure BDA0003738223210000064
is a permanent magnet flux linkage, T e Representing electromagnetic torque, P is the number of pole pairs, i d 、i q ，u d 、u q The d-q axis current and the voltage of the stator are respectively, so that the quadrature axis inductance parameter L can be reduced q Parameter psi of flux linkage with permanent magnet f And stator direct axis inductance L d And stator resistance R is more accurate.
S3, injecting a virtual high-frequency signal to further obtain a current angle of an MTPA working point;
the virtual signal injection method is one of high-frequency signal injection methods, and is mainly characterized in that a torque equation is reconstructed, then a high-frequency signal is injected into a mathematical model of the equation, the first-order partial differential of the torque to a current angle is 0 through closed-loop control, and then an MTPA solution is obtained, so that the jitter and extra loss caused by high-frequency signal injection can be avoided. The method specifically comprises the following steps:
s31, injecting the virtual high-frequency signal delta beta to obtain a torque equation after the virtual high-frequency signal is injected;
Figure BDA0003738223210000065
wherein the content of the first and second substances,
Figure BDA0003738223210000066
wherein Δ β ═ Asin (ω) h t) is a high frequency current angle signal;
Figure BDA0003738223210000067
representing the torque after the high-frequency signal is injected;
Figure BDA0003738223210000068
the stator d-q axis currents after high-frequency signal injection are respectively.
And (3) expanding a torque model containing high-frequency information according to a Taylor formula, namely:
Figure BDA0003738223210000069
s32, the torque equation of the step S31 is compared with sin (omega) h t) are multiplied to obtain:
Figure BDA00037382232100000610
wherein the content of the first and second substances,
Figure BDA00037382232100000611
s33, filtering the high-frequency term through a low-pass filter to obtain a first-order partial derivative of the electromagnetic torque
Figure BDA00037382232100000612
Make it
Figure BDA00037382232100000613
Obtaining the current angle beta of the MTPA working point by integration MTPA 。
S4, obtaining quadrature axis current and direct axis current when the MTPA is operated according to the current angle and the stator current vector of the MTPA working point, wherein the quadrature axis current and the direct axis current are as follows:
i q-MTPA ＝I s sinβ MTPA ；
i d-MTPA ＝I s cosβ MTPA ；
wherein, I s Is stator current vector, i q-MTPA For quadrature axis current, i, during MTPA operation d-MTPA Direct axis current for MTPA operationThe current is properly determined by the electrical angular velocity w r And the given value of the electrical angular velocity is obtained by a rotating speed regulator.
Fig. 2 is a comparison of conventional and improved signal extraction for the present invention. When the existing virtual signal injection method is used for extracting the first-order partial differential signal amplitude of the torque to current angle, a band-pass filter and a low-pass filter are required to be matched, so that time delay is brought, and the response speed is slowed down. The invention utilizes the characteristic of neglecting the band-pass filter, so that the calculation is simpler, and the response speed of the system is improved.
Fig. 4 is a control block diagram of a virtual signal module therein. The method solves the problems that the traditional torque equation ignores parameter change, electromagnetic torque cannot be accurately calculated, and accurate MTPA solution is difficult to obtain, and is based on the stator direct-axis inductance L obtained by identification d The stator resistance R constructs a torque equation with higher precision and utilizes the quadrature axis inductance L q Magnetic linkage psi with permanent magnet f The torque equation is further simplified, and the stator quadrature axis inductance L is omitted q And permanent magnet flux linkage psi f The influence of the method reduces the number of parameters of the model, can carry out accurate electromagnetic torque estimation, and further improves the robustness of the system.
The foregoing embodiments are merely illustrative of the principles and utilities of the present invention and are not intended to limit the invention. Any person skilled in the art can modify or change the above-mentioned embodiments without departing from the spirit and scope of the present invention. Accordingly, it is intended that all equivalent modifications or changes which can be made by those skilled in the art without departing from the spirit and technical spirit of the present invention be covered by the claims of the present invention.

Claims (5)

1. A MTPA control method based on a permanent magnet synchronous motor is characterized by comprising the following steps:
s1, obtaining the direct axis inductance L according to the model reference self-adaptive system d And a stator resistance R;
s2, according to the direct axis inductance L d Establishing a torque equation with the stator resistor R;
s3, injecting a virtual high-frequency signal to further obtain a current angle of an MTPA working point;
and S4, obtaining quadrature axis current and direct axis current when the MTPA operates according to the current angle of the MTPA working point and the stator current vector.
2. The MTPA control method based on the permanent magnet synchronous motor according to claim 1, wherein a reference model of the model reference adaptive system is as follows:
Figure FDA0003738223200000011
wherein:
Figure FDA0003738223200000012
i. u is stator current and voltage, respectively; l is d ，L q Are respectively stator d-q axis inductors; r is a stator resistor; psi f A permanent magnet flux linkage; omega is the electrical angular velocity;
the adjustable model of the model reference adaptive system is as follows:
Figure FDA0003738223200000013
wherein:
Figure FDA0003738223200000014
m is a matrix of gains, and M is a gain matrix,
Figure FDA0003738223200000015
3. the MTPA control method based on the permanent magnet synchronous motor according to claim 2, wherein the torque equation of step S2 is:
Figure FDA0003738223200000016
wherein, the first and the second end of the pipe are connected with each other,
Figure FDA0003738223200000017
is a quadrature axis inductor, and is characterized in that,
Figure FDA0003738223200000018
is a permanent magnet flux linkage, T e Representing electromagnetic torque, P being the number of pole pairs, i d 、i q ，u d 、u q Stator d-q axis currents and voltages, respectively.
4. The MTPA control method based on the permanent magnet synchronous motor according to claim 3, wherein the step S3 includes:
s31, injecting the virtual high-frequency signal delta beta to obtain a torque equation after the virtual high-frequency signal is injected;
s32, the torque equation of the step S31 is combined with sin (omega) h t) multiplication;
s33, filtering the high-frequency term through a low-pass filter to obtain a first-order partial derivative of the electromagnetic torque
Figure FDA0003738223200000019
And adjusting the first partial derivative
Figure FDA0003738223200000021
The current angle of the MTPA operating point is obtained by integration.
5. The MTPA control method based on the permanent magnet synchronous motor according to claim 4, wherein a torque equation after the virtual high-frequency signal injection is as follows:
Figure FDA0003738223200000022
wherein Δ β ═ Asin (ω) h t) is a high-frequency current angle signal;
Figure FDA0003738223200000023
representing the torque after the injection of the high-frequency signal;
Figure FDA0003738223200000024
the d-q axis currents of the stator after high-frequency signal injection are respectively.
CN202210853521.6A 2022-07-09 2022-07-09 MTPA control method based on permanent magnet synchronous motor Pending CN115085608A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202210853521.6A CN115085608A (en) 2022-07-09 2022-07-09 MTPA control method based on permanent magnet synchronous motor

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202210853521.6A CN115085608A (en) 2022-07-09 2022-07-09 MTPA control method based on permanent magnet synchronous motor

Publications (1)

Publication Number Publication Date
CN115085608A true CN115085608A (en) 2022-09-20

Family

ID=83259139

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202210853521.6A Pending CN115085608A (en) 2022-07-09 2022-07-09 MTPA control method based on permanent magnet synchronous motor

Country Status (1)

Country Link
CN (1) CN115085608A (en)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN117040339A (en) * 2023-10-09 2023-11-10 潍柴动力股份有限公司 Vector decoupling method, device and equipment for permanent magnet synchronous motor and storage medium

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN117040339A (en) * 2023-10-09 2023-11-10 潍柴动力股份有限公司 Vector decoupling method, device and equipment for permanent magnet synchronous motor and storage medium
CN117040339B (en) * 2023-10-09 2024-01-16 潍柴动力股份有限公司 Vector decoupling method, device and equipment for permanent magnet synchronous motor and storage medium

Similar Documents

Publication Publication Date Title
CN110429889B (en) Amplitude-adjustable square wave injection maximum torque current ratio motor control method
CN107577149B (en) Follow-up control method adopting fractional order fast terminal sliding mode control
CN112468035B (en) Method for selecting full-speed-domain optimal-efficiency control magnetization state of adjustable-flux permanent magnet synchronous motor and online control method
CN111342728A (en) Permanent magnet synchronous motor parameter identification method based on variable step size NLMS algorithm
CN111711396A (en) Method for setting control parameters of speed ring of permanent magnet synchronous motor based on fractional order sliding mode controller
CN115085608A (en) MTPA control method based on permanent magnet synchronous motor
Huynh et al. On-line parameter estimation of an induction machine using a recursive least-squares algorithm with multiple time-varying forgetting factors
CN114726278A (en) Permanent magnet synchronous motor self-adaptive control method based on mechanical parameter identification
KR101815858B1 (en) Simulation method of synchronous generator system for ships
CN111313773A (en) Permanent magnet synchronous motor parameter identification method based on variable step length LMS algorithm
WO2022252369A1 (en) Method, apparatus and device for controlling three-phase permanent magnet synchronous electric motor, and medium
Hu et al. Dynamic loss minimization control of linear induction machine
CN107181437B (en) Excitation control method for synchronous generator
CN115102444B (en) Permanent magnet synchronous motor self-adaptive integral sliding mode prediction control method
Matsuki et al. High‐Response Torque Control of IPMSM Based on a New Coordinate System Suitable for Voltage Amplitude and Phase Control
Chen et al. Simulation of surface mounted PMSM Vector Control Based on Fuzzy PI control
CN113852309B (en) Robot joint motor parameter identification and control parameter self-tuning method
CN115276494A (en) Decoupling control method, device, equipment and storage medium for permanent magnet synchronous motor
CN116599399A (en) Permanent magnet synchronous motor control method and permanent magnet synchronous motor
CN109039194B (en) Method for tracking and controlling rotating speed of permanent magnet synchronous motor
CN109905063B (en) MTPA method for injecting virtual signals of multi-stage starting/power generator
CN110380656B (en) Permanent magnet synchronous motor position sensorless control method based on simplified MRAS method
CN112468032A (en) Full-speed domain efficiency MAP graph generation method of permanent magnet synchronous motor
CN105469318A (en) Parameter identification algorithm for circulating pump motor of direct-current power transmission valve cooling system
Shaowei et al. Identify PMSM's parameters by single-layer neural networks with gradient descent

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination