CN115037330A - anti-Doppler transmission method, transmission device and terminal - Google Patents
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Abstract
The invention discloses an anti-Doppler sending method, a sending device and a terminal, wherein the anti-Doppler sending method comprises the following steps: setting an initial frequency set of the linear frequency modulation signals; coding and converting data to be transmitted into a bit sequence; grouping the bit sequences according to the size of the initial frequency set to obtain one or more bit sequence groups, wherein the length of each bit sequence group is the same; mapping each bit sequence into a linear frequency modulation signal corresponding to a different initial frequency in an initial frequency set in a grouping manner; the chirp signal is transmitted over radio frequency. According to the scheme of the invention, when the linear frequency modulation signal is used for transmitting the bit data, the initial frequency set is set, and the interval of the initial frequency between different signals is increased, so that the frequency interval between effective frequency points is increased, the influence caused by Doppler drift is reduced, and the Doppler drift resistance is improved.
Description
Technical Field
The present invention relates to the field of communications, and in particular, to an anti-doppler transmission method, a transmission apparatus, and a terminal.
Background
Chirp modulation (LFM) is a spread spectrum modulation technique that does not require a pseudo-random code sequence. Chirp signals are also known as Chirp Spread Spectrum (CSS) signals because their spectral bandwidth falls within the audible range and sounds like a bird. The LFM technology is widely used in radar and sonar technologies, for example, in radar positioning technology, it can be used to increase the radio frequency pulse width, increase the communication distance, and increase the average transmission power, while maintaining sufficient signal spectrum width without reducing the range resolution of radar.
With the rapid development of space technology, space communication carriers (rockets, satellites, spacecraft, and the like) have been expanded from near-earth space to deep space. Their flight distances are getting longer and faster, and the flight speeds are also getting faster and faster. In addition, when the communication carrier moves at a high speed, especially under the condition of large acceleration, the carrier frequency of the signal generates high dynamic Doppler frequency offset, so that the received signal is asynchronous, and the error rate is generated.
Disclosure of Invention
The invention provides an anti-Doppler transmission method, an anti-Doppler transmission device and an anti-Doppler terminal, and aims to solve the problem of Doppler frequency offset generated between a sender and a receiver which are communicated with each other under a high dynamic condition. The technical scheme is as follows:
in one aspect, the present invention provides an anti-doppler transmission method, including the following steps:
s101: setting an initial frequency set of the linear frequency modulation signals;
s102: coding and converting data to be transmitted into a bit sequence;
s103: grouping the bit sequences according to the size of the initial frequency set to obtain one or more bit sequence groups, wherein the length of each bit sequence group is the same;
s104: mapping each bit sequence into a different linear frequency modulation signal in a grouping way, wherein the initial frequencies corresponding to the linear frequency modulation signals are different;
s105: the chirp signal is transmitted over radio frequency.
Further, step S101 includes the steps of:
s1011: setting a linear frequency modulation signal;
s1012: calculating an initial frequency set of the linear frequency modulation signals;
the chirp signal is as follows:
wherein B is a signalBandwidth, T s For the duration of a single chirp signal,
at the moment of frequency turnover, f 0 ∈[-B/2，B/2]The time-bandwidth product of the chirp signal is BT for the initial frequency of the chirp signal s ＝N；
The calculation method of the initial frequency set in step S1012 is:
wherein
For settable variables, an initial set of frequencies F t The number of elements in is
At most, the chirp signal
Seed bit sequence grouping.
Further, step S103 includes:
the length p of the bit sequence packet is determined by:
Further, step S103 further includes:
for a length k (k) to be transmitted>0) Bit sequence B of t ＝[d 1 d 2 ...d k ]When k ≠ p, in the bit sequence B t Bit stuffing is performed on the last bit, and the number of the stuffed bits is:
the padded bit values are all 0 or all 1, and the padded bit sequence B' t The length is k ' ═ k + Δ k, and the padded bit sequence B ' is formed ' t Is divided into
Grouping bit sequences
Each bit sequence grouping
Containing p bits.
Further, step S104 includes:
determining bit sequence grouping by mapping relation
And parameter K i In which the parameter K i Is an initial set of frequencies F t Parameter K corresponding to i The mapping relation is
Further, step S105 includes: sequentially using the linear frequency modulation signals corresponding to the g bit sequence groups as transmission signals, wherein the set of the linear frequency modulation signals is
Wherein the content of the first and second substances,
representing an initial frequency of
The frequency of the linear frequency-modulated signal of (a),
i is 1,2,3, …, g, t is n/B is a digital sampling point, n is an integer, and n is>＝0。
Further, step S105 includes:
in transmitting a set of chirp signals x t (n) before, combining the chirp signal x t And (n) performing DA conversion or up-conversion, and finally transmitting through an antenna.
In another aspect, the present invention provides an anti-doppler transmission apparatus including: the device comprises a frequency generation module, a grouping mapping module and a sending module;
the frequency generation module calculates according to the available linear frequency modulation signals to obtain an initial frequency set of the linear frequency modulation signals;
the grouping module encodes communication data to be transmitted, converts the communication data into bit sequences, and groups the bit sequences according to the size of the initial frequency set to obtain one or more bit sequence groups, wherein the length of each bit sequence group is the same;
the grouping mapping module is used for grouping and mapping each bit sequence into a linear frequency modulation signal corresponding to different initial frequencies in an initial frequency set;
and the sending module sends the linear frequency modulation signals processed by the grouping mapping module through radio frequency.
Further, the initial frequency set is calculated in the following manner:
wherein
For settable variables, an initial set of frequencies F t The number of elements in is
At most, the chirp signal can represent
Seed bit sequence grouping.
In another aspect, the present invention provides an anti-doppler terminal including the above anti-doppler transmission device.
The invention has the beneficial effects that: by using the scheme of the invention, before the linear frequency modulation signal is used for transmitting the bit data, the initial frequency set of the linear frequency modulation signal is set, and the interval of the initial frequency between different signals is increased, so that the frequency interval between effective frequency points is increased, the influence caused by Doppler drift is reduced, and the Doppler drift resistance is improved.
Drawings
FIG. 1 is a flow chart of an embodiment of an anti-Doppler transmission method according to the invention;
FIG. 2 is a sub-flow diagram of a method of transmitting anti-Doppler in FIG. 1;
FIG. 3 is a real waveform of an embodiment of a chirp signal of the present invention;
FIG. 4 is a diagram of an imaginary waveform of an embodiment of a chirp signal of the present invention;
FIG. 5 is a flowchart illustrating an exemplary embodiment of a receiving method according to the present invention;
FIG. 6 is a schematic structural diagram of an embodiment of an anti-Doppler transmission apparatus according to the invention;
FIG. 7 is a schematic structural diagram of a receiving device according to an embodiment of the present invention;
FIG. 8 is a schematic diagram of an embodiment of the frequency detection module shown in FIG. 7;
FIG. 9 is a graph illustrating the performance of the anti-Doppler improvement according to an embodiment of the present invention.
Detailed Description
In order to facilitate an understanding of the invention, the invention is described in more detail below with reference to the accompanying drawings and specific examples. Preferred embodiments of the present invention are shown in the drawings. This invention may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete.
It is to be noted that, unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this invention belongs. The terminology used in the description of the invention herein is for the purpose of describing particular embodiments only and is not intended to be limiting of the invention.
Example one
In one aspect, as shown in fig. 1, the present invention provides an anti-doppler transmission method capable of using communication data to be transmitted through a selected initial frequency f 0 And modulating the corresponding linear frequency modulation signal and sending out. The key point of the invention is the calculation of the initial frequency set, and when the corresponding initial frequency is selected, the performance of resisting the Doppler frequency offset is improved by setting the interval size between the initial frequencies, so that the reliability of the communication resisting the high-dynamic Doppler frequency offset can be effectively improved by utilizing the initial frequency set setting of the invention.
The anti-Doppler transmission method comprises the following steps:
s101: setting an initial frequency set of the linear frequency modulation signals;
s102: coding and converting data to be transmitted into a bit sequence;
s103: grouping the bit sequences according to the size of the initial frequency set to obtain one or more bit sequence groups, wherein the length of each bit sequence group is the same;
s104: mapping each bit sequence into a linear frequency modulation signal corresponding to a different initial frequency in the initial frequency set in a grouping manner;
s105: and transmitting the linear frequency modulation signal through radio frequency.
Further, for step S101, the following steps are also included:
s1011: setting a linear frequency modulation signal;
s1012: calculating an initial frequency set of the linear frequency modulation signals;
specifically, for step S1011, at the transmitting end, since the modulation is performed by using different offset sequences of the chirp signal to represent the bit sequence packets to be modulated, an available chirp signal can be set as follows:
wherein B represents the signal bandwidth, T s Representing the duration of a single chirp signal,
is the frequency turnover time, f 0 ∈[-B/2，B/2]Is the initial frequency of the chirp signal, with different information bit sequence groupings corresponding to different f 0 . The time-bandwidth product of the chirp signal is BT s ＝N。
Fig. 3 is a real part waveform diagram of an embodiment of the chirp signal, and fig. 4 is an imaginary part waveform diagram of an embodiment of the chirp signal. It can be seen from the figure that when the time of 0.125ms is reached, frequency folding is performed, and t in this embodiment is f ＝0.125。
Specifically, for example, for the above-mentioned chirp signal, the values of the parameters may be: b1 MHz, Ts 0.512ms, then passes BT s N-512, initial frequency f can be calculated 0 ∈[-0.5，0.5]；
If the initial frequency f is selected 0 0.5MHz, the corresponding frequency turnover time t f ＝0.5*0.512ms＝0.256ms；
If the initial frequency f is selected 0 0.25MHz, the corresponding frequency turnover time t f ＝0.75*0.512ms＝0.384ms。
Specifically, for step S1012, when selecting the corresponding initial frequency, the performance of resisting the doppler frequency offset may be improved by setting the size of the interval between the initial frequencies, and the initial frequency set F of the chirp signal is calculated by the present invention t The method of (1) is as follows:
wherein
For a settable variable, which can be set to 0 in general, an initial set of frequencies F t The number of the start frequencies in (1) is
Can therefore represent at most
Seed bit sequence grouping.
In particular, for each parameter value of the chirp signal in the above embodiment, the initial frequency set F of the available chirp signal may be set t The parameters in (1) are set as: s4, N512, B1 MHz, f r 0, can thereby yield
The initial frequency set F t A size of
Therefore, a maximum of 128 bit sequence packets can be represented.
Initial frequency f set in this manner 0 The physical meaning is to increase the initial frequency f between different signals 0 S > - < 2, reduces the partial data transmission rate, increasesResistance to doppler shift.
Further, for step S102, the following steps are included:
firstly, judging whether communication data need to be transmitted, if so, coding and converting the communication data to be transmitted into a bit sequence, wherein the bit sequence comprises different information bits, and the form is specifically represented as 1001. The encoding process may include increasing scrambling codes, encoding, and the like, and preferably uses scrambling codes and encoding methods with lower algorithm complexity.
Further, for step S103, the following steps are included:
in order to achieve maximum spectral efficiency, it is necessary to make maximum use of the frequency resources in the initial frequency set. Specifically, bit sequences to be transmitted are grouped to obtain one or more bit sequence groups, and the bit sequence groups are modulated into corresponding chirp signals to be transmitted. The length of each bit sequence group is set by calculation, so that the length of each bit sequence group is equal, and all the initial frequencies in one initial frequency set can be used up.
Specifically, assume that a bit sequence packet of length p is transmitted as:
wherein, c j Is represented by c 1 -c p Any one of which takes the value 0 or 1;
further, the size of p is set as:
further, to achieve maximum spectral efficiency, one may generally make
To an integer power of 2. For example, in the above embodiment, if the initial frequency set size is 128, then p is log 2 128＝7。
This is because the integral power of 2 is discrete data, and the length p of a bit sequence packet is an integer and cannot be a decimal number, so the maximum number of bit sequence packets that can be expressed when the initial frequency set size is large is
And when the power is not an integral power of 2, frequency resources are wasted. And correspondingly, the pitch at the time of detection becomes smaller, and the performance becomes worse.
In particular, for a bit sequence B of length k (k > 0) to be transmitted t ＝[d 1 d 2 …d k ]，d 1 -d k Any one of the values is 0 or 1, and B is to be added t The packet is a packet containing g (g is a positive integer) bit sequences of equal length and equal length to p
Bit stuffing issues are involved. This is because the bit sequence B t Cannot be exactly equal to a bit sequence packet each time
Is an integer multiple of p, so that when k is not an integer multiple of p, it is necessary to perform bit sequence B t Bit filling is carried out on the last bit, and the number of the filled bits is
In particular, due to the bit sequence B t The bit value of the last-bit padding does not affect the data transmission, and thus all 0 s or all 1 s, for example, 0.. 0 or 1.. 1 s, may be padded arbitrarily. Let us assume post-padding bit sequence B' t The length becomes k ' ═ k + Δ k, then the padded bit sequence B ' can be applied ' t Is divided into
Grouping bit sequences
Each bit sequence grouping
Contains p bits of
c j ＝0，1。
The following provides an example of three padding bits, taking the bit sequence packet length p as an example 7:
for example, for a bit sequence 101001 with k-6, the number of bits padded at its end is
The filling value is 0 or 1, thereby obtaining
The bit sequences are grouped. The bit sequence is grouped into 1010010 when the padding value is 0 and 1010011 when the padding value is 1.
For another example, for a bit sequence 10100101 with k equal to 8, the number of bits padded at its end bit is
The filling value is 000000 or 111111, thereby obtaining
The bit sequences are grouped. When the padding value is 000000, the resulting bit sequence is grouped 1010010, 1000000, and when the padding value is 111111, the resulting bit sequence is grouped 1010010, 1111111.
As another example, for a bit sequence 101.. 10 with k 800, the number of bits padded at its end bit is
The filling value is 00000 or 11111, thereby obtaining
The bit sequences are grouped. Specifically, 101.. 1000000 or 101.. 1011111 is divided into 115 bit sequences of length 7 in sequence, and when the padding value is 00000, the 115 th bit sequence is divided into 1000000, and when the padding value is 11111, the 115 th bit sequence is divided into 1011111.
Further, for step S104, the following steps are also included:
at the transmitting end, the bit sequence packet to be modulated is determined by a given mapping relation A
And parameter K i In a one-to-one correspondence of, wherein K i Is a different value of the corresponding parameter K in the initial frequency set of the transmitted chirp signal, as follows:
correspondingly, there is an inverse function of the mapping relation A, according to which the bit sequence grouping is solved at the receiving end
The process of (1). In order to increase reliability, encoding and scrambling can be performed during mapping, and correspondingly, decoding and descrambling processes are performed at a receiving end.
Further, according to the above-mentioned calculation method of the initial frequency set, once the parameter K is uniquely determined, each initial frequency f 0 Corresponding to a determined value of the parameter K, and thus the initial frequency f 0 Will also be uniquely determined.
Specifically, g bit sequence groups are obtained after grouping the bit sequences
Each bit sequence grouping
The number of groups is p, is:
c j ＝0，1。
correspondingly, K i The calculation method of (d) may be:
K i ＝2 0 c 1 +2 1 c 2 +…+2 p-1 c p ，
this way, the bit sequence can be uniquely grouped
Mapping to the K i Initial frequency f corresponding to value i Thereby using the f i Corresponding chirp signal as a transmission signal for modulating the bit sequence packet
In addition, K i The calculation method of (3) is not limited to the above method, as long as a unique correspondence is established, and for example, the method may further include: k i ＝2 0 c p +2 1 c p-1 +…+2 p-1 c 1 。
Repeating the mapping process, and finally, sequentially using the chirp signals corresponding to the g bit sequence groups as transmission signals, as follows:
wherein the content of the first and second substances,
representing an initial frequency of
Of the chirp signal, K i ＝A(b i ) I 1,2,3, …, g, t n/B are numerical sampling points, n is an integer, and n is>＝0。
Further, for step S105, the method further includes:
grouping g bit sequences and obtaining a linear frequency modulation signal set x through mapping t (n) undergoes necessary operations such as DA conversion, up-conversion, etc., and is finally transmitted through an antenna. DA conversion refers to digital-to-analog conversion, which converts a digital signal into an analog signal. In high-frequency electronic circuits, it is often necessary to linearly shift the frequency spectrum of a signal, that is, the frequency spectrum structure is not changed, the relative amplitude of each frequency component is not changed, and the frequency components are not increased or decreased, but are only moved in parallel on the frequency axis. Up-conversion is a conversion of the input signal frequency to a higher frequency, and this spectrum shift is not only beneficial to improve the performance of the device, but also can be adapted to many application systems, such as broadcasting systems, television systems, mobile communication systems, etc.
Example two
On the other hand, the invention provides an anti-doppler receiving method, which can receive and acquire a chirp signal, acquire an initial frequency corresponding to the chirp signal through iterative frequency compensation, acquire a bit sequence packet carried by the chirp signal through demodulation and decoding, and finally acquire accurate communication data. The anti-Doppler receiving method can effectively improve the performance of resisting high dynamic Doppler frequency offset, thereby improving the communication reliability.
Referring to fig. 5, the above-mentioned anti-doppler receiving method includes the following steps:
s201: receiving a signal, and sampling the signal to obtain a linear frequency modulation signal;
s202: finishing initial frequency offset estimation and initial timing of the linear frequency modulation signal through a leader sequence, and setting an initial value of a frequency compensation factor;
s203: performing frequency compensation on the linear frequency modulation signal according to the frequency compensation factor;
s204: detecting an initial frequency of the chirp signal;
s205: demodulating a bit sequence group corresponding to the linear frequency modulation signal according to the initial frequency;
s206: adjusting the frequency compensation factor according to the initial frequency;
s207: judging whether a linear frequency modulation signal needing to be demodulated exists, if so, executing the steps S203 to S206 again, and if not, executing the next step S208;
s208: and decoding the bit sequence packet.
Specifically, for steps S203 to S207, the frequency detection and frequency compensation are performed on the chirp signal according to a single chirp signal duration Ts, each Ts time only includes one chirp signal, and a frequency compensation factor for the next Ts time is correspondingly adjusted after the initial frequency is compensated, so that all chirp signals are traversed all the time in a circulating manner.
Further, for step S201, at the receiving end, the signal is received and sampled, and the received signal is nyquist sampled to obtain a chirp signal, where the chirp signal is as follows:
where h (n) is channel gain, f d (n) represents a doppler frequency shift,
representing phase change during transmission, w (n) representing receiver noise, x t (n) is the original chirp signal and B represents the signal bandwidth.
Further, as for step S202, there are various ways to obtain the initial frequency offset at the receiving end, for example, the initial frequency offset estimation and the initial timing can be completed through the preamble sequence, and the sampling start time is considered to be equal to the initial arrival time, and the duration T is used s As the sampling interval of the Nyquist sampling, then the ith T s The signals received in the cycle are as follows:
wherein f is d ' (n) denotes residual frequency offset corrected by initial frequency offset estimation, w i (n) represents the receiver noise and,
indicating the phase.
Further, an initial value of a frequency compensation factor for performing frequency compensation on the chirp signal sampled in the next sampling interval time may be set according to circumstances. The initial value may be set to 0 or adjusted according to a specific communication environment, for example, according to a traveling speed or acceleration of the communication terminal or the like.
Further, for step S203, due to Doppler f d ' (n) varies with time, and it is necessary to perform doppler tracking on the received signal to cope with erroneous detection due to doppler shift, and therefore the present invention performs doppler tracking using a tracking loop. During the detection process, the duration T of a single chirp signal is used s Detection is performed for the smallest unit. Firstly, the received ith duration is T s Is frequency compensated, expressed as
Wherein the content of the first and second substances,
for a first single chirp duration T, as a frequency compensation factor s Internal signal, frequency compensation factor of the signal
Set as an initial value of the frequency compensation factor set in step S202, e.g.
For the subsequent ith (i > 1) individual chirp duration T s Internal signal, frequency compensation factor of the signal
Will be set in a subsequent step.
Further, for step S204, with a single chirp duration T s Detecting the initial frequency of the chirp signal for an interval, comprising:
the calculation expression of the initial frequency specifically refers to the initial frequency set in the first embodiment, and is not described herein again.
Further, for the detection of the initial frequency, the initial frequency is obtained by estimating the value of the parameter K in the calculation expression in which the initial frequency is combined with the initial frequency set, because according to the scheme described in the first embodiment, the initial frequency can be uniquely determined by the parameter K, and therefore, obtaining the value of the parameter K is equivalent to obtaining the initial frequency of the chirp signal, and the description of the relation expression between the parameter K and the initial frequency is omitted here for reference to the first embodiment.
In particular, an estimate K of the parameter K i * As follows:
wherein for n i * The following calculation method is adopted:
wherein n is i * The physical meaning of the estimated expression of (a) is a number making the FFT point a maximum value;
K i * the physical meaning of the estimation expression is the result of rounding the serial number with the FFT point as the maximum value;
x l (n) is a native sequence, as follows:
the parameters in the above expression may specifically refer to the detailed description of the chirp signal and the initial frequency set in the first embodiment, and are not described herein again.
Further, for step S205, the following is included:
due to the fact that
The initial frequency can be uniquely determined and the bit sequence packet is mapped to the parameter K correspondingly at the transmitting end i In relation to (2)
Thus, according to the above
The duration may be reverse mapped to T s Is uniquely grouped into a corresponding bit sequence as follows:
wherein A is -1 Is the inverse mapping of A. Thus it is based on
A complete bit sequence packet after frequency compensation is obtained
Further, for step S206, the following is included:
since n is i * And
also in a one-to-one correspondence, which can be based on n i * To update the next frequency compensation factor
The values of (a) are as follows:
specifically, G is an adjustment strategy function with an argument of n i * And
the result is used to update the next frequency compensation factor
And will update the frequency compensation factor
For the next duration of T s Frequency compensation of the signal of (2).
Specifically, the adjustment policy function G may be as follows:
wherein, 0 is more than delta f',
for adjustable parameters,% represents the remainder operation.
Note that this is only one embodiment, and the present invention is not limited to the specific implementation of the adjustment policy function G.
In addition, parameter S/2 is also an adjustable parameter.
Further, for step S207, the following is included:
at the receiving end, each duration is T s After receiving the signal, judging whether a signal needs to be demodulated; when there are more signals to demodulate, steps S203 to S206 are repeated to ensure that all signals can be frequency compensated and demodulated into bit sequence packets. After all the signals are received, the next step S208 may be performed, and the obtained bit sequence packet is decoded, and finally, communication data is obtained.
EXAMPLE III
In order to more intuitively explain the anti-doppler transmission method and the anti-doppler reception method of the present invention, the following is a practical example:
the system bandwidth is B-1 MHz, and the duration of single linear frequency modulation signal is T s When the time bandwidth product is 0.512ms, the time bandwidth product is 512. When S is 4, the initial frequency set size of the available chirp signal is 512/4-128. Suppose f r 0, then the initial set of frequencies is as follows:
thus p is 7. Assuming that 800 bits are to be transmitted, where the 800 bits can be generated by scrambling and interleaving original communication data, 5 bits are to be padded, and the padded information bits are to be transmittedThe sequence is divided into 115 packets of g 805/7, each packet containing 7 bits. Meanwhile, the function a is a value obtained by converting every 7 bits into a 10-system number as K, that is, K is 2 0 b 1 +2 1 b 2 +…+2 p-1 b 7 . The g bit sequence packets correspond to the chirp signals which are sequentially used as transmission signals, as follows:
at the receiving end, the signal is sampled and the compensated signal is detected, K i The estimated value of (c) can be expressed as:
wherein n is i * The following calculation method is adopted:
wherein, the local sequence x l (n) is represented by
The inverse of function a is:
thus, it can be estimated
the frequency compensation factor, denoted as
Namely:
further, referring to fig. 9, as shown in the figure, a packet loss rate curve of the present embodiment in a large doppler scenario is shown, wherein the packet length is 100 bytes. As can be seen from the figure, the anti-doppler performance is excellent, and substantially coincides with the case of no doppler frequency offset.
Example four
In another aspect, referring to fig. 6, the present invention provides an anti-doppler transmitting apparatus, including: a frequency generation module 301, a grouping module 302, a grouping mapping module 303 and a sending module 304.
The anti-doppler transmitting apparatus can implement the anti-doppler transmitting method according to the first embodiment, and transmit the communication data to be transmitted to the anti-doppler receiving apparatus for communication by modulating the communication data with the chirp signal corresponding to the selected initial frequency.
When transmitting bit data by using a chirp signal, the frequency generation module 301 sets an initial frequency set, and increases the interval of initial frequencies between different signals, thereby increasing the doppler shift resistance.
Specifically, the frequency generation module 301 performs calculation according to the available chirp signals to obtain an initial frequency set of the chirp signals.
The grouping module 302 encodes the communication data to be transmitted, converts the encoded communication data into bit sequences, and groups the bit sequences according to the size of the initial frequency set to obtain one or more bit sequence groups, so that the length of each bit sequence group is the same, and the number of the bit sequence groups can just use up the initial frequency set when mapping subsequent groups.
The block mapping module 303 maps each bit sequence block to a chirp signal corresponding to a different initial frequency in the set of initial frequencies.
The transmitting module 304 transmits the chirp signal processed by the packet mapping module 303 through radio frequency.
For the specific flow related to the anti-doppler transmission method related to each module, please refer to the foregoing embodiment of the anti-doppler transmission method, which is not described herein again.
EXAMPLE five
In another aspect, referring to fig. 7 and 8, the invention provides an anti-doppler receiving apparatus, which is capable of implementing the anti-doppler receiving method according to the second embodiment, receiving and acquiring a chirp signal, acquiring an initial frequency corresponding to the chirp signal through frequency compensation, and acquiring a bit sequence packet carried by the chirp signal through demodulation and decoding, so as to finally acquire accurate communication data.
Preferably, the anti-doppler receiving apparatus includes: a receiving module 401, a frequency detecting module 402, a packet reflection module 403 and a decoding module 404.
The receiving module 401 receives a signal and samples the signal to obtain a chirp signal.
The frequency detection module 402 performs initial frequency detection on the chirp signal, which further includes performing frequency compensation on the initial frequency.
The packet demapping module 403 performs demapping on the chirp signal to obtain a bit sequence packet carried by the chirp signal.
The decoding module 404 performs unified decoding on all the obtained bit sequence packets in sequence to obtain final communication data.
Each chirp signal has a duration Ts, and in this time period, the frequency detection module 402 and the packet reflection module 403 cooperate with each other, and each time a chirp signal is received, it is determined whether there is a next chirp signal to be demodulated; when there is any chirp signal to be demodulated, the frequency detection module 402 and the packet reflection module 403 continue to operate, for example, detect the initial frequency corresponding to the current chirp signal, and perform packet reflection to obtain a bit sequence packet, thereby ensuring that all signals can be frequency compensated and demodulated into a bit sequence packet.
Preferably, the frequency detection module 402 includes: initial frequency offset estimation section 4021, frequency compensation section 4022, initial frequency calculation section 4023, and frequency compensation factor generation section 4024.
The initial frequency offset estimation unit 4021 completes initial frequency offset estimation and initial timing of the chirp signal through the preamble sequence, and sets an initial value of the frequency compensation factor.
The frequency compensation unit 4022 performs frequency compensation on the chirp signal based on the frequency compensation factor.
The initial frequency calculation unit 4023 detects an initial frequency of the chirp signal.
The frequency compensation factor generating unit 4024 adjusts the frequency compensation factor according to the initial frequency.
For the specific flow related to the anti-doppler receiving method related to each module, please refer to the foregoing anti-doppler receiving method embodiment, which is not described herein again.
Example six
In another aspect, the present invention provides an anti-doppler terminal including the anti-doppler transmitting apparatus according to the fourth embodiment and/or the anti-doppler receiving apparatus according to the fifth embodiment, and two anti-doppler terminals can perform anti-doppler mobile communication by using the anti-doppler transmitting method according to the first embodiment and the anti-doppler receiving method according to the second embodiment.
The above description is only for the specific embodiments of the present invention, but the scope of the present invention is not limited thereto, and any person skilled in the art can easily think of the changes or substitutions within the technical scope of the present invention, and shall cover the scope of the present invention. Therefore, the protection scope of the present invention shall be subject to the protection scope of the appended claims.
By the embodiment of the invention, the Doppler shift can be obviously improved, and the communication reliability under a high-dynamic Doppler scene is improved, particularly referring to a performance change diagram of an attached drawing.
Claims (10)
1. An anti-doppler transmission method, comprising:
s101: setting an initial frequency set of the linear frequency modulation signals;
s102: coding and converting data to be transmitted into a bit sequence;
s103: grouping the bit sequences according to the size of the initial frequency set to obtain one or more bit sequence groups, wherein the length of each bit sequence group is the same;
s104: mapping each bit sequence into a different linear frequency modulation signal in a grouping way, wherein the corresponding initial frequencies of the linear frequency modulation signals are different;
s105: and transmitting the linear frequency modulation signal through radio frequency.
2. The doppler-resistant transmission method according to claim 1, wherein the step S101 comprises the steps of:
s1011: setting the linear frequency modulation signal;
s1012: calculating an initial frequency set of the chirp signals;
the chirp signal is as follows:
where B is the signal bandwidth, T s For the duration of a single chirp signal,
is the frequency turnover time, f 0 ∈[-B/2，B/2]Is the initial frequency of a chirp signal having a time-bandwidth product of BT s ＝N；
The calculation method of the initial frequency set in step S1012 is as follows:
wherein
The initial set of frequencies F being a settable variable t The number of elements in is
At most, the chirp signal represents
Seed bit sequence grouping.
3. The doppler-resistant transmission method according to claim 2, wherein step S103 comprises:
the length p of the bit sequence packet is determined by:
4. The doppler-resistant transmitting method according to claim 3, wherein the step S103 further comprises:
for a bit sequence B of length k (k > 0) to be transmitted t ＝[d 1 d 2 ...d k ]When k ≠ p, in the bit sequence B t Bit stuffing is performed on the last bit, and the number of the stuffed bits is:
the padded bit value is all 0 or all 1, and the padded bit sequence B' t A length of k ═ k + Δ k, and the padded bit sequence B' t Is divided into
A bit sequence is grouped
Each of the bit sequence packets
Containing p bits.
5. The anti-doppler transmission method according to claim 4, wherein the step S104 comprises:
determining the bit sequence grouping by mapping relation
And parameter K i In which the parameter K i Is said initial set of frequencies F t Parameter K corresponding to i The mapping relation is
6. The method of claim 5, wherein step S105 comprises: sequentially using the chirp signals corresponding to the g bit sequence groups as transmission signals, wherein the set of the chirp signals is
Wherein the content of the first and second substances,
representing an initial frequency of
The frequency of the chirp signal of (a) is,
t is a digital sampling point, n is an integer, and n is 0.
7. The doppler-resistant transmission method according to claim 6, wherein the step S105 comprises:
in transmitting a set of chirp signals x t (n) prior to, combining said chirp signal x t And (n) performing DA conversion or up-conversion, and finally transmitting through an antenna.
8. An anti-doppler transmission apparatus, comprising: the device comprises a frequency generation module, a grouping mapping module and a sending module;
the frequency generation module calculates according to available linear frequency modulation signals to obtain an initial frequency set of the linear frequency modulation signals;
the grouping module encodes communication data to be transmitted, converts the communication data into bit sequences, and groups the bit sequences according to the size of the initial frequency set to obtain one or more bit sequence groups, wherein the length of each bit sequence group is the same;
the grouping mapping module is used for grouping and mapping each bit sequence into the chirp signal corresponding to a different initial frequency in the initial frequency set;
and the sending module sends the linear frequency modulation signals processed by the grouping mapping module through radio frequency.
9. The doppler-resistant transmission device according to claim 8, wherein the initial frequency set is calculated by:
wherein
The initial set of frequencies F being a settable variable t The number of elements in is
At most, the chirp signal can represent
Seed bit sequence grouping.
10. An anti-doppler terminal characterized by comprising the anti-doppler transmission apparatus according to claim 8 or 9.
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116112327A (en) * | 2023-02-14 | 2023-05-12 | 南京理工大学 | Communication system based on linear frequency modulation signal |
Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102710580A (en) * | 2012-06-12 | 2012-10-03 | 哈尔滨工程大学 | Combined modulation method of phase modulation and symmetrical raised cosine frequency modulation |
| US20120300810A1 (en) * | 2011-05-24 | 2012-11-29 | Cambridge Silicon Radio Limited | Chirp communications |
| CN103905159A (en) * | 2014-04-28 | 2014-07-02 | 厦门大学 | Time-frequency coding method for underwater acoustic communication system |
| US20170118004A1 (en) * | 2015-10-26 | 2017-04-27 | Higher Ground Llc | Phase tracking |
| CN106646420A (en) * | 2016-09-28 | 2017-05-10 | 西安电子科技大学 | Method for designing MIMO (Multiple-input multiple-output) radar transmitting direction diagram based on LFM (Linear Frequency Modulation) signals |
| US20180323822A1 (en) * | 2017-05-08 | 2018-11-08 | Hangzhou Vango Communications, Inc. | Frequency modulated spread spectrum modulation method, modulator, and frequency modulated spread spectrum demodulation method, demodulator |
| CN109347777A (en) * | 2018-08-29 | 2019-02-15 | 中国科学院声学研究所 | A kind of operating factor of highband MT-MFSK underwater acoustic communication method |
| CN112422168A (en) * | 2020-10-27 | 2021-02-26 | 清华大学 | Signal modulation and demodulation method and system in high-mobility satellite communication |
-
2022
- 2022-05-31 CN CN202210612632.8A patent/CN115037330A/en active Pending
Patent Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20120300810A1 (en) * | 2011-05-24 | 2012-11-29 | Cambridge Silicon Radio Limited | Chirp communications |
| CN102710580A (en) * | 2012-06-12 | 2012-10-03 | 哈尔滨工程大学 | Combined modulation method of phase modulation and symmetrical raised cosine frequency modulation |
| CN103905159A (en) * | 2014-04-28 | 2014-07-02 | 厦门大学 | Time-frequency coding method for underwater acoustic communication system |
| US20170118004A1 (en) * | 2015-10-26 | 2017-04-27 | Higher Ground Llc | Phase tracking |
| CN106646420A (en) * | 2016-09-28 | 2017-05-10 | 西安电子科技大学 | Method for designing MIMO (Multiple-input multiple-output) radar transmitting direction diagram based on LFM (Linear Frequency Modulation) signals |
| US20180323822A1 (en) * | 2017-05-08 | 2018-11-08 | Hangzhou Vango Communications, Inc. | Frequency modulated spread spectrum modulation method, modulator, and frequency modulated spread spectrum demodulation method, demodulator |
| CN109347777A (en) * | 2018-08-29 | 2019-02-15 | 中国科学院声学研究所 | A kind of operating factor of highband MT-MFSK underwater acoustic communication method |
| CN112422168A (en) * | 2020-10-27 | 2021-02-26 | 清华大学 | Signal modulation and demodulation method and system in high-mobility satellite communication |
Non-Patent Citations (1)
| Title |
|---|
| 赵玉振: "一种基于OFDM-chirp的雷达通信一体化波形设计与处理方法", 《雷达学报》, vol. 10, no. 3, 30 June 2021 (2021-06-30) * |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116112327A (en) * | 2023-02-14 | 2023-05-12 | 南京理工大学 | Communication system based on linear frequency modulation signal |
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