CN114977929A - Permanent magnet synchronous motor control and parameter optimization method based on load torque observation - Google Patents
Permanent magnet synchronous motor control and parameter optimization method based on load torque observation Download PDFInfo
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Abstract
The invention discloses a permanent magnet synchronous motor control and parameter optimization method based on load torque observation.A compensation subentry load torque observation value is included in an output item of a sliding mode speed controller, so that under the condition that a given current part output by the sliding mode speed controller is not required to be adjusted greatly, the related influence caused by disturbance of a load or change of system parameters can be counteracted, and the buffeting of a system is effectively weakened. The feedback gain of the load torque observer is automatically adjusted according to the load torque set value and the variation of the load torque observed value, the feedback gain can be adjusted in advance when the load torque set value is changed or the load torque observed value is changed due to system speed change, parameter change, load disturbance and the like, when the load torque observed value really generates an observation error, the response speed of the observer is accelerated, the observation error of the load torque observed value is quickly reduced, and the rapidity and the accuracy of motor speed control are further improved.
Description
The invention discloses a motor drive control system of a high-voltage circuit breaker, which is a divisional application with an original application number of 202010918602.0 and an application date of 09-04 of 2020.
Technical Field
The invention relates to the technical field of permanent magnet synchronous motors, in particular to a permanent magnet synchronous motor control and parameter optimization method based on load torque observation.
Background
The conventional operating mechanisms of the high-voltage circuit breaker mainly comprise an electromagnetic operating mechanism, a spring operating mechanism, a pneumatic operating mechanism, a hydraulic operating mechanism and the like. The permanent magnet synchronous motor has the advantages of high efficiency, large torque, good rotating speed performance and the like, is widely applied to the fields of manufacturing, electric automobiles, industrial production and the like, adopts the permanent magnet synchronous motor to directly drive the circuit breaker to operate, and provides conditions for operating the opening and closing operation of the circuit breaker with different speed characteristics. The permanent magnet synchronous motor adopts a PI controller which cannot meet the requirement of high dynamic response, and the sliding mode control method can generate obvious buffeting of the motor speed when load disturbance or internal parameter perturbation occurs.
Disclosure of Invention
The invention aims to provide a load torque observation-based permanent magnet synchronous motor control and parameter optimization method for improving load torque observation response speed and reducing torque observation volatility aiming at the characteristic of high dynamic response requirement of high-voltage circuit breaker opening and closing operation. The parameters of the sliding mode speed controller and the parameters of the load torque observer are optimized and set uniformly by adopting a particle swarm algorithm, and the target function is
Q 3 ＝ω z +γ z τ；
Wherein, ω is z For tracking the rotor angular velocity jitter, tau is the tracking delay time, gamma z Adjusting the coefficients and gamma for fitness balance z ＞0。
When parameters of the sliding mode speed controller and parameters of the load torque observer are optimized and adjusted uniformly by adopting a particle swarm optimization, the angular speed omega of the rotor is given * Is a sine wave signal; rotor angular velocity tracking jitter omega z For the buffeting amplitude of the rotor angular velocity omega, the tracking delay time tau is the rotor angular velocity omega and the given rotor angular velocity omega * The delay time in between.
Obtaining rotor angular velocity tracking jitter omega z The method comprises the following steps: rotor angular velocity tracking jitter omega z Tracking jitter omega for multiple period rotor angular velocity peaks z1 And rotor angular velocity valley tracking jitter omega z2 Average value of (a). Obtaining the tracking jitter omega of the rotor angular velocity peak z1 The method of (1) is that the average value of 2 times of maximum sampling values of the rotor angular speed in the peak top area is taken as the maximum value of the peak top, and the minimum sampling value between the sampling moments of the 2 times of maximum sampling values is taken as the minimum value of the peak top; rotor angular velocity peak tracking jitter omega z1 Is the absolute value of the difference between the peak-top maximum and the peak-top minimum. Obtaining rotor angular velocity valley bottom tracking jitter omega z2 The method comprises the following steps: angle of rotorThe average value of 2 times of minimum sampling values of the speed in the valley bottom area is used as the minimum value of the valley bottom, and the maximum sampling value between the sampling moments of the 2 times of minimum sampling values is used as the maximum value of the valley bottom; rotor angular velocity valley bottom tracking jitter omega z2 Is the absolute value of the difference between the minimum value of the bottom of the valley and the maximum value of the bottom of the valley.
The method for acquiring the tracking delay time τ is as follows: the tracking delay time is a peak-to-peak tracking delay time of multiple periods 1 Sum bottom tracking delay time tau 2 Average value of (a). Peak top tracking delay time tau 1 The absolute value of the time difference between the moment of the maximum value of the angular speed of the rotor and the moment of the maximum value of the angular speed of the given rotor; valley tracking delay time tau 2 Is the absolute value of the time difference between the moment of the minimum value of the angular velocity of the rotor and the moment of the minimum value of the angular velocity of the given rotor. The method for obtaining the maximum time and the minimum time of the rotor angular speed is that the central point time of the rotor angular speed between 2 times of maximum sampling value sampling time in the peak area is used as the maximum time of the rotor angular speed, and the central point time of the rotor angular speed between 2 times of minimum sampling value sampling time in the valley area is used as the minimum time of the rotor angular speed.
The state variable of the sliding mode speed controller is
Where ω is the rotor angular velocity, ω * Is the given rotor angular velocity.
The sliding mode surface of the sliding mode speed controller is s y ＝c y y 1 +y 2 ，c y Is a slip form face parameter, and c y Is greater than 0; slip-form speed controller output load torque set value
And q-axis torque current setpoint
Is composed of
Wherein J is the moment of inertia, p is the motor pole pair number, psi f Is a permanent magnet flux linkage, B is a coefficient of friction,
is a load torque observation; coefficient mu 1 、μ 2 、μ 3 And mu 4 Exponential rate of approach coefficient for speed sliding mode control, and mu 1 ＞0，μ 2 ＞0，1＜μ 3 ＜2，μ 4 ＞0。
The load torque observer depends on the angular speed omega and the current i of the rotor q Observing the load torque to obtain a load torque observed value
. The load torque observer is
Wherein,
is an estimated value of the angular velocity of the rotor, g is a feedback gain of the load torque observer and g is less than 0;
k W is the proportional gain of the load torque observer and k W ＜0。
The load torque observer is used for setting a load torque according to the load torque output by the sliding mode speed controller
Is used to adjust the feedback gain g of the load torque observerThe method comprises the following steps:
step A, a load torque observer measures load torque T L Observing to obtain the observed value of the load torque
The sliding mode speed controller carries out control operation to obtain
Step B, calculating
Step C, judgment
Whether or not greater than epsilon 2 (ii) a When in use
Greater than epsilon 2 Taking feedback gain g equal to g min And withdrawing; when DeltaT is less than or equal to epsilon 2 Entering the step D;
step D, judgment
Whether or not less than epsilon 1 (ii) a When in use
Less than epsilon 1 Taking feedback gain g equal to g max And withdrawing; when in use
Is greater than or equal to epsilon 1 Entering the step E;
step E, feedback gain g is according to formula
And exiting after calculation.
ε 1 Comparing thresholds, e, for lower limits of torque variation 2 Comparing threshold values for upper limits of torque variation, and 0 & ltepsilon 1 ＜ε 2 ；g max For high value of feedback gain, g min Is a feedback gain low value, and g min ＜g max ＜0。
The parameters of the sliding mode speed controller and the parameters of the load torque observer are optimized and set uniformly by adopting a particle swarm optimization, and the parameter vector to be optimized is theta z2 ＝[c y ，μ 1 ，μ 2 ，μ 3 ，μ 4 ，G max ，G min ，ε 1 ，ε 2 ，β]；g max And G max In a relationship of
g min And G min In a relationship of
k W The relationship with beta is
T N Is the rated torque of the motor; beta is more than 0. Further, beta is more than or equal to 1 and less than or equal to 20.
The particle swarm algorithm is as follows:
step 301, initializing a particle swarm; the initial position of the particles is
Wherein M is the number of particles;
step 302, initializing a particle speed and a particle swarm optimal solution; taking the initial position of each particle as the initial optimal value of each particle, calculating the fitness value of each particle according to an objective function and storing the fitness value as the optimal particle fitness value of each particle; comparing the fitness values of the particles to obtain an initial particle swarm optimal solution and a particle swarm optimal fitness value, and storing the initial particle swarm optimal solution and the particle swarm optimal fitness value;
step 303, according to formula
z n+1 ＝z n +u n+1
Updating the speed and position of each particle; n is the current number of iterations, u n And z n Is the velocity vector and position of the particle; c. C 0 The inertia weight is the value range of 0-1.4; c. C 1 、c 2 Taking a value between 1 and 2 as a learning factor;
the random number is a random number with a value range of 0-1;
for the optimal solution found so far for the particles themselves,
representing the optimal solution of the particle swarm of the whole swarm up to now;
step 304, calculating the fitness value of each particle according to the objective function;
step 305, for
And corresponding optimal particle fitness value are updated, to
Updating the optimal fitness value of the corresponding particle swarm;
step 306, judging whether a cycle termination condition is met, if so, ending the particle swarm algorithm, and finally obtaining the optimal solution of the particle swarm as the optimal parameters of the sliding mode speed controller and the load torque observer; otherwise, return to step 303.
The permanent magnet synchronous motor control method based on load torque observation detects the rotor position theta of the permanent magnet synchronous motorAnd three-phase current i a 、i b And i c (ii) a According to three-phase current i a 、i b And i c Clark conversion is carried out on the permanent magnet synchronous motor to obtain current i under an alpha-beta axis coordinate system α Current i β According to the current i α Current i β Carrying out Park conversion on the rotor position theta to obtain a current i under a d-q axis coordinate system d Current i q 。
The control method of the permanent magnet synchronous motor based on load torque observation is realized by a motor drive control system comprising a sliding mode speed controller, a load torque observer, a q-axis current controller, a d-axis current controller, a Clarke conversion module, a position and speed detection module, a Park conversion module, a Park inverse conversion module, an SVPWM module and a three-phase inverter.
The sliding mode speed controller has the advantages that the output item of the sliding mode speed controller comprises the compensation subentry load torque observed value, the compensation subentry load torque observed value is equivalent to feedforward compensation of the load torque observed value to a given value of a current regulator, under the condition that the given current part output by the sliding mode speed controller does not need to be adjusted greatly, the load disturbance or related influence caused by the change of system parameters can be counteracted, and the buffeting of a system is effectively weakened. The feedback gain g is automatically adjusted according to the variable quantity of the given value of the load torque, so that the problems of large torque observation fluctuation caused by selecting a small fixed feedback gain and long convergence time caused by selecting a large fixed feedback gain by a load torque observer are solved, the observation error of the load torque can be quickly reduced when the given subentry part in the given value of the load torque changes or/and the observed value part of the load torque changes caused by the change of control parameters, model parameters and the like of a system or the disturbance of the load, and the rapidity and the accuracy of the observation effect and the speed control of the motor are improved. The feedback gain is automatically adjusted when the load torque given value changes, the load torque observed value can not change greatly, but the load torque observed value is caused to have large fluctuation because the given value of the rotor angular speed or/and the actual value of the rotor angular speed changes to change the given subentry part in the given value of the load torque or because the system model parameters change to change the given subentry part in the given value of the load torque, the feedback gain is adjusted in advance, when the load torque observed value really generates an observation error, the response speed of an observer is accelerated, the observation error of the load torque observed value is quickly reduced, and the rapidity and the accuracy of the motor speed control are further improved.
Drawings
Fig. 1 is a block diagram of an embodiment 1 of a motor drive control system of a high-voltage circuit breaker;
FIG. 2 is a flowchart of an embodiment 1 of a method for automatically adjusting feedback gain;
FIG. 3 is a block diagram of an embodiment 2 of a motor drive control system for a high voltage circuit breaker;
FIG. 4 is a flowchart of an embodiment 2 of a method for automatically adjusting feedback gain;
FIG. 5 is a sine wave signal and a load torque signal for a given rotor angular velocity;
fig. 6 is a schematic diagram of a rotor angular velocity signal and a rotor angular velocity response for 1 cycle of a sine wave.
Detailed Description
The present invention will be described in further detail below with reference to the accompanying drawings and examples.
Fig. 1 is a block diagram of an embodiment 1 of a motor drive control system for a high-voltage circuit breaker. In fig. 1, a Clarke conversion module inputs three-phase current i of a permanent magnet synchronous motor (i.e., PMSM) a 、i b And i c And outputs the current i under the two-phase static alpha-beta axis coordinate system α 、i β (ii) a A position sensor in the position and speed detection module detects the position theta of the rotor of the permanent magnet synchronous motor and converts the position theta into the angular speed omega of the rotor for output; park conversion module input current i α 、i β And rotor position theta, and outputs current i under a rotating d-q axis coordinate system d 、i q (ii) a SMC (sheet molding compound) input rotor given angular speed omega into sliding mode speed controller * And rotor angular velocity omega, output load torque set value T L * And torque current given component i' q (ii) a Input load torque set value T of load torque observer L * Rotor angular velocity ω and current i q The output torque current compensation component i ″) q (ii) a Torque current given component i' q And a torque current compensation component i ″) q After addition, as a given value i of q-axis torque current * q (ii) a q-axis current PI controller inputs q-axis torque current given value i * q And current i d And outputting a control voltage U under a q-axis coordinate system q (ii) a A q-axis torque current given value i is input by a d-axis current PI controller * d And current i d And outputting control voltage U under d-axis coordinate system d D-axis torque current setpoint i * d is equal to 0; the Park inverse transformation module inputs a control voltage U under a d-q axis coordinate system d 、U q And outputs the control voltage U under the alpha-beta axis coordinate system α 、U β (ii) a The SVPWM module (space vector pulse width modulation module) inputs a control voltage U α 、U β Outputting pulse signals to a three-phase inverter, which converts the DC voltage U dc Converting into three-phase AC power supply U a 、U b 、U c Thereby driving the permanent magnet synchronous motor to operate.
Neglecting the influence of core eddy current and hysteresis loss, etc., adopting i d The PMSM rotor magnetic field orientation control of 0, establishes a mathematical model of PMSM under a d-q axis rotating coordinate system, and the voltage equation is as follows:
for adopting i d The salient pole PMSM vector control system adopts a control mode of 0, and an electromagnetic torque equation is as follows:
the PMSM equation of motion is:
in the formulae (1), (2) and (3), u d 、u q Voltages of d-q axes, respectively; i.e. i d 、i q Currents of d-q axes, respectively; l is d 、L q Inductances of the d-q axes, respectively; t is e Is an electromagnetic torque; t is L Is the load torque; r is the resistance of the stator; p is the number of pole pairs of the motor; omega e Is the rotor electrical angular velocity, i.e. angular frequency; ω is the rotor angular velocity, i.e. the mechanical angular velocity of the rotor of the electrical machine; psi f Is a permanent magnet flux linkage; j is the moment of inertia; b is the coefficient of friction; t is time.
Let the angular speed error e of the rotor of the motor be omega * -ω，ω * Is the given rotor angular velocity of the motor. The state variables defining the high voltage circuit breaker motor drive control system embodiment 1 are:
obtained by the formulae (2), (3) and (4):
equation (5) is simplified to 1.5p ψ f /J，
The system state space equation of the embodiment 1 can be obtained as follows:
selecting a sliding mode surface function as follows:
s＝cx 1 +x 2 (7)
in the formula (7), s is a sliding mode surface, c is a parameter of the sliding mode surface, and c is more than 0. In equation (7), c is a coefficient of the rotor angular velocity error term, and its influence on the control action is mainly similar to a proportional coefficient in PID control, and the value of c also balances the rotor angular velocity error and the rate of change of the rotor angular velocity error, and is usually selected within a range of greater than 0 and less than 1000, for example, c is 60. The derivation of equation (7) can be:
the expression of the conventional exponential approximation law is:
in the formula (9), sgn () is a sign function, -k 1 sgn(s) is the constant velocity approach term, -k 2 s is an exponential approach term, k 1 、k 2 Two coefficients respectively determine the buffeting of the slip form surface and the motion quality of the approaching process, and k 1 、k 2 Are all greater than 0. In order to improve the response speed of the system, the improvement is carried out on the basis of the traditional exponential approach rate, the constant-speed approach term is changed into a variable-speed approach term, and the improved approach law is as follows:
wherein k is 1 ＞0，k 2 ＞0，0＜k 3 ＜1，k 4 Is greater than 0. When the absolute value | x of the rotor angular speed error of the motor 1 When the l is large, the ratio,
the approach speed of the variable speed approach item is higher, and the approach movement speed of the slip form can be accelerated; when | x 1 When the l is small, the ratio of l,
the approach speed of the variable speed approach term is smaller, and the buffeting can be weakened. k is a radical of 4 The value can refer to the steady-state jitter limit value of the rotor angular speed when the permanent magnet synchronous motor stably runs, the value is suggested to be not more than the inverse value of the steady-state jitter limit value, and furthermore, the inverse value of the steady-state jitter limit value is 50% -100%Taking values within a range; for example, if the steady-state jitter limit of the angular velocity of the rotor of the PMSM is 5rad/s (radian/second) and the reciprocal value is equal to 0.2, k is 4 Can take values within the range of 0.1-0.2. k is a radical of 3 Typically around 0.5, and further, k 3 Typically in the range of 0.4 to 0.6. Generally, when the control of the permanent magnet synchronous motor with low power is carried out, the coefficient k 1 And coefficient k 2 The values of (A) are all less than 2000; coefficient k 2 The larger the system state can approach the sliding mode at a greater speed; coefficient k 1 Determining the speed, k, of arrival at the switching plane 1 The smaller the distance and jitter across the switching plane. k is a radical of 1 And k 2 Respectively, a variable speed approaching term coefficient and an exponential approaching term coefficient, because
The value of (b) varies around 1, and therefore the coefficient k of the shift approach term in the equation (10) 1 And exponential approximation term coefficient k 2 The setting can be performed according to a method for adjusting the medium-speed approaching term coefficient and the exponential approaching term coefficient in the traditional exponential approaching rate. k is a radical of formula 3 Is the migration coefficient, the magnitude of which changes the shift critical point; k is a radical of 4 The magnitude of the variable speed coefficient changes the variable speed. E in the formula (10) is a natural exponent, i.e., a base of a natural logarithm.
Combining formulas (8) and (10), and taking the calculated q-axis given current as the torque current given component i' q Obtaining the given value T of the load torque output by the sliding mode speed controller L * And torque current given component i' q Comprises the following steps:
the sliding mode speed controller in the embodiment 1 of the high-voltage circuit breaker motor driving control system comprises an integral term in output, and filtering is carried out on control quantity, so that buffeting of a system can be weakened, and steady-state errors of the system can be reduced. Defining the Lyapunov function as:
from formulas (10) and (12):
in formula (13), k 1 ＞0，k 2 ＞0，s·sgn(s)≥0，
Therefore, it is
The system tracking error can be converged to zero in a limited time, and the system can stably run.
Setting parameters c, k in designing sliding mode speed controller 1 、k 2 、k 3 、k 4 Is that k is first determined 3 、k 4 A value of (d); given value i of q-axis torque current * q Comprising only a given component i 'of the input torque current' q (i.e. not carrying out load torque compensation control), and then adjusting the sliding mode surface parameter c and the variable speed approaching term coefficient k from small to large in the sliding mode of the system 1 Until the system generates obvious buffeting, the buffeting suppression and the system state convergence speed are considered on the basis, and the sliding mode surface parameter c and the variable speed approaching term coefficient k are properly reduced 1 A value of (d); finally, the index approach term coefficient k is adjusted mainly according to the rapidity of the system arrival section (for example, the motor starting stage of the step response) under the condition of considering the suppression of the sliding mode buffeting 2 And to make appropriate fine adjustments to other parameter values of the sliding mode speed controller.
According to the PMSM electromagnetic torque and the motion equation, the constant value can be regarded as a constant value in a change period for constant step load, namely
The angular speed and the load torque of the motor rotor are taken as state variablesAnd the PMSM state equation is formed as follows:
based on equation (14), a load torque observer embodiment 1 is established with load torque and motor rotor angular velocity as objects to be observed:
in the formula (15), the reaction mixture is,
is an observed value of the load torque,
is an estimate of the rotor angular velocity, g is the feedback gain of the load torque observer,
k g is the sliding mode gain of the load torque observer embodiment 1, and the load torque observer embodiment 1 is a sliding mode observer. Motor friction is smaller in specific weight than load torque, and if B is 0 and the influence of friction is ignored, load torque observer embodiment 1 of equation (15) becomes:
from (14) and equation (16) when B is 0, the error equation of load torque observer embodiment 1 is obtained as:
in the formula (17), the reaction mixture is,
for the estimation error of the angular velocity of the rotor,
for the observation error of the load torque, and defining the sliding mode surface of the observer as
According to the accessibility condition of the sliding mode, the system stability condition of the observer with the formula (16) is k g ≤-|e 2 And g is less than 0.
Based on equation (14), with load torque and motor rotor angular velocity as objects to be observed, a load torque observer embodiment 2 can also be established as follows:
motor friction is smaller in specific weight than load torque, and if B is 0 and the influence of friction is ignored, load torque observer embodiment 2 of equation (18) becomes:
in the formulae (18) and (19),
is an observed value of the load torque,
is an estimate of the rotor angular velocity, g is the feedback gain of the load torque observer,
k W is the proportional gain of load torque observer embodiment 2, load torque observer embodiment 2 being a state observer. According to the formula (14) and the formula (19) when B is 0, the error equation of the load torque observer embodiment 2 is obtained as follows:
in the formula (20), the reaction mixture is,
for the estimation error of the angular velocity of the rotor,
is the load torque observation error. The state observer of equation (19) is an autonomous linear system, at k W < 0, and g < 0, the observer is asymptotically stable. Formula (15) of load torque observer embodiment 1 and formula (18) of load torque observer embodiment 2 both take into account friction factors of the motor, and the addition of small friction damping gives a fast system response, but can increase the stability on the basis of formula (16) and formula (19), respectively.
In observer embodiment 1 in which expressions (15) and (16) are selected, sliding mode gain k g Is according to
A selection is made. In the formula (21), alpha is more than or equal to 1; typically, the value of α is selected in the range of 1 to 5, for example, α is selected to be equal to 1.5. Load torque observer embodiment 1 in observing load torque, k g Is selected to be too small when | e 2 The observer cannot enter a sliding mode state when l is larger; k is a radical of g The absolute value of the observer is selected to be large enough to ensure that the observer enters a sliding mode state, but the steady-state observation fluctuation of the load torque is increased; k is a radical of g The value of (2) is changed along with the change of the load torque observation error, and the stability of the observer can be improved and the steady state observation fluctuation of the load torque can be reduced at the same time.
When observer embodiment 2 of equations (18) and (19) is selected, proportional gain k W Is set according to
Selection is performed. In the formula (22), T N Is the rated torque of the motor, beta is more than 0; the value of β is generally selected within the range of 1 to 20, and β is, for example, 10. When the selection of beta is increased, the steady state fluctuation observed by the load torque is increased, but the tracking overshoot of the torque observation is reduced; when the beta selection is decreased, the steady state fluctuation of the load torque observation becomes small, but the torque observation overshoot amount becomes large.
In the observers represented by equations (15) and (16) or equations (18) and (19), the magnitude of the feedback gain g greatly affects the load torque observation result. The larger the feedback gain g is, the smaller the fluctuation of the observed torque is, but the slower the identification speed of the observed torque is; the smaller the feedback gain g, the faster the observed torque speed, but the greater the observed torque ripple. In consideration of this problem, in the conventional load torque observer, the observation speed and the fluctuation of the load torque are considered together, and the feedback gain g is taken as a folding median value, but this abandons the advantages of small fluctuation when the feedback gain is large and fast observation speed when the feedback gain is small.
The motor sliding mode speed control mainly inhibits the influence of parameter change and external load disturbance on a system by increasing the amplitude of discontinuous terms in a controller, but the increase of the amplitude can cause the inherent buffeting of the sliding mode. In order to solve the contradiction between the buffeting and the disturbance resistance of the sliding mode control system, the observer is used for observing the load disturbance change in real time, and the load torque observed value is subjected to feedforward compensation to the current regulator, so that the amplitude of a discontinuous item in the sliding mode control is reduced, the given torque change caused by the parameter change is weakened, or the system buffeting is caused by the load disturbance. In order to fully utilize the advantages of the feedback gain g in high and low values, according to the load torque observation values at two adjacent moments and the magnitude of the load torque set value variation, when the load torque set value variation is small and the load torque observation value variation is small, a larger value is given to the feedback gain g, so that the observation result has small fluctuation and stronger stability; when the change of the set value of the load torque is large or the change of the observed value of the load torque is large, a smaller value of the feedback gain g is given to accelerate the observation speed, and finally, the comprehensive result of high observation speed, small fluctuation and stronger stability is obtained by adjusting the feedback gain g.
When the embodiment 1 of the load torque observer or the embodiment 2 of the load torque observer is used in the embodiment 1 of the motor drive control system of the high-voltage circuit breaker in the figure 1, the load torque observer sets a given value according to the load torque
And load torque observed value
Is adjusted in dependence on the rotor angular velocity omega and the current i q Observing the load torque to obtain a new load torque observed value
Fig. 2 is a flowchart of an embodiment 1 of a feedback gain automatic adjustment method, and when the embodiment 1 of the load torque observer or the embodiment 2 of the load torque observer is used in the embodiment 1 of the motor drive control system of the high-voltage circuit breaker in fig. 1, the feedback gain automatic adjustment is performed. In FIG. 2,. epsilon 1 Comparing thresholds, e, for lower limits of torque variation 2 Comparing a threshold value for a torque variation upper limit; sum of variation of given value of load torque and variation of observed value of load torque in last 2 times
Wherein, Delta T L * For the difference between the last 2 load torque setpoints,
the difference between the last 2 load torque observations. In the periodic control process of the primary motor drive control system, the adjustment of the feedback gain g shown in fig. 2 (a) precedes the load torque observation and the output calculation of the sliding mode speed controller, and includes:
step one, calculation
Step two, judging whether delta T is larger than epsilon 2 (ii) a When Δ T is greater than ε 2 Taking feedback gain g equal to g min And entering the fifth step; when DeltaT is less than or equal to epsilon 2 Then, go to step three;
step III, judging whether delta T is less than epsilon 1 (ii) a When Δ T is less than ε 1 Taking feedback gain g equal to g max And entering the fifth step; when DeltaT is greater than or equal to epsilon 1 Then, the step IV is carried out;
step four, feedback gain g is according to
And (6) performing calculation.
Fifthly, the load torque observer measures the load torque T according to the feedback gain g L Observing to obtain the observed value of the load torque
The sliding mode speed controller carries out control operation to obtain a load torque set value
At this time
Is composed of
Is composed of
Adjusting the feedback gain g to the next timeThis time, the time
Become into
Become into
Wherein epsilon 1 Comparing thresholds, e, for lower limits of torque variation 2 Comparing threshold values for upper limits of torque variation, and 0 & ltepsilon 1 ＜ε 2 ；g max For high value of feedback gain, g min Is a low value of feedback gain, and g min ＜g max ＜0。
In the periodic control process of the primary motor speed, the adjustment of the feedback gain g shown in (b) of fig. 2 is later than the load torque observation and the output calculation of the sliding mode speed controller, the feedback gain g adjustment method changes the steps from the fifth step to the fifth step, changes the steps from the first step to the fourth step to the fifth step, and changes the entering step from the fifth step to the exiting step in each step.
In FIG. 2, (b) is
When Δ T is greater than ε 2 When the feedback gain g is equal to g, the feedback gain g is selected to indicate that the observed value of the load torque has large fluctuation or the observed value of the load torque has large fluctuation due to the change of system model parameters, the change of the set value of the rotor angular speed and the change of the actual value of the rotor angular speed, so that the change of the set value of the load torque is large and the observed value of the load torque has large fluctuation min Carrying out rapid identification and observation on the load torque; when Δ T is less than ε 1 When the feedback gain g is equal to g, the change of the given value of the load torque is small, the fluctuation of the observed value of the state load torque is small, and the feedback gain g is selected to be equal to g max Carrying out load torque identification and observation mainly based on stability; when DeltaT is greater than or equal to epsilon 1 And is less than or equal to epsilon 2 And then, the feedback gain g is calculated according to the formula (23), so that the feedback gain g is reduced along with the increase of the delta T in the interval, and the adverse effect on the working stability of the torque observer, which is caused by the fact that the feedback gain g is changed violently due to small change of the delta T, is avoided. In FIG. 2, the given torque variation comparison threshold 0 < ε 1 ＜ε 2 ，ε 1 、ε 2 The specific value of (a) is related to the sampling control period (cycle time) of the sliding mode speed controller, the permanent magnet synchronous motor and the load condition thereof, and epsilon 2 The value is generally set in a range of less than 5% of the rated torque, for example, 22 N.m for the rated torque, ε 1 ＝0.1N·m，ε 2 0.6N · m. The value of the feedback gain g satisfies g min ＜g max < 0, in general, g min ≥-5000。g min When the value is suddenly changed, the torque observation tracking overshoot of the load torque observer output observation value is within the torque observation tracking overshoot limit value; g max The value should be that when the load torque is unchanged and the load torque observer and the sliding mode speed controller are both in a steady state, the sum Delta T of the variation of the given value of the load torque and the variation of the observed value of the load torque is less than epsilon for the last 2 times 1 (ii) a For example, the feedback gain g is selected max ＝-0.5，g min -10. Selecting g min 、g max 、ε 1 、ε 2 The specific method of the value is that firstly, when the load torque is unchanged and the load torque observer and the sliding mode speed controller are both in a stable state, the feedback gain g is started from a larger value, for example, the feedback gain g is gradually reduced from-0.01, the steady state jitter observed by the load torque is gradually increased, and when the steady state jitter observed by the load torque reaches the steady state jitter observed by the load torque, the feedback gain g at the moment is determined to be g max (ii) a Keeping the load torque constant and making the feedback gain g equal to g max While continuously carrying out F 1 Measurement of the sub- Δ T value, and F will be at this time 1 Maximum F in sub- Δ T measurements 2 The average value of the measured values of delta T is used as a lower limit comparison threshold epsilon of the torque variation 1 (ii) a Then, when the load torque observer and the sliding mode speed controller are both in a steady state, the load torque is suddenly changed, and g is adjusted and determined by shortening the tracking and adjusting time of the output observed value of the load torque observer as much as possible on the premise of ensuring that the torque observation tracking overshoot of the output observed value of the load torque observer is within the torque observation tracking overshoot limit value min A value; then, the load torque is kept constant and the feedback gain g is made equal to g min While continuously carrying out F 1 Measurement of the sub- Δ T value, and F will be at this time 1 Maximum F in sub- Δ T measurements 2 The average value of the measured values of delta T is used as a torque change upper limit comparison threshold epsilon 2 。
When designing a sliding mode speed controller and a load torque observer of a high-voltage circuit breaker motor drive control system in embodiment 1, parameters of the sliding mode speed controller and the load torque observer can be set by adopting optimization algorithms such as a particle swarm algorithm, a wolf pack algorithm, a genetic algorithm and the like. Adopting wolf group algorithm to control parameters c and k of sliding mode speed controller 1 、k 2 、k 3 、k 4 The method comprises the steps of setting a target function for comprehensively evaluating various performance indexes of a sliding mode speed controller in embodiment 1 of a motor drive control system of the high-voltage circuit breaker in a timing manner
In the formula (24), Q 11 The integral term in (1) is an IAE criterion (error integral criterion) of the step response of the angular speed of the rotor of the motor, e (t) is an instantaneous value of the angular speed error of the rotor, t m The time is the transition process time of the angular speed step response of the motor rotor, and t is 0 which is the starting time of the motor step response; q 11 The second term γ in (1) m1 (1-sgn(e(t)+ω δ ) Is an angular velocity overshoot penalty function, where γ m1 Taken one large enough (
5 times and above the rational value), omega) of a positive number δ For rotor angular speed overshoot limit (i.e. rotor angular speed overshoot allowed by the system)Maximum value); when the overshoot of the angular speed step response of the motor rotor does not exceed the rotor angular speed overshoot limit value omega δ The term overshoot penalty function is equal to 0 when, and is equal to γ otherwise m1 ；Q 1 2 is the steady state jitter penalty function, ω Δ Is a steady-state jitter limit value of the angular speed of the rotor; when the steady-state jitter of the angular speed step response of the motor rotor does not exceed the steady-state jitter limit value omega of the angular speed of the rotor Δ The steady state jitter penalty function term is equal to 0 when, and is equal to γ otherwise m1 ；Q 1 The function value is an objective function value, namely an adaptive value of parameter optimization of the sliding mode speed controller by the wolf pack algorithm; the smaller the adaptive value of an individual in the wolf group is, the better the corresponding position is. Gamma ray m1 When taking value, firstly, the value is estimated
Reasonable value (upper limit); for example, if the rated rotation speed of the motor is 1500r/min (corresponding to the rated rotor angular speed of 157rad/s) and the starting time is about 0.2s, the motor is started
Reasonable value of not more than 40, gamma m1 By 5 times or more of 40, for example, by γ m1 ＝200。γ m2 Typically greater than or equal to 2, the magnitude of which determines how long the steady-state jitter of the rotor angular velocity is measured, e.g. gamma m2 When the value is equal to 6, the time t of the transition process is 5 times m The steady-state jitter of the rotor angular velocity is measured. The speed controller parameter optimization may establish other objective functions than the vertical (24) if other index factors need to be considered, such as whether the transient process time is short enough, whether the steady state error is small enough, and so on.
When parameters in the embodiment 1 of the load torque observer or the embodiment 2 of the load torque observer used in the embodiment 1 of the motor drive control system of the high-voltage circuit breaker are adjusted by adopting a wolf colony algorithm, an objective function for comprehensively evaluating various performance indexes of the load torque observer in the embodiment 1 of the motor drive control system of the high-voltage circuit breaker is established as
In formula (25), Q 2 The integral term in 1 is the IAE criterion of the observed step response of the motor load torque,
for load torque observation error, e 2 (t) is an instantaneous value of the observed error of the load torque, t p Tracking and adjusting time of motor load torque observation step response, wherein t is 0, and the load sudden change moment of the load torque observation step response is obtained; q 21 The second term γ in (1) p1 (1-sgn(e 2 (t)+T δ ) Track overshoot penalty function for torque observations, where γ p1 One is big enough
5 times and more of the rational value), T) of a positive number δ Tracking overshoot limit for torque observation, tracking overshoot limit when torque observation tracking overshoot does not exceed torque observation tracking overshoot limit T δ The torque observation tracking overshoot penalty function term is equal to 0 when, and is equal to gamma otherwise p1 。Q 22 Max (| e) in the first term 2 (t) |) is the absolute value of steady-state jitter observed by the maximum torque, gamma p2 Taking a constant larger than 0 for the fitness balance weight coefficient; q 22 Middle second term gamma p1 (1-sgn(e 2 (t)+T Δ ) Is a penalty function for the steady state jitter of the torque observations, T Δ Observing a steady-state jitter tolerance limit value for the load torque; when the observed steady state slip of the torque does not exceed the observed steady state slip limit T of the load torque Δ The torque observed steady state jitter penalty function term is equal to 0 when, and is equal to γ otherwise p1 。Q 2 The function value is an objective function value, namely an adaptive value for setting the parameters of the load torque observer by adopting a wolf pack algorithm; the smaller the adaptation value of the individual wolf, the better the corresponding position. Gamma ray p1 When taking value, firstly, the value is estimated
Reasonable value (upper limit)) (ii) a For example, assuming that the rated torque of the motor is 22N m, the maximum predicted torque is observed to track the regulation time t p About 0.1s, the value of the integral term of the IAE criterion in the formula (25) is not more than 2; fitness balance side weight coefficient gamma p2 Has 2 functions, namely balancing IAE criterion integral term and maximum torque observation steady-state jitter absolute value term, for example, setting load torque observation steady-state jitter limit value T Δ Is 1 N.m, then gamma p2 When 2 is taken, the IAE criterion integral term and the maximum torque observation steady-state shake difference absolute value term are relatively balanced, or the objective function value Q of the integral term and the maximum torque observation steady-state shake difference absolute value term are obtained 2 The functions are equivalent, in this case
Has a reasonable value of not more than 4, gamma p1 A constant equal to or greater than 20 may be used. Reduction of gamma p2 Value, then objective function value Q 2 The weight of the integral term of the middle IAE criterion is increased, and the rapidity of torque observation is more biased; increase gamma p2 Value, then objective function value Q 2 The weight of the steady-state shaking difference absolute value item observed by the medium and maximum torque is increased, and the steady-state performance observed by the torque is more biased. Gamma ray p3 Typically greater than or equal to 2, the magnitude of which determines how long the measurement of the steady-state jitter observed for the load torque is performed, e.g. gamma p3 When the value is equal to 6, tracking and adjusting time (namely transition process time) t is 5 times p The interval of (2) is measured for load torque observation steady state jitter.
The method comprises the following specific steps of optimizing parameters of a sliding mode speed controller or parameters of a load torque observer by adopting a wolf colony algorithm:
step 101, initializing wolf groups. The initial position of an individual in the wolf group is set as
Wherein M is the number of individuals in the wolf pack, generally selected from 20-150, and the initial position is required to be randomly distributed.
(1) For the sliding mode speed controller in embodiment 1 of the motor driving control system of the high-voltage circuit breaker, the parameter vector to be optimized is θ ═ c, k 1 ，k 2 ，k 3 ，k 4 ]At this time, the search space dimension N of the wolf pack algorithm is equal to 5, and the final head wolf position value is the optimal parameter of the sliding mode speed controller. The position value interval is [ m ] imin m imax ]The range interval can be given according to the prior knowledge or experience, for example, the value interval [ m ] of the parameter c 1min m 1max ]Is [ 01000 ]]Parameter k 1 Value range of [ m ] 2mi n m 2max ]Is [02000 ]]Parameter k 2 Value range of [ m ] 3min m 3max ]Is [02000 ]]Parameter k 3 Value range of [ m ] 4min m 4max ]Is [ 0.40.6 ]]Parameter k 4 Value range of [ m ] 5min m 5max ]Is [ 0.5/omega ] Δ 1/ω Δ ]。
(2) Aiming at the embodiment 1 of the load torque observer in the embodiment 1 of the motor drive control system of the high-voltage circuit breaker, when the feedback gain automatic adjustment is carried out by adopting the feedback gain automatic adjustment method embodiment 1, the parameter vector to be optimized is theta 1 ＝[G max ，G min ，ε 1 ，ε 2 ，α]The search space dimension N of the wolf pack algorithm is now equal to 5.
(3) Aiming at the embodiment 2 of the load torque observer in the embodiment 1 of the motor drive control system of the high-voltage circuit breaker, when the feedback gain automatic adjustment is carried out by adopting the feedback gain automatic adjustment method embodiment 1, the parameter vector to be optimized is theta 2 ＝[G max ，G min ，ε 1 ，ε 2 ，β]The search space dimension N of the wolf pack algorithm is now equal to 5.
For vector theta 1 、θ 2 During medium parameter optimization, g is obtained after the final wolf head position (optimal position) is obtained through optimization max 、g min According to
Respectively calculating to obtain; sliding mode gain k g Calculating according to the parameter alpha and the formula (21); proportional gain k W Calculated according to equation (22) based on the parameter β. Vector theta 1 、θ 2 Position dereferencing of middle parametersInterval is [ m ] imin m imax ]The range interval can be given based on prior knowledge or experience, e.g., the parameter G max Value range of [ m ] 1min m 1max ]Is [ -44 ]](ii) a Parameter G min Value range of [ m ] 2min m 2max ]Is [ -44 ]](ii) a Parameter epsilon 1 Value range of [ m ] 3min m 3max ]And parameter ε 2 Value range of [ m ] 4min m 4max ]Are all [ 00.05T N ]，T N Rated torque of the motor; value range [ m ] of parameter alpha 5min m 5max ]Is [15 ]]Or, the value interval [ m ] of the parameter beta 5min m 5max ]Is [ 120 ]]。
And step 102, hunting competition. Calculating the adaptive value of each wolf in the wolf group, wherein the smaller the adaptive value is, the better the position of the wolf is, and selecting the R with the optimal position 1 The wolf is a competitive wolf. R 1 The hunting wolves are developed by the hunting wolves according to the formula (26), and meanwhile, the hunting wolves compete for the wolfs according to the size of the adaptive value, which is specifically as follows:
step 1021, randomly selecting h for each wolf contest 1 A direction, which is further advanced and then retreated according to formula (26) along each direction search parameter; calculating the adaptive values after advancing, selecting the minimum adaptive values in all directions, and replacing the home position of the wolf race with the position of the minimum adaptive value if the minimum adaptive value is smaller than the adaptive value of the home position of the wolf race;
step 1022, repeat h for each contested wolf 2 The next step 1021;
step 1023, all R 1 After the picking wolf is completed in step 1022, the best picking wolf is selected as the wolf.
In the formula (26), i is 1, 2, …, R 1 (ii) a j ═ 1, 2, …, N; rand (-1, 1) is uniformly distributed in [ -11 ]]A random number within; 1, 2, …, h 1 (ii) a Stepa is the hunting step length, and the value range of the suggested Stepa is [ 0.10.9 ]]；m i ＝[m i1 m i2 …m iN ]Is the location of the ith winning wolf. R is 1 Suggested in the interval [0.1M 0.25M]Taking a fixed value or a random value; number of directions h 1 Suggesting in the interval [38]Value, repetition number h 2 Suggesting in the interval [ 310 ]]And (4) taking values.
And step 103, calling the running. And (3) expanding the running search behavior according to the formula (27) by the wolfs except the competitive wolf, and running towards the head wolf. Calculating an adaptive value of the new position of the ith wolf, changing the position of the ith wolf when the new position searched by the ith wolf is superior to the current position of the ith wolf, and keeping the position unchanged if the new position searched by the ith wolf is not superior to the current position of the ith wolf; if the new position searched by the ith wolf is better than the wolf position, the ith wolf is converted into the wolf and the call is initiated again.
m′ ij ＝m ij +rand(-1，1)·stepb·(m bj -m ij ) (27)
In the formula (27), i is 1, 2, …, M-R 1 ；j＝1，2，…，N；m′ i ＝[m′ i1 m′ i2 …m′ iN ]Indicating the location of the ith wolf search update; m is i ＝[m i1 m i2 …m iN ]Represents the current position of the ith wolf; m is a unit of b ＝[m b1 m b2 …m bN ]Indicating the current wolf location; stepb is the running step length, and the suggested value range of Stepb is [ 1.32.5 ]]。
And step 104, surrounding and attacking preys. Upon summoning of the head wolf, other wolf buttons (28) deploy a prey. Calculating an adaptive value of the new position, and changing the position of the wolf when the new position searched in the ith wolf attack process is superior to the current position, otherwise, keeping the position unchanged; if the ith wolf is containment in the new position found to be better than the wolf position, then the ith wolf is converted to a wolf.
In formula (28), i is 1, 2, …, M-1; j ═ 1, 2, …, N;
representing the current position of the ith wolf (i.e. the position over n iterations),
representing the attack update position of the ith wolf; m is b ＝[m b1 m b2 …m bN ]Indicating the current head wolf position; delta is a pre-established threshold value, and the value range of the suggested delta is [ 0.10.4 ]](ii) a Stepc is the attack step size and is calculated according to equation (29).
In the formula (29), n is the current iteration number, and n max Is the set maximum iteration number; stepc max 、stepc min Respectively is a set maximum attack step length and a set minimum attack step length. Suggested stepc min Is in the value range of [ 0.31.3]，stepc max Is taken to be stepc min 5 to 100 times higher. m is jmax And m jmin Respectively is the maximum value and the minimum value of the value interval of the jth dimension parameter. E in the formula (29) is a natural exponent, i.e., the base of the natural logarithm.
And step 105, judging the termination condition. If the loop iteration times reach or the head wolf adaptive value is smaller than a certain threshold value, the optimization process is terminated, and the head wolf position parameter is the optimal parameter of the optimized parameter vector. Otherwise, let n be n +1, go to step 106.
And step 106, competing for updating. Randomly generating R according to the principle of high-priority and low-priority 2 Wolf replacing original R 2 The rejected wolf with the worst fitness value competes for updating wolf clusters, and the process goes to step 102. R 2 Suggested in the interval [0.05M 0.15M]Take a fixed value or a random value.
In the above steps, a new position of the individual wolf is randomly generated, or when the individual wolf searches for the new position, the dimensional variable of the new position of each wolf cannot exceed the value range corresponding to the variable.
In step 105, the termination condition is adoptedMaximum iteration step limit mode, maximum iteration number n max Suggested in the interval [ 20500]A fixed value is taken. When the parameter in the vector θ is optimized and a condition that the head wolf adaptive value is smaller than a certain threshold is set, for example, the rated rotation speed of the motor is 1500r/min (corresponding to a rated rotor angular speed of 157rad/s), and the start time requirement is within 0.2s, the threshold of the termination condition may be set to 15. For vector theta 1 、θ 2 Optimizing parameters, and setting a termination condition that the head wolf adaptive value is smaller than a certain threshold value, wherein reference is needed to the rated torque of the motor and the expected torque observation, tracking and regulation time t p Torque observation tracking overshoot limit T δ Load torque observation steady state jitter limit T Δ And the adaptability balance side weight coefficient gamma p2 Etc. to determine the threshold size; the rated torque of the motor is 22 N.m, T δ Is 2 N.m, T Δ Is 1 N.m.gamma p2 Equal to 1.5, the desired torque observation tracks the adjustment time t p Less than 0.04s, the threshold for the termination condition may be set at 1.8.
In each step, aiming at parameter optimization of the vector theta, when calculating an adaptive value of a new position of the individual wolf, the position of the individual wolf is required to be converted into a corresponding controller parameter, the motor is controlled to start (or started in a simulation system), e (t) of the angular speed step response of the motor rotor required in the formula (24) is obtained, and the transition process time t is determined according to e (t) m Calculating to obtain the adaptive value Q of the individual wolf 1 . For vector theta 1 、θ 2 Optimizing medium parameters, and when calculating an adaptive value of a new position, requiring to convert the position of an individual wolf into corresponding load torque observer parameters in turn, when the given speed of the motor is unchanged and the sliding mode speed controller is in a steady state, enabling the load torque to change suddenly, controlling the motor to operate (or operate in a motor simulation system), and obtaining a motor load torque observation step response e required in a formula (25) 2 (t) according to e 2 (t) determining a transient time t p Calculating to obtain an adaptive value Q 2 。
In the above steps, a new position of the individual wolf is randomly generated, or when the individual wolf searches for generating the new position,the variable of each dimension of the new position of each wolf can not exceed the value range corresponding to the variable. Among the parameters to be optimized, g max 、g min With a constraint g in between min ＜g max Corresponding to the constraint G min ＞G max . When randomly generating a new location of an individual wolf or searching for an individual wolf to generate a new location, first, the individual wolf m i Parameter m in i1 (i.e. G) max ) According to the value-taking interval [ m 1min m 1max ]Randomly generating a location or performing a location update, then, the individual wolf m i Parameter m of i2 (i.e. G) min ) According to the value-taking interval [ m i1 m 2max ]Randomly generating position or updating position to make individual wolf m i Satisfies the constraint condition G min ＞G max I.e. satisfies the constraint g min ＜g max 。ε 1 、ε 2 With a constraint condition epsilon between 1 ＜ε 2 When randomly generating a new location of an individual wolf or searching for an individual wolf to generate a new location, first, the individual wolf m i Parameter m in i3 (i.e.. epsilon.) 1 ) According to the value-taking interval [ m 3min m 3max ]Randomly generating a location or performing a location update, then, the individual wolf m i Parameter m of i4 (i.e.. epsilon.) 2 ) According to the value-taking interval [ m i3 m 4max ]Randomly generating position or updating position to make individual wolf m i Satisfies the constraint condition epsilon 1 ＜ε 2 。
Because the initial position of the individual wolf is required to obey random distribution, and the space search mode of the wolf group algorithm is a linear mode, the feedback gain is directly subjected to the high value g max And a low value g of feedback gain min In the interval [ -50000]In search optimization, the absolute value of the feedback gain, which has a large influence on the observer operating state, is in a low range, for example, in the range of [ -100 [)]Meanwhile, the probability of randomly generating entry or searching entry is small, and the feedback gain high value g is difficult to obtain through optimization max And a low value g of feedback gain min The optimal position of (a). The feedback gain is not directly adjusted to a high value g in the optimization process max And a low value g of feedback gain min Search optimization is performed, but optimization is performed in a gain-like manner, with the parameter interval [ -100 [ -]The search interval is expanded, and a high value g of the feedback gain is easily obtained max And a low value g of feedback gain min The optimal position of (a); at this time, the feedback gain is high value g max And a low value g of feedback gain min The parameter intervals of (A) are [ -10000-0.0001 [ -10000 [ -0.0001 [ ]](ii) a High value g of feedback gain max Normally, it will not be in the range [ -0.00010 [)]Selecting within the range, otherwise, causing the observer to respond too slowly; in addition, the upper limit of the interval is-0.0001, and the high value g of the feedback gain is also avoided max The observer caused by taking a value of 0 does not work properly.
In the periodic control process of the speed of the permanent magnet synchronous motor in the embodiment 1 of the motor drive control system of the high-voltage circuit breaker, the given value of the load torque calculated at the current k moment (or the k step) is set
Is marked as
Observed value of load torque
Is marked as
The moment k-1 is the previous periodic control process moment of the moment k, and the given value of the load torque
Is marked as
Observed value of load torque
Is marked as
The k-2 time is before the k-1 timeOnce the time of the periodic control process, the given value of the load torque
Is marked as
Observed value of load torque
Is marked as
The process of controlling the speed of the permanent magnet synchronous motor in the embodiment 1 of the high-voltage circuit breaker motor driving control system comprises the following steps:
step one, detecting the rotor position theta, the rotor angular speed omega and the three-phase current i of the permanent magnet synchronous motor a 、i b And i c ；
Step two, according to three-phase current i a 、i b And i c Clark conversion is carried out on the permanent magnet synchronous motor to obtain current i under an alpha-beta axis coordinate system α 、i β According to the current i α 、i β Carrying out Park conversion on the rotor position theta to obtain a current i under a d-q axis coordinate system d 、i q ；
Step three, feedback gain g is given value T according to load torque L * And load torque observed value
Is adjusted;
step four, the load torque observer sets a value T according to the load torque L * Observed value of load torque
Rotor angular velocity ω and current i q Observing the load torque to obtain a new load torque observed value
And a torque current compensation component
Step five, the sliding mode speed controller gives the angular speed omega according to the input rotor * And the rotor angular speed omega is subjected to control calculation to obtain a load torque set value
And torque current given component i' q ；
Step six, giving component i 'according to torque current' q And a torque current compensation component
Calculating to obtain a given value i of q-axis torque current q * (ii) a d-axis current controller setting value i according to d-axis torque current d * And the current i under the d-axis coordinate system d The difference value between the two is subjected to PI control operation to obtain a control voltage U under a d-axis coordinate system d (ii) a The q-axis current controller sets a value i according to the q-axis torque current q * With current i in q-axis coordinate system q The difference value between the two is subjected to PI control operation to obtain a control voltage U under a q-axis coordinate system q (ii) a According to the control voltage U under a d-q axis coordinate system d 、U q Carrying out Park inverse transformation to obtain a control voltage U under an alpha-beta axis coordinate system α 、U β (ii) a d-axis torque current set value i d * Equal to 0;
step seven, controlling the voltage U under the alpha-beta axis coordinate system α 、U β As input of the SVPWM module, the SVPWM module controls a three-phase inverter to generate a three-phase alternating current power supply U a 、U b 、U c Thereby driving the permanent magnet synchronous motor to operate.
In the above steps, the sequence of the step three and the step four and the step five can be interchanged, that is, the step four and the step five can be performed first, and then the step three can be performed. FIG. 2 (a) is a schematic diagram showing the steps of the third, fourth and fifth stepsThe feedback gain is automatically adjusted in sequence, then the load torque observation and the speed control are carried out,
in fig. 2, (b) load torque observation and speed control are performed first, and then feedback gain automatic adjustment is performed,
in the above steps, the fourth step and the fifth step are performed first, and then the third step is performed.
Observing to obtain a load torque observed value
Then, the observed value of the load torque is measured
Converted into a torque current compensation component i ″) q Feedforward compensation is carried out to the input of a q-axis current PI controller, and a component i 'is given to a torque current output by a sliding mode speed controller' q Compensation is performed. q-axis torque current given value i of q-axis current PI controller * q Comprises the following steps:
in the formula (30), k q ＝2/(3pψ f ) The compensation factor is observed for torque. Comparing the equation (11) with the equation (30), when the load is disturbed or the system parameter is changed, the load torque compensation is not added in the equation (11), and a larger k needs to be selected 1 、k 2 The value is used for providing enough large given current variation to counteract the disturbance of the load or the related influence of the variation of the system parameters so as to ensure that the rotating speed of the motor can be quickly constant; equation (30) feed-forward compensates the load torque observations into the current regulator without requiring a large k 1 、k 2 Under the condition of the value, when the load is disturbed or the system parameter is changed, a given current variable quantity which is large enough is provided to offset the relevant influence of the disturbance of the load or the change of the system parameter, the output pressure of the sliding mode speed controller and the amplitude of a discontinuous term are reduced, and the buffeting of the system is effectively weakened.
When the feedback gain value is fixed, the smaller the feedback gain g is, the larger the oscillation amplitude observed by the load torque is, and the stronger the fluctuation is; the larger the feedback gain g is, the smaller the oscillation amplitude observed by the load torque is, and the higher the observation accuracy is. The automatic gain adjustment algorithm solves the problems that small feedback gains in a load torque observer cause large torque observation fluctuation and large feedback gains are long in convergence time, convergence time and fluctuation amplitude indexes are superior to those of a compromise gain algorithm, a load torque change value can be tracked quickly, observation errors caused by given changes or parameter changes can be reduced quickly, the oscillation amplitude is small, observation precision is high, and a good observation effect is achieved.
When a given rotation speed is changed at a rated load torque, although the actual load torque is not changed, as can be seen from the load torque observer constructed by equations (15), (16) or equations (18), (19), when the rotor angular velocity ω is changed, the observed torque observed value changes even if the load torque is not changed, resulting in an observation error. When the given rotating speed is changed under the rated load torque, the control and regulation process of the sliding mode control system of the permanent magnet synchronous motor is that firstly, the sliding mode speed controller changes according to the given speed to ensure that the output load torque given value T is changed L * Is changed so that the given value i of the torque current * q Is changed, so that the electromagnetic torque T of the permanent magnet synchronous motor is further changed e The change drives the motor to change the angular speed omega of the rotor; if the feedback gain g is only based on the variation of the observed value of the load torque
Automatic adjustment is carried out, and only when the angular speed omega of the rotor changes, the observed value of the load torque is enabled to be
After the change, the feedback gain g is adjusted; variation delta T of feedback gain g according to given value of load torque L * And amount of change in observed value of load torque
Is automatically adjusted, when the given rotation speed is changed, the given value T of the load torque is caused to be changed L * Change, load torque observed value
If no change has occurred, the feedback gain g is adjusted in advance, and the observed value of the load torque is adjusted
When the observation error is really generated, the response speed of the observer can be accelerated, and the observed value of the load torque can be eliminated (reduced) as soon as possible
The observation error of the motor is further improved, and the rapidity and the accuracy of the speed control of the motor are further improved. Similarly, when the system model parameter changes, the given value T of the load torque is caused to change L * Anticipating load torque observations
When the feedback gain g changes, the feedback gain g changes according to the variable quantity delta T of the given value of the load torque L * And amount of change in observed value of load torque
The feedback gain g can be adjusted in advance by automatic adjustment, the response speed of the observer is accelerated, and the observed value of the load torque is eliminated (reduced) as soon as possible
The speed control method and the device can further improve the rapidity and the accuracy of the speed control of the motor. Of course, ifThe observed value is caused by the disturbance of the load
When the change is made, the user can select the desired mode,
when a large change occurs, as can be seen from fig. 2, the feedback gain g can also be automatically adjusted to quickly cancel (reduce) the load torque observed value
To make the load torque observed value
Follow up on load torque T as soon as possible L A change in (c).
When the parameters of the load torque observer are optimized, the parameters of the sliding mode speed controller in embodiment 1 of the high-voltage circuit breaker motor driving control system need to be well set, and the optimization is performed under the condition of realizing load torque compensation control. Further, in embodiment 1 of the motor driving control system of the high-voltage circuit breaker, after the parameters of the sliding mode speed controller and the parameters of the load torque observer are set in sequence manually or in an optimization manner, the parameters of the sliding mode speed controller may be subjected to manual fine adjustment under the condition of realizing the load torque compensation control, or the parameters of the sliding mode speed controller are re-optimized by adopting a wolf pack algorithm according to step 101-.
Fig. 3 is a block diagram of embodiment 2 of the motor drive control system of the high-voltage circuit breaker. Fig. 3 differs from the embodiment 1 in fig. 1 in that the speed sliding mode controller performs load torque compensation in a manner that a load torque set value includes a load torque observed value item by using an integral sliding mode control manner; observed value of load torque observer
Is sent to a speed sliding mode controller, and a load torque observed value is already included in a given q-axis current (a given torque current component) output by the sliding mode speed controller
Therefore, the q-axis given current (the torque current given component) output by the speed sliding mode controller in embodiment 2 can also play a role in load torque compensation as the q-axis torque current given value is directly used as the q-axis torque current given value; given value T of load torque output by speed sliding mode controller L Δ Also already including load torque observations
The load torque observer directly follows the load torque set value T L Δ The function of the feedback gain automatic adjustment is the same as that of the feedback gain automatic adjustment performed by the feedback gain automatic adjustment method in embodiment 1 according to the sum Δ T of the variation of the load torque set value and the variation of the load torque observed value of the last 2 times;
the state variables defining the high voltage circuit breaker motor drive control system embodiment 2 are:
selecting a sliding mode surface function as follows:
s y ＝c y y 1 +y 2 (32)
in the formula (32), c y Is a slip form face parameter, and c y Is greater than 0. C in formula (32) y The coefficient of the rotor angular velocity error integral term, the influence of the size of the coefficient on the control action is mainly similar to the proportional coefficient in PID control, c y The value of (c) is also taken into account for balancing the rotor angular velocity error integral term and the rotor angular velocity error term, under the normal condition y Selected within a range of greater than 0 and less than 100. The derivation of equation (32) can be:
on the basis of the traditional exponential approach law, the improved approach law is as follows:
μ 1 、μ 2 、μ 3 、μ 4 exponential rate coefficient for speed sliding mode control, where 1 ＞0，μ 2 ＞0，1＜μ 3 ＜2，μ 4 Is greater than 0. When the rotor angular speed error y of the motor 2 When the size of the particles is larger than the required size,
the approaching speed of the variable speed approaching item is higher, and the approaching movement speed of the slip form can be accelerated; when y is 2 When the ratio of the water to the oil is small,
the approaching speed of the variable speed approaching term is smaller, and the buffeting can be weakened. Mu.s 4 The value can be obtained by referring to the steady-state jitter limit value of the angular speed of the rotor when the permanent magnet synchronous motor stably runs, and the value is recommended to be obtained within the range of 50-150% of the square value of the steady-state jitter limit value; for example, if the steady-state jitter limit of the PMSM is 4rad/s (radians/sec), and the square of the steady-state jitter limit is equal to 16, then μ 4 The value can be in the range of 8-24. Mu.s 3 The larger the speed change, the larger μ 3 Generally, the value is in the range of 1.05-1.3. Generally, when the control of the permanent magnet synchronous motor with low power is carried out, the coefficient mu 1 Coefficient of sum μ 2 Are all less than 5000. Mu.s 1 And mu 2 Respectively, a variable speed approach term coefficient and an exponential approach term coefficient, because
Is changed in the vicinity of 1, and therefore, the coefficient μ of the shift approach term in the formula (34) 1 Coefficient of sum exponential approximation term mu 2 Can adjust the conventional indexAnd (4) setting a medium-speed approaching term coefficient and an exponential approaching term coefficient of the approaching rate by a method. Mu.s 3 The speed change coefficient is the speed change coefficient, and the speed change speed is changed according to the size of the speed change coefficient; mu.s 4 Is the mobility coefficient, the magnitude of which changes the shift critical point.
In combination with formulae (2), (3), and (33), to give:
combining formulas (34) and (35) to directly use the calculated q-axis given current as a q-axis torque current given value i Δ q The given value i of the q-axis torque current output by the controller can be obtained Δ q And a given value T of load torque L Δ Comprises the following steps:
in equation (36), the load torque value T L Using the output value of a load torque observer
Instead of that. Defining the Lyapunov function as:
from formulas (32) and (34):
in the formula (38), mu 1 ＞0，μ 2 ＞0，
s y ·sgn(s y ) Not less than 0, so
The tracking error of the observer can be converged to zero in a limited time, and the system can stably run.
Setting parameter c in designing sliding mode speed controller y 、μ 1 、μ 2 、μ 3 、μ 4 Is first determined 3 、μ 4 A value of (d); let the output value of the load torque observer in equation (36)
(i.e., without load torque compensation control), and then adjusting the sliding mode surface parameter c from small to large in the sliding mode of the system y Coefficient of shift approach [ mu ] 1 Until the system generates obvious buffeting, the buffeting suppression and the system state convergence speed are considered on the basis, and the sliding mode surface parameter c is properly reduced y And a coefficient mu of a shift approximation term 1 A value of (d); finally, the exponential approximation term coefficient μ is adjusted primarily based on the rapidity of the system reach segment (e.g., the motor start-up phase of the step response) while simultaneously suppressing slip mode buffeting 2 And to make appropriate fine adjustments to other parameter values of the sliding mode speed controller.
The load torque observer in the embodiment 2 of the high-voltage circuit breaker motor driving control system still adopts the aforementioned embodiment 1 of the load torque observer, or adopts the aforementioned embodiment 2 of the load torque observer; at the moment, the load torque observer is used for setting the load torque according to the load torque output by the sliding mode speed controller
Is adjusted in dependence on the rotor angular velocity omega and the current i q To load torque T L Observing to obtain load torque observed value
FIG. 4 is a flow chart of an embodiment 2 of the feedback gain automatic adjustment method, which is implemented in an embodiment 1 of a load torque observer, or a load torque observerExample 2 when used in example 2 of the motor drive control system of the high voltage circuit breaker of fig. 3, the feedback gain is automatically adjusted. In FIG. 4,. epsilon 1 Comparing thresholds, e, for lower limits of torque variation 2 Comparing threshold values for upper limits of torque variation, and 0 & ltepsilon 1 ＜ε 2 ；g max For high value of feedback gain, g min Is a low value of feedback gain, and g min ＜g max ＜0；ΔT L Δ The difference between the load torque set points for the last 2 times. During the periodic control of the primary motor speed, the adjustment of the feedback gain g shown in fig. 4 (a) precedes the observation of the load torque and the calculation of the output of the sliding mode speed controller by:
step (one), calculating
Step (2), judgment
Whether or not greater than epsilon 2 (ii) a When in use
Greater than epsilon 2 Taking feedback gain g equal to g min And entering the step (5); when DeltaT is less than or equal to epsilon 2 Entering the step (III);
step (III) of judgment
Whether or not less than epsilon 1 (ii) a When in use
Less than epsilon 1 Taking feedback gain g equal to g max And entering the step (5); when the temperature is higher than the set temperature
Is greater than or equal to epsilon 1 Entering the step (IV);
step (IV), the feedback gain g is according to
After calculation, entering step (5);
step (5) of the load torque observer to the load torque T L Observing to obtain the observed value of the load torque
The sliding mode speed controller carries out control operation to obtain
At this time
Is composed of
Becomes during the next periodic control of motor speed
In the periodic control process of the primary motor speed, the adjustment of the feedback gain g shown in (b) of fig. 4 is later than the load torque observation and the output calculation of the sliding mode speed controller, and the specific method is as follows:
step A, a load torque observer measures load torque T L Observing to obtain the observed value of the load torque
The sliding mode speed controller carries out control operation to obtain
. At this time
Is composed of
Becomes during the next periodic control of motor speed
Step B, calculating
Step C, judgment
Whether or not greater than epsilon 2 (ii) a When in use
Greater than epsilon 2 Taking feedback gain g equal to g min And withdrawing; when DeltaT is less than or equal to epsilon 2 Entering the step D;
step D, judgment
Whether or not less than epsilon 1 (ii) a When in use
Less than epsilon 1 Taking feedback gain g equal to g max And withdrawing; when in use
Is greater than or equal to epsilon 1 Entering the step E;
and E, calculating the feedback gain g according to the formula (39) and then quitting.
T L Δ The output items of (1) include given sub-items in a change state due to the change of system parameters, or the change of a set value of the angular speed of the rotor, or the change of an actual value of the angular speed of the rotor
Also includes compensating for the fractional load torque observations
. When the temperature is higher than the set temperature
Greater than epsilon 2 In time, the observed value of the load torque is shown to have large fluctuation, or the T is caused by the change of system model parameters, the change of the set value of the rotor angular speed and the change of the actual value of the rotor angular speed L Δ Will cause large fluctuations in the load torque observations, the feedback gain g is chosen to be equal to g min Carrying out rapid identification and observation on the load torque; when | Δ T L Δ | is less than epsilon 1 A factor (i.e., T) that indicates that the load torque observation is fluctuating little and will cause the load torque observation to fluctuate significantly L Δ Given partial term in) is small, the feedback gain g is chosen to be equal to g max Carrying out load torque identification and observation mainly based on stability; when | Δ T L Δ | is greater than or equal to epsilon 1 And is less than or equal to epsilon 2 Then, the feedback gain g is calculated according to equation (39) such that the feedback gain g follows | Δ T in this interval L Δ Decrease with increasing | Δ T to avoid the effect of | Δ T L Δ The small change of | can cause the feedback gain g to generate a violent change, which can adversely affect the working stability of the torque observer. In FIG. 4,. epsilon 1 、ε 2 The specific value of (a) is related to the sampling control period (cycle time) of the sliding mode speed controller, the permanent magnet synchronous motor and the load condition thereof, and epsilon 2 The value is generally set in a range of less than 5% of the rated torque, for example, 22 N.m for the rated torque, ε 1 ＝0.1N·m，ε 2 0.6N · m. The value of the feedback gain g satisfies g min ＜g max < 0, in general, g min ≥-5000。g min When the value is suddenly changed, the torque observation tracking overshoot of the load torque observer output observation value is within the torque observation tracking overshoot limit value; g max The value is constant under the condition of load torque, and the load torque is observedDifference | Delta T between the last 2 load torque set points when both the controller and the sliding mode speed controller are in steady state L Δ | is less than epsilon 1 (ii) a For example, the feedback gain g is selected max ＝-0.5，g min -10. Selecting g min And g max The specific method of the value is that firstly, when the load torque is unchanged and the load torque observer and the sliding mode speed controller are both in a stable state, the feedback gain g is started from a larger value, for example, the feedback gain g is gradually reduced from-0.01, the steady state jitter observed by the load torque is gradually increased, and when the steady state jitter observed by the load torque reaches the steady state jitter observed by the load torque, the feedback gain g at the moment is determined to be g max (ii) a Keeping the load torque constant and making the feedback gain g equal to g max While continuously carrying out F 1 Sub |. DELTA.T L Δ Measurement of | value, and will be F at this time 1 Sub |. DELTA.T L Δ Maximum F in | measurement 2 A | Delta T L Δ The average value of | measured values is used as a torque variation lower limit comparison threshold epsilon 1 (ii) a Then, when the load torque observer and the sliding mode speed controller are both in a steady state, the load torque is suddenly changed, and g is adjusted and determined according to the condition that the tracking and adjusting time of the output observed value of the load torque observer is as short as possible on the premise that the torque observation tracking overshoot of the output observed value of the load torque observer is within the torque observation tracking overshoot limit value min A value; then, the load torque is kept unchanged and the feedback gain g is made equal to g min Simultaneously carrying out F1 times of | Delta T L Δ Measurement of | value, and will be F at this time 1 Sub | Δ T L Δ Maximum F in | measurement 2 A | Delta T L Δ The average value of the | measured values is used as a torque variation upper limit comparison threshold epsilon 2 。
G is selected from the above min 、g max In the specific method for comparing the value and the threshold value, the parameters in the sliding mode speed controller are set and are realized under the condition of carrying out load torque compensation control; when the parameter value is determined manually, suggestion F is made 1 Is an integer of 20 or more, F 2 Is not less than 5 and not more than etcAt 0.5F 1 Is an integer of (1).
In embodiment 2 of the high-voltage circuit breaker motor drive control system, parameters of the sliding-mode speed controller and the load torque observer may be set by using optimization algorithms such as a particle swarm algorithm, a wolf pack algorithm, and a genetic algorithm under the condition of realizing load torque compensation control. The specific method for setting parameters in the sliding mode speed controller and the load torque observer in the embodiment 1 (or the embodiment 2 of the load torque observer) of the high-voltage circuit breaker motor drive control system in the embodiment 2 by adopting the particle swarm optimization is as follows:
system motor given rotor angular speed omega * Is a sine wave signal, as shown in (a) of fig. 5. Given rotor angular velocity ω * The sine wave signal having a period of T * Maximum value of angular velocity of rotor
Not greater than rated angular speed of motor and minimum value of angular speed of rotor
Not less than 10% of rated angular speed of motor and maximum value of angular speed of rotor
Minimum value of angular speed of rotor
The difference between the two is not less than 50% of the rated angular speed of the motor. When the high-voltage circuit breaker motor driving control system in the embodiment 2 is started under the rated load torque, the starting rise time to the rated rotating speed is T r Then T is * At 5-10T r Selecting. The system motor gives the angular speed omega of the rotor according to the sine wave * When the signal is running, a load torque T is applied according to (b) in FIG. 5 L That is, the system motor gives the rotor angular velocity ω in accordance with a sine wave * When the signal starts to operate, the load torque is a low value T of the load torque Lmin (ii) a After the motor enters a rotor angular speed stable following state, the load torque is changed from a low value T Lmin Mutation increases to a high value of T Lmax (ii) a The load torque is maintained at a high value T Lmax Run time
Then, from a high value T Lmax Reduction of the mutation to a low value of T Lmin (ii) a Wherein the load torque is high value T Lmax Not greater than rated load torque of motor, and low value T of load torque Lmin Not less than 10% of rated load torque of motor, high value T of load torque Lmax With low value T of load torque Lmin The difference between the two is not less than 50% of the rated load torque of the motor;
is 2 to 5T * To a random value. The system motor gives the angular speed omega of the rotor according to the sine wave * The signal runs for at least 2 periods T * Then entering a stable following state of the angular speed of the rotor.
FIG. 6 shows 1 sine wave period T in the steady following state of the rotor angular velocity of the motor * Is a given rotor angular velocity signal and a rotor angular velocity response diagram, wherein the curve (r) is a given rotor angular velocity (omega) * And a curve II is the angular speed response omega of the rotor, and buffeting exists. In order to clearly distinguish ω * And ω, given rotor angular velocity ω in FIG. 6 * And the rotor angular velocity response omega in a different scale from the ordinate of the vertical axis of the rotor angular velocity response omega. Rotor angular velocity tracking jitter omega z For the buffeting amplitude of the rotor angular velocity omega, the tracking delay time tau is the rotor angular velocity omega and the given rotor angular velocity omega * The delay time in between. In FIG. 6,. omega. z1 Tracking jitter at the rotor angular velocity peak when the rotor angular velocity response omega is at a maximum state (peak state), tau 1 Is the peak-to-peak tracking delay time, which is the absolute value of the time difference between the moment of the maximum value of the angular velocity of the rotor (the peak-to-peak moment) and the moment of the maximum value of the angular velocity of the given rotor (the peak-to-peak moment); omega z 2 is the rotor angular velocity valley tracking jitter, τ, when the rotor angular velocity response ω is in the minimum state (valley state) 2 Is the valley bottom tracking delay time, which is the minimum value time (valley bottom time) and the supply time of the rotor angular velocityThe absolute value of the time difference between the minimum angular velocity moments (bottom moments) of the stator and rotor. Continuous measurement involving load torque from a low value T Lmin Mutation increases to a high value of T Lmax To the load torque from a high value T Lmax Reduction of the mutation to a low value of T Lmin For example, 10 or more than 10T periods * Period) of the rotor angular velocity peak-to-peak tracking jitter ω z 1. Rotor angular velocity valley bottom tracking jitter omega z2 Peak-to-peak tracking delay time τ 1 Bottom of valley tracking delay time tau 2 (ii) a Rotor angular velocity tracking jitter omega z For the multiple periods omega z1 And ω z2 Average value of (d); the tracking delay time τ being the plurality of periods τ 1 And τ 2 Average value of (a). The sinusoidal signal is used as the angular speed signal of the given rotor of the motor, the load torque sudden change is controlled when the motor operates, the performance indexes are constructed through the tracking jitter of the angular speed of the rotor and the tracking delay time of the angular speed of the rotor to simultaneously optimize the parameters of the sliding mode speed controller and the load torque observer, the influence of the performance of the load torque observer on the performance of the angular speed of the rotor is unified to the performance indexes of the angular speed of the rotor, the parameter optimization process is simplified, and meanwhile, the performance indexes of the angular speed of the rotor can be improved to the maximum extent. The moment of the maximum value of the angular speed of the given rotor (the peak top moment) and the moment of the minimum value of the angular speed of the given rotor (the valley bottom moment) pass through the given angular speed omega of the rotor * The sinusoidal signal is calculated.
Obtaining the tracking jitter omega of the rotor angular velocity peak z1 The method comprises the following steps: taking the average value of 2 times of maximum sampling values of the rotor angular speed in the peak top area as the maximum value of the peak top, and taking the minimum sampling value between the sampling moments of the 2 times of maximum sampling values as the minimum value of the peak top; rotor angular velocity peak tracking jitter omega z1 Is the absolute value of the difference between the peak-top maximum and the peak-top minimum. Obtaining rotor angular velocity valley bottom tracking jitter omega z2 The method comprises the following steps: taking the average value of 2 times of minimum sampling values of the angular speed of the rotor in a valley bottom area as a valley bottom minimum value, and taking the maximum sampling value between the sampling moments of the 2 times of minimum sampling values as a valley bottom maximum value; rotor angular velocity valley bottom tracking jitter omega z2 Is the absolute value of the difference between the minimum value of the bottom of the valley and the maximum value of the bottom of the valley.
The method for acquiring the maximum time and the minimum time of the rotor angular speed comprises the following steps: and taking a central point (central point moment) of the rotor angular velocity between 2 times of maximum sampling value sampling moments in the peak top area as the maximum value moment of the rotor angular velocity, and taking a central point (central point moment) of the rotor angular velocity between 2 times of minimum sampling value sampling moments in the valley bottom area as the minimum value moment of the rotor angular velocity.
An objective function for comprehensively evaluating performance indexes of a sliding mode speed controller and a load torque observer in an embodiment 2 of a motor drive control system of a high-voltage circuit breaker is established
Q 3 ＝ω z +γ z τ (40)
In the formula (40), Q 3 The particle fitness value is an objective function value, namely a particle fitness value for performing parameter optimization on a sliding mode speed controller and a load torque observer in an embodiment 2 of a high-voltage circuit breaker motor driving control system by adopting a particle swarm algorithm, and consists of a rotor angular speed tracking jitter term and a tracking delay time term; gamma ray z The fitness balance adjustment coefficient is a constant larger than 0; setting a steady-state shake difference limit value omega of the angular speed of the rotor of the system Δ 1.5rad/s, start-up rise time T of the motor r Is 0.1s, and the tracking delay time tau is not more than the starting rising time T under the normal working condition r Thus, γ z When the value is 15, the relative balance between the tracking delay time term and the rotor angular speed tracking jitter term is kept; or the tracking delay time term and the rotor angular speed tracking jitter term play equivalent roles; reduction of gamma z Value, then objective function value Q 3 The weight of the angular speed tracking jitter term of the middle rotor is increased, and the system performance is more biased to the stability of speed control; increase gamma z Value, then objective function value Q 3 The weight of the middle tracking delay time item is increased, and the system performance is more biased to the rapidity of the speed control.
The method specifically comprises the following steps of optimizing parameters of a sliding mode speed controller and a load torque observer in an embodiment 2 of a high-voltage circuit breaker motor drive control system by a particle swarm algorithm:
step 301, initialize a particle swarm. Setting the initial position of the particle in the particle groupIs arranged as
Wherein M is the number of particles in the particle swarm, generally selected from 20-150, and the initial position is required to be randomly distributed. For different optimized objects, there are:
(1) aiming at a sliding mode speed controller and a load torque observer in a high-voltage circuit breaker motor drive control system embodiment 2, in a feedback gain automatic adjustment method embodiment 2, when feedback gain is automatically adjusted, a parameter vector to be optimized is theta z1 ＝[c y ，μ 1 ，μ 2 ，μ 3 ，μ 4 ，G max ，G min ，ε 1 ，ε 2 ，α]The search space dimension N of the algorithm is now equal to 10.
(2) Aiming at a sliding mode speed controller and a load torque observer embodiment 2 in a high-voltage circuit breaker motor drive control system embodiment 2, when a feedback gain automatic adjustment method embodiment 2 is adopted to carry out feedback gain automatic adjustment, a parameter vector to be optimized is theta z2 ＝[c y ，μ 1 ，μ 2 ，μ 3 ，μ 4 ，G max ，G min ，ε 1 ，ε 2 ，β]The search space dimension N of the algorithm is now equal to 10.
In each embodiment of step 301, the optimal position in the finally constructed particle is the optimal parameter, g max 、g min According to
Respectively calculating to obtain; sliding mode gain k g Calculating according to the parameter alpha and the formula (21); proportional gain k W Calculated according to equation (22) based on the parameter β.
In each embodiment of step 301, the initial position of the ith particle is represented as
Corresponding to each parameter vector to be optimized; the position value interval is [ z ] imin z imax ]The range interval can be given based on prior knowledge or experience, e.g. the parameter c y Value range of [ z ] 1min z 1max ]Is [010 ]](ii) a Parameter mu 1 Value range of [ z ] 2min z 2max ]Is [ 05000](ii) a Parameter mu 2 Value range of [ z ] 3min z 3max ]Is [ 05000](ii) a Parameter mu 3 Value range of [ z ] 4min z 4max ]Is [1.051.3 ]](ii) a Parameter mu 4 Value range of [ z ] 5min z 5max ]Is [ 0.5/omega ] Δ 2 1.5/ω Δ 2 ]，ω Δ Is a steady-state jitter tolerance limit value of the angular speed of the rotor; parameter G max Value range of [ z ] 6min z 6max ]Is [ -44 ]](ii) a Parameter G min Value range of [ z ] 7min z 7max ]Is [ -44 ]](ii) a Parameter epsilon 1 、ε 2 Value range of [ z ] 8min z 8max ]、[z 9min z 9max ]Are all [ 00.05T N ]，T N Rated torque of the motor; value range [ z ] of parameter alpha 10min z 10max ]Is [15 ]]Or, the value range [ z ] of the parameter beta 10min z 10max ]Is [ 120 ]]。
Step 302, initializing a particle speed and a particle swarm optimal solution; the initial position z of each particle (0) As an initial optimum value z of each particle b (0) Calculating a fitness function value (i.e., a particle fitness value) of each particle according to equation (40) and storing the fitness function value as an optimal particle fitness value for each particle; the fitness values of all the particles are compared to obtain the optimal solution z of the initial particle swarm g (0) And storing the particle swarm optimal fitness value. Let the initial velocity of the particles be
Also following a random distribution, the initial velocity of the ith particle is then expressed as
(ii) a Extreme value of speed variation of parameter u imin u imax ]Is generally set as 5 percent of the value range of the parameter-20%; for example, the parameter G max Value range of [ z ] 1min z 1max ]Is [ -44 ]]And the interval range is 8, the 1 st dimension variable (parameter G) of each particle max ) Speed change limit value u 1min u 1max ]Is [ -0.40.4 ] in accordance with a value of 5%]The value is [ -1.61.6 ] according to 20%]。
Step 303, according to formula
Updating the speed and position of each particle; the speed change of each dimension variable cannot exceed the corresponding speed change extreme value of each dimension variable, and the updating position of each dimension variable cannot exceed the corresponding value interval of each dimension variable. In the formula (41), n is the current iteration number, u n And z n Is the velocity vector and position of the particle; c. C 0 The value range is 0-1.4 for the inertial weight, the search range and the search speed can be changed by adjusting the value of the inertial weight, and further, the adaptive reduction c is realized along with the increase of the iteration times 0 The value is favorable for achieving balance between searching capability and convergence speed; c. C 1 、c 2 Taking values between 1 and 2 as learning factors, and taking 2 as suggestions;
the random number is a random number with a value range of 0-1;
for the optimal solution (optimal position) found so far for the particle itself,
indicates the optimal solution (optimal position) of the particle group for the whole population up to now.
Step 304, calculate the particle fitness value of each particle according to equation (40).
Step 305, for
And the corresponding optimal particle fitness value is updated to
And updating the corresponding particle swarm optimal fitness value.
Step 306, judging whether a cycle termination condition is met, if so, ending the particle swarm algorithm, and finally obtaining the optimal solution of the particle swarm as the optimal parameters of the optimized parameter vector, namely the optimal parameters of the sliding mode speed controller and the load torque observer; otherwise, return to step 303.
Loop termination conditions are typically either reaching a maximum iteration step limit or an optimal particle adaptation value less than a certain threshold. And (3) setting parameters of the sliding mode speed controller and the load torque observer by adopting a particle swarm algorithm, and adopting a maximum iteration step number limiting mode as a cycle termination condition, wherein the maximum iteration step number is usually selected from 100-2000. Meanwhile, when a threshold condition of the particle swarm optimal fitness value is set, the threshold condition needs to comprehensively consider the rapidity and the stability of speed control. For example, rotor angular velocity steady state jitter limit ω Δ 1.5rad/s, start-up rise time T of the motor r Is 0.1s, gamma z At a value of 15, the threshold for the termination condition may be selected to be 1.5.
When the particle adaptability value of each particle is calculated according to the formula (40), the position of each particle is required to be converted into corresponding sliding mode speed controller parameters and load torque observer parameters in turn, the motor is controlled to operate (or operate in a simulation system), and the angular speed omega of the rotor of the motor in the system is given * Being a sine wave signal, load torque T L Under the condition that the rotor angular speed is in a stable following state and suddenly changed, the speed response of the motor is obtained, and the tracking jitter omega of the rotor angular speed is determined according to the speed response z And tracking the delay time tau, and calculating according to the formula (40) to obtain a particle fitness value.
Among the parameters to be optimized, g max 、g min With a constraint g in between min ＜g max Corresponding to the constraint G min ＞G max . In each of the above steps, particles are randomly generatedWhen the position or the position of the particle is updated, first, the particle z i Parameter z in i6 (i.e. G) max ) According to the value range [ z 6min z 6max ]Randomly generating positions or performing position updates, then the particles z i Parameter z of i7 (i.e. G) min ) According to the value interval [ z i6 z 7max ]Randomly generating positions or performing position updates to make particles z i Satisfies the constraint condition G min ＞G max I.e. satisfies the constraint g min ＜g max 。ε 1 、ε 2 With a constraint condition epsilon between 1 ＜ε 2 When randomly generating a new position of a particle, or searching for a new position of a particle, first, the particle z i Parameter z in i8 (i.e.. epsilon.) 1 ) According to the value range [ z 8min z 8max ]Randomly generating positions or performing position updates, then the particles z i Parameter z of i9 (i.e.. epsilon.) 2 ) According to the value range [ z i8 z 9max ]Randomly generating positions or performing position updates to make particles z i Satisfies the constraint condition epsilon 1 ＜ε 2 。
In the periodic control process of the speed of the permanent magnet synchronous motor in the embodiment 2 of the motor drive control system of the high-voltage circuit breaker, the given value of the load torque calculated at the current k moment (or the k step) is set
Is marked as
Observed value of load torque
Is marked as
The moment k-1 is the previous periodic control process moment of the moment k, the given value of the load torque
Is marked as
Observed value of load torque
Is marked as
The moment k-2 is the previous periodic control process moment of the moment k-1, and the given value of the load torque
Is marked as
Observed value of load torque
Is marked as
When the feedback gain g is adjusted according to (a) in fig. 4, the periodic control process of the speed of the permanent magnet synchronous motor includes the following steps:
step one, detecting the rotor position theta, the rotor angular speed omega and the three-phase current i of the permanent magnet synchronous motor a 、i b And i c ；
Step two, according to three-phase current i a 、i b And i c Clark conversion is carried out on the permanent magnet synchronous motor to obtain current i under an alpha-beta axis coordinate system α 、i β According to the current i α 、i β Carrying out Park conversion on the rotor position theta to obtain a current i under a d-q axis coordinate system d 、i q ；
Thirdly, setting the feedback gain g of the load torque observer according to the load torque
Is adjusted;
step four, the load torque observer is used for observing the rotor angular speed omega and the current i q Observing the load torque to obtain a load torque observed value
Step five, the sliding mode speed controller gives the angular speed omega according to the input rotor * Rotor angular velocity ω and load torque observed values
Control calculation is carried out to obtain a given value of load torque
And q-axis torque current setpoint
Step six, the d-axis current controller sets a value i according to the d-axis torque current d * And the current i under the d-axis coordinate system d The difference value between the two is subjected to PI control operation to obtain a control voltage U under a d-axis coordinate system d (ii) a The q-axis current controller sets the value according to the q-axis torque current
And the current i under a q-axis coordinate system q The difference value between the two is subjected to PI control operation to obtain a control voltage U under a q-axis coordinate system q (ii) a According to the control voltage U under a d-q axis coordinate system d 、U q Carrying out Park inverse transformation to obtain a control voltage U under an alpha-beta axis coordinate system α 、U β ；
Step seven, controlling the voltage U under the alpha-beta axis coordinate system α 、U β As input of the SVPWM module, the SVPWM module controls a three-phase inverter to generate a three-phase alternating current power supply U a 、U b 、U c Thereby driving the permanent magnet synchronous motor to operate.
When the feedback gain g is adjusted according to (b) in fig. 4, in the step of the control process, the contents of the step four and the step five are performed first, and the content of the step three is performed later.
Inclusion of a compensated binomial load torque observation in the output term of a sliding-mode speed controller of equation (36)
Equivalent to the feedforward compensation of the load torque observed value in the formula (30) to the given value of the current regulator, under the condition that the given current part output by the sliding mode speed controller does not need to be adjusted greatly, the related influence caused by the disturbance of the load or the change of the system parameters can be counteracted, and the buffeting of the system is effectively weakened. Variation delta T of feedback gain g according to given value of load torque L Δ The algorithm for automatic adjustment avoids the problems of large torque observation fluctuation caused by selecting a fixed small feedback gain and long convergence time caused by selecting a fixed large feedback gain of a load torque observer, can quickly reduce the observation error of the load torque when the given subentry part in the load torque set value is changed or/and the load torque observed value part is changed due to the change of control parameters, model parameters and the like of a system or the disturbance of the load, and improves the observation effect and the rapidity and the accuracy of the motor speed control. The feedback gain g is automatically adjusted when the load torque given value changes, the load torque observed value can not change greatly, but the load torque observed value is caused to have large fluctuation due to the change of the rotor angular speed given value or/and the change of the rotor angular speed actual value to change the given subentry part in the load torque given value or the change of the given subentry part in the load torque given value due to the change of system model parameters, the feedback gain g is adjusted in advance, when the load torque observed value really generates an observation error, the response speed of an observer is accelerated, the observation error of the load torque observed value is quickly reduced, and the rapidity and the accuracy of the motor speed control are further improved.
In each of the above embodiments, the torque observation tracking overshoot limit is typically 1% to 10% of the rated torque of the motor, and specifically, the torque observation tracking overshoot limit is 2% of the rated torque, or 5% of the rated torque, or 10% of the rated torque, and so on. The load torque is suddenly changed from one fixed value to another fixed value, the moment when the sudden change starts to the moment when the load torque observer outputs an observed value and stably enters the range of the steady-state jitter limit value of load torque observation is a torque observation transition process, and the tracking adjustment time refers to the time of the transition process; the load torque observation steady state jitter refers to an error between an observation torque instantaneous value and a load torque when the load torque is unchanged and the load torque observer is in a steady state, wherein the error comprises an observation error caused by buffeting of the sliding mode observer and an observation error caused by interference reasons other than load fluctuation, or the observation error caused by buffeting of the angular speed of the rotor and the observation error caused by interference reasons other than load fluctuation of the state observer; the load torque observation steady-state jitter limit value is the maximum absolute value of the load torque observation steady-state jitter allowed by the load torque observer; the load torque observation steady-state jitter limit is generally the same as the maximum value of the load torque observation steady-state error allowed by the system; the load torque observed steady state jitter limit is typically 1% to 5% of the rated torque of the motor, specifically, the load torque observed steady state jitter limit is 1% of the rated torque, or 2% of the rated torque, or 5% of the rated torque, and so on. The torque observation tracking overshoot refers to that the load torque is suddenly changed from one constant value to another constant value, and the observed value output by the load torque observer exceeds the maximum deviation value of the load torque after sudden change. When the observed steady state jitter of the load torque is within a range near the observed steady state jitter limit of the load torque, for example, within a range of 95% to 105%, or within a range of 98% to 102%, the observed steady state jitter of the load torque is deemed to have increased to the observed steady state jitter limit of the load torque. The sliding mode speed controller is in a stable state, namely the sliding mode speed controller is stably in a sliding mode; the rotor angular speed steady-state jitter refers to a difference value between an instantaneous value and a steady-state value of the angular speed of the motor rotor in a steady state, and the rotor angular speed steady-state jitter limit value is a maximum absolute value of the rotor angular speed steady-state jitter allowed by a system. In the load torque observer, the sliding mode observer of the embodiment 1 being in a stable state means that the sliding mode observer is stably in a sliding mode; the state observer of embodiment 2 being in a steady state refers to an operating state of the state observer after a transient process of torque observation. The rotor angular speed steady-state jitter refers to a difference value between an angular speed instantaneous value and a steady-state value of the motor rotor in a steady state, and the rotor angular speed steady-state jitter limit value is a maximum absolute value of the rotor angular speed steady-state jitter allowed by a system; the rotor angular velocity steady-state jitter limit is generally the same as the maximum value of the rotor angular velocity steady-state error allowed by the system.
In the invention, the motor of the high-voltage circuit breaker motor driving control system is a permanent magnet synchronous motor, and the high-voltage circuit breaker motor driving control system is a permanent magnet synchronous motor speed control system. The speed control system of the permanent magnet synchronous motor and the speed control and parameter optimization method of the permanent magnet synchronous motor provided by the invention can be used for the drive control of a high-voltage circuit breaker motor and can also be used for other application occasions of the permanent magnet synchronous motor.
In addition to the technical features described in the specification, other technical features related to the invention are the conventional technical skill which is mastered by a person skilled in the art. For example, the q-axis current controller and the d-axis current controller adopt PI controllers for control and selection of controller parameters, the sliding mode speed controller for selection of control parameters, the position and speed detection module uses a rotary transformer or a photoelectric encoder for detection of the rotation angle and the rotation speed of the rotor of the permanent magnet synchronous motor, and the Clarke transformation module, the Park inverse transformation module, the SVPWM module, and the transformation method and the application method of the three-phase inverter, etc., all of which are conventional techniques grasped by those skilled in the art.
Claims (6)
1. A permanent magnet synchronous motor control and parameter optimization method based on load torque observation is characterized in that the observed value of a load torque observer is sent to a speed sliding mode controller, and q-axis given current output by the sliding mode speed controller comprises a calculation item of the load torque observed value; the parameters of the sliding mode speed controller and the parameters of the load torque observer are optimized and set uniformly by adopting a particle swarm algorithm, and the target function is
Q 3 ＝ω z +γ z τ；
Wherein, ω is z For tracking the rotor angular velocity jitter, tau is the tracking delay time, gamma z Adjusting the coefficients and gamma for fitness balance z ＞0；
When parameters of the sliding mode speed controller and parameters of the load torque observer are optimized and integrated uniformly by adopting a particle swarm algorithm, the angular speed omega of the rotor is given * Is a sine wave signal; rotor angular velocity tracking jitter omega z For the buffeting amplitude of the rotor angular velocity omega, the tracking delay time tau is the rotor angular velocity omega and the given rotor angular velocity omega * The delay time in between.
2. The PMSM control and parameter optimization method based on load torque observation as claimed in claim 1, wherein rotor angular velocity tracking jitter ω is obtained z The method comprises the following steps: rotor angular velocity tracking jitter omega z Tracking jitter omega for multiple period rotor angular velocity peaks z1 And rotor angular velocity valley tracking jitter omega z2 Average value of (d);
obtaining the tracking jitter omega of the rotor angular velocity peak z1 The method of (1) is that the average value of 2 times of maximum sampling values of the rotor angular speed in the peak top area is taken as the maximum value of the peak top, and the minimum sampling value between the sampling moments of the 2 times of maximum sampling values is taken as the minimum value of the peak top; rotor angular velocity peak tracking jitter omega z1 Is the absolute value of the difference between the peak-top maximum and the peak-top minimum;
obtaining rotor angular velocity valley bottom tracking jitter omega z2 The method comprises the following steps: taking the average value of 2 times of minimum sampling values of the angular speed of the rotor in a valley bottom area as a valley bottom minimum value, and taking the maximum sampling value between the sampling moments of the 2 times of minimum sampling values as a valley bottom maximum value; rotor angular velocity valley bottom tracking jitter omega z2 The absolute value of the difference between the minimum value of the bottom of the valley and the maximum value of the bottom of the valley;
the method for acquiring the tracking delay time τ is as follows: tracking delayTime tau is a multiple period peak-to-peak tracking delay time tau 1 Sum bottom tracking delay time tau 2 Average value of (d);
peak top tracking delay time tau 1 The absolute value of the time difference between the moment of the maximum value of the angular speed of the rotor and the moment of the maximum value of the angular speed of the given rotor; valley tracking delay time tau 2 The absolute value of the time difference between the moment of the minimum value of the angular speed of the rotor and the moment of the minimum value of the angular speed of the given rotor;
the method for acquiring the maximum time and the minimum time of the rotor angular speed is to take the central point time of the rotor angular speed between the 2 maximum sampling values in the peak top area as the maximum time of the rotor angular speed and the central point time of the rotor angular speed between the 2 minimum sampling values in the valley bottom area as the minimum time of the rotor angular speed.
3. The PMSM control and parameter optimization method based on load torque observation as claimed in claim 2, wherein the state variable of the sliding mode speed controller is
Where ω is the rotor angular velocity, ω * Is a given rotor angular velocity; the sliding mode surface of the sliding mode speed controller is s y ＝c y y 1 +y 2 ，c y Is a slip form face parameter, and c y Is greater than 0; slip-form speed controller output load torque set value
And q-axis torque current setpoint
Is composed of
Wherein J is the moment of inertia, p is the motor pole pair number, psi f Is a permanent magnet flux linkage, B is a coefficient of friction,
is a load torque observation; coefficient mu 1 Coefficient of μ 2 Coefficient of μ 3 Coefficient of sum μ 4 Exponential rate of approach coefficient for speed sliding mode control, and mu 1 ＞0，μ 2 ＞0，1＜μ 3 ＜2，μ 4 ＞0；
The load torque observer depends on the angular speed omega and the current i of the rotor q Observing the load torque to obtain a load torque observed value
The load torque observer is
Wherein,
is an estimated value of the angular velocity of the rotor, g is a feedback gain of the load torque observer and g is less than 0;
The load torque observer is used for setting a load torque according to the load torque output by the sliding mode speed controller
Is used to adjust the feedback gain g of the load torque observer.
4. Such asThe method for permanent magnet synchronous motor control and parameter optimization based on load torque observation of claim 3, wherein the load torque observer is used for setting the load torque according to the load torque output by the sliding mode speed controller
The method for adjusting the feedback gain g of the load torque observer by the change of (2) is as follows:
step A, a load torque observer measures load torque T L Observing to obtain the observed value of the load torque
The sliding mode speed controller carries out control operation to obtain
Step B, calculating
Step C, judgment
Whether or not greater than epsilon 2 (ii) a When in use
Greater than epsilon 2 Taking feedback gain g equal to g min And withdrawing;
when DeltaT is less than or equal to epsilon 2 When the step is finished, entering the step D;
step D, judgment
Whether or not less than epsilon 1 (ii) a When in use
Less than epsilon 1 Taking feedback gain g equal to g max And withdrawing;
when in use
Is greater than or equal to epsilon 1 Entering the step E;
step E, feedback gain g is according to formula
Exiting after calculation;
ε 1 comparing thresholds, e, for lower limits of torque variation 2 Comparing threshold values for upper limits of torque variation, and 0 & ltepsilon 1 ＜ε 2 ；g max For high value of feedback gain, g min Is a low value of feedback gain, and g min ＜g max ＜0。
5. The load torque observation-based permanent magnet synchronous motor control and parameter optimization method according to claim 4, wherein parameters of the sliding mode speed controller and the load torque observer are optimized and set by a particle swarm optimization, and a parameter vector to be optimized is theta z2 ＝[c y ，μ 1 ，μ 2 ，μ 3 ，μ 4 ，G max ，G min ，ε 1 ，ε 2 ，β]；g max And G max In a relationship of
g min And G min In a relationship of
k W The relationship with beta is
T N Is the rated torque of the motor; beta is more than 0.
6. The PMSM control and parameter optimization method based on load torque observation according to any one of claims 1-5, characterized in that rotor position θ and three-phase current i of the PMSM are detected a 、i b And i c (ii) a According to three-phase current i a 、i b And i c Clark conversion is carried out on the permanent magnet synchronous motor to obtain current i under an alpha-beta axis coordinate system α Current i β According to the current i α Current i β Carrying out Park conversion on the rotor position theta to obtain a current i under a d-q axis coordinate system d Current i q 。
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| CN114900086A (en) | 2022-08-12 |
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