CN114640399A

CN114640399A - Signal processing method and device

Info

Publication number: CN114640399A
Application number: CN202011481341.7A
Authority: CN
Inventors: 李润洲; 芮佳依; 黄勤; 吴志航
Original assignee: Huawei Technologies Co Ltd
Current assignee: Huawei Technologies Co Ltd
Priority date: 2020-12-15
Filing date: 2020-12-15
Publication date: 2022-06-17

Abstract

A signal processing method and device, the method comprising: the receiving device receives the carrier signal, converts the carrier signal into a first electric signal and then converts the first electric signal into a first signal; the receiving device processes the first signal according to a set demodulation method to obtain a first information sequence of the first signal; the receiving device determines a standard correction value and a first correction value of the first information sequence according to a preset error correction code, determines an angle of phase change of the first signal according to the standard correction value and the first correction value, and processes the phase of the first signal. In the method, the receiving device can determine the standard correction values of a plurality of phase angles and the correction value of the first information sequence according to a preset error correcting code, and further determine and process the angle of the phase change of the first signal according to the correlation value between the correction value of the first information sequence and each standard correction value, so that the phase jump of the signal can be efficiently solved.

Description

Signal processing method and device

Technical Field

The present application relates to the field of communications technologies, and in particular, to a method and an apparatus for processing a signal.

Background

With the development of high-speed communication systems, such as coherent optical communication systems, phase jump becomes a common problem. In a coherent optical communication system, a phase jump of a signal is generally caused by dispersion, a nonlinear effect of an optical fiber, laser phase noise, and the like. The phase jump is specifically expressed in that when the receiver recovers the phase of the received carrier signal by means of phase inversion, a periodic multivalued problem (i.e., phase ambiguity) occurs. The phase jump causes symbol errors of continuous information, and the errors are difficult to correct by an error correcting code, thereby greatly affecting the recovery and processing of signals.

At present, the method is used for solving the problem of phase jump, and mainly comprises four schemes, namely differential coding and decoding, pilot symbol auxiliary carrier phase recovery, redundant code mapping and blind algorithm. However, the prior art still has a large disadvantage, and the problem of signal phase jump cannot be efficiently solved.

Disclosure of Invention

The application provides a signal processing method and a signal processing device, which are used for efficiently solving the problem of signal phase jump.

In a first aspect, an embodiment of the present invention provides a signal processing method, which may be executed by a sending apparatus, or may be executed by a chip in the sending apparatus, and is not limited thereto. The method comprises the following steps: firstly, acquiring a first signal, and coding the first signal according to a preset error correcting code to obtain a coding sequence of the first signal; then, processing the coding sequence of the first signal by using a set modulation method to obtain an information sequence of the first signal; further converting the first signal to obtain a first electrical signal, wherein the first electrical signal carries an information sequence of the first signal; and finally, converting the first electric signal to obtain a carrier signal and sending the carrier signal.

Through the design, the sending device side acquires a first signal to be processed, and codes the signal by using a preset error correcting code, so that the first signal is converted into a signal which can be communicated, transmitted or stored, namely a coding sequence of the first signal; then, the coded sequence of the first signal is processed by using the set modulation method to obtain the information sequence of the first signal. The first signal is further converted into an electric signal, the electric signal is converted into a carrier signal so as to carry an information sequence of the first signal, finally the carrier signal carrying the information sequence is sent so as to be converted into the first signal after a receiving device receives the carrier signal, and the phase change of the first signal is further detected by using a corresponding preset error correcting code, so that the problem of phase jump of the signal in the transmission process can be effectively solved, and the transmitted signal can be accurately recovered.

In a possible design, after the coded sequence of the first signal is processed according to a set modulation method to obtain the information sequence of the first signal, the information sequence of the first signal may be further adjusted by using a digital processing technique.

Through the design, after the information sequence of the first signal is obtained according to the coding sequence of the first signal by the set modulation method, the information sequence of the signal is adjusted by using a digital processing technology, and the loss of the first signal sequence caused by the interference in a channel in the transmission process can be compensated in advance.

In one possible design, the generator matrix G of the predetermined error correction code includes k rows G₁,g₂,......g_kWherein g is_jIs the jth row vector of the generator matrix, j is a positive integer not greater than k, g₀All-zero row vector, g, expressed as the number of rows of the matrix being 1₀The length of (b) is the column width of the generator matrix; the first verification matrix H of the preset error correcting code comprises m rows H₁,h₂,......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀All-zero row vector, h, expressed as the number of rows of the matrix being 1₀Is the column width of the first verification matrix; the generator matrix G may satisfy the following formula requirement:

and

or the first verification matrix H, satisfying the following formula:

and f_i(h₀)·H^T≠0；

Wherein rank (·) represents the rank of the matrix, i represents the angle, and f_i(.) representing the corresponding sequence transformation function when the phase of the signal changes by i degrees, p_i(.) represents the position permutation function of the corresponding sequence when the phase of the signal changes by i degrees.

Through the design, any one of a generating matrix or a first verification matrix of the preset error correcting code meets the formula, or both the generating matrix and the first verification matrix meet the formula, so that the error correcting code can be used in the application, and therefore the flexibility of setting the error correcting code is high.

In a second aspect, an embodiment of the present invention provides a signal processing method, where the method may be executed by a receiving apparatus, and may also be executed by a chip in the receiving apparatus. The method comprises the following steps: receiving a carrier signal, wherein the carrier signal can be converted to obtain a first electric signal; then the receiving device converts the first electric signal into a first signal; the receiving device processes the first signal according to a set demodulation method and acquires a first information sequence of the first signal; secondly, the receiving device can determine a standard correction value and a first correction value of the first information sequence according to a preset error correcting code; the further receiving means may determine an angle of phase change of the first signal based on the standard correction value and a first correction value of the first information sequence; and finally, the receiving device processes the phase of the first signal according to the angle of the phase change of the first signal.

Through the design, after the receiving device receives the carrier signal, the carrier signal is processed to obtain a first signal, so that the signal can be processed subsequently. And then the receiving device processes the first signal by using a set demodulation method to obtain a corresponding first information sequence. Further, the receiving device uses a preset error correcting code to determine a standard correction value of the signal sequence and a correction value of the first information sequence, and then compares the correction value of the first information sequence with the standard correction value of the signal sequence to determine the angle of the phase change of the first signal. Finally, the receiving device adjusts the phase of the first signal according to the angle of the phase change, so that the information sequence of the first signal with the correct phase can be obtained for the subsequent correct decoding.

In a possible design, after the receiving device converts the first electrical signal into a first signal, the receiving device may also use digital processing techniques to adjust the first signal.

With this design, since the carrier signal transmitted by the transmitting apparatus generates some loss during transmission, in this design, the first signal obtained by processing the carrier signal is adjusted to compensate for the loss of the signal generated in the transmission channel, so that the receiving apparatus can accurately recover the first signal transmitted by the transmitting apparatus as much as possible.

In one possible design, the receiving device determines the standard correction value according to a preset error correction code, and the method includes: the receiving device determines a generating matrix and a first verification matrix according to the preset error correcting code; and the receiving device calculates the standard correction value according to an information sequence of a preset signal, the generating matrix, the first verification matrix and a preset first correction formula.

With this design, the receiving apparatus can determine the generation matrix and the first verification matrix of the error correction code according to a preset error correction code. The receiving device may further obtain a standard correction value according to the information sequence of the preset signal, the generation matrix and the first verification matrix of the error correction code, and the preset first correction formula, and match the correction values of the other signal sequences with the standard correction value by using the standard correction value as a reference, so as to subsequently determine the angle of the phase change of the first signal.

In a possible design, the calculating, by the receiving apparatus, the standard correction value according to an information sequence of a preset signal, the generator matrix, the first verification matrix, and a preset first correction formula includes: the receiving device multiplies the information sequence of the preset signal by the generating matrix to obtain a second information sequence; the receiving device determines N phase-changed third information sequences corresponding to N angles of phase change of the preset signal according to the second information sequence; n is a positive integer greater than 0; and the receiving device substitutes each third information sequence and the transposed matrix of the first verification matrix into the preset first correction formula to calculate and obtain N standard correction values.

Through the design, the receiving device can effectively calculate and obtain the corresponding standard correction value according to the information sequence of the preset signal, the generation matrix and the first verification matrix of the preset error correcting code and the preset first correction formula.

In one possible design, the determining, by the receiving device, a first correction value of the first information sequence according to a preset error correction code includes: the receiving device may determine a generator matrix and a first verification matrix according to the preset error correction code; then the receiving device determines a fourth information sequence according to the first information sequence, wherein the fourth information sequence is the information sequence after the phase angle of the first signal is changed; and finally, the receiving device substitutes the fourth information sequence and the first verification matrix into a preset first correction formula to obtain a first correction value of the first information sequence.

By means of the design, the receiving device can effectively calculate the first correction value of the first information sequence according to the first information sequence of the first signal, the generation matrix and the first verification matrix of the preset error correcting code, so that the angle of the phase change of the first signal can be determined by checking the first correction value of the first information sequence.

In one possible design, the generator matrix of the predetermined error correction code includes k rows g₁,g₂,......g_kWherein g is_jIs the jth row vector of the generator matrix, j is a positive integer not greater than k, g₀All-zero row vector, g, expressed as the number of rows of the matrix being 1₀The length of (b) is the column width of the generator matrix; m rows h are contained in the first verification matrix of the preset error correcting code₁,h₂,......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀All-zero row vector, h, expressed as the number of rows of the matrix being 1₀Is the column width of the first verification matrix; wherein the generator matrix G satisfies the following formula:

and

or the first verification matrix H, satisfies the following formula:

and f_i(h₀)·H^T≠0；

Through the design, any one of a generating matrix or a first verification matrix of a preset error correcting code meets the formula, or both the generating matrix and the first verification matrix meet the formula, so that the error correcting code can be used for detecting the phase change of the first signal, and therefore the flexibility of setting the error correcting code is high.

In one possible design, the preset first correction formula satisfies:

S_i＝f_i(x)*H^T

wherein i represents the size of the angle, S_iIndicating the corresponding correction value for a phase change of the signal by i degrees, f_i(.) representing the corresponding sequence transformation function when the phase of the signal changes by i degrees, x representing the row vector with the matrix row number 1, the length of x representing the column width of the first verification matrix, H^TA transpose matrix representing the first validation matrix.

Through the design, the correction values corresponding to different signal sequences can be effectively calculated by using the first correction formula, and the universality is good.

In one possible design, the receiving device determining the angle of the phase change of the first signal based on the standard correction value and the first correction value of the first information sequence includes: the receiving device determines that the standard correction values comprise N corresponding standard correction values when the phase of a preset signal changes by N different angles, each angle corresponds to one standard correction value, and N is a positive integer greater than 0; the receiving device respectively carries out correlation value calculation on the N standard correction values and the first correction value to obtain N correlation values; when the receiving device determines that a first correlation value of the standard correction value and the first correction value corresponding to the phase change of the preset signal by an ith angle is maximum and the first correlation value meets a set condition, the receiving device determines that the phase change angle of the first signal is the ith angle; i is a positive integer value greater than 0 and less than or equal to N; the set conditions comprise that the first correlation value is larger than a first set threshold value, and errors between the first correlation value and other N-1 correlation values are larger than a second set threshold value.

Through the design, the standard correction values comprise N standard correction values corresponding to N different angles of phase change of the preset signal, therefore, the receiving device can determine the correlation value of each standard correction value and the correction value of the first information sequence by comparing the correction value of the first information sequence with the N standard correction values, and select the standard correction value which meets the set condition and has the maximum correlation value, so that the angle of phase change of the first signal can be effectively determined according to the phase angle corresponding to the standard correction value with the maximum correlation value.

In a possible design, after the receiving apparatus processes the phase of the first signal according to the angle of the change of the phase of the first signal, the receiving apparatus obtains the information sequence of the first signal after the phase processing; and the receiving device decodes the information sequence of the first signal after the phase processing according to the preset error correcting code to obtain the information sequence of the first signal after decoding.

Through the design, the receiving device acquires the correct information sequence of the first signal after processing the phase of the first signal, and then the receiving device can decode the information sequence of the first signal according to the corresponding error correcting code, so that the decoded information sequence of the first signal is accurately acquired.

In a third aspect, the present application provides a signal processing apparatus, which may be used as a transmitting apparatus and has the function of implementing the method according to the first aspect or any one of the possible designs of the first aspect. The function can be realized by hardware, and can also be realized by executing corresponding software by hardware. The hardware or software includes one or more modules corresponding to the functions described above. For example, the device includes a transmitting unit and a coding unit, a modulation unit, a digital processing unit (optional), a digital-to-analog conversion unit, a first conversion unit, a transmitting unit, etc.

In a fourth aspect, the present application provides a signal processing apparatus, which may be used as a receiving apparatus and has the function of implementing the method according to the second aspect or any one of the possible designs of the second aspect. The function can be realized by hardware, and can also be realized by executing corresponding software by hardware. The hardware or software includes one or more modules corresponding to the functions described above. For example, the device includes a receiving unit, a first converting unit, a digital-to-analog converting unit, a digital processing unit (optional), a demodulating unit, a phase-jump detecting unit, a decoding unit, and the like.

In a fifth aspect, this embodiment of the present application further provides a computer storage medium, where a software program is stored, and the software program, when read and executed by the encoder, the modulator, the digital processor, the digital-to-analog converter, and the first converter, may implement the method provided in the first aspect or any one of the designs.

In a sixth aspect, this embodiment of the present application further provides a computer storage medium, where a software program is stored, and the software program, when read and executed by the first converter, the digital-to-analog converter, the digital processor, the demodulator, the phase-jump detector, and the decoder, can implement the method provided in the second aspect or any one of the designs.

In a seventh aspect, embodiments of the present application further provide a computer program product containing instructions, which when run on a computer, cause the method provided in the above first aspect or any one of the designs to be performed, or cause the method provided in the above second aspect or any one of the designs to be performed.

In an eighth aspect, an embodiment of the present application provides a chip system, where the chip system includes a processor, configured to support a sending apparatus to implement the functions recited in the first aspect, or support a receiving apparatus to implement the functions recited in the second aspect.

In one possible design, the system-on-chip may also include a memory for storing necessary program instructions and data.

In a ninth aspect, an embodiment of the present application further provides a communication system, where the communication system includes a sending apparatus for executing the method provided in the first aspect or any design thereof, a receiving apparatus for executing the method provided in the second aspect or any design thereof, and a transmission channel for implementing communication between the sending apparatus and the receiving apparatus.

Technical effects that can be achieved in the third aspect to the ninth aspect may be described with reference to technical effects that can be achieved by any one of the designs in the first aspect or the second aspect, and will not be described repeatedly herein.

Drawings

Fig. 1 is a schematic diagram of a communication system suitable for use in embodiments of the present application;

fig. 2 is a schematic diagram of a communication system according to a signal processing method provided in an embodiment of the present application;

fig. 3 is a schematic flowchart of a signal processing method according to an embodiment of the present disclosure;

fig. 4A is a schematic diagram of a QPSK constellation according to an embodiment of the present application;

fig. 4B is a schematic diagram of a 16QAM constellation provided in the embodiment of the present application;

fig. 4C is a schematic diagram illustrating sequence transformation of symbols under 16QAM according to an embodiment of the present application;

fig. 4D is a schematic diagram of permutation of sequence positions of symbols in QPSK according to an embodiment of the present application;

fig. 4E is a schematic diagram of permutation of sequence positions of symbols under 16QAM according to an embodiment of the present application;

fig. 5 is a schematic structural diagram of a phase transition detector and a decoder according to an embodiment of the present disclosure;

fig. 6 is a schematic flowchart of determining a phase jump angle of a signal according to an embodiment of the present application;

FIG. 7A is a diagram illustrating a single row validation submatrix according to an embodiment of the present disclosure;

FIG. 7B shows a syndrome Hamming weight-L according to an embodiment of the present application_φA schematic diagram of a curve of (a);

FIG. 8A is a schematic diagram of a decoding system for phase jump detection according to an embodiment of the present application;

fig. 8B is a schematic structural diagram of sliding window decoding according to an embodiment of the present application;

fig. 9 is a schematic structural diagram of a signal processing apparatus according to an embodiment of the present application;

fig. 10 is a schematic structural diagram of a signal processing apparatus according to an embodiment of the present application;

fig. 11 is a schematic structural diagram of a signal processing apparatus according to an embodiment of the present application;

fig. 12 is a schematic structural diagram of a device for processing a signal according to an embodiment of the present application.

Detailed Description

The technical solutions in the embodiments of the present application will be described below with reference to the drawings in the embodiments of the present application.

Hereinafter, some terms in the embodiments of the present application are explained to facilitate understanding by those skilled in the art.

1) The first signal referred to in the embodiments of the present application may be an index signal; a digital signal may refer to a signal in which the independent variable and the dependent variable are both discrete values, and the independent variable of such a signal may be represented by an integer and the dependent variable may be represented by one of finite numbers. In computers, the magnitude of a digital signal is often represented by a binary number with a limit. The digital signal has strong anti-interference capability, and can be applied to communication technology and information processing technology.

2) The carrier signal referred to in the embodiments of the present application may refer to a waveform, generally a sine wave, that is modulated and used to transmit a signal. Generally, ordinary signals (sound and images) are loaded on high-frequency signals with certain frequency, and the amplitude of the signals after loading changes along with the change of the ordinary signals (amplitude modulation), and can be phase-modulated and frequency-modulated. The carrier signal generally requires that the frequency of the sinusoidal carrier be much higher than the bandwidth of the modulated signal, otherwise aliasing occurs, distorting the transmitted signal.

The carrier signal referred to in the embodiments of the present application may be a high-frequency wave used for carrying signal information, such as a telecommunication wave or an optical signal, and is not limited specifically.

3) The signal modulation related in the embodiment of the present application is mainly to move a signal spectrum to a high-frequency channel for transmission in order to ensure that a communication signal reaches a receiving device for long-distance signal transmission, and therefore, the modulation can be a process of loading a signal to be transmitted to a high-frequency signal. The most basic modulation method mainly comprises the following steps: amplitude Shift Keying (ASK), Frequency-Shift Keying (FSK), and Phase Shift Keying (PSK). Other Modulation methods are improved or combined based on the most basic Modulation method, such as Quadrature Amplitude Modulation (QAM) obtained by combining Amplitude Modulation and Phase Modulation, Quadrature Phase Shift Keying (QPSK), and the like.

In which QAM modulation uses the amplitude and phase of a carrier to convey information bits, maps one bit to a vector having a real part and an imaginary part, then modulates onto two carriers that are orthogonal in the time domain, and then transmits. The more bits that are represented on a carrier at a time with amplitude and phase, the more efficient it is to transmit. In general, the modulation order M of QAM satisfies M-2^2mM is a positive integer, such as 4QAM, 16QAM, 64QAM, 256QAM, etc., taking 16QAM as an example, which specifies 16 states of amplitude and phase, 1 binary number of 4 bits can be transmitted at a time.

QPSK, also known as quadrature absolute phase shift modulation, mainly uses four phases of a carrier to represent digital information, each carrier phase representing two bits of information, and thus each quad-symbol is called a bi-bit symbol. QPSK mainly includes both absolute phase shift and relative phase shift. Since the absolute phase shift method has a problem of phase ambiguity, the relative phase shift method DQPSK is mainly used in practice. The modulation mode has high frequency spectrum utilization rate and strong anti-interference performance, and can be applied to various communication systems.

4) Signal demodulation, as referred to in the embodiments of the present application, is a process by which messages can be recovered from a modulated signal carrying information. In various information transmission or processing systems, a transmitting device modulates a carrier wave to produce a signal carrying this message. The receiving end must recover the transmitted message for use, which is demodulation.

Demodulation is the inverse process of modulation, so the modulation method corresponds to the demodulation method, and if the modulation method is different, the demodulation method is different.

5) The signal coding referred to in the embodiments of the present application is to code a signal (e.g., a bit stream) or data into a signal that can be communicated, transmitted, or stored. The specific encoding method is not specifically limited in the present application.

6) The first converter referred to in the embodiments of the present application may be used to convert an analog electrical signal into a carrier signal, and since there may be a plurality of types of carrier signals, the first converter may include a plurality of types in the embodiments of the present application, and the present application is not particularly limited. For example, when the carrier signal is an optical signal carrying information, then the first converter may be an optical-to-electrical converter.

7) The plurality referred to in the embodiments of the present application means two or more.

In addition, it should be understood that in the description of the present application, the "phase jump" described in the present application may be simply referred to as "phase jump", and both have the same meaning. Additionally, the terms "first," "second," and the like, as used herein, are used for descriptive purposes only and not for purposes of indication or implication for relative importance, nor for order of indication or implication.

Please refer to fig. 1, which is a schematic diagram of a communication system applicable to an embodiment of the present application, the communication system mainly includes a transmitter, a receiver, and physical channels (the communication system may also use optical fiber, wireless, etc. physical channels). For example, a transmitter processes a signal to be transmitted to obtain a carrier signal, and transmits the carrier signal to a receiver through a physical channel, and after receiving the carrier signal, the receiver recovers the phase of the carrier signal. However, the phase jump of the signal will affect the recovery and processing of the carrier signal by the transmitter.

For the above problem of phase jump, the prior art mainly includes the following four schemes:

the first scheme is as follows: the method mainly utilizes differential coding and error correcting codes to solve the problem of phase jump, firstly codes information to be transmitted through a forward error correcting code FEC coder to obtain coded information, and further transmits the coded information to a transmission channel after differential mapping is carried out on the coded information through a differential coder. Since the differential encoder encodes according to each symbol of the signal and its previous symbol, i.e. the symbol output by the differential encoder only represents the change between the two symbols and does not represent the value of the input symbol. Therefore, when a code word transmitted through a channel has a phase jump error, the correlation between symbols within the coverage of the phase jump error is constant, and an output signal within the coverage of the phase jump can be recovered by a differentially encoded soft decoder.

However, this scheme often reduces the performance cost of differential encoding in order to cooperate with a differential encoder, and a maximum a posteriori probability algorithm, such as BCJR (the letter is the first letter of the names of four inventors Bahl, Cocke, Jelinek, and Raviv) needs to be adopted in decoding by a receiver, which has higher computational complexity, thereby resulting in higher time delay and higher cost.

The second scheme is as follows: the problem of phase jump is mainly solved by inserting known data (such as pilot symbols) into a data frame to assist carrier phase recovery and combining an error correction code. After the receiver receives the signal, the receiver can detect the phase jump through the pilot symbols, and calculate the angle of the phase jump, correct the data on the unit short frame, and combine the Error Correction coding, such as Low-Density Parity-Check Code (LDPC), Forward Error Correction (FEC), etc., to eliminate the symbol Error caused by the phase jump, thereby improving the correctness of the receiver decoding.

However, the number of transmission symbols is increased in the scheme, which not only reduces the code rate, but also makes the communication system overhead large, and when the interleaver is used to disperse the symbol errors, the decoding delay is also large.

In the third scheme: mainly, the constellation point number is larger than the code word to be mapped by selecting a specific modulation mode, and then the mapping from the code word to the constellation point is carried out according to a designed rule. At a receiving end, when the received signal is determined to generate phase jump, the position of the demodulated constellation point does not accord with a preset rule, so that the code word can be judged to generate the phase jump and error correction can be carried out. For example, using a Quadrature Amplitude Modulation (QAM) constellation of Gray Mapping (Gray Mapping), under a typical phase jump angle of plus or minus ± 90 ° and 180 °, a receiving end may determine whether a phase jump occurs according to a property that parity of a bit number corresponding to a symbol on the constellation is 1 is changed. The receiving end can solve the error of + -90 DEG phase jump by an equalization process (for example, correct by a reverse mapper), and can detect and correct the error of 180 DEG phase jump by the distribution of multi-path signals.

However, in this scheme, taking 16-QAM as an example, in order to ensure that the receiving end can modulate the signal into an odd number of QAM symbols, a parity bit needs to be added to every n data bits, which results in a low code rate during transmission. In addition, the parity check is easily affected by random noise in a channel during transmission, and under the condition that the signal-to-noise ratio is not high enough, a certain bit judgment error is caused by the random noise, so that the judgment of phase jump is affected. In addition, the receiving end processes the data into a plurality of paths of signals for error correction coding, and receives long data at one time for better error correction performance. Moreover, when the receiving end detects that the 180-degree phase jump occurs in the signal, the decoding needs to be performed again after the bit of some signal branches is inverted, so that the delay is increased, and the decoding of different branches is asynchronous, which results in extra calculation resource overhead of the decoder.

A fourth scheme: the problem of phase jump is mainly solved through error correction coding. At present, the scheme mainly aims at pi angle phase jump under BPSK, and the phase jump of pi angle is equivalent to negation of each bit of a code word, namely equivalent to adding a full 1 vector to the code word. However, in this scheme, the receiving end does not include all 1 codewords by screening or constructing linear block codes such as LDPC codes, and once pi angle phase jump occurs, many errors may remain after conventional decoding, so as to determine that phase jump occurs, flip each bit, and then perform decoding. Or, the received code word and the code word after the turnover are subjected to iterative decoding for a plurality of times, the convergence conditions of the two groups of likelihood ratios are compared, the better group is obtained to continue decoding, and then the decoding result is output.

However, the technical scheme is only applicable to BPSK, can only be used for detecting phase jump of pi angle, and cannot be applied to higher order modulation formats, so the application range of the scheme is limited.

In summary, the prior art still has a large disadvantage and cannot effectively solve the problem of signal phase jump.

Therefore, in the method, a sending device acquires a first signal, and then the sending device encodes the first signal according to a preset error correcting code to obtain an encoding sequence of the first signal; then, the sending device processes the coding sequence of the first signal according to a set modulation method to obtain an information sequence of the first signal; the sending device converts the first signal through a digital-to-analog conversion module to obtain a first electric signal, wherein the first electric signal carries an information sequence of the first signal; and finally, the sending device sends the carrier signal after converting the first electric signal into the carrier signal through the first conversion module. After receiving the carrier signal, the receiving device converts the carrier signal into a first electric signal through a first conversion module, and then converts the first electric signal into a first signal through a digital-to-analog conversion module; the receiving device further processes the first signal according to a set demodulation method to acquire a first information sequence of the first signal; then, according to a preset error correcting code, a standard correction value and a first correction value of the first information sequence are determined, and then, according to the standard correction value and the first correction value of the first information sequence, an angle of phase change of the first signal is determined; and finally, the receiving device processes the phase of the first signal according to the angle of the phase change of the first signal. In the method, the receiving device can determine the standard correction values of a plurality of phase angles and the correction value of the first information sequence according to a preset error correcting code, and further determine and process the angle of the phase change of the first signal according to the correlation value between the correction value of the first information sequence and each standard correction value, so that the phase jump of the signal can be better solved.

The embodiments of the present application provide a signal processing method, which relates to a transmitting device and a receiving device in the above communication system, and the following describes specific structures of the transmitting device and the receiving device in detail.

Referring to fig. 2, the transmitting apparatus may mainly include an FEC encoder, a modulator, a digital processor (optional), and an optical-to-electrical converter. The receiving device may mainly include an optical-to-electrical converter, a digital processor (optional), a demodulator, a phase-hopping detector, and an FEC decoder.

The functions performed by the respective hardware devices in the transmitting apparatus are described in detail below:

and the FEC encoder is used for encoding the source bit stream b by adopting an FEC code preset in the application after receiving the source bit stream b to obtain a bit stream sequence c, and the output bit stream sequence c.

It should be noted that the preset FEC code pattern in the present application needs to satisfy the following formula one and formula two in step S301 of fig. 3, or satisfy the following formula three and formula four in step S301 of fig. 3; the specific encoding method is not specifically limited in the embodiments of the present application.

The modulator: after receiving the bit stream sequence c output by the FEC encoder, the modulator may generate a (polarization-multiplexed) QAM symbol stream S from the bit stream sequence c according to QPSK and QAM gray modulation mapping scheme of square constellation, and output the symbol stream S.

A Digital processor, which is optional, in practical system use, in order to pre-compensate other losses caused by the channel, Digital Signal Processing (DSP) technology is usually adopted to perform operations such as pulse shaping and spectrum filtering on the received Signal, so as to obtain an output symbol stream S ', and the symbol stream S ' is input back to the modulator, where the symbol stream S ' and the symbol stream S are compared to ensure that the error between the symbol stream S ' and the symbol stream S is minimum, so as to output the symbol stream S ' to the optical-to-electrical converter.

And the double-bias electro-optical modulator receives the digitally processed symbol stream S ', converts the symbol stream S' into an analog signal through digital-to-analog conversion of a DAC (digital-to-analog converter), and drives the double-bias electro-optical modulator after radio frequency amplification. In the double-bias photoelectric modulator, a single-frequency continuous light source is input, the light field E after electro-optical modulation correspondingly carries the information of S ', namely an optical signal E carrying the information of S' is obtained, and the optical signal is output to an optical fiber transmission channel.

The following describes in detail the functions performed by the respective hardware devices in the receiving apparatus:

the optical-to-electrical converter may be a double-bias electro-optical modulator (which may implement the functions of a digital-to-Analog converter and a first converter), receive the optical signal E 'carrying the information of S', may first mix a single-frequency continuous light source with the received optical signal, further down-convert the optical signal and convert the optical signal into an electrical signal by a photodetector, and finally convert the electrical signal into a digital signal via an Analog-to-digital converter (ADC), and output the digital signal to a digital processor.

It should be noted that the receiving device may receive the optical signal E 'carrying the information of S' through the optical fiber transmission channel and the optical signal E sent by the sending device, and there may be a corresponding error due to interference of the quality of the optical fiber transmission channel or other factors, and therefore, the two signals cannot be directly equivalent.

A digital processor, which is optional, and can perform operations such as equalization, filtering and the like on the received digital signal to recover the symbol stream of the signal in practical system use

Ensuring symbol flow of output digital signal

And a symbol stream S of a signal in the transmission apparatus, and outputting the symbol stream of the signal

A demodulator: the demodulator may include two functions, the first function is that after the demodulator receives the symbol stream S ', a corresponding demodulation mapping mode may be determined according to a modulation mapping mode of a modulator of the transmitting apparatus, and the symbol stream S' is generated to obtain a bit stream sequence

Outputting a bitstream sequence

A second function, the demodulator is also operable to use the most likely criterion for estimation, such that the output bit stream sequence

The error with the bit stream sequence c in the transmitting device is minimal.

It should be noted that the symbol stream S' of the signal output by the digital processor may have phase jumps, which may result in a bit stream sequence that is not effectively output by the demodulator

The error with the bit stream sequence c in the transmitting device is minimal. Therefore, in the present application, a phase-jump detector is added after the demodulator.

The phase-hop detector may be used to perform a second function of the demodulator. In particular, the phase-jump detector receives a stream of symbols of a signal output by the digital processor

And combining the characteristics of FEC code to detect and process phase jump to make output bit stream sequence

And bit stream sequence c in the transmitting apparatusThe error is minimal. In particular, how to implement the detection and processing of the phase jump, reference may be made to steps S307 to S309 in fig. 3 described below.

An FEC decoder for receiving the bit stream sequence output by the phase-jump detector

Then, according to the coding method in the FEC coder of the transmitting device, the corresponding decoding method is used for the bit stream sequence

Decoding to obtain bit stream

And make the bit stream

And bit stream b in the transmitter, and outputting the bit stream

The specific decoding method is not specifically limited in the embodiments of the present application.

It should be noted that the sending device and the receiving device may further include a receiver and a transmitter, both of which may be used to implement communication to receive or send corresponding signals, data or information, etc., and will not be described in detail herein.

Please refer to fig. 3, which is a flowchart illustrating a signal processing method according to an embodiment of the present disclosure. The method can be applied to the communication systems shown in fig. 1-2, and can of course be applied to communication systems other than those shown in fig. 1-2, which is not limited in this application. Referring to fig. 3, the method may include the following process flow.

S301: the sending device acquires the first signal, and codes the first signal according to a preset error correcting code to obtain a coding sequence of the first signal.

In an embodiment, the preset error correction code may be a forward error correction code FEC, or may be another error correction code, and the present application is not particularly limited as long as the preset error correction code satisfies the following conditions.

Assume that a generator matrix of the preset error correction code is G and a first verification matrix of the preset error correction code is H. Wherein, the generator matrix G comprises k rows G₁,g₂,......g_k. Wherein, g_jTo generate the jth row vector of the matrix, j is a positive integer no greater than k, g₀All-zero row vector, g, expressed as the number of rows of the matrix being 1₀May be the generator matrix column width.

The first verification matrix H comprises m rows H₁,h₂,......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀All-zero row vector, h, expressed as the number of rows of the matrix being 1₀Is the first validation matrix column width.

Wherein the generator matrix and the first verification matrix may satisfy the following formula:

the preset generator matrix G may satisfy the following formula one and formula two, or the first verification matrix H of the preset error correction code may satisfy the following formula three and formula four.

f_i(h₀)·H^TNot equal to 0 formula four

Wherein rank (·) represents the rank of the matrix, i represents the angle, and f_i(.) representing the corresponding sequence transformation function when the phase of the signal changes by i degrees, p_i(.) representing the phase of the signalThe position permutation function of the corresponding sequence when the bit changes by i degrees.

In this step, since the generation matrix and the first verification matrix of the FEC code may satisfy the condition of the above formula, the FEC code may be used as an error correction code used in the implementation of the present application.

In one embodiment, the transmitting device may encode the first signal by using a certain encoding method according to the FEC code to obtain an encoded sequence of the first signal. The specific encoding method is not specifically limited in this application.

Alternatively, the first signal may be a digital signal, and the digital signal may refer to a signal in which an independent variable is discrete and a dependent variable is also discrete, and the independent variable of the signal may be represented by an integer and the dependent variable may be represented by one of finite numbers. In a computer, the magnitude of a digital signal is usually represented by a binary number with a limit, for example, a binary number with a word length of 2 bits can represent digital signals of 4 sizes, 00, 01, 10 and 11 respectively.

Specifically, the coding sequence of the first signal obtained by the transmitting apparatus may be a bit stream sequence of the first signal encoded by the FEC code. It should be noted that since the digital signal represents 0 and 1 in two physical states, the digital signal itself has much stronger interference resistance than the analog signal.

S302: the transmitting device processes the coded sequence of the first signal by using the set modulation method to obtain the information sequence of the first signal.

Optionally, in the embodiment of the present application, a mapping method of QAM gray modulation of QPSK and square constellation may be adopted.

In one embodiment, the transmitting apparatus uses a mapping method of QAM gray modulation of a square constellation to generate an information sequence of the first signal from an encoding sequence (i.e., a bit stream sequence) of the first signal, where the information sequence of the first signal may be a QAM symbol stream.

In step S302, the mapping method for QPSK and QAM gray modulation of square constellation is adopted in the embodiment of the present application, and therefore, the mapping method for QPSK and QAM modulation of square constellation is specifically described below.

The QAM modulation of the square constellation is that points on the modulation constellation are arranged into a square with the origin as the center, the modulation order M of the square constellation M-QAM is satisfied, and M is 2^2mWherein m is a positive integer. As shown in fig. 4A, it is a gray mapped QPSK constellation; as shown in fig. 4B, which is a 16QAM constellation.

Illustratively, the 16QAM constellation of fig. 4B shows A, B two points, which correspond to "1000" and "1100" bit sequences, respectively, and the two bit sequences differ only by the second bit.

Under the QAM modulation using QPSK and square constellation, after the symbol undergoes phase hopping, the corresponding bit sequence can be represented as the bit sequence corresponding to the original symbol, which is subjected to position permutation, and then a specific vector is added (here, the addition refers to modulo-2 addition, i.e., exclusive or operation). Channel phase jump angle of

Or pi or

I.e. 90 deg., 180 deg. and 270 deg., defining a sequence transformation function f_i(.) where i equals

Or pi or

I.e. f_i(.) may be used to represent a symbol or a sequence of bits corresponding to a symbol

Or pi or

The angle-hopped bit sequence of (1).

For example, under QPSK, the bit sequence corresponding to symbol 00 is expressed in terms of

Or pi or

The bit sequences after the angle jump are respectively:

f_π(00)＝11，

referring to fig. 4C, under 16QAM, the bit sequence corresponding to symbol 0001 is expressed as follows

Or pi or

The bit sequences after the angle jump are respectively:

f_π(0001)＝1011，f_π(0001)＝0110。

the bit sequence position permutation can define a sequence position permutation function p_i(.) wherein i is equal to

Or pi or

Bit position permutation occurs within a symbol, and when in QPSK, bit position permutation occurs only between every 2 bits. When under 16QAM, bit position permutation only occurs between every 4 bits.

The following is an example of how the bit sequence corresponding to the symbol after the symbol has undergone phase jump is represented as a bit sequence corresponding to the original symbol after position permutation, and then a specific vector is added.

As shown in fig. 4D, under QPSK, symbol a₁a₂A position permutation function of

p_π(a₁a₂)＝a₁a₂Thus, it can be seen that i is equal to

And

under the angle, two adjacent bits exchange positions, and under the condition that i is equal to the angle pi, the positions of the bits are unchanged. For example, a specific vector is in

π、

Respectively at angles of 01, 11 and 10, in the example 01

π、

The positions under the angle are respectively 10, 01 and 10 after the position replacement, the

specific vectors

01, 11 and 10 are respectively added to obtain respectively 11, 10 and 00, and the

symbols

11, 10 and 00 are symbols after the corresponding angle phase jump.

As shown in FIG. 4E, under 16QAM, symbol a₁a₂a₃a₄A position permutation function of

p_π(a₁a₂a₃a₄)＝a₁a₂a₃a₄Thus, it can be seen that i is equal to

And

under the angle, the first bit and the third bit interchange positions, the second bit and the fourth bit interchange positions, and the positions of the bits are unchanged when i is equal to the angle of pi. For example, a specific vector is in

π、

Respectively 1000, 1010 and 0010 under the angle, if 0001 in the example

π、

The positions under the angle are respectively 0100, 0001 and 0100 after being displaced, and 1000, 1010 and 0010 are respectively added to obtain 1100, 1011 and 0110 in sequence, and then 1100, 1011 and 0110 are symbols after corresponding angle phase jumps.

It should be noted that, in an actual system, after the step 302, the transmitting apparatus further needs to perform a modulation process on the first Signal through a Digital Signal Processing (DSP) to pre-compensate for some loss caused by the channel.

In one embodiment, after the transmitting apparatus processes the coded sequence of the first signal according to the set modulation method to obtain the information sequence of the first signal, the transmitting apparatus further needs to use a digital processing technology (digital processor) to adjust the information sequence of the first signal.

Specifically, the transmitting apparatus performs operations such as pulse shaping and spectrum filtering on the first signal by using Digital Signal Processing (DSP), and outputs an information sequence (adjusted QAM symbol stream) of the adjusted first signal by using the Digital Signal Processing (DSP). The information sequence of the adapted first signal (the adapted QAM symbol stream) is subjected to the next step of processing.

S303: the sending device converts the first signal to obtain a first electric signal, the first electric signal carries an information sequence of the first signal, and the sending device converts the first electric signal to obtain a carrier signal.

Optionally, the sending apparatus may convert the first signal into a first electrical signal through a digital-to-analog converter, and then convert the first electrical signal into a carrier signal through the first converter. The digital-to-analog converter and the first converter may be dual-polarization electro-optical modulators, and are used to implement step S303.

In one embodiment, the transmitting device converts the information sequence (QAM symbol stream) of the first signal obtained in step S302 into a first electrical signal (i.e., analog signal) through a Digital-to-analog converter (DAC), and converts the first electrical signal into a carrier signal through the first converter.

The carrier signal may be used to carry digital information on a computer, and the carrier signal may be a telecommunication wave, a light wave, or the like, and the present application is not particularly limited.

Optionally, the carrier signal in this embodiment is an optical signal as an example. The double-bias photoelectric modulator can be driven after radio frequency amplification, and in the double-bias photoelectric modulator, a single-frequency continuous light source (optical signal) is used as input, and the optical field after photoelectric modulation is switched on, so that the optical signal carries an information sequence of a first signal.

It should be noted that, in actual use, the information sequence (adjusted QAM symbol stream) of the adjusted first signal obtained in step S302 is processed in step S303, and the final carrier signal carries the information sequence (adjusted QAM symbol stream information) of the adjusted first signal.

S304: the transmitting device transmits the carrier signal, and the receiving device receives the carrier signal.

Alternatively, the transmitting device may transmit the carrier signal over an optical fiber link, and the receiving device may thereby receive the carrier signal transmitted by the transmitting device.

It should be noted that, in the process of transmitting the carrier signal through the optical fiber link by the transmitting device, there are usually problems of loss and phase jump of the carrier signal received by the receiving device due to poor quality of the transmission channel/link and interference caused by factors such as chromatic dispersion, nonlinear effect of the optical fiber, and phase noise during transmission. Therefore, the carrier signal received by the receiving apparatus and the carrier signal transmitted by the transmitting apparatus are not completely equal.

S305: the receiving device converts the carrier signal into a first electrical signal, and then converts the first electrical signal into a first signal.

Optionally, the receiving device may convert the carrier signal into a first electrical signal through the first converter, and then convert the first electrical signal into a first signal through the digital-to-analog converter. The digital-to-analog converter and the first converter in step S305 may use the same digital-to-analog converter and the same first converter as in step S304, and the digital-to-analog converter and the first converter may be a double polarization electro-optical modulator for implementing step S305.

In one embodiment, after the receiving device converts the first electrical signal into a first signal through a digital-to-analog converter, the first signal may be adjusted through a digital processor DSP.

Specifically, the carrier signal is converted to obtain a first signal through step S305, and an information sequence (which may be a QAM symbol stream) of the first signal may be obtained at the same time; and then, carrying out operations such as equalization, filtering and the like on the first signal by adopting a digital processing technology DSP, outputting the information sequence of the adjusted first signal by a digital processor, and ensuring that the error between the information sequence of the adjusted first signal and the acquired information sequence of the first signal is minimum.

S306: and the receiving device processes the first signal according to a set demodulation method to acquire a first information sequence of the first signal.

Optionally, in the embodiment of the present application, a mapping method of QAM gray demodulation of QPSK and square constellation may be adopted.

Specifically, the carrier signal is converted into the first signal through step S305, and the information sequence (which may be a QAM symbol stream) of the first signal may be acquired at the same time. The transmitting apparatus may use a mapping method of QAM gray demodulation of a square constellation to generate the information sequence of the first signal into a first information sequence of the first signal (i.e., a coded sequence of the first signal).

S307: the receiving device determines a standard correction value and a first correction value of the first information sequence according to a preset error correction code.

In one embodiment, the preset error correcting code may be a forward error correcting code (FEC code), and the generation matrix of the preset error correcting code needs to satisfy both formula one and formula two in step S301, or the first verification matrix of the preset error correcting code needs to satisfy both formula three and formula four in step S301. Specifically, refer to step S301, which is not described herein in detail.

The following description is made with respect to a formula one and a formula two, or a formula three and a formula four, for which a generation matrix of a preset error correction code and a first verification matrix of the preset error correction code need to be satisfied.

Under QAM modulation of square constellation such as QPSK, the phase jump of a symbol can be represented by the position permutation of the bit sequence corresponding to the original symbol, and then adding a specific vector, so the phase jump of a codeword (information sequence of a signal) can also be represented by the position permutation of the bit sequence in each symbol, and then adding a specific vector.

Bit sequence position permutation of codeword c may be represented as

C the sequence obtained after the phase jump is

f_π(c)＝p_π(c)+v_π，

v_π,

Is a specific vector of the same length as c.

If the generating matrix of an FEC error correcting code is G and the first matrix is H, for any legal code word c, the condition c.H is satisfied^T0. Where 0 represents an all-zero vector. The error correcting code capable of resisting phase jump provided by the application meets the following conditions:

if the legal code word c is obtained after phase jump

And f is a_i(c) Not a legal code word, i.e. f_i(c)·H^TNot equal to 0, and f_i(c)·H^TI.e. the syndrome, has only a unique value at a specific jump angle. When the phase jump occurs, the error correcting code does not generate code words confused with legal code words, and the angle of the phase jump can be conveniently detected.

The present application indicates that the predetermined error correction code needs to satisfy both the above formula one and formula two. Equivalently, the formula three and the formula four can be satisfied simultaneously for one preset error correction code resistant to phase jump.

When the preset error correcting code for resisting phase jump simultaneously meets the first formula and the second formula or simultaneously meets the third formula and the fourth formula, any code word with complete phase jump is not a legal code word, and the error correcting code can detect the angle of the phase jump.

For the preset error correcting code provided in step S307, the preset error correcting code only needs to satisfy the first formula and the second formula, or satisfy the third formula and the fourth formula, and the preset error correcting code can be used to detect the phase jump of the signal. Therefore, in the present application, a low density parity check code LDPC is provided, and how to construct the LDPC code can refer to the third embodiment described below.

In addition, the present application also provides a Low-Density Parity-Check Convolutional Code (LDPCC) resistant to phase jump, and how to construct the LDPCC Code specifically refers to the following fourth embodiment, and a method for improving the construction of the LDPCC resistant to phase jump is also described in the fourth embodiment. Further, the structure and principle of the LDPCC code receiving device system are described in detail, and reference may be made to the fifth embodiment described below.

In one embodiment, the receiving device determines the standard correction value according to a preset error correction code, and the standard correction value can be obtained by: firstly, determining a generating matrix and a first verification matrix according to a preset error correcting code; and calculating to obtain the standard correction value according to an information sequence of a preset signal, the generating matrix, the first verification matrix and a preset first correction formula.

Specifically, firstly, the receiving device multiplies an information sequence of a preset signal by a generating matrix to obtain a second information sequence; then, the receiving device determines N phase-changed third information sequences corresponding to N angles of phase change of the preset signal according to the second information sequence; n is a positive integer greater than 0; and finally, the receiving device substitutes each third information sequence and the transpose matrix of the first verification matrix into a preset first correction formula to calculate and obtain N standard correction values.

The preset first correction formula satisfies the following formula:

S_i＝f_i(x)*H^Tformula five

Wherein i represents the size of the angle, S_iIndicating the corresponding correction value for a phase change of the signal by i degrees, f_i(.) representing the corresponding sequence transformation function when the phase of the signal changes by i degrees, x representing a row vector with 1 row number of the matrix, the length of x representing the column width of the first validation matrix, H^TA transpose matrix representing the first validation matrix.

Wherein the second information sequence can be used as a sequence transformation function f_i(.), each third information sequence corresponding to a sequence transformation function f_i(.) and if it is determined that the phase of the preset signal needs to be changed by N degrees, N third information sequences are correspondingly output.

Specifically, how to determine the standard correction value according to the preset error correction code can be explained as follows:

formula one shows that for any row vector of the generator matrix, after bit position permutation, the row vector in G can still be linearly represented. Therefore, after any legal codeword c is permuted by bit position, it can still be linearly represented by the row vector in G, i.e. it is still a legal codeword, so p_i(c)·H ^T0. Because the all-zero sequence remains unchanged through any bit position permutation, under different phase jump angles

I.e. the specific vector to be added after bit position permutation in the phase jump decomposition under the angle. Therefore, after a certain legal codeword c (i.e. the above information sequence) undergoes a phase jump, the corresponding correction value (vector) can be calculated by using the above condition as follows:

S_π＝f_π(c)*H^T＝(f_π(h₀)+p_π(c))*H^T＝f_π(h₀)*H^Tformula seven

If the code words obtained by the different code words after the same angle phase jump have the same correction value (vector), the syndromes are the standard correction values (vectors), so that the phase jump angle can be detected by using the standard correction values (vectors).

In one embodiment, the receiving device may determine the first correction value of the first information sequence according to a preset error correction code, including: the receiving device determines a generating matrix and a first verification matrix according to a preset error correcting code; then the receiving device determines a fourth information sequence according to the first information sequence, wherein the fourth information sequence is the information sequence after the phase angle of the first signal is changed; and the receiving device substitutes the fourth information sequence and the first verification matrix into the preset first correction formula to obtain a first correction value of the first information sequence.

It should be noted that a receiving apparatus may be provided with a soft message, and the first information sequence may be input with the soft message, so as to output a fourth information sequence corresponding to the first information sequence. If the phase angle of the first signal changes, the fourth information sequence is the corresponding information sequence after the phase angle of the first signal changes; if the phase angle of the first signal is not changed, the fourth information sequence is equal to the first information sequence.

S308: the receiving device determines the angle of the phase change of the first signal based on the standard correction value and the first correction value of the first information sequence.

In one embodiment, the receiving device determines the angle of the phase change of the first signal based on the standard correction value and the first correction value of the first information sequence, comprising the steps of:

the first step is as follows: determining N standard correction values corresponding to N different angles of phase change of a preset signal in the standard correction values, wherein each angle corresponds to one standard correction value, and N is a positive integer greater than 0;

the second step is as follows: respectively carrying out correlation value calculation on the N standard correction values and the first correction value to obtain N correlation values;

the third step: when the condition that the first correlation value of the corresponding standard correction value and the first correction value is the largest when the phase of the preset signal changes by the ith angle is determined, and the first correlation value meets the set condition, determining that the phase change angle of the first signal is the ith angle; i is a positive integer value greater than 0 and less than or equal to N;

the setting conditions comprise that the first correlation value is larger than a first setting threshold value, and errors between the first correlation value and other N-1 correlation values are larger than a second setting threshold value.

It should be noted that, when the receiving device determines the standard correction value according to the preset error correction code, it is not only applicable to determine the angle of the phase change of the first signal in the embodiment of the present application, but also applicable to other signals. Therefore, the standard correction value in the embodiment of the present application may be used not only as a reference standard value for determining a change in the phase of the first signal in the embodiment of the present application, but also as a reference standard value for determining a change in the phase of another signal.

S309: the receiving device processes the phase of the first signal according to the angle of the phase change of the first signal.

In one embodiment, the receiving device performs angle processing in the opposite direction on the phase of the first signal according to the angle of the phase change of the first signal, and can obtain the information sequence of the first signal after the phase processing.

It should be noted that the phase angle adjusted first signal corresponds to the first signal encoded in step S301 (i.e., the encoded sequence of the phase adjusted first signal). Therefore, after the receiving device processes the phase of the first signal according to the angle of the phase change of the first signal, the receiving device needs to decode the encoded sequence of the phase-adjusted first signal by the error correction code preset in step S310 to obtain the information sequence of the decoded first signal.

For the process of detecting and processing the phase jump of the signal by the receiving apparatus in the above steps S307 to S309, the present application provides a specific phase jump detection procedure, and reference may be made to the first embodiment described below.

In the second embodiment, a specific implementation example of the detection and processing of the signal phase jump is described in detail.

S310: the receiving device decodes the information sequence of the first signal after the phase processing by using a preset error correcting code.

In one embodiment, the receiving device receives an information sequence of the phase-adjusted first signal output by the phase-jump detector, and decodes and corrects the sequence by a preset FEC code.

In the method provided by the embodiment of the application, a sending device acquires a first signal, and then the sending device encodes the first signal according to a preset error correcting code to obtain an encoding sequence of the first signal; then, the sending device processes the coding sequence of the first signal according to a set modulation method to obtain an information sequence of the first signal; the sending device converts the first signal through a digital-to-analog conversion module to obtain a first electric signal, wherein the first electric signal carries an information sequence of the first signal; and finally, the sending device sends the carrier signal after converting the first electric signal into the carrier signal through the first conversion module. After receiving the carrier signal, the receiving device converts the carrier signal into a first electric signal through a first conversion module, and then converts the first electric signal into a first signal through a digital-to-analog conversion module; the receiving device further processes the first signal according to a set demodulation method to obtain a first information sequence of the first signal; then, according to a preset error correcting code, a standard correction value and a first correction value of the first information sequence are determined, and then, according to the standard correction value and the first correction value of the first information sequence, an angle of phase change of the first signal is determined; and finally, the receiving device processes the phase of the first signal according to the phase change angle of the first signal.

In the method, a receiving device converts a received carrier signal into an electric signal, acquires a first information sequence of a first signal, determines standard correction values of a plurality of phase angles and correction values of the first information sequence according to a preset error correcting code, calculates correlation values of the correction values of the first information sequence and the standard correction values, further determines an angle of phase change, and processes according to the angle of phase change, so that the phase change of the signal can be efficiently solved.

Based on the signal processing method provided by the above embodiment, the present application also provides the following specific examples to explain the technical solutions of the present application in detail.

In the first embodiment of the present application, according to the receiving apparatus performing the phase jump detection and processing procedures in steps S307 to S309, a specific flow of signal phase jump detection and processing is provided in the embodiment of the present application.

As shown in fig. 5, the phase jump detector of the receiving apparatus may be independent of the FEC encoder, and the phase jump detector and the soft information memory (the soft information memory may be located in the phase jump detector) may simultaneously receive the soft information output by the demodulator, and may determine a codeword using the soft information, and input the codeword to the phase jump detector for performing the phase jump detection operation. If the phase jump detector detects the occurrence of the phase jump and determines the phase jump angle, the corresponding code word information in the soft information memory is controlled, the soft information is turned over according to the correct phase, the correct code word obtained after the turning over is input into the FEC decoder for decoding, and the correct code word is output.

Specifically, after the phase jump detector outputs the phase jump angle decision value, the soft information memory correspondingly turns the stored codeword soft information back to the correct angle according to the phase jump angle, and then inputs the codeword soft information to the FEC decoder for decoding operation, and finally outputs the result, thereby completing the processing work of the whole receiver.

The specific flipping operation is determined by a specific modulation format, such as QPSK modulation shown in fig. 4D, and when the soft information is log-likelihood ratio (LLR) information, the 2 bits of information corresponding to each symbol are (L)₁,L₂) When the phase jump angle is detected to be lower, the soft information is respectively inverted to (-L)₂,L₁)，(-L₁,-L₂)，(L₂,-L₁). In 16QAM modulation as shown in FIG. 4E, the 4 bits of information per symbol are (L)₁,L₂,L₃,L₄) When the phase jump angle is detected, the soft information is respectively inverted to (L)₃,L₄,-L₁,L₂)，(-L_-1,L₂,-L3,L₄)，(-L₃,L₄,L₁,L₂)。

When the phase jump starts in the middle of the code word, the phase jump detector may output an erroneous phase jump angle detection value, and a large number of residual errors can be found after decoding. At this time, the error detection retransmission system can be combined to request the transmitting end to retransmit the code word, thereby providing the overall performance of the system.

The following describes how the phase jump detector specifically detects the phase jump of the signal and determines the angle of the phase jump, as shown in fig. 6, the specific flow is as follows:

s601: the codeword bits are input.

In this step, the codeword bits are the codewords directly decided by the soft information stored in the phase-hopping detector, and the codewords can be represented as the corresponding bit sequences after the symbols undergo phase hopping.

S602: and multiplying the code word bits by the transpose of the check matrix of the preset FEC error correcting code to calculate a syndrome S.

In this step, the syndrome S can be calculated by the formula five in the above step S307. The codeword bits are equivalent to f in equation five_i(h₀) The transpose of the check matrix of the preset FEC error correction code is H in formula five^T。

S603: standard syndromes S corresponding to the syndromes S to the respective angles of phase jump_iThe correlation value is calculated and the phase jump angle corresponding to the standard syndrome with the maximum syndrome S correlation value is determined.

In the present application, the correlation value between the syndrome S and each standard syndrome can be calculated by calculating the number of bits between the syndrome and each standard syndrome, which is called the correlation value.

E.g. phase jump

π、

The standard syndromes for the angles are:

S_π、

comparing S with

S and S_πS and

the number of bits having the same bit value is used as the correlation value

cor(S,S_π)、

And further determining the phase jump angle alpha corresponding to the standard syndrome with the maximum correlation value.

S604: syndrome S and standard syndrome S_iWhether the correlation values are all greater than the first threshold value.

If yes, go to step S605, otherwise go to step S606.

S605: syndrome S and standard syndrome S_iWhether the maximum correlation value and the other correlation values are both greater than the second threshold value. If so, execute step S607, otherwise execute step S606.

S606: it is determined whether the phase jump angle corresponding to the standard syndrome with the largest syndrome S correlation value is equal to 0.

If yes, S607 is executed.

S607: and outputting the phase jump angle.

It should be noted that the threshold conditions involved in steps S604 and S605 are set to reduce the false alarm rate and increase the detection accuracy. And setting a first threshold value as a threshold for judging the occurrence of phase jump for the correlation value of the syndrome of the judged code word relative to each standard syndrome. A second threshold is set, and when the difference between the maximum correlation value and the correlation values of the other two angles is greater than the second threshold, it indicates that the correlation value for the correct angle is significantly greater than the correlation values of the other two angles.

Therefore, it can be seen that the phase state memory is changed, and the following conditions need to be satisfied: 1) the correlation value obtained by the syndrome calculation is larger than a first threshold value; 2) the difference between the maximum correlation value and the correlation values of the other two angles is greater than a threshold value of 2.

If the above condition is not satisfied, the default phase jump detector outputs a phase jump angle of 0. The first threshold and the second threshold may be set by a user, or determined by simulation and test, and in addition, the first threshold and the second threshold may be set to be changed according to different signal-to-noise ratios, or may be fixed values. These thresholds are set to improve the performance of the phase jump detector, and are not essential, and in a simplified case, the angle corresponding to the standard syndrome having the largest correlation value and satisfying the threshold condition may be directly taken as the detected phase jump angle.

In the second embodiment of the present application, a specific implementation example of the detection and processing of the signal phase jump is provided according to the phase detection process performed by the receiving apparatus in the above steps S307 to S309.

Taking a preset FEC code as an example, it is first verified that the preset FEC code simultaneously satisfies the first formula and the second formula, or simultaneously satisfies the third formula and the fourth formula.

A simple generator matrix of (12,6) error correction codes can be expressed as:

the first check matrix of the error correction code may be expressed as:

i.e. G.H^T0. All row vectors of the first check matrix H are H₁,h₂,…,h₆Under QPSK

And

bit position permutation of angles (i.e.Adjacent two-bit interchange positions), the composition matrix can be expressed as:

it can be seen that the first verification matrix H has a rank of 6, and the matrix H_pCan be obtained from H by elementary row transformation, so the first validation matrix satisfies formula three and formula four.

Then, based on the preset FEC code, it can be determined that

π,

Under the angle, the corresponding standard syndromes (i.e. standard correction vectors) are:

s_π＝f_π(h₀)*H^T＝[0,1,0,0,1,0]，

and the standard syndromes are all non-zero vectors. And meanwhile, the first check matrix can be further determined to be a check matrix of the anti-phase jump error correcting code.

For example, when the information sequence of the acquisition signal is [0,1,0,1,1 ]]Multiplying by G to obtain a codeword of [1,0,0,1,1,1,0,0,0,1, 1]The whole code word is in

π,

The code words obtained by phase jump under the angle are [0,0,1,1,1,0,0,1,1,1,1, respectively]，[0,1,1,0,0,0,1,1,1,0,1,0]，[1,1,0,0,0,1,1,0,0,0,0,0]Then, the syndromes calculated by multiplying the code word obtained by the phase jump by the transpose of H are just the syndromes respectively

s_π,

Further, a syndrome (i.e., a correction vector) may be calculated, and the syndrome is compared to a standard syndrome

s_π，

And comparing, detecting the angle with which the phase jump occurs, and reversely jumping according to the angle so as to recover the original code word.

When the correlation between the syndromes and the standard syndromes is calculated when the syndromes are aligned with the standard syndromes (vectors), in one embodiment, the phase jump angle corresponding to the standard syndrome with the largest number can be taken as the detected phase jump angle by counting the number of the same bits between the syndrome and each standard syndrome.

For example, the calculated syndrome is [1,0,1,1, 1%]Comparing with the three standard syndromes ((vectors) mentioned above, the number of bits obtained is 5,1,3 respectively, so as to determine the phase jump angle

Finally, it should be noted that the error correction code in the above example can also be adapted to be a suitable error correction code resistant to phase jumps under 16QAM modulation. Column exchange is carried out on every 4 columns of the first verification matrix H of the error correcting code, namely, the 2 nd and 3 rd column exchange, the 6 th and 7 th column exchange and the 10 th and 11 th column exchange, and the obtained first check matrix of the error correcting code can verify that the formula three and the formula four are met under 16 QAM. In addition, the same column permutation is carried out on the generating matrix G, and the error correcting code which is resistant to phase jump under 16QAM is obtained.

In the process of constructing error correcting code resisting phase jumpOne principle that should be followed is to make the all-zero syndrome and the standard syndrome

s_π,

The Hamming distance between every two, that is, the number of different bits of the same position bit is as large as possible, so that the allowable error bit number of the syndrome can be improved, and the accuracy is higher when the syndrome is compared with the standard syndrome.

In the third embodiment of the present application, a way of constructing a phase-hopping quasi-cyclic low-density parity-check code LDPC based on Reed-Solomon (RS) codes is provided according to a predetermined error correction code (i.e., the predetermined error correction code needs to satisfy both the first formula and the second formula, or both the third formula and the fourth formula) involved in the above step S301 or step S307.

Let the primitive of the finite field gf (q) be denoted α, where q ═ p^tP is a prime number greater than 2, and t is a positive integer. Let m be the maximum prime factor of q-1, and q-1 be cm. Since p is greater than 2, p is odd, and thus c is even. Let beta be alpha^cThen β is GF (q) an element of order m, i.e. m is minimal such that β ^m1 is a positive integer.

Constructing an m × m matrix over gf (q) may satisfy the following:

where the exponent of β is obtained by modulo m. Obtaining a sub-matrix with the size of k multiplied by n from the matrix, and taking the sub-matrix as alpha^αPower of instead of beta^βCan obtain the RS, constructing a base matrix of the LDPC code, which can satisfy the following:

since c is an even number, σ_i，jI is more than or equal to 0 and less than or equal to k-1, and j is more than or equal to 0 and less than or equal to n-1 and is even number. The RS thus constructed, thereby constructing an LDPC code whose first verification matrix may satisfy the following:

wherein, the matrix P is a cyclic permutation matrix with size (q-1) x (q-1), and the cyclic permutation matrix P can satisfy the following:

wherein, P⁰Is a unit array.

Corresponding to a cyclic shift of the unit array to the right by sigma_i，jA bit. Thus, the LDPC code is a quasi-cyclic LDPC code and the first verification matrix has a size of k (q-1) × n (q-1).

Because of σ_i，jAre all even, can verify

Corresponding to the adjacent two-bit interchange position of the previous row (subscript starting from 0). Thus, the first of the entire first validation matrices

Line is equivalent to line 2i under QPSK

And

bit position permutation of angles.

And since bit position permutation under pi is equivalent to position invariance, the first verification matrix satisfies the above formula three. And the row weight of the first verification matrix is an odd number only by taking the value of n as the odd number, so that the fourth formula can be ensured to be met. Therefore, the RS constructed in this way can be used for constructing the LDPC code, namely a phase jump resistant linear block code under QPSK modulation.

For 16QAM, the first validation matrix constructed under QPSK modulation can be obtained by performing the 2 nd and 3 rd column interchange operations for every 4 columns according to the operations in the fourth embodiment. In addition, for higher order square constellation QAM, the first verification matrix can be obtained by column exchange according to the phase hopping rule of the constellation diagram in the same way.

In the fourth embodiment of the present application, a low density parity check convolutional code LDPCC and an improved method for constructing the LDPCC code are provided according to a predetermined error correction code (i.e. the predetermined error correction code needs to satisfy both the formula one and the formula two, or both the formula three and the formula four) in step S301 or step S307. The LDPCC code is a convolution form of the LDPC code, has better decoding performance, has the characteristic of decoding while receiving, and has lower delay. The characteristics are beneficial to detecting the phase jump in a short time after the phase jump occurs, and the method is suitable for scenes that the phase jump occurs randomly and often lasts for a long time in optical communication and the like.

Referring to the method for constructing the phase jump resistant LDPC code in the third embodiment, the method can also be used for constructing the phase jump resistant LDPCC code. The LDPCC code first validation matrix may be represented by a two-sided infinity check:

wherein each sub-matrix

Has a size of a x c and a code rate of about

Each sub-matrix is a sparse matrix, m_s+1 is the syndrome matrix contained in each rowNumber of arrays, in which m_sThe memory length of the LDPCC code is referred to as syndrome forward memory length. A truncated form of the LDPCC code, i.e. the SC-LDPC code (spatially coupled LDPC code), the first validation matrix may satisfy the following:

wherein the first verification matrix is a matrix formed by sub-matrices

May be represented as a single row of validation submatrices. Because the code word of the LDPCC code or SC-LDPC code is very long, in the embodiment of the present application, every c bits of the code word may be formed into one code word segment.

The method for constructing the anti-phase jump LDPCC code may specifically include the following:

verifying the single row of the submatrix

And the whole is regarded as a first verification matrix, and the LDPCC code is determined to be the LDPCC code resisting the phase jump as long as the first verification matrix meets the third formula and the fourth formula. The single-row verification submatrix is constructed by the same construction method based on the RS code as the embodiment, so that the anti-phase-jump LDPCC code can be constructed, and the truncation form is the anti-phase-jump SC-LDPC code.

The phase detection process of the anti-phase-jump LDPCC code is similar to that of the anti-phase-jump LDPC code, and specifically may include the following:

in the process of transmitting the code word, if the phase jump starts to occur in the kth section, since the length of the jump duration is generally longer, from the (k +1) th section, as long as the phase jump covers the length of the single row of the verification submatrix, the single row of the verification submatrix can be used for detecting the phase jump angle. Segment the k +1 th to the k + m_sThe codeword bits of +1 sectors constitute a vector c' which is multiplied by a single row of validation submatrices

By transposing, a syndrome vector s 'can be obtained, the syndrome vector s' being associated with

The angle of phase jump can be judged by comparing the corresponding standard syndromes.

It should be noted that the phase detection process of the anti-phase-jump LDPCC code may be the same as the working process of the phase jump detector described in the third embodiment, and a method in which a plurality of rows of verification sub-matrices are regarded as a whole may also be used to perform phase jump detection, so as to improve the detection accuracy. After the phase jump angle is detected, the bits of the segment completely covered by the phase jump can be inverted according to the correct phase, and then decoding is performed.

The accurate detection of the phase jump angle requires the phase jump to completely cover m_s+1 sectors, i.e., a single row of validation submatrix lengths. And once the phase jump is located at the middle position of the section and is judged to be not phase jump or completely covered by the phase jump, a large number of errors are generated after decoding.

Therefore, in order to avoid this, and minimize the loss code rate, the receiver does not miss the segment where the phase jump starts, and the structure of the anti-phase jump LDPCC code can be improved to some extent. The embodiment can accurately judge the time when the phase jump occurs and erase the initial section in time.

The improvement can cause that once the phase jump happens, the phase jump is expressed as a large number of non-zero positions on the syndrome with high probability, and when the phase jump detector detects that the syndrome has abnormal non-zero positions, the phase jump is judged to happen from the input section at the moment. Thus, the present embodiment sets a syndrome weight threshold, which determines that a phase jump begins to occur when the hamming weight (i.e., the number of non-zero bits) of the syndrome exceeds.

The present application may also improve the structure of the anti-phase-hopping LDPCC code, and the specific method may include the following:

defining a phase hop coverage length L_φSuch asFIG. 7A shows that when a single row verifies a submatrix

Covers all 1 errors, and the length of the all 1 sequence is called the phase jump coverage length L_φ。

The phase hopping LDPCC code can be modified by Masking operations, i.e. by

And setting a plurality of included sub-matrixes as zero matrixes. Covering length L at phase jump by randomly trying masked sub-matrix_φGreater than a small value and less than (m)_s+ 1). c, so that the tail end passes the single row verification submatrix under all 1 errors

The calculated syndrome has a larger hamming weight.

Wherein the mask operation is aimed at making the syndrome Hamming weight-L_φThe curve takes a shape similar to that of FIG. 7B, i.e. only at L_φWhen the syndrome weight is low at smaller values, the remainder L_φThe syndrome hamming weight remains at a large value under the value.

The syndrome weight threshold may be set to a fixed value. At this time, under a high signal-to-noise ratio, since random errors are continuously reduced along with the increase of the signal-to-noise ratio, the weight of the syndrome is reduced as a whole, and a fixed syndrome weight threshold value can miss part of the phase jump. Therefore, in order to increase the sensitivity of judgment of the occurrence of the phase jump, the syndrome weight threshold varying with the signal-to-noise ratio may be set so as to be as close as possible to the upper limit of the syndrome weight under the random error.

The determination method may be: the maximum value of the syndrome weight that is affected only by random errors at different signal-to-noise ratios is obtained by simulation and this value (or a number slightly smaller than this value) is set as the threshold. The syndrome weight threshold stored at the receiving end can be fitted by a piecewise function or polynomial on the signal-to-noise ratio, or the threshold at each signal-to-noise ratio is directly stored and used in a table look-up manner.

For LDPCC codes resistant to phase jumps, the phase jump detector combines previously stored m, one segment at a time_sSoft information of each section, a code word vector c' and a single row verification submatrix are determined

The transpose multiplication of (c) to obtain the syndrome vector s'. And (4) counting the number of non-zero elements in the s', if the number is larger than the syndrome weight threshold value, judging that phase jump occurs from the input section, and if not, considering that the phase jump does not occur.

Therefore, the system adopting the improved structure of the anti-phase jump LDPCC code can judge whether the phase jump occurs or not, thereby determining whether the detection operation of the phase jump angle is carried out or not, avoiding the resource waste caused by the detection of each section and reducing the operation amount of a receiving end. For a space-coupled Low-Density Parity-Check Code (SC-LDPC) that is a truncated version of the LDPCC Code, all processing of the phase jump detector is the same.

However, in some high-speed communication systems, especially optical communication systems, the phase jump occurs over a long sequence. The transmission symbols are generally transmitted according to frames, the frame header realizes the functions of synchronization, phase identification and the like, and symbols carrying data information are arranged between the frame header and the frame header. The present embodiment uses a phase jump resistant LDPCC code or SC-LDPC code to achieve correction of phase jump errors in conjunction with such a general frame structure. In this embodiment, the receiving system determines the absolute phase of the symbol sequence through the frame header, but does not need to insert the pilot symbol to assist the correction of the phase jump, thereby saving the number of transmitted symbols and not changing the frame structure of the general high-speed communication system.

In addition, the transmission codeword in this embodiment may be a long anti-phase-jump LDPCC code or an SC-LDPC code, and is divided into multiple frames for transmission. Dividing the transmission code word into code word sections according to each c bits, wherein a plurality of sections are a frame. The phase of the frame header can be accurately detected, so that at the beginning of each frame, the phase is accurate, the phase jump can occur in the middle of one frame, and the phase jump continues to the end of the frame, and the next frame recovers the correct phase.

Therefore, in a fifth embodiment of the present application, the structure and principle of the LDPCC code receiving device system will be described in detail according to the anti-phase-jump LDPCC code constructed in the fourth embodiment.

The receiving device carries out frame synchronization on data through a frame synchronizer, judges a correct symbol absolute phase, calculates Log-Likelihood Ratio (LLR) of a code word part through a soft information output device, and inputs the LLR value into a decoding system. The decoding system can be mainly divided into a sliding window decoder and a phase jump detector, and the system block diagram is shown in fig. 8A.

Sliding window decoding as shown in fig. 8B, a part of the check matrix (decoding window) selected from the frame may be used for decoding, and the decoding window is continuously slid as the decoding proceeds. A portion a of green in fig. 8B may represent codewords that have been decoded, a portion B of blue in fig. 8B may represent current target codewords, and a portion c of gray in fig. 8B may represent codewords that have not been decoded. At the current moment, the decoding window is as shown by a solid line box in fig. 8B, belief propagation decoding is performed according to a certain iteration number to obtain a B-part code word, and then the decoding window slides to a position shown by a dotted line box to perform decoding at the next moment.

The receiving apparatus side of this embodiment mainly uses a single row of validation submatrices for detection, and can also be generalized to a multi-row validation submatrix. At phase jump occurs and covers m_sWith +1 sector, accurate detection is possible.

As shown in FIG. 8A, when the phase jump detector and the decoder operate simultaneously in the decoding system, the decoding delay is adopted to perform the phase jump detection m_sThe +1 codeword section scheme allows all processing to be done consecutively without pauses. The LLR memory and the phase jump detector in the decoding system simultaneously receive the log-likelihood ratio information output by the demodulator. Wherein the sliding window decoder has a length of L sections, i.e. L.c bits, LLR memoryLonger than the sliding window decoder by m_s+1 sectors, phase jump detector length m_s+2 sectors, phase jump state memory having m_s+2 bits. The phase jump detector can change the value of the phase jump state memory in real time and further control the LLR memory to the L-1 to the L + m_sThe LLR value of the section is inverted and the like. The sliding window decoder receives the LLR information of the first L sections of the LLR memory and outputs a decoding result through belief propagation iterative decoding (such as sum-product algorithm, minimum sum algorithm and the like).

When decoding, each bit of the phase jump status memory indicates the status of the section it points to by an integer, for example, 0 indicates that the section points to no phase jump, 1,2,3 respectively indicate that the section has completely covered

π,

The phase jump of the angle, 4, indicates that the phase jump of the segment occurs from the middle of the segment, etc., indicating that the LLR of the segment should be set to zero.

After the above processing, in each frame, when the phase jump completely covers the length of the single row verification submatrix, i.e. covers L-L + m_sAfter the section, the phase jump angle can be accurately detected for the first time. At the first detection, a phase jump may occur at the middle position of the L-1 th segment. To prevent error diffusion, bit 0 of the phase jump state memory, i.e., the L-1 segment of the LLR memory, is reserved as a buffer. At this time, it can be determined that the L-1 th segment of the LLR memory is a segment where the phase jump starts to occur, the 0 th bit of the phase jump state memory is set to 4, and the 1 st bit to the m th bit_sThe +1 position is set to an integer corresponding to the detected phase jump angle. And the phase jump state memory controls the LLR value in the LLR memory to restore and turn over or zero according to the phase jump angle, and then the LLR value input into the sliding window decoder can eliminate errors caused by phase jump.

Decoding delay for the system of FIG. 8ACompared with the L sections decoded by the common LDPCC code, the specific delay is L + m_s+1 sectors. In combination with the improvement of the anti-phase-jump LDPCC code in the fourth embodiment, a counter is added to the phase jump detector, and when the syndrome hamming weight calculated by the phase jump detector is greater than the syndrome weight threshold, the counter counts. The counter value returns to zero when the syndrome hamming weight is less than the syndrome weight threshold, and accumulates when it continues to be greater than the syndrome weight threshold.

In this embodiment, the specific work flow between the phase jump detector and the decoder of the receiving apparatus is as follows:

when the receiving device is in operation, the LLR memory and the phase jump detector simultaneously receive the LLR information output by the soft information output device and synchronously update the LLR information. And each time the LLR value stored by the phase jump detector is updated, the judgment of the code word is carried out and the syndrome is calculated, and the counter updates the value according to the weight of the syndrome.

When the counter value reaches m_sAnd +2, triggering the detection of the phase jump angle and detecting the phase. Upon detecting the occurrence of a phase jump, 1 st to m th phase jump state memories_sThe +1 bit is updated to the corresponding integer, and the 0 th position is 4. And after the process is finished, the LLR values of the 0 th section to the L th section of the LLR memory are input into a sliding window decoder, and a decoding result of one section is output after a plurality of iterations. Then, the soft information outputter outputs LLR information of the next section, and repeats the above operation.

In this embodiment, before the phase jump detector works, f corresponding to the single row verification sub-matrix under different phase jump angles i is calculated_i(h₀) And a single row validation submatrix

The resulting vectors multiplied by the transpose of (c) are used together with the all-zero syndrome as the standard syndrome.

The specific working flow of the phase jump detector is as follows:

the first step is as follows: the LLR information stored in the phase-jump detector is decided as codeword bits with a single row of validation submatrices every time a codeword of one sector is updated

The transpose of (c) is multiplied to calculate a syndrome vector and the hamming weight of the syndrome is counted.

The second step is as follows: the counter counts when the syndrome hamming weight is greater than the syndrome weight threshold. The counter value returns to zero when the syndrome hamming weight is less than the syndrome weight threshold, and accumulates when it continues to be greater than the syndrome weight threshold. When the counter value reaches m_sAnd +2, triggering the detection of the phase jump angle to carry out correlation detection.

The third step: the principle of detecting the phase jump angle and the threshold condition are the same as the working flow (including the principle) of detecting the phase jump in steps S602 to S607 in the third embodiment, and details are not repeated here.

The fourth step: and if the threshold condition of the phase jump detection is met, correspondingly updating the value of the phase jump state memory, otherwise, waiting for the next phase jump detection when the 0 th position of the phase jump state memory is zero.

When the phase jump angle is detected for the first time in each frame, the 0 th position of the phase jump state memory is 4, the 1 st position to the m th position_sThe +1 position is an integer corresponding to the phase jump angle. When the phase jump angle is detected subsequently, the 0 th bit of the phase jump state memory is not changed any more.

When the next frame of code word begins to be input, the counter restores to zero value, and the mth of the phase jump state memory_sThe +1 position is zero and the phase jump detection is restarted. And if the count value of the counter is greater than 0 but the detection of the phase jump angle is not triggered, ending the code word of the frame, and recording the count value as N, and setting LLR values of the last N small blocks of the current LLR storage register to be zero.

In this embodiment system, the segments with zeros in the LLR memory may also be marked to indicate that the data is erased and log-likelihood ratio information of the preceding and following segments may be stored to facilitate possible further processing.

If the anti-phase jump LDPCC code of the improved structure of the fourth embodiment is not used in the phase jump detection, it is not possible to determine which segment the phase jump starts from, and therefore, it is necessary to provide sufficient buffering to prevent error diffusion. That is, when the phase jump angle is detected for the previous times, the 0 th position of the phase jump state memory is set to 4, the corresponding LLR memory is set to zero, and other m values are set_sThe +1 bit is updated to the detected phase jump angle and then changed to the 0 th to the m th bits_sThe +1 bits are all updated to the detected phase jump angle. The times can be set according to different anti-phase jump LDPCC codes or SC-LDPC codes and signal-to-noise ratio, and the range is 1 to m_s+2 times, so that the decoding performed after each detected phase jump requires erasing 1 to m_sFor +2 sectors of data, the lost code rate will increase.

Therefore, the embodiment can accurately restore most section code words covered by the phase jump, and can utilize the good error correction performance of the LDPCC code or the SC-LDPC code to enable the code word bit error rate on the sections to reach a low level. The anti-phase jump LDPCC code constructed in combination with the improvement of the fourth embodiment can make only one sector of codeword information erased every time a phase jump occurs. And for the erased sector, the transmission can be carried out in a retransmission mode, and the code rate loss is less when the frame length is longer. Or further FEC decoding may be performed by concatenated codes, which may use interleavers that are short and may be interleaved regularly, since only a small number of sections per frame may be erased. Compared with the large-scale random interleaver generally needed in the prior art, the interleaver can obviously reduce the complexity of the interleaver, reduce decoding delay and save a large amount of system resources.

To sum up, in the method of the present application, a transmitting device acquires a first signal, and then the transmitting device encodes the first signal according to a preset error correction code to obtain an encoding sequence of the first signal; then, the sending device processes the coding sequence of the first signal according to a set modulation method to obtain an information sequence of the first signal; the sending device converts the first signal into a first electric signal through a digital-to-analog converter, wherein the first electric signal carries an information sequence of the first signal; and finally, the transmitting device converts the first electric signal into a carrier signal through the first converter and then transmits the carrier signal. After receiving the carrier signal, the receiving device converts the carrier signal into a first electric signal through a first converter, and then converts the first electric signal into a first signal through a digital-to-analog converter; the receiving device further processes the first signal according to a set demodulation method to acquire a first information sequence of the first signal; then, according to a preset error correcting code, a standard correction value and a first correction value of the first information sequence are determined, and then, according to the standard correction value and the first correction value of the first information sequence, an angle of phase change of the first signal is determined; and finally, the receiving device processes the phase of the first signal according to the angle of the phase change of the first signal. In the method, the receiving device can determine the standard correction values of a plurality of phase angles and the correction value of the first information sequence according to a preset error correcting code, and further determine and process the angle of the phase change of the first signal according to the correlation value between the correction value of the first information sequence and each standard correction value, so that the phase jump of the signal can be efficiently solved.

Based on the same technical concept, the embodiment of the present application further provides a signal processing apparatus, which has the behavior function of the transmitting apparatus in the method embodiment described above. The signal processing apparatus may include a module or a unit corresponding to one or more of the methods/operations/steps/actions described in the foregoing method embodiments, and the module or the unit may be a hardware circuit, a software circuit, or a combination of a hardware circuit and a software circuit. The device may have a configuration as shown in fig. 9.

As shown in fig. 9, the apparatus 900 may include a receiving unit 901, an encoding unit 902, a modulating unit 903, a digital-to-analog converting unit 904, a first converting unit 906, and a transmitting unit 907, which are described in detail below.

The receiving unit 901 is configured to receive a first signal; the encoding unit 902 is configured to encode the first signal according to a preset error correcting code to obtain an encoding sequence of the first signal; the modulation unit 903 is configured to process a coding sequence of the first signal according to a set modulation method, so as to obtain an information sequence of the first signal; the digital-to-analog conversion unit 904 is configured to convert the first signal to obtain a first electrical signal, where the first electrical signal carries an information sequence of the first signal; the first converting unit 906 is configured to convert the first electrical signal into a carrier signal; the transmitting unit 907 is further configured to transmit the carrier signal.

In a possible implementation manner, the apparatus 900 further includes a digital processing unit 905, configured to adjust the information sequence of the first signal after the modulator processes the coded sequence of the first signal according to a set modulation method to obtain the information sequence of the first signal.

In a possible embodiment, the generator matrix G of the predetermined error correction code includes k rows G₁,g₂,......g_kWherein g is_jIs the jth row vector of the generator matrix, j is a positive integer not greater than k, g₀All-zero row vector, g, expressed as 1 row number of the matrix₀Is the column width of the generator matrix; the first verification matrix H of the preset error correcting code comprises m rows H₁,h₂,......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀Expressed as all-zero row vector with 1 row number of the matrix, h₀Is the column width of the first verification matrix; wherein the generator matrix G satisfies the following formula:

and

or the first verification matrix H, satisfies the following formula:

and f_i(h₀)·H^T≠0；

Wherein rank (·) represents the rank of the matrix, i represents the angle, and f_i(.) representing the corresponding sequence transformation function when the phase of the signal changes by i degrees, p_i(.) represents a change in phase of the signal_iThe position permutation function of the corresponding sequence at angle.

Based on the same technical concept, the embodiment of the present application further provides a signal processing apparatus, which has the behavior function of the receiving apparatus in the foregoing method embodiment. The signal processing apparatus may include a module or a unit corresponding to one or more of the methods/operations/steps/actions described in the foregoing method embodiments, and the module or the unit may be a hardware circuit, a software circuit, or a combination of a hardware circuit and a software circuit. The device may have a configuration as shown in fig. 10.

As shown in fig. 10, the apparatus 1000 may include a receiving unit 1001, a first converting unit 1002, a digital-to-analog converting unit 1003, a demodulating unit 1005, and a phase-jump detecting unit 1006, which are described in detail below.

A receiving unit 1001 for receiving a carrier signal;

the first converting unit 1002 may be configured to convert the carrier signal into a first electrical signal;

the digital-to-analog conversion unit 1003 may be configured to convert the first electrical signal into a first signal;

the demodulation unit 1005 may be configured to process the first signal according to a set demodulation method, so as to obtain a first information sequence of the first signal;

the phase jump detection unit 1006 may be configured to determine a standard correction value and a first correction value of the first information sequence according to a preset error correction code; then, according to the standard correction value and the first correction value of the first information sequence, determining the phase change angle of the first signal; and finally, processing the phase of the first signal according to the angle of the phase change of the first signal.

In a possible embodiment, a digital processing unit 1004 (optional) is further included, and is configured to adjust the first signal after the digital-to-analog conversion unit 1003 converts the first electrical signal into the first signal.

In a possible implementation manner, when determining the standard correction value according to a preset error correction code, the phase jump detection unit 1006 may specifically determine a generator matrix and a first verification matrix according to the preset error correction code; and then, the standard correction value can be calculated according to the information sequence of the preset signal, the generating matrix, the first verification matrix and a preset first correction formula.

In a possible implementation manner, when the standard correction value is obtained through calculation according to an information sequence of a preset signal, the generator matrix, the first verification matrix, and a preset first correction formula, the phase jump detection unit 1006 may be specifically configured to perform multiplication operation on the information sequence of the preset signal and the generator matrix to obtain a second information sequence; then, according to the second information sequence, determining N phase-changed third information sequences corresponding to N angles of phase change of the preset signal; n is a positive integer greater than 0; and finally, substituting each third information sequence and the transpose matrix of the first verification matrix into the preset first correction formula to calculate N standard correction values.

In a possible implementation manner, when determining the first correction value of the first information sequence according to a preset error correction code, the phase jump detection unit 1006 may specifically be configured to determine a fourth information sequence according to the first information sequence, where the fourth information sequence is an information sequence after the phase angle of the first signal is changed; then, a generating matrix and a first verification matrix can be determined according to the preset error correcting code; and finally, substituting the first information sequence and the first verification matrix into a preset first correction formula to obtain a first correction value of the first information sequence.

In a possible embodiment, the generator matrix G of the predetermined error correction code includes k rows G₁,g₂,......g_kWherein g is_jIs the jth row vector of the generator matrix, j is a positive integer not greater than k, g₀All-zero row vector, g, expressed as 1 row number of the matrix₀Is the column width of the generator matrix; the first verification matrix H of the preset error correcting code comprises m rows H₁,h₂,......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀Expressed as all-zero row vector with 1 row number of the matrix, h₀Is the column width of the first verification matrix; wherein, the generator matrix G may satisfy the following formula:

and

or the first verification matrix H, satisfies the following formula:

and f_i(h₀)·H^T≠0；

In a possible embodiment, the preset first correction formula may satisfy the following:

S_i＝f_i(x)*H^T

In a possible implementation manner, when determining the angle of the phase change of the first signal according to the standard correction value and the first correction value of the first information sequence, the phase jump detection unit 1006 may be specifically configured to determine, in advance, N standard correction values corresponding to N different angles of the phase change of a preset signal, where each angle corresponds to one standard correction value, and N is a positive integer greater than 0; then, the N standard correction values and the first correction value are respectively subjected to correlation value calculation to obtain N correlation values; when it is determined that the phase of the preset signal changes by the ith angle, a first correlation value obtained by calculating a corresponding standard correction value and the first correction value is the largest and the first correlation value meets a set condition, the phase change angle of the first signal can be determined to be the ith angle; i is a positive integer value greater than 0 and less than or equal to N; the set conditions comprise that the first correlation value is larger than a first set threshold value, and errors between the first correlation value and other N-1 correlation values are larger than a second set threshold value.

In a possible implementation manner, the apparatus further includes a decoding unit 1007, configured to obtain an information sequence of the phase-processed first signal after the phase jump detection unit 1006 processes the phase of the first signal according to the angle of the phase change of the first signal; and further decoding the information sequence of the first signal after the phase processing according to the preset error correcting code to obtain the information sequence of the first signal after decoding.

In addition, an embodiment of the present application further provides a signal processing device, which may have a structure as shown in fig. 11 and has a behavior function of the transmitting apparatus in the foregoing method embodiment. The apparatus 1000 for processing signals shown in fig. 11 may include a receiver 1101, an encoder 1102, a modulator 1103, a digital processor (optional) 1104, a digital-to-analog converter 1105, a first converter 1106, and a transmitter 1107, where the receiver 1101, the encoder 1102, the modulator 1103, the digital processor (optional) 1104, the digital-to-analog converter 1105, the first converter 1106, and the transmitter 1107 may be configured to be coupled with a memory 1108 (the memory 1108 in the embodiment of the present application may not be limited to this coupling form, and may also exist in other forms, such as being separate from hardware in the apparatus, or being located outside the apparatus 1100), and read and execute instructions in the memory 1108 to implement steps involved in a transmitting apparatus in the method provided by the embodiment of the present application.

The encoder 1102 may be configured to implement the functions of the encoding unit 902 of the transmitting apparatus in fig. 9, for example, the encoder 1102 may be configured to the apparatus 1100 to perform the signal encoding step shown in S301 in the signal processing method shown in fig. 3. The modulator 1103 may be configured to implement the functions of the modulation unit 903 of the transmitting apparatus in fig. 9, for example, the modulator 1103 may be configured to be used by the apparatus 1100 to perform the step shown in S302 in the signal processing method shown in fig. 3. The digital processor 1104 is optional hardware, and can be used to implement the functions of the digital processing unit 904 of the transmitting apparatus in fig. 9, and the information sequence of the first signal can be adjusted after the modulator 1103 executes the step shown as S302 in the signal processing method shown in fig. 3. The dac 1105 may be configured to implement the functions of the dac unit 905 of the transmitting apparatus in fig. 9, for example, the dac 1105 may be configured in the apparatus 1100 to perform the step of converting the first signal into the first electrical signal in S303 in the signal processing method shown in fig. 3. The first converter 1106 may be configured to implement the functions of the first converting unit 906 of the transmitting apparatus in fig. 9, for example, the first converter 1106 may be configured to be used by the apparatus 1100 to perform the step of converting the first electrical signal into the carrier electrical signal in S303 in the signal processing method shown in fig. 3. The transmitter 1107 may be configured to implement the function of the transmitting unit 906 of the transmitting apparatus in fig. 9, for example, the transmitter 1107 may be configured to the apparatus 1100 to perform the step shown in S304 in the signal processing method shown in fig. 3.

Optionally, the apparatus 1100 may further include a memory 1108, where a computer program and instructions are stored, where the memory 1108 may be coupled with the receiver 1101, the encoder 1102, the modulator 1103, the digital processor (optional) 1104, the digital-to-analog converter 1105, the first converter 1106, and the transmitter 1107, and is used for supporting the receiver 1101, the encoder 1102, the modulator 1103, the digital processor (optional) 1104, the digital-to-analog converter 1105, the first converter 1106, and the transmitter 1107 to call up the computer program and instructions in the memory 1108 so as to implement the steps involved in the transmitting apparatus in the method provided by the embodiments of the present application; additionally, the memory 1108 may also be used for storing information or data related to embodiments of the methods of the present application, e.g., for storing data, information, and instructions necessary to enable the receiver 1101 and/or the transmitter 1107 to perform an interaction.

The embodiment of the present application further provides a signal processing device, which may have a structure as shown in fig. 12 and has a behavior function of the receiving apparatus in the above method embodiment. The apparatus 1200 for processing signals as shown in fig. 12 may comprise a receiver 1201, a first converter 1202, a digital-to-analog converter 1203, a digital processor (optional) 1204, a demodulator 1205, a phase-jump detector 1206, a decoder 1207. Optionally, the signal processing device 1200 may further comprise a transmitter, which is not described in detail in this application.

The receiver 1201, the first converter 1202, the digital-to-analog converter 1203, the digital processor (optional) 1204, the demodulator 1205, the phase-jump detector 1206, and the decoder 1207 may be configured to be coupled to the memory 1208 (the memory 1208 may not be limited to this coupling form in this embodiment of the present application, and may also exist in other forms, for example, separately provided from hardware in the apparatus, or disposed outside the apparatus 1200), and read and execute instructions in the memory 1208 to implement steps involved in receiving a communication apparatus in the method provided in this embodiment of the present application.

The receiver 1201 may be configured to implement the functions of the receiving unit 1001 of the receiving apparatus in fig. 10, for example, the receiver 1201 may be configured to perform the signal encoding step shown in S304 in the signal processing method shown in fig. 3 by the apparatus 1200.

The first converter 1202 may be configured to implement the functions of the first conversion unit 1002 of the receiving apparatus in fig. 10, for example, the first converter 1202 may be configured to the apparatus 1100 to perform the step of converting the carrier signal into the first electrical signal in S305 in the signal processing method shown in fig. 3.

The digital-to-analog converter 1203 may be configured to implement the function of the digital-to-analog converting unit 1003 of the receiving apparatus in fig. 10, for example, the digital-to-analog converter 1203 may be configured to perform the step of converting the first electrical signal into the first signal in S305 in the signal processing method shown in fig. 3 by the apparatus 1200.

The digital processor 1104 is optional hardware, and can be used to implement the functions of the digital processing unit 1004 of the receiving apparatus in fig. 10, and the first signal can be adjusted after the digital-to-analog converter 1203 executes the step shown as S305 in the signal processing method shown in fig. 3.

The demodulator 1205 may be configured to implement the function of the demodulation unit 1005 of the receiving apparatus in fig. 10, for example, the demodulator 1205 may be configured to the apparatus 1200 to execute the step S306 in the signal processing method shown in fig. 3.

The phase jump detector 1206 can be used to realize the functions of the phase jump detection unit 1006 of the receiving apparatus in fig. 10, for example, the phase jump detector 1206 can be used in the apparatus 1200 to execute the steps shown in S307-S309 in the signal processing method shown in fig. 3.

The decoder 1207 may be configured to implement the functions of the decoding unit 1007 of the receiving apparatus shown in fig. 10, for example, the decoder 1207 may be configured to the apparatus 1200 to execute the step S310 in the signal processing method shown in fig. 3.

Optionally, the apparatus 1200 may further include a memory 1208, in which a computer program and instructions are stored, where the memory 1208 may be coupled with the receiver 1201, the first converter 1202, the digital-to-analog converter 1203, the digital processor (optional) 1204, the demodulator 1205, the phase jump detector 1206, and the decoder 1207, and is configured to support the receiver 1201, the first converter 1202, the digital-to-analog converter 1203, the digital processor (optional) 1204, the demodulator 1205, the phase jump detector 1206, and the decoder 1207 to call the computer program and instructions in the memory 1208, so as to implement the steps involved in the receiving apparatus in the method provided in the embodiment of the present application; in addition, the memory 1208 can be used for storing information or data related to the embodiments of the method of the present application, for example, for storing data, information, and instructions necessary for supporting the receiver 1201 and/or the transmitter to implement the interaction.

Based on the same concept as the above method embodiments, the present application also provides a computer program product, which when called by a computer can perform the method as referred to in the method embodiments and any possible design of the above method embodiments.

Based on the same concept as the above method embodiments, the present application also provides a chip, which may include a processor and an interface circuit, for implementing the method as referred to in any one of the possible implementations of the above method embodiments, wherein "coupled" means that two components are directly or indirectly joined to each other, which may be fixed or movable, which may allow flowing liquid, electric, electrical or other types of signals to be communicated between the two components.

Through the above description of the embodiments, those skilled in the art will clearly understand that the embodiments of the present application can be implemented by hardware, firmware, or a combination thereof. When implemented in software, the functions described above may be stored on or transmitted over as one or more instructions or code on a computer-readable medium. Computer-readable media includes both computer storage media and communication media including any medium that facilitates transfer of a computer program from one place to another. A storage media may be any available media that can be accessed by a computer. Taking this as an example but not limiting: the computer-readable medium may include RAM, ROM, an Electrically Erasable Programmable Read Only Memory (EEPROM), a compact disc read-Only memory (CD-ROM) or other optical disk storage, magnetic disk storage or other magnetic storage devices, or any other medium that can be used to carry or store desired program code in the form of instructions or data structures and that can be accessed by a computer. Furthermore, the method is simple. Any connection is properly termed a computer-readable medium. For example, if software is transmitted from a website, a server, or other remote source using a coaxial cable, a fiber optic cable, a twisted pair, a Digital Subscriber Line (DSL), or wireless technologies such as infrared, radio, and microwave, the coaxial cable, the fiber optic cable, the twisted pair, the DSL, or the wireless technologies such as infrared, radio, and microwave are included in the fixation of the medium. Disk and disc, as used in accordance with embodiments of the present application, includes Compact Disc (CD), laser disc, optical disc, Digital Versatile Disc (DVD), floppy disk and blu-ray disc where disks usually reproduce data magnetically, while discs reproduce data optically with lasers. Combinations of the above should also be included within the scope of computer-readable media.

In short, the above description is only an example of the present application, and is not intended to limit the scope of the present application. Any modifications, equivalents, improvements and the like made in accordance with the disclosure of the present application should be included in the scope of the present application.

Claims

1. A method of processing a signal, the method comprising:

the sending device acquires a first signal;

the transmitting device encodes the first signal according to a preset error correcting code to obtain an encoding sequence of the first signal;

the sending device processes the coding sequence of the first signal according to a set modulation method to obtain an information sequence of the first signal;

the sending device converts the first signal to obtain a first electric signal, and the first electric signal carries an information sequence of the first signal;

the transmitting device converts the first electric signal to obtain a carrier signal;

the transmitting device transmits the carrier signal.

2. The method of claim 1, wherein after the transmitting device processes the encoded sequence of the first signal according to the set modulation method to obtain the information sequence of the first signal, the method further comprises:

the transmitting device adjusts the information sequence of the first signal using digital processing techniques.

3. The method according to claim 1, wherein the predetermined error correction code generator matrix G comprises k rows G₁，g₂，...g_kWherein g is_jIs the jth row vector of the generator matrix, j is a positive integer not greater than k, g₀All-zero row vector, g, expressed as the number of rows of the matrix being 1₀Is the column width of the generator matrix; the first verification matrix H of the preset error correcting code comprises m rows H₁，h₂，......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀All-zero row vector, h, expressed as the number of rows of the matrix being 1₀Is the column width of the first verification matrix; wherein the generator matrix G satisfies the following formula:

and

or the first verification matrix H, satisfies the following formula:

and f_i(h₀)·H^T≠0；

Wherein rank (·) represents the rank of the matrix, i represents the angle, and f_i(. DEG) a corresponding sequence transformation function, p, representing the phase of the signal as it changes by i degrees_i(. cndot.) represents the position permutation function of the corresponding sequence when the phase of the signal changes by i degrees.

4. A method of processing a signal, the method comprising:

the receiving device receives a carrier signal;

the receiving device converts the carrier signal into a first electric signal;

the receiving device converts the first electric signal into a first signal;

the receiving device processes the first signal according to a set demodulation method to acquire a first information sequence of the first signal;

the receiving device determines a standard correction value and a first correction value of the first information sequence according to a preset error correcting code;

the receiving device determines the angle of the phase change of the first signal according to the standard correction value and the first correction value of the first information sequence;

the receiving device processes the phase of the first signal according to the angle of the phase change of the first signal.

5. The method of claim 4, wherein after the receiving device converts the first electrical signal into a first signal, the method further comprises:

the receiving device adjusts the first signal using digital processing techniques.

6. The method of claim 4, wherein the receiving device determines the standard correction value based on a preset error correction code, comprising:

the receiving device determines a generating matrix and a first verification matrix according to the preset error correcting code;

and the receiving device calculates to obtain the standard correction value according to an information sequence of a preset signal, the generating matrix, the first verification matrix and a preset first correction formula.

7. The method of claim 6, wherein the step of calculating the standard correction value by the receiving device according to the information sequence of the predetermined signal, the generating matrix and the first verifying matrix, and a predetermined first correction formula comprises:

the receiving device multiplies the information sequence of the preset signal by the generating matrix to obtain a second information sequence;

the receiving device determines N phase-changed third information sequences corresponding to N angles of phase change of the preset signal according to the second information sequence; n is a positive integer greater than 0;

and the receiving device substitutes each third information sequence and the transpose matrix of the first verification matrix into the preset first correction formula to calculate and obtain N standard correction values.

8. The method of claim 4, wherein the receiving device determining a first correction value for the first information sequence based on a preset error correction code comprises:

the receiving device determines a fourth information sequence according to the first information sequence, wherein the fourth information sequence is the information sequence after the phase angle of the first signal is changed;

and the receiving device substitutes the fourth information sequence and the first verification matrix into a preset first correction formula to obtain a first correction value of the first information sequence.

9. Method according to any of claims 6 to 8, wherein the generator matrix of the predetermined error correction code comprises k rows g₁，g₂，......g_kWherein, g_jIs the jth row vector of the generator matrix, j is a positive integer not greater than k, g₀All-zero row vector, g, expressed as the number of rows of the matrix being 1₀Is the column width of the generator matrix; m rows h are contained in the first verification matrix of the preset error correcting code₁，h₂，......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀All-zero row vector, h, expressed as the number of rows of the matrix being 1₀Is the column width of the first verification matrix; wherein the generator matrix G satisfies the following formula:

and

or the first verification matrix H, satisfies the following formula:

and f_i(h₀)·H^T≠0；

10. The method according to any one of claims 6 to 8, wherein the preset first correction formula satisfies:

S_i＝f_i(x)*H^T

wherein i represents the angle size, s_iIndicating the corresponding correction value for a phase change of the signal by i degrees, f_i(. cndot.) represents the corresponding sequence transformation function when the phase of the signal changes by i degrees, x is represented as a row vector with a matrix row number of 1, the length of x represents the column width of the first validation matrix, H^TA transpose matrix representing the first validation matrix.

11. The method of claim 4, wherein said receiving means determining an angle of phase change of said first signal based on said standard correction value and a first correction value of said first information sequence, comprises:

the receiving device determines that the standard correction values comprise N corresponding standard correction values when the phase of a preset signal changes by N different angles, each angle corresponds to one standard correction value, and N is a positive integer greater than 0;

the receiving device respectively carries out correlation value calculation on the N standard correction values and the first correction value to obtain N correlation values;

when the receiving device determines that a corresponding standard correction value and the first correction value are calculated to obtain a maximum first correlation value when the phase of the preset signal changes by an ith angle, and the first correlation value meets a set condition, the receiving device determines that the phase change angle of the first signal is the ith angle; i is a positive integer value greater than 0 and less than or equal to N;

the set conditions comprise that the first correlation value is larger than a first set threshold value, and errors between the first correlation value and other N-1 correlation values are larger than a second set threshold value.

12. The method of claim 4, wherein after the receiving device processes the phase of the first signal according to the angle at which the phase of the first signal changes, the method further comprises:

the receiving device acquires an information sequence of the first signal after phase processing;

and the receiving device decodes the information sequence of the first signal after the phase processing according to the preset error correcting code to obtain the information sequence of the first signal after decoding.

13. A transmitting apparatus, comprising:

a receiver for receiving a first signal;

the encoder is used for encoding the first signal according to a preset error correcting code to obtain an encoding sequence of the first signal;

the modulator is used for processing the coding sequence of the first signal according to a set modulation method to obtain an information sequence of the first signal;

the digital-to-analog converter is used for converting the first signal to obtain a first electric signal, and the first electric signal carries an information sequence of the first signal;

a first converter for converting the first electrical signal into a carrier signal;

a transmitter for transmitting the carrier signal.

14. The transmitting apparatus of claim 13, further comprising a digital processor for adjusting the information sequence of the first signal after the modulator processes the encoded sequence of the first signal according to a set modulation method to obtain the information sequence of the first signal.

15. The transmission apparatus according to claim 13, wherein the generator matrix G of the predetermined error correction code includes k rows G₁，g₂，......g_kWherein g is_jIs the jth row vector of the generator matrix, j is a positive integer not greater than k, g₀All-zero row vector, g, expressed as the number of rows of the matrix being 1₀Is the column width of the generator matrix; the packet in the first verification matrix H of the preset error correcting codeContaining m rows h₁，h₂，......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀All-zero row vector, h, expressed as the number of rows of the matrix being 1₀Is the column width of the first verification matrix; wherein the generator matrix G satisfies the following formula:

and

or the first verification matrix H, satisfies the following formula:

and f_i(h₀)·H^T≠0；

16. A receiving apparatus, comprising:

a receiver for receiving a carrier signal;

the first converter is used for converting the carrier signal into a first electric signal;

the digital-to-analog converter is used for converting the first electric signal into a first signal;

the demodulator is used for processing the first signal according to a set demodulation method to obtain a first information sequence of the first signal;

a phase jump detector for determining a standard correction value and a first correction value of the first information sequence according to a preset error correction code; determining an angle of phase change of the first signal based on the standard correction value and a first correction value of the first information sequence; and processing the phase of the first signal according to the angle of the phase change of the first signal.

17. The receiving device of claim 16, further comprising a digital processor for conditioning the first signal after the digital-to-analog converter converts the first electrical signal into the first signal.

18. The receiving device according to claim 16, wherein the phase-jump detector, when determining the standard correction value based on a preset error correction code, is specifically configured to:

determining a generating matrix and a first verification matrix according to the preset error correcting code;

and calculating to obtain the standard correction value according to an information sequence of a preset signal, the generating matrix, the first verification matrix and a preset first correction formula.

19. The receiving apparatus as claimed in claim 18, wherein the phase jump detector, when calculating the standard correction value according to an information sequence of a preset signal, the generating matrix, the first verifying matrix, and a preset first correction formula, is specifically configured to:

multiplying the information sequence of the preset signal and the generating matrix to obtain a second information sequence;

determining N phase-changed third information sequences corresponding to N angles of phase change of the preset signal according to the second information sequence; n is a positive integer greater than 0;

and substituting each third information sequence and the transposed matrix of the first verification matrix into the preset first correction formula to calculate and obtain N standard correction values.

20. The receiving device according to claim 16, wherein the phase-jump detector, when determining the first correction value of the first information sequence according to a preset error correction code, is specifically configured to:

determining a fourth information sequence according to the first information sequence, wherein the fourth information sequence is the information sequence of the first signal after the phase angle is changed;

and substituting the first information sequence and the first verification matrix into a preset first correction formula to obtain a first correction value of the first information sequence.

21. The reception apparatus according to any one of claims 18 to 20, wherein the predetermined error correction code generator matrix G includes k rows G₁，g₂，......g_kWherein g is_jIs the jth row vector of the generator matrix, j is a positive integer not greater than k, g₀All-zero row vector, g, expressed as the number of rows of the matrix being 1₀Is the column width of the generator matrix; the first verification matrix H of the preset error correcting code comprises m rows H₁，h₂，......h_mWherein h is_nIs the n-th row vector of the first verification matrix, n is a positive integer not greater than m, h₀All-zero row vector, h, expressed as the number of rows of the matrix being 1₀Is the column width of the first verification matrix; wherein the generator matrix G satisfies the following formula:

and

or the first verification matrix H, satisfies the following formula:

and f_i(h₀)·H^T≠0；

22. The receiving apparatus according to any one of claims 18 to 20, wherein the preset first correction formula satisfies:

S_i＝f_i(x)*H^T

23. The receiving device of claim 16, wherein the phase-jump detector, when determining the angle of change of the phase of the first signal based on the standard correction value and the first correction value of the first information sequence, is specifically configured to:

determining N standard correction values corresponding to N different angles of phase change of a preset signal in the standard correction values, wherein each angle corresponds to one standard correction value, and N is a positive integer greater than 0;

respectively carrying out correlation value calculation on the N standard correction values and the first correction value to obtain N correlation values;

when determining that a first correlation value obtained by calculating a corresponding standard correction value and the first correction value is the largest when the phase of the preset signal changes by the ith angle, and the first correlation value meets a set condition, determining that the phase change angle of the first signal is the ith angle; i is a positive integer value greater than 0 and less than or equal to N;

24. The receiving apparatus according to claim 16, further comprising a decoder for obtaining an information sequence of the phase-processed first signal after the phase jump detector processes the phase of the first signal according to an angle of change of the phase of the first signal; and decoding the information sequence of the first signal after the phase processing according to the preset error correcting code to obtain the information sequence of the first signal after decoding.

25. A computer-readable storage medium storing computer instructions which, when executed on a computer, cause the computer to perform the method of any one of claims 1 to 3 or perform the method of any one of claims 4 to 12.