CN114285183B - Modularized reconfigurable wireless charging system - Google Patents
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- CN114285183B CN114285183B CN202111492927.8A CN202111492927A CN114285183B CN 114285183 B CN114285183 B CN 114285183B CN 202111492927 A CN202111492927 A CN 202111492927A CN 114285183 B CN114285183 B CN 114285183B
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Abstract
The application provides a modularized reconfigurable wireless charging system, and in the technical scheme disclosed by the application, as the modules of the same type are not adjacent, the coupling between different transmitting coils is small and can be ignored. Meanwhile, the class A square transmitting end module and the class B square transmitting end module work at different frequencies, and the decoupling on the equivalent circuit can be realized by matching with the filtering characteristic of the resonance compensation network in the transmitting end module. After the technical scheme disclosed by the application is adopted, the reconfigurable emission plane and the random expansion of the charging area are realized through area division, so that the offset problem under single load charging can be solved, standardized emission end design schemes can be provided for receiving terminals with different sizes and power levels, and the system has the capability of charging multiple terminals simultaneously.
Description
Technical Field
The present application relates to a wireless charging system.
Background
In recent years, wireless power transmission technology based on magnetic coupling resonance has been widely applied to low-power intelligent terminals such as headphones and mobile phones due to its excellent energy transmission characteristics. At present, all countries are aware of the importance of industrial manufacturing, and need to realize crossing development by means of new technologies such as intelligent manufacturing, 5G, internet of things, artificial intelligence and the like. In this process, it is important to remove the last line of "least intelligence" for various intelligent terminals (e.g. unmanned aerial vehicle, mobile robot, unmanned logistics vehicle) through wireless power transmission technology. The wireless charging system utilizing magnetic coupling at least needs two coils to form a coupler to realize energy transfer, and the coil position deviation can cause the coupling coefficient to be reduced so as to influence the transmission performance. When the receiving coil is embedded in various terminals, it is necessary to ensure that there is a sufficient magnetic field in the charging area in order to satisfy the positional freedom. The customized design aiming at different scenes can meet the application requirements to a certain extent, but the research and development cost and the maintenance cost of the whole system are extremely high, and the large-scale popularization is not facilitated. The target area is divided into N identical modules by using a modularized concept, so that the design and control of the system can be greatly simplified as long as each transmitting module can work independently and are not mutually influenced. Meanwhile, the modular design can be used for conveniently customizing the charging area, and is suitable for more intelligent terminals with different power requirements. Therefore, critical issues in planar modular wireless charging systems must be addressed.
In a conventional wireless charging system, a single transmitting end and a single receiving end are generally adopted, and an LCC-S system shown in fig. 1 is more typical. The transmitting end of the LCC-S system includes an inverting, transmitting end compensating network (Lt, ct, ctx) and a transmitting coil Ltx. The receiving end of the LCC-S system comprises a receiving coil Lrx, a receiving end compensation network (Cr), a rectifier and a load R. In the LCC-S system shown in fig. 1, the parameters of each equivalent element need to satisfy the following formula (1):
in the formula (1), w is the angular frequency of the transmitting end and the receiving end.
Currently, multi-coil technology has been widely used in the structural design of couplers. The transmitting end can obviously improve the offset range of the receiving end by using a multi-coil design. However, the electromagnetic coupling between the coils of the transmitting end increases unnecessary circulation current, which greatly increases the complexity of system design and control. For example, in the case of the modular wireless charging system shown in fig. 2, where there is cross coupling between the transmitting coils, such as M12, M1n, M2n in fig. 2, these cross couplings may increase the complexity of the design of the system, and the conditions satisfied by the system will be significantly more complex than equation (1) in order to satisfy the resonance condition and the output load independence.
Therefore, in order to achieve a modular design, ensuring independence between modules, the cross-coupling between the transmit coils must be eliminated, for which the following solutions are proposed by the person skilled in the art:
the first solution is that the decoupling between two or three coils can be realized by the customized design and reasonable placement of the coils, but the principle cannot be used for the scene of any number of coils, and the requirement of modularized design is difficult to meet.
Solution two) through the method of transmitting coil tiling, cooperate the switching network to open a certain coil selectively, although can avoid the adverse effect of cross coupling, because only single transmitting coil is stimulated, can't adapt to the receiving terminal of equidimension.
Solution three) decoupling of the equivalent circuit level can be achieved by additional introduction elements, but the method requires the actual physical connection introduced, which is not applicable to modular systems at all.
Disclosure of Invention
The application aims to solve the technical problems that: some key issues of modular design for multi-coil technology currently have no reasonable solution.
In order to solve the technical problems, the technical proposal of the application provides a modularized reconfigurable wireless charging system which is characterized by comprising a plurality of wireless charging systems with f working frequencies A A first type of transmitting end module and a plurality of operating frequencies f B The second type of transmitting terminal module forms a charging area and a dual-frequency receiving terminal module, wherein:
in the charging region, the operating frequency f A Not equal to the operating frequency f B The similar transmitting end modules are not adjacent;
the first type transmitting end module comprises a first type inverter circuit, a first type transmitting end compensation network and a first type transmitting coil, wherein: the output frequency of the first inverter circuit is f A Is a signal of an alternating current (ac); a first type filter is connected in series in a first type transmitting end compensation network, and the first type filter is used for passing the frequency f A And block the frequency f B By blocking the frequency f B The first type of filter is also used for blocking the controlled source formed in the first type of transmitting end module by the second type of transmitting coil of the second type of transmitting end modulef A Resonance with a first type of transmitting coil;
the second-type transmitting end module comprises a second-type inverter circuit, a second-type transmitting end compensation network and a second-type transmitting coil, wherein: the output frequency of the second type inverter circuit is f B Is a signal of an alternating current (ac); a second type filter is connected in series in a second type transmitting end compensation network, and the second type filter is used for passing the frequency f B And block the frequency f A By blocking the frequency f A The second type of filter is also used for blocking the controlled source formed by the first type of transmitting coil of the first type of transmitting end module in the second type of transmitting end module at the frequency f B Resonance with a second type of transmitting coil;
the dual-frequency receiving terminal module comprises a multiplexing frequency f A Operating frequency f B A lower receiving coil and a receiving end compensating circuit; when only the first square transmitting end module or the second square transmitting end module exists, the equivalent capacitor Crx_eq of the receiving end compensation circuit and the receiving coil are in series resonance, and the parameter design meets the following formula:
wherein Lrx is equivalent inductance, w A Is the angular frequency of the first square transmitting end module and has w A ＝2πf A ；w B Is the angular frequency of the second square transmitting end module and has w B ＝2πf B 。
Preferably, the first type of transmitting end module and the plurality of second type of transmitting end modules are square transmitting end modules, any two first type of transmitting end modules or any two second type of transmitting end modules are arranged diagonally, and the first type of transmitting end modules and the second type of transmitting end modules are arranged adjacently.
In the technical scheme disclosed by the application, as the similar modules are not adjacent, the coupling between different transmitting coils is small and can be ignored. Meanwhile, the class A square transmitting end module and the class B square transmitting end module work at different frequencies, and the decoupling on the equivalent circuit can be realized by matching with the filtering characteristic of the resonance compensation network in the transmitting end module.
After the technical scheme disclosed by the application is adopted, the reconfigurable emission plane and the random expansion of the charging area are realized through area division, so that the offset problem under single load charging can be solved, standardized emission end design schemes can be provided for receiving terminals with different sizes and power levels, and the system has the capability of charging multiple terminals simultaneously.
Drawings
FIG. 1 illustrates a conventional LCC-S wireless charging system;
FIG. 2 illustrates a system architecture of a prior art modular wireless charging system;
fig. 3 illustrates a compensation network with filtering characteristics;
fig. 4 illustrates a filter ctx_eq1 with Notch points;
fig. 5 illustrates a filter ctx_eq2 with Notch points;
FIG. 6 illustrates a dual frequency receiver module;
FIG. 7 illustrates a receiver side compensation circuit;
FIG. 8 illustrates that the dual-band receiver module may operate in a dual-band mode when receiving energy from both class A and class B square transmitter modules;
FIG. 9 illustrates a wireless charging system of a dual frequency transmit module;
fig. 10A illustrates the filter characteristics of the transmitting end TX 1;
fig. 10B illustrates the filter characteristics of the transmitting end TX 2;
fig. 10C illustrates the filtering characteristics of the receiving end RX;
FIG. 11 illustrates a dual-frequency two-transmit single-receive system scheme;
fig. 12A to 12C illustrate specific simulation results, in which: FIG. 12A illustrates a system waveform at 100kHz at a single transmitting end; FIG. 12B illustrates the system waveform at 300kHz at a single transmitting end; fig. 12C illustrates the system waveform when the dual-frequency transmitting terminal 100 is more than 300 khz.
Detailed Description
The application will be further illustrated with reference to specific examples. It is to be understood that these examples are illustrative of the present application and are not intended to limit the scope of the present application. Furthermore, it should be understood that various changes and modifications can be made by one skilled in the art after reading the teachings of the present application, and such equivalents are intended to fall within the scope of the application as defined in the appended claims.
The same coil tiling inevitably has electromagnetic coupling, and the application is suitable for realizing modularized design through decoupling of an equivalent circuit layer. Specifically, the present application proposes to operate at frequency f A Class a square transmitting end module operating at frequency f B Class B square transmitting end module f A ≠f B . And under the condition that the same type of modules are not adjacent, a plurality of A-type square transmitting end modules and a plurality of B-type square transmitting end modules form a charging area.
For the sake of brevity, the present embodiment uses only two-phase transmitting coils as an example to further explain the technical solution of the present application. The design idea of the application is as follows:
as shown in fig. 3, the a-type square transmitting end module and the B-type square transmitting end module are selected to invert at different frequencies, and the frequency of the alternating current signal output by the inverting circuit in the a-type square transmitting end module is f A The frequency of the alternating current signal output by the inverter circuit in the B-class square transmitting end module is f B ，f A ≠f B . Thus, the frequency band of the energy wave of each phase of the alternating current signal output by the inverter circuit in the class A square transmitting end module is different from that of the energy wave of each phase of the alternating current signal output by the inverter circuit in the class B square transmitting end module.
The filter is connected in series with the transmitting end compensation network in the A type square transmitting end module and the B type square transmitting end module, the filter Ctx_eq1 is connected in series with the A type square transmitting end module, and the filter Ctx_eq2 is connected in series with the B type square transmitting end module. The filter Ctx_eq1 and the filter Ctx_eq2 are respectively at the frequency f A Frequency f B Different filtering and frequency selecting characteristics are provided, so that the influence caused by cross coupling is eliminated. When the filter Cthe transmission coil Ltx of the class B square transmitting end module forms a controlled source (jw) in the class a square transmitting end module in the presence of tx_eq1 B X M12 x ILtx 2) will be blocked by the filter ctx_eq1 filtering characteristic. Similarly, the filter ctx_eq2 in the class B square transmitting end module isolates the influence of the transmitting coil Ltx1 in the class a square transmitting end module. In this way, under different working frequencies, the equivalent circuit decoupling can be realized by utilizing the filter characteristics of the compensation network. Of course, the design principle of the filter ctx_eq1 and the filter ctx_eq2 includes two:
the resonance conditions of the transmitter coil Ltx in the class A square transmitter module and the transmitter coil Ltx in the class B square transmitter module are respectively met, as shown in the formula (1);
and (II) respectively meeting the filtering characteristics, namely, a filter Ctx_eq1 in the A-type square transmitting end module can filter out the influence caused by the B-type square transmitting end module, and a filter Ctx_eq2 in the B-type square transmitting end module can filter out the influence caused by the A-type square transmitting end module.
In the design process, the selection of the filter ctx_eq1 and the filter ctx_eq2 is not unique, and the design method proposed in this embodiment is Notch point filtering, and for the equivalent circuit of the filter ctx_eq1 and the filter ctx_eq2 shown in fig. 4 and fig. 5, the equivalent elements thereof satisfy the following formula:
w A is the angular frequency of a square transmitting end module of A type and hasw B Is the angular frequency of a B-type square transmitting end module and is +.>Ctx_eq1 and ctx_eq2 are equivalent capacitances of the filter ctx_eq1 and the filter ctx_eq2 shown in fig. 4 and fig. 5, respectively; ltx1 and Ltx are the equivalent inductance of the transmitting coil of the class a square transmitting end module and the equivalent inductance of the transmitting coil of the class B square transmitting end module, respectively.
The application has a double-frequency receiving terminal module, and the design method is as follows:
different terminals have different receiving areas, and the magnetic field of the transmitting end can be fully utilized by using the receiving coils with the sizes suitable for the terminals. When a class A square transmitting end module and a class B square transmitting end module exist in the system, the dual-frequency receiving terminal module provided by the application can select a proper transmitting end to transmit energy according to the working condition, so that three conditions exist: only the A-type square transmitting end module is required to work, only the B-type square transmitting end module is required, and the A-type square transmitting end module and the B-type square transmitting end module are required to work together. Therefore, the dual-frequency receiving terminal module needs to simultaneously receive the energy of two frequency bands, and the design process of the dual-frequency receiving terminal module is as follows:
according to the formula (1), the design of the receiving end is very simple under a single frequency, and the compensation circuit only needs to meet the requirement of resonance of the receiving coil under the working frequency. However, in the dual-frequency system, in order not to increase the number and volume of the receiving coils, the present application needs to multiplex the receiving coils Lrx at the operating frequency fA and the operating frequency fB, and can operate at both frequencies at the same time. Therefore, in the application, the compensation circuit of the dual-frequency receiving terminal module needs to present different capacitance values under different frequencies, so the parameter design satisfies the following formula:
in the formula (4), lrx is an equivalent inductance of a receiving coil of the dual-frequency receiving terminal module, and crx_eq is an equivalent capacitance of a compensation circuit of the dual-frequency receiving terminal module.
The crx_eq has different values according to different frequencies, and the calculation method is that the impedance is connected in series and parallel, which is not described herein. When the formula (4) is satisfied, when only the square transmitting end module of the A type exists, the equivalent capacitor Crx_eq can be in series resonance with the receiving coil of the dual-frequency receiving terminal module, and the system can work as in the traditional mode. Similarly, when only the square transmitting end module of class B is provided, the equivalent capacitor crx_eq will also resonate in series with the receiving coil of the dual-frequency receiving terminal module, and the system will work as in the conventional mode. Therefore, the dual-frequency receiving terminal module can work under any A-type square transmitting end module and B-type square transmitting end module.
When the A-type square transmitting end module and the B-type square transmitting end module exist at the same time, the dual-frequency receiving terminal module can work in a dual-frequency mode. When the transmitting end simultaneously has the A-type square transmitting end module and the B-type square transmitting end module, the controlled source model of the receiving end is shown on the left side of the figure 8, and the receiving coil Lrx and the compensation network Crx_eq can be equivalently regarded as shown on the right side of the figure 8 through the design of an equivalent circuit, and then the actual circuit parameters can be reversely deduced from the right side of the figure 8. At this time, lrx is made similar to the conventional receiver-side system -1 *Crx _1 ＝1/w A 2 ,Lrx -2 *Crx _2 ＝1/w B 2 Thus, two controlled sources can see the network of series resonance under respective frequency, so that energy under two frequencies can be simultaneously transferred to the rectifier bridge, and then the double-frequency alternating current energy can be converted into direct current through the rectifier bridge, thereby realizing the receiving of the double-frequency energy. The parameter design meets the following formula:
where sLRx represents the impedance in the complex frequency domain, the inductance impedance in the complex frequency domain: z(s) =sl, L represents inductance, s is complex frequency; 1/sCrx_eq represents the capacitive impedance in the complex frequency domain, the capacitive impedance in the complex frequency domain: z(s) =1/sC, C represents capacitance, s is complex frequency.
The principle is to calculate the impedance of two circuits and then obtain the parameters of the actual circuit by using the coefficient consistency principle, wherein the parameters of the circuit are not unique.
The above expression is an expanded form of the third expression in the expression (5), the meaning of the expression is to calculate the impedance of the two circuits in fig. 8 in the complex frequency domain, where s represents the complex frequency, sL represents the impedance in the inductive complex frequency domain, and 1/sC represents the impedance in the capacitive complex frequency domain, so that the meaning of each expression is not repeated here, and specific reference can be made to fig. 8 and 5. By combining the homogeneous phases, each parameter in Crx_eq can be obtained when the consistency of the coefficients is ensured.
The A-type square transmitting end module and the B-type square transmitting end module in the application work at different frequencies, the same modules are arranged diagonally, and different modules are arranged adjacently, so that the cross coupling of transmitting coils among the same kind of modules is negligible, and the different kinds of modules are suitable for realizing decoupling through an equivalent circuit layer.
As shown in fig. 9, in the design process, a specific accounting 1 is required to be designed according to the frequency of the transmitting end, as shown in fig. 10A, the filtering characteristic of the transmitting end TX1, which indicates that it can pass through the frequency f A But can block the frequency f B Is a function of the energy of the (c). Similarly, the graph 10B compensation 2 can be tuned to a frequency f B But can block the frequency f A Through such filtering characteristics to achieve the electrical decoupling of TX1 and TX 2. Simultaneously designs the COM RX parameter of the receiving end, and the filtering characteristic of the COM RX parameter is that the frequency f can be received simultaneously A And frequency f B And the dual-frequency energy of any transmitting end or dual-transmitting end is received. It should be noted that in the present application, the circuit components of the compensation network are not unique in composition and shape, and parameters are not unique, and only the above filtering characteristics need to be satisfied.
According to the above technical solution, a set of topology shown in fig. 11 and parameters shown in table 1 below can be designed, but it should be noted that the topology shown in fig. 11 and parameters shown in table 1 below are not only used.
Table 1: dual-frequency two-emission system parameter
As described above, the simulation results show that: in a dual-frequency two-transmit system, a specific compensation network can eliminate the influence of cross coupling between transmit coils and realize dual-frequency energy reception. In addition, the receiving end can work normally even under single phase, namely single frequency. Therefore, the system can select different transmitting ends according to the characteristics of the receiving ends, and the transmitting ends can be modularized, so that more system possibilities are provided.
Claims (2)
1. A modular reconfigurable wireless charging system of the type comprising a plurality of operating frequencies f A A first type of transmitting end module and a plurality of operating frequencies f B The second type of transmitting terminal module forms a charging area and a dual-frequency receiving terminal module, wherein:
in the charging region, the operating frequency f A Not equal to the operating frequency f B The similar transmitting end modules are not adjacent;
the first type transmitting end module comprises a first type inverter circuit, a first type transmitting end compensation network and a first type transmitting coil, wherein: the output frequency of the first inverter circuit is f A Is a signal of an alternating current (ac); a first type filter is connected in series in a first type transmitting end compensation network, and the first type filter is used for passing the frequency f A And block the frequency f B By blocking the frequency f B The first type of filter is also used for blocking the controlled source formed by the second type of transmitting coil of the second type of transmitting end module in the first type of transmitting end module at the frequency f A Resonance with a first type of transmitting coil;
the second type transmitting terminal module comprises a second type inverter circuit, a second type transmitting terminal compensation network and a second type transmitting terminalA coil, wherein: the output frequency of the second type inverter circuit is f B Is a signal of an alternating current (ac); a second type filter is connected in series in a second type transmitting end compensation network, and the second type filter is used for passing the frequency f B And block the frequency f A By blocking the frequency f A The second type of filter is also used for blocking the controlled source formed by the first type of transmitting coil of the first type of transmitting end module in the second type of transmitting end module at the frequency f B Resonance with a second type of transmitting coil;
the dual-frequency receiving terminal module comprises a multiplexing frequency f A Operating frequency f B A lower receiving coil and a receiving end compensating circuit; when only the first square transmitting end module or the second square transmitting end module exists, the equivalent capacitor Crx_eq of the receiving end compensation circuit and the receiving coil are in series resonance, and the parameter design meets the following formula:
wherein Lrx is equivalent inductance, w A Is the angular frequency of the first square transmitting end module and has w A ＝2πf A ；w B Is the angular frequency of the second square transmitting end module and has w B ＝2πf B 。
2. The modular reconfigurable wireless charging system of claim 1, wherein the first type of transmitting end module and the plurality of second type of transmitting end modules are square transmitting end modules, any two of the first type of transmitting end modules or any two of the second type of transmitting end modules are arranged diagonally, and the first type of transmitting end modules and the second type of transmitting end modules are arranged adjacently.
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