CN114257134A - Direct torque control method for harmonic suppression of double three-phase synchronous reluctance motor - Google Patents
Direct torque control method for harmonic suppression of double three-phase synchronous reluctance motor Download PDFInfo
- Publication number
- CN114257134A CN114257134A CN202111487715.0A CN202111487715A CN114257134A CN 114257134 A CN114257134 A CN 114257134A CN 202111487715 A CN202111487715 A CN 202111487715A CN 114257134 A CN114257134 A CN 114257134A
- Authority
- CN
- China
- Prior art keywords
- vector
- vectors
- harmonic
- subspace
- calling
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/10—Arrangements for controlling torque ripple, e.g. providing reduced torque ripple
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/04—Arrangements for controlling or regulating the speed or torque of more than one motor
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/04—Arrangements for controlling or regulating the speed or torque of more than one motor
- H02P2006/045—Control of current
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Control Of Ac Motors In General (AREA)
Abstract
The invention relates to a direct torque control method for harmonic suppression of a double three-phase synchronous reluctance motor, which decomposes variables of the double three-phase synchronous reluctance motor into a fundamental wave subspace and harmonic wave subspaces based on a vector space decoupling principle, wherein each control period T issThree adjacent large vectors are selected in an internal alpha-beta fundamental wave subspace to synthesize a harmonic-free control vector, the vector meets the control requirements of flux linkage and torque in the fundamental wave subspace, and is mapped to z1‑z2The harmonic subspace is synthesized into zero, the low-harmonic direct torque control of the double three-phase synchronous motor is realized, and the problems of increased harmonic loss and reduced operation efficiency caused by large harmonic currents of 5 th and 7 th of the double three-phase synchronous motor are solved. Compared with the traditional single-voltage vector direct torque control and four-vector SVPWM synthesis, the method provided by the invention reserves the advantages of simple structure and small calculation amount of the direct torque control method, and has the advantages of harmonic suppression, switching frequency reduction and higher performanceThe operating efficiency and the utilization rate of the direct current power supply.
Description
Technical Field
The invention belongs to the technical field of control of multiphase motors, and particularly relates to a direct torque control method for harmonic suppression of a double three-phase synchronous reluctance motor.
Background
With the rapid development of industry and agriculture, high power becomes one of the development trends of the alternating-current transmission system, but the power grade of the power electronic device becomes a main factor for limiting the power improvement of the transmission system. The development of a multi-phase motor becomes an effective solution for solving the contradiction that the power of a transmission system needs to be improved and the power grade of a power electronic device is difficult to improve, and in various multi-phase motors, a double three-phase motor with double Y phase shifts of 30 degrees is similar to a traditional three-phase motor, so that the development of the multi-phase motor becomes a hot research field of the multi-phase motor.
The winding structure of the double-Y phase-shift 30-degree motor enables 5 th and 7 th harmonic magnetomotive forces to be mostly cancelled, the motor has extremely small impedance for the 5 th and 7 th harmonic waves, so that large harmonic currents can be generated by small harmonic voltage, the harmonic waves with the highest content in the stator currents of the motor are the 5 th and 7 th harmonic waves, the harmonic loss is increased, the temperature rise is increased, and therefore the harmonic suppression problem must be considered in the control strategy for the multi-phase motor. Although the traditional direct torque control can be directly applied to a double-Y phase-shift 30-degree motor by increasing the number of control vectors, 5 th and 7 th harmonics cannot be suppressed, and the practical application of the motor is not facilitated, so that the traditional direct torque control needs to be improved, and the traditional direct torque control has a harmonic suppression function on the basis of keeping high-performance regulation of torque and flux linkage.
The synchronous reluctance motor has continuous reluctance change, less torque pulsation and noise during running, no permanent magnet on the rotor, low cost, no problem of weak magnetism and easy demagnetization of the permanent magnet motor, high reliability, more stable efficiency during long-term use and very good comprehensive performance. Therefore, the synchronous reluctance motor can meet the requirements of integration and high reliability of flywheel energy storage and power generation and the requirement of high-performance speed regulation driving of industrial automation, and is a motor with great development prospect.
Disclosure of Invention
The invention provides a direct torque control method for harmonic suppression of a double three-phase synchronous reluctance motor, which solves the problems of large current harmonic, harmonic loss and increased temperature rise after the traditional direct torque control is applied to a multi-phase motor.
The technical scheme adopted by the invention is that three adjacent large vectors are synthesized to form a harmonic-free vector to replace 12 large vectors controlled by the traditional direct torque to control the motor, and the method is implemented according to the following steps:
step 1: decomposing various variables of the double three-phase synchronous reluctance motor into alpha-beta fundamental wave subspace and z through six-phase static coordinate transformation1-z2Harmonic subspace, o1-o2In the zero sequence subspace, the current component corresponding to the alpha-beta subspace mainly forms a rotary magnetomotive force in an air gap to participate in electromechanical energy conversion; z is a radical of1-z2The corresponding harmonic component in the subspace is mainly 6k +/-1, which can not generate electromagnetic torque but can generate harmonic current o1-o2The subspace corresponds to mainly the zero sequence component;
step 2: dividing sectors with the sequence numbers of 1 to 12 in the alpha-beta subspace by taking 12 large vectors in the alpha-beta subspace as boundaries, and ensuring that the control effect of the same voltage vector on flux linkage and torque in each sector is unchanged;
and step 3: defining every three adjacent large vectors in alpha-beta subspace as a group of basic vectors, wherein the basic vector in the group at the middle position is called a central vector, the other two basic vectors are called two side vectors, and 12 groups of basic vectors can be combined into 12 harmonic-free control vectors M1-M12；
And 4, step 4: adjusting the calling sequence and time of basic vectors to make the output voltage waveform symmetrical, and the vectors at both sides are in each control period TsInternal calling time is Tsid1Is arranged in the control period TsIn the middle of (1), the calling time is TmidThe intermediate vector is divided into two, and the calling time is Tsid1Before and after the vector of (1), the call time is Tsid2The two-side vector calling time is divided into two and is arranged in the control period TsTwo ends, if vector V41Vector V9Vector V11The set of basic vectors, a control period TsCalling in the following order, vector V41Calling Tsid1V2, vector V9Calling TmidV2, vector V11Calling Tsid2Vector V9Calling TmidV2, vector V41Calling Tsid1/2；
And 5: according to the flux linkage difference delta psisCorresponding state value DF, torque difference Delta TeSelecting the harmonic-free vector M in step 3 according to the three values of the state value DT and the sector value N1-M12The harmonic suppression switch meter is formed and used for controlling the torque and flux linkage of the double three-phase synchronous reluctance motor.
Further, the synthesized 12 harmonic-free vectors M1-M12The method comprises the following steps:
M1-M1for the resultant 12 harmonic-free vectors, V9、V11、V27、V26、V18、V22、V54、V52、V36、V37、V45、V41Is the 12 large vectors, T, used in the synthesis of the harmonic-free vectorsid1And Tsid2Two side vectors in each group of basic vectors are in a control period TsInternal calling time, TmidIs a central vector of each group of basic vectorssThe call time in.
And further, the method adopts three-phase inverter control, the two sets of three-phase inverters are not connected, and a star connection mode of isolating neutral points is adopted, so that zero sequence components in the system are avoided.
Further, the specific synthesis method of the harmonic-free control vector is as follows:
step 3.1: after vector space decoupling is carried out by six-phase static coordinate transformation, included angles of three adjacent large vectors in an alpha-beta subspace are different by 30 degrees and 60 degrees, and the three vectors are mapped to z1-z2Three small vectors are arranged in the subspace, and the difference of included angles is 150 degrees and 30 degrees, so that the calling time of three large vectors in the alpha-beta subspace is controlled to enable the mapping to be mapped to z1-z2Three small vectors in the subspace are combined into zero, so that the motor control can be satisfiedThe requirement is made, and the generation of harmonic waves can be inhibited;
step 3.2: according to the trigonometric function relation, the total calling time of the central vector in the three large vectors in the alpha-beta subspace in each control period is calculated to be
In the same way, the total calling time of the vectors at two sides in the three large vectors is the same, namely
All the 12 large vectors and two adjacent large vectors are in each control period TsThe 12 harmonic-free control vectors M can be obtained by calling given time in sequence1-M12。
Compared with the prior art, the invention has the beneficial effects that after the technical scheme is adopted:
(1) the harmonic-free vector is synthesized by calling the fixed time and the sequence of the basic vector in each control period, so that the calculation amount is greatly reduced compared with a four-vector SVPWM (space vector pulse width modulation) technology, the switching frequency is also reduced, and the characteristics of simple structure and small calculation amount of a direct torque control method are reserved;
(2) harmonic current is effectively reduced by synthesizing the harmonic-free vector control motor, a current regulator in a harmonic subspace is omitted, and the advantage of high dynamic response speed of direct torque control is reserved;
(3) by adjusting the large vector calling sequence, the switching state of only one phase of power device is changed at each time, symmetrical output voltage waveforms are obtained, and the harmonic suppression effect is improved.
Drawings
FIG. 1 shows the space voltage vector α - β subspace and z of a dual three-phase synchronous reluctance machine1-z2A distribution map in a subspace;
FIG. 2 is a schematic diagram of a dual three-phase inverter with neutral isolation;
FIG. 3 is a sectional view of a stator flux linkage sector of a dual three-phase synchronous reluctance motor;
FIG. 4 is a schematic diagram illustrating the calculation of the calling time of each large vector when three adjacent large vectors are combined to form a harmonic-free control vector;
FIG. 5 shows a harmonic-free vector M1Switching table of switching sequence of each phase;
FIG. 6 is a schematic diagram illustrating an analysis of the effect of space voltage vector control in sector 1;
fig. 7 is a schematic block diagram of harmonic suppression direct torque control of a dual three-phase synchronous reluctance motor.
Detailed Description
The technical solution in the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings in the embodiments of the present invention.
The harmonic suppression direct torque control strategy is implemented according to the following steps:
step 1: as shown in figure 1, various variables of the double three-phase synchronous reluctance motor are decomposed into alpha-beta fundamental wave subspace, z through six-phase coordinate transformation1-z2Harmonic subspace, o1-o2In the zero sequence subspace, the current component corresponding to the alpha-beta subspace mainly forms a rotary magnetomotive force in an air gap to participate in electromechanical energy conversion; z is a radical of1-z2The corresponding harmonic component in the subspace is mainly 6k +/-1, which can not generate electromagnetic torque but can generate harmonic current o1-o2The subspace corresponds to mainly the zero sequence component; as shown in FIG. 2, the neutral point isolation inverter is used to connect the motor windings, zero sequence o1-o2Zero sequence component in the subspace is zero;
step 2: as shown in FIG. 1, non-zero vectors can be divided into large vectors (outermost, magnitude) according to the magnitude of the vector
Middle vector (second layer, amplitude of
) Original, originalA start vector (third layer, amplitude of 1), a small vector (innermost layer, amplitude of 1)
As shown in fig. 3, with 12 large vectors in the α - β subspace as boundaries, dividing the α - β subspace by-15 ° -15 ° for sector 1, 15 ° -45 ° for sector 2, 45 ° -75 ° for sector 3, 75 ° -105 ° for sector 4, 105 ° -135 ° for sector 5, 135 ° -165 ° for sector 6, 165 ° -180 ° and-180 ° -165 ° for sector 7, -165 ° -135 ° for sector 8, -135 ° -105 ° for sector 9, -165 ° -135 ° for sector 10, -135 ° -105 ° for sector 11, -165 ° -135 ° for sector 12, the control effect of the same voltage vector on magnetic chains and torque in each sector is guaranteed to be constant;
and step 3: as shown in FIG. 1, the 12 large vectors in the α - β subspace correspond to z1-z2Small and medium vectors in the subspace, and the included angle of the alpha axis of each large vector in the alpha-beta subspace is that the corresponding small vector is in z1-z2In subspace with z1The angle between the axes is 5 times, for example large vector 9 in the alpha-beta subspace, and the angle between large vector 9 and the alpha axis in the alpha-beta subspace is 15 deg., corresponding to z1-z2The small vectors 9 and z in the subspace1The included angle of the axes is 75 deg.. The rule is formed by vector space decoupling, and the synthesis of a harmonic-free vector can be realized by utilizing the rule;
the synthesis principle of the harmonic-free control vector is as follows: if the basic vector selected in a control period still meets the motor control requirement after vector synthesis in the fundamental wave subspace, and the used basic vector is mapped to the harmonic wave subspace and then synthesized to be zero, the synthesized vector is called as a harmonic-free control vector.
The specific calculation method for the synthesis of the harmonic-free vector is as follows: the vector in the middle of a group of three large vectors is called a central vector, the other two vectors are called two-side vectors, and each control period TsThe invocation time of the three large vectors within is fixed. With vector V in FIG. 441Vector V9Vector V11Three adjacent large vectors are synthesized into a harmonic-free vector M1For example calculation, vector V11Is in three vectorsThe centering vector of (1), the total time of invocation of which is noted as TmidVector V41、V11The vectors on two sides of the three large vectors are used, and the total calling time is recorded as Tsid1And Tsid2. Vector V41Vector V9Vector V11Mapping to z1-z2Corresponding vector v in subspace41V vector v9V vector v11. Vector V41Sum vector V9Is 30 DEG, vector V9Sum vector V11Angle of 30 deg., mapped to z1-z2Subspace vector v41Sum vector v9Is 150 DEG, vector v9Sum vector v11The included angle is 150 degrees, so the trigonometric function relation can be known, when the requirement is satisfied
Time vector v41V vector v9V vector v11Synthesized to zero, at which time vector V41Vector V9Vector V11The resultant is a harmonic-free vector. The control period is fixed to TsThe following can be obtained:
Tmid+Tsid1+Tsid2＝Ts (2)
therefore, it is not only easy to use
The voltage vector magnitude of the synthesized harmonic-free vector is
The direct current power supply utilization ratio at this time is:
and 4, step 4: adjusting the basic vector during a control period TsThe sequence of calling makes the output voltage waveform of the harmonic-free vector symmetrical, and improves the effect of harmonic suppression. The specific adjusting method comprises the following steps: in each group of three vectors in each control period TsInternal calling time is Tsid1Is arranged in the control period TsIn the middle of (1), the calling time is TmidThe intermediate vector is divided into two, and the calling time is Tsid1Before and after the vector of (1), the call time is Tsid2The two-side vector calling time is divided into two and is arranged in the control period TsTwo ends. By vector V9Vector V11Vector V27For example, as shown in FIG. 5, one control period TsThe vector V is called in the following sequence41Calling Tsid1V2, vector V9Calling TmidV2, vector V11Calling Tsid2Vector V9Calling TmidV2, vector V41Calling Tsid1And/2, as in Table 1. The other vectors are synthesized into 12 harmonic-free vectors M according to the method1-M12The following are:
M1-M12for the resultant 12 harmonic-free vectors, V9、V11、V27、V26、V18、V22、V54、V52、V36、V37、V45、V41Is the 12 large vectors, T, used in the synthesis of the harmonic-free vectorsid1And Tsid2Is the calling time T of two side vectors in each group of basic vectors in one periodmidIs the call time within one cycle of the centered vector for each set of basis vectors.
And 5: and (3) calculating the estimated flux linkage amplitude by using a back electromotive force integration method and formulas (5) and (6), and judging the sector by using a formula (7).
Te＝np(ψsαisβ-ψsβisα) (8)
In the formula is magnetic linkage psisαIs an alpha-axis flux linkage, psisβIs a beta axis flux linkage, UsαIs alpha axis voltage, UsβIs the beta axis voltage, isαIs an alpha-axis current, isβIs beta axis current, R is stator resistance,
is the flux linkage position angle, TeIs an electromagnetic torque, npIs the number of pole pairs;
estimating torque by adopting a formula (8), inputting estimated values of the torque and the flux linkage and given values into state values DT and DF obtained by a hysteresis comparator, and then inputting the state values into a switch table by combining a sector number N;
step 6: the switching table is obtained by analyzing the effect of each vector in 12 sectors, taking sector 1 as an example, as shown in FIG. 6, when the flux linkage psisFalling within sector 1, vector M1、M2、M3Can increase flux linkage and torque simultaneously, and has vector M1Fastest response to flux linkage, slowest response to torque, and vector M3The torque response is fastest, and the flux linkage response is slowest; vector M4、M5、M6Increase flux linkage reducing torque, vector M6Fastest response to flux linkage, slowest response to torque, and vector M4The torque response is fastest, and the flux linkage response is slowest; vector M7、M8、M9The flux linkage and the torque are reduced simultaneously, vector M7Fastest response to flux linkage, slowest response to torque, and vector M9The torque response is fastest, and the flux linkage response is slowest; vector M10、M11、M12Enabling flux linkage to increase and torque to decrease, vector M12Fastest response to flux linkage, slowest response to torque, and vector M10Maximum torque responseFast, flux linkage response is slowest. In order to accelerate the dynamic response of the system, the vector is selected by taking the fastest torque response as a standard, so that the vector M is selected when DT is 1 and DF is 1 in 1 sector3The vector M is selected when DT-1 and DF-110The vector M is selected when DT-1 and DF-14The vector M is selected when DT-1 and DF-19And selecting the non-harmonic vectors from the other sectors according to the same rule to form a switch table shown in the table 1.
And 7: as shown in the schematic diagram of the direct torque control of the dual three-phase synchronous reluctance motor of fig. 7, the flux linkage difference value Δ ψsCorresponding state value DF, torque difference Delta TeAnd inputting the corresponding three conditions of the state value DT and the sector number N into a switch table shown in the table 1, and selecting a proper harmonic-free voltage vector to control the torque and flux linkage of the motor.
TABLE 1
Claims (4)
1. A direct torque control method for harmonic suppression of a double three-phase synchronous reluctance motor is characterized by comprising the following steps:
step 1: decomposing various variables of the double three-phase synchronous reluctance motor into alpha-beta fundamental wave subspace and z through six-phase static coordinate transformation1-z2Harmonic subspace, o1-o2In the zero sequence subspace, the current component corresponding to the alpha-beta subspace mainly forms a rotary magnetomotive force in an air gap to participate in electromechanical energy conversion; z is a radical of1-z2The corresponding harmonic component in the subspace is mainly 6k +/-1, which can not generate electromagnetic torque but can generate harmonic current o1-o2The subspace corresponds to mainly the zero sequence component;
step 2: dividing sectors with the sequence numbers of 1 to 12 in the alpha-beta subspace by taking 12 large vectors in the alpha-beta subspace as boundaries, and ensuring that the control effect of the same voltage vector on flux linkage and torque in each sector is unchanged;
and step 3: defining every three adjacent large vectors in alpha-beta subspace as a group of basic vectors, wherein the basic vector in the group at the middle position is called a central vector, the other two basic vectors are called two side vectors, and 12 groups of basic vectors can be combined into 12 harmonic-free control vectors M1-M12；
And 4, step 4: adjusting the calling sequence and time of basic vectors to make the output voltage waveform symmetrical, and the vectors at both sides are in each control period TsInternal calling time is Tsid1Is arranged in the control period TsIn the middle of (1), the calling time is TmidThe intermediate vector is divided into two, and the calling time is Tsid1Before and after the vector of (1), the call time is Tsid2The two-side vector calling time is divided into two and is arranged in the control period TsTwo ends, if vector V41Vector V9Vector V11The set of basic vectors, a control period TsCalling in the following order, vector V41Calling Tsid1V2, vector V9Calling TmidV2, vector V11Calling Tsid2Vector V9Calling TmidV2, vector V41Calling Tsid1/2；
And 5: according to the flux linkage difference delta psisCorresponding state value DF, torque difference Delta TeSelecting the harmonic-free vector M in step 3 according to the three values of the state value DT and the sector value N1-M12The harmonic suppression switch meter is formed and used for controlling the torque and flux linkage of the double three-phase synchronous reluctance motor.
2. The direct torque control method for harmonic suppression of a dual three-phase synchronous reluctance machine according to claim 1, wherein 12 harmonic-free vectors M are synthesized1-M12The method comprises the following steps:
M1-M12for the resultant 12 harmonic-free vectors, V9、V11、V27、V26、V18、V22、V54、V52、V36、V37、V45、V41Is the 12 large vectors, T, used in the synthesis of the harmonic-free vectorsid1And Tsid2Two side vectors in each group of basic vectors are in a control period TsInternal calling time, TmidIs a central vector of each group of basic vectorssThe call time in.
3. The direct torque control method for harmonic suppression of a double three-phase synchronous reluctance motor according to claim 1, further comprising the step of controlling by using three-phase inverters, wherein two sets of three-phase inverters are not connected, and a star connection mode for isolating a neutral point is adopted, so that zero sequence components in the system are avoided.
4. The direct torque control method for harmonic suppression of the double three-phase synchronous reluctance motor according to claim 1, wherein the specific synthesis method of the harmonic-free control vector is as follows:
step 3.1: after vector space decoupling is carried out by six-phase static coordinate transformation, included angles of three adjacent large vectors in an alpha-beta subspace are different by 30 degrees and 60 degrees, and the three vectors are mapped to z1-z2Three small vectors are arranged in the subspace, and the difference of included angles is 150 degrees and 30 degrees, so that the calling time of three large vectors in the alpha-beta subspace is controlled to enable the mapping to be mapped to z1-z2Three small vectors in the subspace are combined into zero, so that the control requirement of the motor can be met, and the generation of harmonic waves can be inhibited;
step 3.2: according to the trigonometric function relation, the total calling time of the central vector in the three large vectors in the alpha-beta subspace in each control period is calculated to be
In the same wayThe total calling time of the vectors at two sides in the three large vectors is the same, and all the three large vectors are
All the 12 large vectors and two adjacent large vectors are in each control period TsThe 12 harmonic-free control vectors M can be obtained by calling given time in sequence1-M12。
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202111487715.0A CN114257134B (en) | 2021-12-07 | 2021-12-07 | Direct torque control method for harmonic suppression of double three-phase synchronous reluctance motor |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202111487715.0A CN114257134B (en) | 2021-12-07 | 2021-12-07 | Direct torque control method for harmonic suppression of double three-phase synchronous reluctance motor |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN114257134A true CN114257134A (en) | 2022-03-29 |
| CN114257134B CN114257134B (en) | 2023-08-22 |
Family
ID=80794199
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202111487715.0A Active CN114257134B (en) | 2021-12-07 | 2021-12-07 | Direct torque control method for harmonic suppression of double three-phase synchronous reluctance motor |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN114257134B (en) |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20090026988A1 (en) * | 2007-07-27 | 2009-01-29 | Sanyo Electric Co., Ltd. | Motor Control Device |
| CN107222146A (en) * | 2017-07-31 | 2017-09-29 | 福州大学 | The Direct Torque Control of double three-phase permanent-magnetic synchronous motor high load capability |
| CN107994832A (en) * | 2017-11-24 | 2018-05-04 | 东南大学 | A kind of multichannel permanent magnet synchronous motor mixing Direct Torque Control |
| CN108683377A (en) * | 2018-04-17 | 2018-10-19 | 西安理工大学 | Five leg inverters drive double three-phase machine system Strategy of Direct Torque Control |
| CN110739896A (en) * | 2019-09-19 | 2020-01-31 | 南京航空航天大学 | control method for multi-harmonic current collaborative injection of double three-phase permanent magnet synchronous motor |
-
2021
- 2021-12-07 CN CN202111487715.0A patent/CN114257134B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20090026988A1 (en) * | 2007-07-27 | 2009-01-29 | Sanyo Electric Co., Ltd. | Motor Control Device |
| CN107222146A (en) * | 2017-07-31 | 2017-09-29 | 福州大学 | The Direct Torque Control of double three-phase permanent-magnetic synchronous motor high load capability |
| CN107994832A (en) * | 2017-11-24 | 2018-05-04 | 东南大学 | A kind of multichannel permanent magnet synchronous motor mixing Direct Torque Control |
| CN108683377A (en) * | 2018-04-17 | 2018-10-19 | 西安理工大学 | Five leg inverters drive double three-phase machine system Strategy of Direct Torque Control |
| CN110739896A (en) * | 2019-09-19 | 2020-01-31 | 南京航空航天大学 | control method for multi-harmonic current collaborative injection of double three-phase permanent magnet synchronous motor |
Non-Patent Citations (2)
| Title |
|---|
| XUEQING WANG ET AL.: "Direct torque control of dual three-phase PMSM drives based on two-step voltage vector synthesis SVM", 2016 IEEE 8TH INTERNATIONAL POWER ELECTRONICS AND MOTION CONTROL CONFERENCE (IPEMC-ECCE ASIA), pages 3655 - 3658 * |
| 刘林阴 等: "非对称六相永磁同步电机的故障容错控制", 《微特电机》, vol. 46, no. 5, pages 52 - 57 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN114257134B (en) | 2023-08-22 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| Zhao et al. | Hybrid modulation fault-tolerant control of open-end windings linear vernier permanent-magnet motor with floating capacitor inverter | |
| Bojoi et al. | Digital synchronous frame current regulation for dual three-phase induction motor drives | |
| CN113271048B (en) | Open-circuit unified fault-tolerant control method for five-phase permanent magnet fault-tolerant motor control driving system | |
| Suhel et al. | Realization of 24-sector SVPWM with new switching pattern for six-phase induction motor drive | |
| CN111726046B (en) | Asymmetric six-phase PMSM model prediction flux linkage control method considering duty ratio optimization | |
| CN110504889B (en) | Fault-tolerant direct torque control method for five-phase permanent magnet synchronous motor | |
| Wu et al. | Field-oriented control and direct torque control for a five-phase fault-tolerant flux-switching permanent-magnet motor | |
| Zhang et al. | Torque ripple RMS minimization in model predictive torque control of PMSM drives | |
| Song et al. | Active harmonic suppression of low-reactance multiphase slotless permanent magnet synchronous machines | |
| Jing et al. | Control strategy for a five-leg inverter supplying dual three-phase PMSM | |
| Shao et al. | Compensation of selective current harmonics for switching-table-based direct torque control of dual three-phase PMSM drives | |
| CN112260605B (en) | Direct torque control method for one-phase-lacking fault of five-phase permanent magnet synchronous motor | |
| CN116961290A (en) | Double three-phase synchronous reluctance motor and phase failure fault-tolerant control method thereof | |
| Yu et al. | Power factor analysis and maximum power factor control strategy for six-phase DC-biased vernier reluctance machines | |
| Chen et al. | Novel harmonic current controller for dc-biased vernier reluctance machines based on virtual winding | |
| CN114257134B (en) | Direct torque control method for harmonic suppression of double three-phase synchronous reluctance motor | |
| Dai et al. | The control strategy of open-winding permanent magnet synchronous motor drive system based on five-leg inverter | |
| CN113422554B (en) | Vector control method and device for twelve-phase permanent magnet synchronous motor flywheel energy storage system | |
| Xu et al. | Paralleled inverters to drive double dual-three-phase induction motors with common-mode voltage mitigation for traction application | |
| Cheng et al. | General Analysis and Vector Control for Doubly Salient Reluctance Machines | |
| CN111464082A (en) | SVPWM control method of six-phase motor with low switching loss and common-mode interference | |
| Yiguang et al. | Fault-tolerant SVPWM control strategy for five-phase PMSM under single-phase open-circuit fault | |
| Dong et al. | Half open-end winding topology based nine-leg VSI for asymmetrical six-phase PMSM drives | |
| Razik et al. | Modelling and analysis of dual-stator induction motors | |
| Zheng et al. | Unified Control Scheme of Five-Phase Open-Winding Permanent-Magnet Synchronous Generator Systems for Aerospace Applications |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |