CN114169278A - Parameter design method and device of resonant converter - Google Patents
Parameter design method and device of resonant converter Download PDFInfo
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- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
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- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
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Abstract
The invention provides a parameter design method of a resonant converter, which comprises the following steps: determining a relation curve of loss of the resonant converter and excitation inductance based on a zero-voltage switching requirement of a primary side switching device and a zero-current switching requirement of a secondary side switching device of the resonant converter, wherein the loss comprises switching loss and on-state loss; and determining a design value of the excitation inductance meeting the optimal efficiency condition based on a relation curve of the loss of the resonant converter and the excitation inductance.
Description
Technical Field
The invention relates to the field of resonant converters, in particular to a parameter design method and device of a resonant converter.
Background
The isolation type DC-DC converter realizes the electrical isolation of the original secondary side, has the advantages of small volume, light weight, high efficiency and the like, has wide-range voltage gain and full-load soft switching characteristics of a resonance type (LLC) high-frequency DC-DC converter, has more outstanding advantages in high-voltage and high-power occasions, is widely applied to the fields of rail transit traction power electronic transformers, multi-port DC-DC power distribution networks, new energy automobiles and the like, and becomes a hot point for research of experts and scholars at home and abroad.
In recent years, with the rapid development of high-frequency power electronic technology, an isolated resonant converter with a power semiconductor device as a core has been widely used. Considering the requirements of the weight and the volume of the high-power converter, the method becomes an effective means for increasing the switching frequency of the converter; however, the higher switching frequency inevitably causes larger switching loss, which brings great challenges to the design and heat dissipation of the converter, and the volume and weight of the system are limited accordingly. Compared with a traditional hard switch, the LLC resonant converter can realize zero-voltage switching-on (ZVS) of a primary power tube and zero-current switching-off (ZCS) of a secondary diode, so that loss of the converter is greatly reduced, and the purposes of reducing weight and size are achieved. Compared with other soft switching technologies, the LLC resonant converter does not need an additional hardware circuit, the voltage borne by the power device is only the bus voltage, the output filter is simple in design, and the LLC resonant converter has the advantages of being simple in structure and high in reliability, and has a great application prospect in a direct-current-direct-current conversion occasion.
The topology of an LLC resonant converter is shown in FIG. 1, where VinIs an input voltage, C1、C2Supporting capacitors, S, respectively upper and lower half-presses1～S8Switching tubes being the primary side of a full bridge three-level, D11～D14Is a clamping diode; l ism、Lr、CrExcitation inductance, resonance inductance and resonance capacitance, i, of the resonant cavity, respectivelyLrFor resonant current, iLmFor exciting current, isec' converting the secondary current to the primary current, isecIs the secondary current; n is the transformation ratio of the high-frequency transformer, V1～V4Is a secondary side switch tube, CdIs an output support capacitor, RLIs a load, V0Is the output voltage. The reasonable design of LLC resonant cavity parameters can implement wide-range adjustable output voltage, and its primary side switchThe device realizes ZVS, and the secondary side switch device realizes ZCS, so the design of LLC resonance parameters is concerned with the performance of the converter.
The traditional design concept of the LLC resonant converter is as follows: the LLC resonant converter is designed according to the traditional design idea that the transformation ratio of a high-frequency transformer is determined under the rated working condition of the converter according to the performance index of the converter; secondly, determining the gain range of the converter through calculation, and further determining the frequency range of the output voltage; thirdly, reasonably selecting the Q value of the converter under the condition of ensuring the realization of the soft switch; after the steps are completed, the design of the resonant cavity parameters can be completed.
The traditional LLC resonant cavity parameter design has the following defects:
1. the traditional LLC resonant cavity parameter design is designed based on the gain of a converter, and a high-power LLC converter basically works at a constant direct current gain ratio. A constant dc gain ratio indicates that the converter operates at approximately a fixed frequency, whereas it is undesirable to have a converter switching frequency range that is too wide, which also burdens the design of the high frequency transformer.
2. In the traditional LLC resonant cavity parameter design, ZVS can be realized by completing charge transfer of junction capacitance in dead time, and the influence of the dead time is not considered. The proportion of dead time is small and can be ignored in a low-power occasion, and the dead time is overlarge in a high-power occasion, so that the resonant current reversely crosses zero, and ZVS cannot be realized.
3. The traditional LLC resonant cavity parameter design cannot ensure the optimal efficiency of the converter. Generally, according to engineering experience, the efficiency is higher when the excitation inductance is larger, and actually, the efficiency and the excitation inductance are not simple linear relations. In the whole parameter design process, the selection of the excitation inductance depends on the inductance ratio k, and the inductance ratio meeting the gain requirement has no array solution, so that the excitation inductance also has no array solution, and the efficiency of the converter under the selected excitation inductance is not necessarily optimal.
4. The traditional LLC resonant cavity parameter design does not take engineering constraints into consideration. The larger the excitation inductance is, the smaller the turn-off current is, considering the turn-off delay of the switching tube (the smaller the turn-off current is, the longer the turn-off time is), if the switching tube is not completely turned off in the dead time, at this time, the turn-on of the other switching tube of the same bridge arm will inevitably generate reverse impact current, and the safe operation of the converter is threatened.
Therefore, in order to solve the above problems, the present invention aims to provide a resonant cavity converter design method, which can realize the optimal design of the converter efficiency.
Disclosure of Invention
The following presents a simplified summary of one or more aspects in order to provide a basic understanding of such aspects. This summary is not an extensive overview of all contemplated aspects, and is intended to neither identify key or critical elements of all aspects nor delineate the scope of any or all aspects. Its sole purpose is to present some concepts of one or more aspects in a simplified form as a prelude to the more detailed description that is presented later.
According to an aspect of the present invention, there is provided a method for designing parameters of a resonant converter, including: determining a relation curve of loss of the resonant converter and excitation inductance based on a zero-voltage switching requirement of a primary side switching device and a zero-current switching requirement of a secondary side switching device of the resonant converter, wherein the loss comprises switching loss and on-state loss; and determining a design value of the excitation inductance meeting the optimal efficiency condition based on a relation curve of the loss of the resonant converter and the excitation inductance.
Still further, the determining an excitation inductance value that allows the resonant converter to reach an efficiency-optimized condition based on a loss versus excitation inductance curve of the resonant converter comprises: determining an excitation inductance value corresponding to the lowest loss point based on a relation curve of the loss of the resonant converter and the excitation inductance to serve as an excitation inductance theoretical value meeting an efficiency optimal condition; determining an excitation inductance critical value meeting the constraint condition based on the constraint condition of the engineering turn-off current; and determining the excitation inductance design value based on the excitation inductance theoretical value and the excitation inductance critical value.
Still further, the determining the excitation inductance design value based on the excitation inductance theoretical value and the excitation inductance critical value comprises: determining the excitation inductance theoretical value as the excitation inductance design value in response to the excitation inductance theoretical value being less than or equal to the excitation inductance critical value; and in response to the excitation inductance theoretical value being greater than the excitation inductance critical value, determining the excitation inductance critical value as the excitation inductance design value.
Further, determining a loss versus excitation inductance curve of the resonant converter based on a zero voltage switching requirement of a primary side switching device and a zero current switching requirement of a secondary side switching device of the resonant converter comprises: determining a transformation ratio of a high frequency transformer within the resonant converter based on a performance index requirement of the resonant converter; determining a resonant frequency of the resonant converter based on a power level of the resonant converter and a model of a switching device; and substituting the transformation ratio, the resonant frequency and other constant parameters into a relational expression of loss and excitation inductance of the resonant converter to determine a relational curve of the loss and the excitation inductance.
Still further, the parameter design method further includes: and establishing a relational expression of the loss of the resonant converter and the excitation inductance.
Further, the establishing of the relation between the loss and the excitation inductance of the resonant converter comprises: realizing a zero-voltage switching requirement based on an excitation inductor and determining a relational expression of an effective value of a resonant current and the excitation inductor by utilizing the relation among the resonant period, the switching period and the dead time, wherein the relational expression relates to the influence of the dead time on the excitation inductor; determining a relational expression of an effective value of the secondary current and the excitation inductance based on the relation among the resonant current, the excitation current and the load current; determining the turn-on loss and the turn-off loss of the primary side switching device and the turn-on loss and the turn-off loss of the secondary side switching device based on the zero-voltage switching requirement of the primary side switching device, the zero-current switching requirement of the secondary side switching device, the relational expression of the effective value of the resonant current and the excitation inductance and the relational expression of the effective value of the secondary side current and the excitation inductance; and solving the sum of the turn-on loss and the turn-off loss of the primary side switching device and the secondary side switching device to be used as a relational expression of the loss of the resonant converter and the excitation inductance.
Further, the determining a transformation ratio of a high frequency transformer within the resonant converter based on the performance index requirement of the resonant converter comprises: the transformation ratio is determined using an input voltage rating and an output voltage rating of the resonant converter.
Still further, the parameter design method further includes: determining an inductance ratio design value of the resonant converter by adopting a successive approximation method; determining a design value of the resonant inductance of the resonant converter based on the design value of the inductance ratio and the design value of the excitation inductance; and determining a design value of a resonant capacitance of the resonant converter based on the design value of the resonant inductance and the resonant frequency.
Further, the determining the designed inductance ratio of the resonant converter by using the successive approximation method comprises: assuming an inductance ratio of the resonant converter; drawing a gain curve corresponding to the assumed inductance ratio by adopting an FHA analysis method to judge whether the gain meets the performance index requirement of the resonant converter; and determining the maximum value of the inductance ratio meeting the performance index requirement of the resonant converter as the set value of the inductance ratio.
Further, the determining the resonant inductance of the resonant converter based on the designed inductance ratio value and the designed excitation inductance value includes: calculation of formula L using resonant inductancer＝LmCalculating the designed value of the resonance inductance by the k, wherein LrDesign value for the resonance inductance, LmAnd k is a designed inductance ratio value.
Further, the determining a design value of a resonant capacitance of the resonant converter based on the resonant inductance and the resonant frequency comprises: using resonant capacitance calculation formula
Calculating the designed value of the resonance capacitance, wherein LrDesign value, f, for the resonance inductancerIs said resonanceFrequency.
According to another aspect of the present invention, there is also provided a parameter design apparatus of a resonant converter, including: a memory; and a processor coupled with the memory, the processor configured to: determining a relation curve of loss of the resonant converter and excitation inductance based on a zero-voltage switching requirement of a primary side switching device and a zero-current switching requirement of a secondary side switching device of the resonant converter, wherein the loss comprises switching loss and on-state loss; and determining a design value of the excitation inductance meeting the optimal efficiency condition based on a relation curve of the loss of the resonant converter and the excitation inductance.
Still further, the processor is further configured to: determining an excitation inductance value corresponding to the lowest loss point based on a relation curve of the loss of the resonant converter and the excitation inductance to serve as an excitation inductance theoretical value meeting an efficiency optimal condition; determining an excitation inductance critical value meeting the constraint condition based on the constraint condition of the engineering turn-off current; and determining the excitation inductance design value based on the excitation inductance theoretical value and the excitation inductance critical value.
Still further, the processor is further configured to: determining the excitation inductance theoretical value as the excitation inductance design value in response to the excitation inductance theoretical value being smaller than the excitation inductance critical value; and in response to the excitation inductance theoretical value being greater than the excitation inductance critical value, determining the excitation inductance critical value as the excitation inductance design value.
Still further, the processor is further configured to: determining a transformation ratio of a high frequency transformer within the resonant converter based on a performance index requirement of the resonant converter; determining a resonant frequency of the resonant converter based on a power level of the resonant converter and a model of a switching device; and substituting the transformation ratio, the resonant frequency and other constant parameters into a relational expression of loss and excitation inductance of the resonant converter to determine a relational curve of the loss and the excitation inductance.
Still further, the processor is further configured to: and establishing a relational expression of the loss of the resonant converter and the excitation inductance.
Still further, the processor is further configured to: realizing a zero-voltage switching requirement based on an excitation inductor and determining a relational expression of an effective value of a resonant current and the excitation inductor by utilizing the relation among the resonant period, the switching period and the dead time, wherein the relational expression relates to the influence of the dead time on the excitation inductor; determining a relational expression of an effective value of the secondary current and the excitation inductance based on the relation among the resonant current, the excitation current and the load current; determining the turn-on loss and the turn-off loss of the primary side switching device and the turn-on loss and the turn-off loss of the secondary side switching device based on the zero-voltage switching requirement of the primary side switching device, the zero-current switching requirement of the secondary side switching device, the relational expression of the effective value of the resonant current and the excitation inductance and the relational expression of the effective value of the secondary side current and the excitation inductance; and solving the sum of the turn-on loss and the turn-off loss of the primary side switching device and the secondary side switching device to be used as a relational expression of the loss of the resonant converter and the excitation inductance.
Still further, the processor is further configured to: the transformation ratio is determined using an input voltage rating and an output voltage rating of the resonant converter.
Still further, the processor is further configured to: determining an inductance ratio design value of the resonant converter by adopting a successive approximation method; determining a design value of the resonant inductance of the resonant converter based on the design value of the inductance ratio and the design value of the excitation inductance; and determining a design value of a resonant capacitance of the resonant converter based on the design value of the resonant inductance and the resonant frequency.
Still further, the processor is further configured to: assuming an inductance ratio of the resonant converter; drawing a gain curve corresponding to the assumed inductance ratio by adopting an FHA analysis method to judge whether the gain meets the performance index requirement of the resonant converter; and determining the maximum value of the inductance ratio meeting the performance index requirement of the resonant converter as the set value of the inductance ratio.
Still further, the processor is further configured to: calculation of formula L using resonant inductancer＝LmCalculating the designed value of the resonance inductance by the k, wherein LrDesign value for the resonance inductance, LmAnd k is a designed inductance ratio value.
Still further, the processor is further configured to: using resonant capacitance calculation formula
Calculating the designed value of the resonance capacitance, wherein LrDesign value, f, for the resonance inductancerIs the resonance frequency.
According to yet another aspect of the present invention, there is also provided a computer storage medium having stored thereon a computer program which, when executed, implements the steps of the method of parametric design of a resonant converter as defined in any one of the above.
The resonant converter designed based on the parameter design method of the resonant converter can keep high-efficiency operation, reduces the cooling design difficulty of the resonant converter, is beneficial to reducing the volume and the weight of the converter and improving the power density of the converter.
The parameter design method of the resonant converter further selects the excitation inductance by reasonably selecting the turn-off current from the aspect of the turn-on and turn-off characteristics of the power semiconductor device, ensures that the power switch tube works in a safe area, and further ensures the safe operation of the resonant converter.
The parameter design method of the resonant converter does not need to repeatedly iterate the design of the excitation inductor, and the solving process is simple.
The parameter design method of the resonant converter is simple in principle and easy to realize in engineering.
Drawings
The above features and advantages of the present disclosure will be better understood upon reading the detailed description of embodiments of the disclosure in conjunction with the following drawings.
FIG. 1 is a schematic diagram of a conventional full-bridge three-level resonant converter topology according to the prior art;
FIG. 2 is a flow diagram illustrating a parameter design methodology in one embodiment according to one aspect of the present invention;
FIG. 3A is a schematic diagram of an equivalent topology according to the equivalent topology of the resonant converter;
FIG. 3B is a schematic diagram of a current waveform according to the equivalent topology of the resonant converter shown in FIG. 3A;
FIG. 4 is a partial flow diagram of a parameter design methodology in one embodiment depicted in accordance with an aspect of the present invention;
FIG. 5A is a graph illustrating the effective value of resonant current versus excitation inductance in one embodiment according to an aspect of the present invention;
FIG. 5B is a graph illustrating the effective value of the secondary current versus the excitation inductance in one embodiment according to an aspect of the present invention;
FIG. 6 is a partial flow diagram of a parameter design methodology in an embodiment depicted in accordance with an aspect of the present invention;
FIG. 7 is a graph illustrating loss versus excitation inductance for a resonant converter in one embodiment according to an aspect of the present invention;
FIG. 8 is a partial flow diagram of a parameter design methodology in an embodiment depicted in accordance with an aspect of the present invention;
FIG. 9 is a partial flow diagram of a parameter design methodology in an embodiment depicted in accordance with an aspect of the present invention;
FIG. 10 is a partial flow diagram of a parameter design methodology in an embodiment depicted in accordance with an aspect of the present invention;
FIG. 11 is a schematic block diagram of a parameter design apparatus in an embodiment according to another aspect of the present invention.
Detailed Description
The following description is presented to enable any person skilled in the art to make and use the invention and is incorporated in the context of a particular application. Various modifications, as well as various uses in different applications will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to a wide range of embodiments. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.
In the following detailed description, numerous specific details are set forth in order to provide a more thorough understanding of the invention. It will be apparent, however, to one skilled in the art that the practice of the invention may not necessarily be limited to these specific details. In other instances, well-known structures and devices are shown in block diagram form, rather than in detail, in order to avoid obscuring the present invention.
The reader's attention is directed to all papers and documents which are filed concurrently with this specification and which are open to public inspection with this specification, and the contents of all such papers and documents are incorporated herein by reference. All the features disclosed in this specification (including any accompanying claims, abstract and drawings) may be replaced by alternative features serving the same, equivalent or similar purpose, unless expressly stated otherwise. Thus, unless expressly stated otherwise, each feature disclosed is one example only of a generic series of equivalent or similar features.
Note that where used, the designations left, right, front, back, top, bottom, positive, negative, clockwise, and counterclockwise are used for convenience only and do not imply any particular fixed orientation. In fact, they are used to reflect the relative position and/or orientation between the various parts of the object. Furthermore, the terms "first" and "second" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance.
In the description of the present invention, it should be noted that, unless otherwise explicitly specified or limited, the terms "mounted," "connected," and "connected" are to be construed broadly, e.g., as meaning either a fixed connection, a removable connection, or an integral connection; can be mechanically or electrically connected; they may be connected directly or indirectly through intervening media, or they may be interconnected between two elements. The specific meanings of the above terms in the present invention can be understood in specific cases to those skilled in the art.
It is noted that, where used, further, preferably, still further and more preferably is a brief introduction to the exposition of the alternative embodiment on the basis of the preceding embodiment, the contents of the further, preferably, still further or more preferably back band being combined with the preceding embodiment as a complete constituent of the alternative embodiment. Several further, preferred, still further or more preferred arrangements of the belt after the same embodiment may be combined in any combination to form a further embodiment.
The invention is described in detail below with reference to the figures and specific embodiments. It is noted that the aspects described below in connection with the figures and the specific embodiments are only exemplary and should not be construed as imposing any limitation on the scope of the present invention.
According to one aspect of the invention, the parameter design method of the resonant converter is suitable for the fields of rail transit traction power electronic transformers, multi-port DC-DC direct-current power distribution networks, new energy vehicles and the like.
In one embodiment, as shown in FIG. 2, the method 200 for designing parameters of a resonant converter includes steps S210-S220.
Wherein, step S210 is: determining a relation curve of loss of the resonant converter and excitation inductance based on Zero Voltage Switch (ZVS) requirements of a primary side Switch device and Zero Current Switch (ZCS) requirements of a secondary side Switch device of the resonant converter, wherein the loss comprises Switch loss and on-state loss.
The equivalent topology of the resonant converter is shown in FIG. 3A, and the corresponding current waveform is shown in FIG. 3B, where iLrFor resonant current, VinIs an input voltage, LrIs a resonant inductor, CrIs a resonant capacitor, LmFor exciting the inductance, ILmFor exciting current, IsecIs the effective value of the primary current, RacIs equal toAn effective load resistance. Those skilled in the art will understand that the equivalent topology shown in fig. 3A can be applied to a resonant converter with various topologies, such as half-bridge, full-bridge, two-level, three-level, or multi-level. The switching tube power device used in the method can adopt IGBT, MOSFET, SiC or other existing or future semiconductor devices.
Specifically, a relational expression between the loss of the resonant converter and the excitation inductance may be established based on the zero-voltage switching requirement of the primary side switching device and the zero-current switching requirement of the secondary side switching device of the resonant converter.
The step of establishing the relation between the loss of the resonant converter and the excitation inductance may be as shown in fig. 4, including steps S410 to S440.
Wherein, step S410 is: and realizing the zero-voltage switching requirement based on the excitation inductance and determining a relational expression of the effective value of the resonant current and the excitation inductance by utilizing the relation among the resonant period, the switching period and the dead time.
Based on FIGS. 3A and 3B, it can be seen that the switching frequency f of the resonant converterswAnd resonant frequency frWhen the same, the expressions of the resonance current and the excitation current are respectively as follows:
wherein, IpriEffective value of resonant current, wrIs a resonant angular frequency and omegar＝2πfrTheta is the initial phase angle, V0Is the voltage across the load, n is the transformation ratio, TrIs the resonance period.
During half a switching cycle, the average value of the output current satisfies the following formula:
wherein, TsIs a switching cycle.
Considering the effect of dead time, the resonant period, switching period and dead time relationship are as follows:
Ts＝Tr+2Td (4)
wherein, TdIs the dead time.
In order to ensure that a primary side switching device of the resonant converter meets the zero-voltage switching requirement, the charge transfer on the junction capacitor needs to be completed within the dead time, so that the critical condition that the excitation inductor just achieves ZVS is as follows:
wherein, CjIs the junction capacitance, and xi is the coefficient.
The relation between the effective value of the resonance current and the excitation inductance obtained by the joint type (1) to (5) is as follows:
further, step S420 is: and determining a relational expression of the effective value of the secondary current and the excitation inductance based on the relation among the resonant current, the excitation current and the load current.
Specifically, the resonance current, the excitation current, and the load current satisfy the following equation:
isec'(t)＝iLr(t)-iLm(t) (7)
the secondary current is thus converted to the effective value i of the primary currentsec' is:
the relation between the effective value of the primary side current and the excitation inductance is calculated as follows:
the relationship between the effective value of the secondary current and the excitation inductance is as follows:
Isec＝nIsec' (10)
formula (9) is substituted for formula (10), and the graphs of formula (6) and formula (10) are shown. Fig. 5A and 5B show graphs of equations (6) and (10) in a specific embodiment. As can be seen from this embodiment, the relationship between the effective value of the resonant current and the excitation inductance and the relationship between the effective value of the secondary current and the excitation inductance do not change linearly, and there is an excitation inductance value that minimizes the corresponding effective value of the resonant current and the effective value of the secondary current.
Further, step S430 is: and determining the turn-on loss and the turn-off loss of the primary side switching device and the turn-on loss and the turn-off loss of the secondary side switching device based on the zero-voltage switching requirement of the primary side switching device, the zero-current switching requirement of the secondary side switching device, the relational expression of the effective value of the resonant current and the excitation inductance and the relational expression of the effective value of the secondary side current and the excitation inductance.
As will be appreciated by those skilled in the art, the losses of a resonant converter are divided into switching losses and on-state losses.
Since the primary power device needs to realize ZVS, the turn-on loss is 0, and the switching loss of the primary power device is mainly concentrated on the turn-off loss. The on-state loss of the primary power device comprises the on-state loss of a switching tube and the on-state loss of a diode. The on-state loss ratio of the diode is very small and can be approximately ignored, so that the on-state loss of the primary side power device can only consider the on-state loss of the switching tube.
For the secondary side diode, the secondary side diode is at ZCS, and has no switching loss and only on-state loss.
And respectively calculating the switching loss of the resonant converter, the on-state loss of the primary side switching tube and the on-state loss of the secondary side diode.
The switching losses of the resonant converter are as follows:
wherein,
to turn off the current, fswTo the switching frequency, EonEnergy required to turn on once (take 0), EoffFor switching off the energy (obtained by consulting the handbook of switching devices), InomFor rated current of switching devices, UnomFor rated voltage of switching devices, UdcThe voltage between the Collector and Emitter (CE) when the switching device is turned off.
The on-state losses of the primary side switching tube are as follows:
Pss_igbt＝(VF0_125·Ipri+RD0_125·Ipri 2)·D1 (12)
wherein, VF0_125Is the on-state voltage drop of the primary side switching tube, RD0_125Is the equivalent resistance of the module lead wire, D1Is the ratio of the on-state time.
The on-state losses of the secondary side diodes are as follows:
Pss_diode＝(VF·Isec)·D2 (13)
wherein, VFIs the on-state voltage drop of the secondary side diode, D2Is the ratio of the on-time of the secondary side diode.
Further, step S440 is: and solving the sum of the turn-on loss and the turn-off loss of the primary side switching device and the secondary side switching device to be used as a relational expression of the loss of the resonant converter and the excitation inductance.
The total losses of the resonant converter are as follows:
Ptotal_loss＝8·Psw_igbt+8·Pss_igbt+4·Pss_diode (14)
then, by substituting equations (6), (10), (11), (12), and (13) for equation (14), the relation between the loss and the excitation inductance of the resonant converter can be obtained as follows:
as will be understood by those skilled in the art, among the parameters involved in equation (15), the transformation ratio n and the resonant frequency frCan be determined based on the performance index requirement, power grade and model of the switching device of the resonant converter, and the switching frequency fswTo the resonance frequency frThe phase of the two phases is equal to each other,
excitation removing inductor LmOther parameters are constant parameters.
The derivation calculation process does not need to be repeated in each design process, and therefore the determination of the excitation inductance can be performed directly using the above equation (15). Step S210 may include steps S211 to S213, as shown in fig. 6.
Wherein, step S211 is: determining a transformation ratio of a high frequency transformer within the resonant converter based on a performance index requirement of the resonant converter.
The performance index requirements of the resonant converter include an output rated voltage V0NAnd rated load RLAnd determining the transformation ratio n of the high-frequency transformer according to the input rated voltage and the output rated voltage, wherein the transformation ratio n is shown as the following formula:
n＝VinN/V0N (16)
wherein, VinNFor inputting rated voltage, V0NTo output a rated voltage.
Step S212 is: determining a resonant frequency of the resonant converter based on the power class of the resonant converter and the model of the switching device.
Preliminarily determining the resonant frequency f of the converter according to the power class of the converter and the type of the switching devicerAnd the switching frequency range of the converter is fsw＝(0.7～0.9)frOf switching frequency fswTo the resonance frequency frAre equal.
Further, step S213 is: and substituting the transformation ratio, the resonant frequency and other constant parameters into a relation between the loss and the excitation inductance of the resonant converter to determine a relation curve between the loss and the excitation inductance.
Determining the transformation ratio n and the resonant frequency f based on the performance index requirement, the power grade and the type of the switching device of the resonant converterrAnd other constant parameters are substituted in the formula (15) and are plotted to obtain a relation curve of loss and excitation inductance. FIG. 7 illustrates a loss versus magnetizing inductance curve in one embodiment, based on which, as shown in FIG. 7, a value L of magnetizing inductance may be determined for a minimum loss valuem_cal。
Step S220 is: and determining a design value of the excitation inductance meeting the optimal efficiency condition based on a relation curve of the loss of the resonant converter and the excitation inductance.
As shown in fig. 7, the excitation inductance value L corresponding to the minimum loss value is determined based on the relationship curve of the loss of the resonant inductor and the excitation inductorm_calIn order to meet the excitation inductance theoretical value of the efficiency optimal condition of the resonant converter, the excitation inductance design value needs to meet engineering requirements, and therefore, the excitation inductance theoretical value can be adopted only when the excitation inductance theoretical value meets the engineering requirements.
Further, as shown in FIG. 8, step S220 may include steps S221-S223.
Wherein, step S221 is: and determining the excitation inductance value corresponding to the lowest loss point based on the relation curve of the loss and the excitation inductance to serve as the excitation inductance theoretical value meeting the optimal efficiency condition.
Step S222 is: and determining an excitation inductance critical value meeting the constraint condition based on the constraint condition of the engineering turn-off current.
It will be understood by those skilled in the art that the theoretical value of the excitation inductance is not necessarily realizable in engineering, if the excitation inductance L ism_calThe parameter is too large, which causes the turn-off delay of the switch tube to increaseWhen the other switching tube of the same bridge arm is switched on, current spikes can appear, and the reliable operation of the converter is seriously threatened. Therefore, the constraints for establishing an engineered off-current are as follows:
based on the formula (17), the excitation inductance critical value L meeting the constraint condition of engineering turn-off current can be obtainedm_temAs shown in formula (18):
wherein, Ioff_temThe critical value of the switch tube turn-off current is.
Further, step S223 is: and determining the excitation inductance design value based on the excitation inductance theoretical value and the excitation inductance critical value.
Specifically, when excitation inductance theoretical value Lm_calResponding to the excitation inductance theoretical value L when the constraint condition of the engineering turn-off current is satisfiedm_calLess than or equal to critical value I of excitation inductanceoff_temThe theoretical value L of the excitation inductancem_calDetermined as the design value I of the exciting inductancem_opt。
When excitation inductance theoretical value Lm_calResponding to the excitation inductance theoretical value L when the constraint condition of the engineering turn-off current is not satisfiedm_calGreater than critical value I of excitation inductanceoff_temCritical value of exciting inductance Ioff_temDetermined as the design value I of the exciting inductancem_opt。
The design process of the excitation inductance parameters of the resonant converter is as above, and the design parameters of the resonant converter further include an inductance ratio, a resonant inductance and a resonant capacitance.
Further, the method 200 for designing parameters of the resonant converter may further include steps S230-250, as shown in FIG. 9.
Wherein, step S230 is: and determining the designed inductance ratio value of the resonant converter by adopting a successive approximation method.
Successive approximation is a method that starts from some easy-to-set condition or some weakened condition that is essentially related to the substance content of the problem, and then gradually expands (or reduces) the range, and approaches in a successive manner until the solution required by the problem is finally reached. The specific steps may include steps S231 to S233 as shown in fig. 10.
Step S231 is: the inductance ratio of the resonant converter is assumed.
Step S232 is: and drawing a gain curve corresponding to the assumed inductance ratio by adopting an FHA (Fundamental harmonic equivalent analysis) method to judge whether the gain meets the performance index requirement of the resonant converter.
The gain of the resonant converter can be expressed by the following equation:
wherein,
fswis the switching frequency, f, of the resonant converterrIs the resonant frequency, LrIs a resonant inductor, CrIs a resonant capacitor and
Racfor load equivalent resistance, k is the assumed inductance ratio.
It will be appreciated that, according to the gain curve, when the switching frequency f isswWhen the output voltage meets the design requirement due to the assumed inductance ratio, the gain is considered to meet the performance index requirement of the resonant converter, otherwise, the step S231 is continuously executed until the inductance ratio is found, which enables the gain to meet the performance index requirement of the resonant converter.
Step S233 is: and determining the maximum value of the inductance ratio values meeting the performance index requirements of the resonant converter as the inductance ratio set value.
Those skilled in the art will appreciate that the step S231 may assume inductance ratios from large to small; step S232, determining whether the gain meets the performance index requirement of the resonant converter one by one according to the assumed inductance ratio until the inductance ratio enabling the gain to meet the performance index requirement of the resonant converter appears; step S233 determines the inductance ratio value such that the gain satisfies the performance index requirement of the resonant converter as the inductance ratio set value.
Alternatively, the step S231 may assume a certain number of inductance ratios; step S232 may be to determine whether the gain satisfies the performance index requirement of the resonant converter for each assumed inductance ratio, so as to determine whether the gain satisfies the inductance ratio required by the performance index of the resonant converter in the assumed inductance ratios; step S233 determines a maximum value from the inductance ratio values such that the gain satisfies the performance index requirement of the resonant converter as an inductance ratio set value.
It can be understood that both of the above two ways can determine a larger inductance ratio that meets the performance index requirements of the resonant converter.
Step S240 is: and determining a design value of the resonant inductance of the resonant converter based on the design value of the inductance ratio and the design value of the excitation inductance.
Specifically, the design value of the resonance inductance is calculated by using a resonance inductance calculation formula, which is as follows:
Lr＝Lm/k (20)
wherein L isrDesign value for the resonance inductance, LmAnd k is a designed inductance ratio value.
Step S250 is: and determining a design value of the resonant capacitance of the resonant converter based on the design value of the resonant inductance and the resonant frequency.
Specifically, a resonant capacitance design value is calculated by using a resonant capacitance calculation formula, which is as follows:
wherein L isrDesign value of resonant inductance, frIs the resonant frequency.
While, for purposes of simplicity of explanation, the methodologies are shown and described as a series of acts, it is to be understood and appreciated that the methodologies are not limited by the order of acts, as some acts may, in accordance with one or more embodiments, occur in different orders and/or concurrently with other acts from that shown and described herein or not shown and described herein, as would be understood by one skilled in the art.
According to another aspect of the invention, a parameter design device of the resonant converter is also provided.
In one embodiment, as shown in fig. 11, the apparatus 1100 for designing parameters of a resonant converter includes a memory 1110 and a processor 1120.
The memory 1110 is used to store computer programs.
The processor 1120 is coupled to the memory 1110 for executing computer programs stored on the memory 1110. The steps of the parameter design method 200 in any of the above embodiments are implemented by the processor 1120 when executing the computer program stored on the memory 1110.
According to yet another aspect of the present invention, there is also provided a computer storage medium having a computer program stored thereon, the computer program when executed implementing the steps of the parametric design method 200 in any of the above embodiments.
Those of skill in the art would understand that information, signals, and data may be represented using any of a variety of different technologies and techniques. For example, data, instructions, commands, information, signals, bits (bits), symbols, and chips that may be referenced throughout the above description may be represented by voltages, currents, electromagnetic waves, magnetic fields or particles, optical fields or particles, or any combination thereof.
Those of skill would further appreciate that the various illustrative logical blocks, modules, circuits, and algorithm steps described in connection with the embodiments disclosed herein may be implemented as electronic hardware, computer software, or combinations of both. To clearly illustrate this interchangeability of hardware and software, various illustrative components, blocks, modules, circuits, and steps have been described above generally in terms of their functionality. Whether such functionality is implemented as hardware or software depends upon the particular application and design constraints imposed on the overall system. Skilled artisans may implement the described functionality in varying ways for each particular application, but such implementation decisions should not be interpreted as causing a departure from the scope of the present invention.
The various illustrative logical modules, and circuits described in connection with the embodiments disclosed herein may be implemented or performed with a general purpose processor, a Digital Signal Processor (DSP), an Application Specific Integrated Circuit (ASIC), a Field Programmable Gate Array (FPGA) or other programmable logic device, discrete gate or transistor logic, discrete hardware components, or any combination thereof designed to perform the functions described herein. A general purpose processor may be a microprocessor, but in the alternative, the processor may be any conventional processor, controller, microcontroller, or state machine. A processor may also be implemented as a combination of computing devices, e.g., a combination of a DSP and a microprocessor, a plurality of microprocessors, one or more microprocessors in conjunction with a DSP core, or any other such configuration.
The steps of a method or algorithm described in connection with the embodiments disclosed herein may be embodied directly in hardware, in a software module executed by a processor, or in a combination of the two. A software module may reside in RAM memory, flash memory, ROM memory, EPROM memory, EEPROM memory, registers, hard disk, a removable disk, a CD-ROM, or any other form of storage medium known in the art. An exemplary storage medium is coupled to the processor such the processor can read information from, and write information to, the storage medium. In the alternative, the storage medium may be integral to the processor. The processor and the storage medium may reside in an ASIC. The ASIC may reside in a user terminal. In the alternative, the processor and the storage medium may reside as discrete components in a user terminal.
In one or more exemplary embodiments, the functions described may be implemented in hardware, software, firmware, or any combination thereof. If implemented in software as a computer program product, the functions may be stored on or transmitted over as one or more instructions or code on a computer-readable medium. Computer-readable media includes both computer storage media and communication media including any medium that facilitates transfer of a computer program from one place to another. A storage media may be any available media that can be accessed by a computer. By way of example, and not limitation, such computer-readable media can comprise RAM, ROM, EEPROM, CD-ROM or other optical disk storage, magnetic disk storage or other magnetic storage devices, or any other medium that can be used to carry or store desired program code in the form of instructions or data structures and that can be accessed by a computer. Any connection is properly termed a computer-readable medium. For example, if the software is transmitted from a web site, server, or other remote source using a coaxial cable, fiber optic cable, twisted pair, Digital Subscriber Line (DSL), or wireless technologies such as infrared, radio, and microwave, then the coaxial cable, fiber optic cable, twisted pair, DSL, or wireless technologies such as infrared, radio, and microwave are included in the definition of medium. Disk (disk) and disc (disc), as used herein, includes Compact Disc (CD), laser disc, optical disc, Digital Versatile Disc (DVD), floppy disk and blu-ray disc where disks (disks) usually reproduce data magnetically, while discs (discs) reproduce data optically with lasers. Combinations of the above should also be included within the scope of computer-readable media.
The previous description is provided to enable any person skilled in the art to practice the various aspects described herein. It is to be understood that the scope of the invention is to be defined by the appended claims and not by the specific constructions and components of the embodiments illustrated above. Those skilled in the art can make various changes and modifications to the embodiments within the spirit and scope of the present invention, and these changes and modifications also fall within the scope of the present invention.
Claims (23)
1. A method of parametric design of a resonant converter, comprising:
determining a relation curve of loss of the resonant converter and excitation inductance based on a zero-voltage switching requirement of a primary side switching device and a zero-current switching requirement of a secondary side switching device of the resonant converter, wherein the loss comprises switching loss and on-state loss; and
and determining a design value of the excitation inductance meeting the optimal efficiency condition based on a relation curve of the loss of the resonant converter and the excitation inductance.
2. The parameter design method of claim 1, wherein determining an excitation inductance value that causes the resonant converter to reach an efficiency optimization condition based on a loss versus excitation inductance curve of the resonant converter comprises:
determining an excitation inductance value corresponding to the lowest loss point based on a relation curve of the loss of the resonant converter and the excitation inductance to serve as an excitation inductance theoretical value meeting an efficiency optimal condition;
determining an excitation inductance critical value meeting the constraint condition based on the constraint condition of the engineering turn-off current; and
and determining the excitation inductance design value based on the excitation inductance theoretical value and the excitation inductance critical value.
3. The parameter design method of claim 2, wherein said determining said excitation inductance design value based on said excitation inductance theoretical value and said excitation inductance critical value comprises:
determining the excitation inductance theoretical value as the excitation inductance design value in response to the excitation inductance theoretical value being less than or equal to the excitation inductance critical value; and
in response to the excitation inductance theoretical value being greater than the excitation inductance critical value, determining the excitation inductance critical value as the excitation inductance design value.
4. The parameter design method of claim 1, wherein determining a loss versus excitation inductance curve for the resonant converter based on a zero voltage switching requirement of a primary side switching device and a zero current switching requirement of a secondary side switching device of the resonant converter comprises:
determining a transformation ratio of a high frequency transformer within the resonant converter based on a performance index requirement of the resonant converter;
determining a resonant frequency of the resonant converter based on a power level of the resonant converter and a model of a switching device; and
and substituting the transformation ratio, the resonant frequency and other constant parameters into a relational expression of the loss and the excitation inductance of the resonant converter to determine a relational curve of the loss and the excitation inductance.
5. The parameter design method of claim 4, further comprising:
and establishing a relational expression of the loss of the resonant converter and the excitation inductance.
6. The parametric design method of claim 5, wherein the establishing a relationship of the resonant converter loss to excitation inductance comprises:
realizing a zero-voltage switching requirement based on an excitation inductor and determining a relational expression of an effective value of a resonant current and the excitation inductor by utilizing the relation among the resonant period, the switching period and the dead time, wherein the relational expression relates to the influence of the dead time on the excitation inductor;
determining a relational expression of an effective value of the secondary current and the excitation inductance based on the relation among the resonant current, the excitation current and the load current;
determining the turn-on loss and the turn-off loss of the primary side switching device and the turn-on loss and the turn-off loss of the secondary side switching device based on the zero-voltage switching requirement of the primary side switching device, the zero-current switching requirement of the secondary side switching device, the relational expression of the effective value of the resonant current and the excitation inductance and the relational expression of the effective value of the secondary side current and the excitation inductance; and
and solving the sum of the turn-on loss and the turn-off loss of the primary side switching device and the secondary side switching device to be used as a relational expression of the loss of the resonant converter and the excitation inductance.
7. The parametric design method of claim 4, wherein the determining a transformation ratio of a high frequency transformer within the resonant converter based on performance index requirements of the resonant converter comprises:
the transformation ratio is determined using an input voltage rating and an output voltage rating of the resonant converter.
8. The parameter design method of claim 4, further comprising:
determining an inductance ratio design value of the resonant converter by adopting a successive approximation method;
determining a design value of the resonant inductance of the resonant converter based on the design value of the inductance ratio and the design value of the excitation inductance; and
and determining a design value of the resonant capacitance of the resonant converter based on the design value of the resonant inductance and the resonant frequency.
9. The parametric design method of claim 8, wherein the determining the design value of the inductance ratio of the resonant converter using successive approximation comprises:
assuming an inductance ratio of the resonant converter;
drawing a gain curve corresponding to the assumed inductance ratio by adopting an FHA analysis method to judge whether the gain meets the performance index requirement of the resonant converter; and
and determining the maximum value of the inductance ratio meeting the performance index requirement of the resonant converter as the set value of the inductance ratio.
10. The parametric design method of claim 8, wherein the determining a resonant inductance of the resonant converter based on the design inductance ratio value and the design excitation inductance value comprises:
calculation of formula L using resonant inductancer＝LmCalculating the designed value of the resonance inductance by the k, wherein LrDesign value for the resonance inductance, LmAnd k is a designed inductance ratio value.
11. The parametric design method of claim 8, wherein the determining a design value for a resonant capacitance of the resonant converter based on the resonant inductance and the resonant frequency comprises:
using resonant capacitance calculation formula
Calculating the designed value of the resonance capacitance, wherein LrDesign value, f, for the resonance inductancerIs the resonance frequency.
12. A parametric design apparatus for a resonant converter, comprising:
a memory; and
a processor coupled with the memory, the processor configured to:
determining a relation curve of loss of the resonant converter and excitation inductance based on a zero-voltage switching requirement of a primary side switching device and a zero-current switching requirement of a secondary side switching device of the resonant converter, wherein the loss comprises switching loss and on-state loss; and
and determining a design value of the excitation inductance meeting the optimal efficiency condition based on a relation curve of the loss of the resonant converter and the excitation inductance.
13. The parametric design apparatus of claim 11, wherein the processor is further configured to:
determining an excitation inductance value corresponding to the lowest loss point based on a relation curve of the loss of the resonant converter and the excitation inductance to serve as an excitation inductance theoretical value meeting an efficiency optimal condition;
determining an excitation inductance critical value meeting the constraint condition based on the constraint condition of the engineering turn-off current; and
and determining the excitation inductance design value based on the excitation inductance theoretical value and the excitation inductance critical value.
14. The parametric design apparatus of claim 13, wherein the processor is further configured to:
determining the excitation inductance theoretical value as the excitation inductance design value in response to the excitation inductance theoretical value being smaller than the excitation inductance critical value; and
in response to the excitation inductance theoretical value being greater than the excitation inductance critical value, determining the excitation inductance critical value as the excitation inductance design value.
15. The parametric design apparatus of claim 12, wherein the processor is further configured to:
determining a transformation ratio of a high frequency transformer within the resonant converter based on a performance index requirement of the resonant converter;
determining a resonant frequency of the resonant converter based on a power level of the resonant converter and a model of a switching device; and
and substituting the transformation ratio, the resonant frequency and other constant parameters into a relational expression of the loss and the excitation inductance of the resonant converter to determine a relational curve of the loss and the excitation inductance.
16. The parametric design apparatus of claim 15, wherein the processor is further configured to:
and establishing a relational expression of the loss of the resonant converter and the excitation inductance.
17. The parametric design apparatus of claim 16, wherein the processor is further configured to:
realizing a zero-voltage switching requirement based on an excitation inductor and determining a relational expression of an effective value of a resonant current and the excitation inductor by utilizing the relation among the resonant period, the switching period and the dead time, wherein the relational expression relates to the influence of the dead time on the excitation inductor;
determining a relational expression of an effective value of the secondary current and the excitation inductance based on the relation among the resonant current, the excitation current and the load current;
determining the turn-on loss and the turn-off loss of the primary side switching device and the turn-on loss and the turn-off loss of the secondary side switching device based on the zero-voltage switching requirement of the primary side switching device, the zero-current switching requirement of the secondary side switching device, the relational expression of the effective value of the resonant current and the excitation inductance and the relational expression of the effective value of the secondary side current and the excitation inductance; and
and solving the sum of the turn-on loss and the turn-off loss of the primary side switching device and the secondary side switching device to be used as a relational expression of the loss of the resonant converter and the excitation inductance.
18. The parametric design apparatus of claim 15, wherein the processor is further configured to:
the transformation ratio is determined using an input voltage rating and an output voltage rating of the resonant converter.
19. The parametric design apparatus of claim 15, wherein the processor is further configured to:
determining an inductance ratio design value of the resonant converter by adopting a successive approximation method;
determining a design value of the resonant inductance of the resonant converter based on the design value of the inductance ratio and the design value of the excitation inductance; and
and determining a design value of the resonant capacitance of the resonant converter based on the design value of the resonant inductance and the resonant frequency.
20. The parametric design apparatus of claim 19, wherein the processor is further configured to:
assuming an inductance ratio of the resonant converter;
drawing a gain curve corresponding to the assumed inductance ratio by adopting an FHA analysis method to judge whether the gain meets the performance index requirement of the resonant converter; and
and determining the maximum value of the inductance ratio meeting the performance index requirement of the resonant converter as the set value of the inductance ratio.
21. The parametric design apparatus of claim 19, wherein the processor is further configured to:
calculation of formula L using resonant inductancer＝LmCalculating the designed value of the resonance inductance by the k, wherein LrDesign value for the resonance inductance, LmAnd k is a designed inductance ratio value.
22. The parametric design apparatus of claim 19, wherein the processor is further configured to:
using resonant capacitance calculation formula
Calculating the designed value of the resonance capacitance, wherein LrDesign value, f, for the resonance inductancerIs the resonance frequency.
23. A computer storage medium having a computer program stored thereon, wherein the computer program when executed implements the steps of a method of parametric design of a resonant converter as claimed in any of claims 1 to 11.
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