CN114094715B - Hybrid electromagnetic coupling wireless power transmission optimization design method - Google Patents

Hybrid electromagnetic coupling wireless power transmission optimization design method Download PDF

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CN114094715B
CN114094715B CN202111444568.9A CN202111444568A CN114094715B CN 114094715 B CN114094715 B CN 114094715B CN 202111444568 A CN202111444568 A CN 202111444568A CN 114094715 B CN114094715 B CN 114094715B
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coil
copper ring
copper
coupling coefficient
ring
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CN114094715A (en
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程瑜华
周金梅
王高峰
李文钧
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Hangzhou Dianzi University
Hangzhou Dianzi University Wenzhou Research Institute Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/005—Mechanical details of housing or structure aiming to accommodate the power transfer means, e.g. mechanical integration of coils, antennas or transducers into emitting or receiving devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/05—Circuit arrangements or systems for wireless supply or distribution of electric power using capacitive coupling
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries

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Abstract

The invention relates to a hybrid electromagnetic coupling wireless power transmission optimization design method. The copper ring is divided into two parts, one part is a copper disk added in the coil, and the other part is a copper ring added outside the coil. The copper plate/copper ring added on the inner/outer side of the coil is placed in/out of the coil on the premise that the copper plate/copper ring is kept at a proper distance from the coil and is not contacted with the coil. The copper disk at the inner side of the coil and the copper ring at the outer side are divided into an upper part and a lower part, and gaps are reserved between the upper part and the lower part respectively. The outer open end and the inner open end of the coil are respectively connected with the inner copper disc and the outer copper ring through two connecting wires. The two open ends in the middle of the coil are used as excitation ports and are connected to the inside of the coaxial cable and the ground. The copper ring and the coil are positioned on the same plane, so that the area of the inner side of the coil is fully utilized; the inner and outer open ends of the coil are respectively connected with the inner copper disc and the outer copper ring, so that the stability of output power is better, and the whole area is smaller; the frequency splitting suppression effect and the transmission efficiency at a relatively short distance are good.

Description

Hybrid electromagnetic coupling wireless power transmission optimization design method
Technical Field
The invention belongs to the technical field of power electronics, and relates to a hybrid electromagnetic coupling wireless power transmission optimization design method.
Background
In recent years, wireless power transmission systems based on magnetic coupling have attracted considerable attention in the field of implanted biomedical devices, mobile electronics, and the like. It has also been found that when using magnetically coupled resonance power transmission, the maximum power transfer that is desired can only be achieved by having the transmitter and receiver at a specific distance. As the distance between the coils becomes smaller, the magnetic coupling increases and the resonant frequency splits, resulting in a decrease in the output power at the original frequency. According to the phase loss characteristics of the electric coupling coefficient and the magnetic coupling coefficient, under the condition of changing the distance, the change of the magnetic coupling strength can be counteracted by the change of the electric coupling strength, so that under the condition of relatively close distance between the transmitter and the receiver, the magnetic coupling can be prevented from being too strong, the frequency splitting is restrained, and stable output power can be realized.
In recent years, scholars have proposed employing adaptive frequency tracking methods to change the operating frequency of the strongly coupled region or using switchable configurations to suppress frequency splitting, such as switchable capacitive arrays, however employing additional frequency control circuits or additional tuning circuits can complicate the system. So, the scholars propose to use a hybrid coupling mode to transmit power, as shown in fig. 1 and 2, and this mode can avoid strong frequency splitting under a short distance under the premise of avoiding the complexity of the system, so that more stable power can be output at the original frequency point.
Disclosure of Invention
The invention aims to provide an optimal design method for hybrid electromagnetic coupling wireless power transmission.
The method specifically comprises the following steps:
step one: according to the use scene and the self-resonance frequency f of the coil st Determining the required coil size, including the number of turns n of the coil, the distance p between each turn, the inner diameter R of the coil, the outer diameter R of the coil, the wire radius dr, the self-resonant frequency f of the coil st The coil is applied to both the receiving end and the transmitting end.
Step two: because the data obtained in the first step is approximate, after the relevant parameters of the coil are determined, the self-resonant frequency f of the coil is obtained by actual measurement st 。
Step three: hybrid couplerWidth w of copper ring (area of copper ring) required for suppressing frequency splitting in a combined manner and coil self-resonance frequency f measured in step two st And the relationship of the resonant frequency f of the coil and the copper ring resonant system is as follows:
Figure BDA0003384555260000011
f in the formula st The self-resonant frequency of the coil, w is the width of the copper ring added to the outer side of the coil required by the hybrid coupling mode, the inner diameter of the copper ring is the outer diameter R of the coil, the outer diameter of the copper ring is (R+w), and the area S=pi ((R+w)/(2-R≡2) of the copper ring is calculated. The copper ring and the coil cannot be in close contact, and because this causes a change in the circuit structure, the changed circuit structure will no longer have the function of suppressing frequency splitting, so that a proper distance is maintained between the coil and the copper ring. dr is the radius of the wire and 2dr is the thickness of the copper ring.
The copper ring is divided into two parts, one part is added into the coil, the other part is added to the outer side of the coil, and the other part is added into the copper disc with the radius of r1, and the width of the part is r 2. The copper plate/copper ring added on the inner/outer side of the coil is placed in/out of the coil on the premise that the copper plate/copper ring is kept at a proper distance from the coil and is not contacted with the coil. The copper disk at the inner side of the coil and the copper ring at the outer side of the coil are divided into an upper part and a lower part, and gaps d1 and d2 are reserved between the upper part and the lower part respectively. The outer open end and the inner open end of the coil are respectively connected with the inner copper disc and the outer copper ring through two connecting wires. The two open ends in the middle of the coil are used as excitation ports and are connected to the inside of the coaxial cable and the ground, and the distance between the receiving end and the transmitting end is D.
Step four: extracting an electric coupling coefficient Km and a magnetic coupling coefficient Ke; according to the formula:
Figure BDA0003384555260000021
Figure BDA0003384555260000022
the electromagnetic coupling coefficients of Km and Ke obtained by calculation are required to satisfy the conditions: />
Figure BDA0003384555260000023
Step five: if the electric coupling coefficient Km and the magnetic coupling coefficient Ke meet the frequency splitting suppression condition in the fourth step, the power transmission efficiency of the proposed new structure under different distances is obtained through actual measurement, and the system is built successfully. And if the electric coupling coefficient and the magnetic coupling coefficient do not meet the frequency splitting suppression condition in the fourth step, adjusting the electric coupling to enable the electric coupling coefficient to meet the frequency splitting suppression condition. If the electric coupling is too strong, the width of the ring should be reduced, if the electric coupling is too weak, the width of the ring should be increased, and the step four is repeated, the width of the copper ring is continuously adjusted until the magnetic coupling coefficient of the electric coupling coefficient meets the condition of inhibiting frequency splitting.
The invention has the beneficial effects that:
the coil and the copper ring of the original structure are not in the same plane, a small gap d exists in the middle, and experiments prove that the existence of the gap has little influence on efficiency and frequency splitting, so that the gap is removed by the novel structure, the copper ring and the coil are in the same plane, and compared with the original structure, the space is saved;
compared with the original structure, the structure is more compact, and the area of the inner side of the coil is fully utilized. Although the inner and outer open ends of the coil are respectively connected with the inner copper plate and the outer copper ring, the capacitive coupling is that the two parts are connected in parallel, so that the two parts are added in capacitance, so that the area of the inner copper plate and the outer copper plate is unequal, but the result is not affected, and as the area of most copper plates is in a more concentrated disc shape on the inner side of the coil, compared with the copper ring which is simply surrounded around the coil by the original structure, the stability of output power is better under the condition of slight dislocation, and the whole area occupied by the new structure is smaller when copper plates with the same area are added;
the frequency splitting inhibition effect is improved by a small extent compared with the original structure, and the transmission efficiency is improved by a small extent compared with the original structure at a short distance.
Drawings
FIG. 1 is a diagram of a primary mode structure;
FIG. 2 is a diagram showing the arrangement of the transmitting end and the receiving end of the original structure;
FIG. 3 is a diagram of a coil structure;
FIG. 4 is a schematic plan view of a novel structure according to the present invention;
FIG. 5 is a diagram showing the arrangement of the receiving end and the transmitting end of the proposed structure;
FIG. 6 is a schematic diagram of a circuit for extracting electromagnetic coupling coefficients by weak coupling at an input/output port;
fig. 7 is an S21 diagram obtained by extracting electromagnetic coupling coefficients from weak coupling of an output port;
FIG. 8 is a circuit block diagram of the present invention;
FIG. 9 is a simulated S21 image of the present invention;
FIG. 10 is a simulated S21 image of the original mode;
Detailed Description
Step one: according to the use scene and the self-resonance frequency f of the coil st Determining the required coil size, as shown in fig. 3, including the number of turns n of the coil, the distance p between each turn, the inner diameter R of the coil, the outer diameter R of the coil and the wire radius dr; self-resonant frequency of coil
Figure BDA0003384555260000031
Where c is the speed of light in air, the coil is applied to both the receiving and transmitting ends.
In this example, n=5, p=5 mm, dr=1 mm, r=100 mm, and r=125 mm.
Step two: because the data obtained in the first step is approximate, after the relevant parameters of the coil are determined, the self-resonant frequency f of the coil is obtained by actual measurement st 。
The coil has a self-resonant frequency of 15.55MHz, as measured in practice in this example.
Step three: the width w of the copper ring required for suppressing frequency splitting by the hybrid coupling mode (the area of the copper ring is determined according to the requirement) and the coil self-resonance frequency f measured in the step two st And the relationship of the resonant frequency f of the coil and the copper ring resonant system is as follows:
Figure BDA0003384555260000032
f in the formula st The self-resonant frequency of the coil, w is the width of the copper ring added to the outer side of the coil required by the hybrid coupling mode, the inner diameter of the copper ring is the outer diameter R of the coil, the outer diameter of the copper ring is (R+w), and the area S=pi ((R+w)/(2-R≡2) of the copper ring is calculated. The copper ring and the coil cannot be in close contact, and because this causes a change in the circuit structure, the changed circuit structure will no longer have the function of suppressing frequency splitting, so that a proper distance is maintained between the coil and the copper ring. dr is the radius of the wire and 2dr is the thickness of the copper ring.
The copper ring is divided into two parts, one part is added into the coil, the other part is added to the outer side of the coil, and the other part is added into the copper disc with the radius of r1, and the width of the part is r 2. The copper plate/copper ring added on the inner/outer side of the coil is placed in/out of the coil on the premise that the copper plate/copper ring is kept at a proper distance from the coil and is not contacted with the coil. The copper disk at the inner side of the coil and the copper ring at the outer side of the coil are divided into an upper part and a lower part, and gaps d1 and d2 are reserved between the upper part and the lower part respectively. The outer open end and the inner open end of the coil are respectively connected with the inner copper disc and the outer copper ring through two connecting wires. As shown in fig. 4, two open ends in the middle of the coil are used as excitation ports and are connected to the inside of the coaxial cable and to the ground; as shown in fig. 5, the distance between the receiving end and the transmitting end is D.
In this embodiment, the overall resonant frequency f is selected to be 13.07MHz, according to the formula:
Figure BDA0003384555260000033
the width of the copper ring required by the original structure is calculated to be 40mm, and a 5mm gap is reserved between the coil and the copper ring, so that the copper ring has 130mm inner diameter and 170mm outer diameter at the moment, and the area of the copper ring is 12000 pi mm at the moment 2 . The inner diameter of the coil is 100mm, so that a gap exists between the coil and the copper disc on the inner side of the coil, and the radius of the copper disc on the inner side of the coil is r1=90 mm, and the gap d1=4 mm between the upper copper disc and the lower copper disc; total copper ring area 12000 pi mm 2 After subtracting the copper plate area, the rest copper plate is placed outside the coil, the width r2=14.2 mm of the copper ring, and the distance d between the upper and lower copper rings 2 Distance d=40 mm between receiving end and transmitting end.
Step (a)Fourth, the method comprises the following steps: in order to verify whether the frequency splitting can be restrained by the result obtained in the step three, the magnetic coupling coefficient Km, the electric coupling coefficient and the integral coupling coefficient K at different distances are extracted. As shown in fig. 6, a series connection of a small inductance and a small capacitance is connected in parallel to the excitation port and the output port to extract, according to the formula:
Figure BDA0003384555260000041
Figure BDA0003384555260000042
Figure BDA0003384555260000043
obtaining Km, ke, K, wherein w Z The frequency f of the lowest point of the efficiency magnitude image (S21 image) obtained after the parallel connection of the small resistor and the small inductor of the transmitting port and the receiving port are connected in series z Is converted to angular frequency, as shown in FIG. 7, w 1 、w 2 The frequencies f1 and f2 of the frequency splitting points are converted into angular frequencies.
The derivation is as follows if frequency splitting is to be avoided: first the two coupled resonators are divided into two parts, enclosed with a dashed line. As shown in fig. 8, each section is considered a two-port network. Z matrix of two parts Z1 and Z2:
Figure BDA0003384555260000044
Figure BDA0003384555260000045
Figure BDA0003384555260000046
m is
Since the two networks of Z1 and Z2 are in series, the total Z matrix can be expressed as: z=z1+z2, let l=l 1 ＝L 2 ,C e ＝C 3 ＝C 4 ,C＝C 1 ＝C 2 ,R＝R 1 ＝R 2 ；
L1 and L2 respectively represent the self-electricity of the transmitting end coil and the receiving end coilThe inductance value, here made equal and equal for ease of calculation; c3 and C4 respectively represent true coupling capacitance values between the transmitting-side copper plate and the receiving-side copper plate, which are made equal and equal to C for the sake of calculation e ；C 1 ，C 2 The leakage capacitance between the upper copper plate and the lower copper plate of the receiving end and the leakage capacitance between the upper copper plate and the lower copper plate of the receiving end are respectively represented, and are made to be equal and equal to C for the convenience of calculation; r is R 1 ，R 2 Ohmic losses of the transmitting-side coil and the receiving-side coil are represented respectively, which are made equal and equal to R here for the sake of calculation convenience;
Figure BDA0003384555260000047
wherein Z is 11 Represents the self-impedance (input impedance) of port 1 when port 2 is open, Z 21 Representing the forward transfer impedance when port 2 is open.
With kirchhoff's voltage law, the loop equation of a circuit is expressed as:
Figure BDA0003384555260000051
wherein Z is IN The input impedance is set to be zero to obtain the resonant frequency of the system: im (Z) IN ) =0; the method comprises the following steps:
Figure BDA0003384555260000052
w 1,2 respectively two frequency values after splitting the system frequency, w 0 Is the resonant frequency value.
Order the
Figure BDA0003384555260000053
Figure BDA0003384555260000054
Where Q is the quality factor of the resonator, Q is well above 1 in an efficient WPT system. Thus, w 1 And w 2 Is simplified as follows: />
Figure BDA0003384555260000055
Obtaining the total coupling coefficient
Figure BDA0003384555260000056
Let Ce equal to zero to obtain the secondary coupling coefficient
Figure BDA0003384555260000057
Let M equal to zero to obtain an electrical coupling coefficient +.>
Figure BDA0003384555260000058
The total coupling coefficient is therefore expressed in terms of the electrical and magnetic coupling coefficients +.>
Figure BDA0003384555260000059
It is seen that due to the out-of-phase characteristics of the magnetic and electrical couplings, they cancel each other out, achieving a uniform total coupling strength to suppress frequency splitting. But even if frequency splitting is suppressed, the operating frequency of the WPT system may not be maintained at w 0 This results in a difference in w 0 Efficiency eta at t Descending.
To avoid frequency shift, for two frequencies w 1 And w 2 W of (a) 1 、w 2 By w 0 Km, ke, both:
Figure BDA00033845552600000510
Figure BDA00033845552600000511
from the formula we can see w 2 Depending on the magnetic coupling coefficient, if it is to be equal to w 0 Km should be infinitely close to zero, which is a violation of system operation. As for w 1 It may be equal to w 0 Not only is provided with
Figure BDA00033845552600000512
The electromagnetic coupling coefficient for suppressing frequency splitting should satisfy the condition: />
Figure BDA00033845552600000513
Step five: if the electric coupling coefficient and the magnetic coupling coefficient meet the condition of suppressing frequency splitting in the fourth step, the power transmission efficiency of the proposed new structure at different distances is obtained by actual measurement, in this embodiment the efficiency is |S21 for simplified analysis 2 And calculating, and setting up the system successfully. And if the electric coupling coefficient and the magnetic coupling coefficient do not meet the frequency splitting suppression condition in the fourth step, the electric coupling coefficient and the magnetic coupling coefficient are matched through adjustment. If the electric coupling is too strong, the width of the ring should be reduced, if the electric coupling is too weak, the width of the ring should be increased, and the step four is repeated, the width of the copper ring is continuously adjusted until the magnetic coupling coefficient of the electric coupling coefficient meets the condition of inhibiting frequency splitting.
The actual measurement of the proposed new structure is carried out to obtain an S21 image, as shown in fig. 9, the frequency division inhibition is better, the efficiency at the resonance point reaches 99.6%, and compared with the original structure in the same condition, the efficiency at the resonance point is improved by 87.8% as shown in fig. 10.

Claims (1)

1. The hybrid electromagnetic coupling wireless power transmission optimization design method is characterized by comprising the following steps of:
the method specifically comprises the following steps:
step one: according to the use scene and the self-resonance frequency f of the coil st Determining the required coil size, including the number of turns n of the coil, the distance p between each turn, the inner diameter R of the coil, the outer diameter R of the coil and the wire radius dr; self-resonant frequency f of coil st The coil is simultaneously applied to the receiving end and the transmitting end;
step two: because the data obtained in the first step is approximate, after the relevant parameters of the coil are determined, the self-resonant frequency f of the coil is obtained by actual measurement st ；
Step three: the width w of the copper ring required for suppressing frequency splitting in a hybrid coupling mode and the coil self-resonance frequency f measured in the step two st And the relationship of the resonant frequency f of the coil and the copper ring resonant system is as follows:
Figure FDA0003384555250000011
f in the formula st The self-resonant frequency of the coil is that w is the width of the copper ring which is required by the hybrid coupling mode and is added to the outer side of the coil, the inner diameter of the copper ring is the outer diameter R of the coil, the outer diameter of the copper ring is R+w, and the area of the copper ring is calculated: s=pi ((r+w)/(2-R >) 2); the coil is not contacted with the copper ring, dr is the radius of the lead, and 2dr is the thickness of the copper ring;
dividing the copper ring into two parts, wherein one part is added into the coil, the other part is added into the outer side of the coil, and the width of the other part is r 2; the copper plate/copper ring added on the inner/outer side of the coil is placed in/out of the coil on the premise that the copper plate/copper ring is kept at a proper distance from the coil and is not contacted with the coil; the copper disc at the inner side of the coil and the copper ring at the outer side are equally divided into an upper part and a lower part, and gaps d1 and d2 are reserved between the upper part and the lower part respectively; the outer open end and the inner open end of the coil are respectively connected with the inner copper disc and the outer copper ring through two connecting wires; the two open ends in the middle of the coil are used as excitation ports and are connected to the inside of the coaxial cable and the ground, and the distance between the receiving end and the transmitting end is D;
step four: extracting an electric coupling coefficient Km and a magnetic coupling coefficient Ke; the electromagnetic coupling coefficient for suppressing frequency splitting should satisfy the condition:
Figure FDA0003384555250000012
step five: if the electric coupling coefficient Km and the magnetic coupling coefficient Ke meet the frequency splitting suppression condition in the fourth step, the power transmission efficiency of the proposed new structure under different distances is obtained through actual measurement, and the system is successfully built; if the electric coupling coefficient and the magnetic coupling coefficient do not meet the frequency splitting suppression condition in the fourth step, the electric coupling is adjusted to be met; if the electric coupling is too strong, the width of the ring should be reduced, if the electric coupling is too weak, the width of the ring should be increased, and the step four is repeated, the width of the copper ring is continuously adjusted until the magnetic coupling coefficient of the electric coupling coefficient meets the condition of inhibiting frequency splitting.
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WO2017084142A1 (en) * 2015-11-16 2017-05-26 华南理工大学 Wireless-power-transfer coil system using magnetoelectric coupling to offset suppression of frequency splitting
CN107546869A (en) * 2017-10-09 2018-01-05 中国矿业大学(北京) The suppressing method of three-winding wireless power transmission systems frequency splitting phenomenon
CN110571942A (en) * 2019-09-30 2019-12-13 山西大同大学 Wireless energy transmission system with stable working frequency

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CA2724341A1 (en) * 2008-05-14 2009-11-19 Massachusetts Institute Of Technology Wireless energy transfer, including interference enhancement
WO2017084142A1 (en) * 2015-11-16 2017-05-26 华南理工大学 Wireless-power-transfer coil system using magnetoelectric coupling to offset suppression of frequency splitting
CN107546869A (en) * 2017-10-09 2018-01-05 中国矿业大学(北京) The suppressing method of three-winding wireless power transmission systems frequency splitting phenomenon
CN110571942A (en) * 2019-09-30 2019-12-13 山西大同大学 Wireless energy transmission system with stable working frequency

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