CN113992016B - Low-voltage large-current output circuit and low-voltage large-current charging system - Google Patents

Low-voltage large-current output circuit and low-voltage large-current charging system Download PDF

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CN113992016B
CN113992016B CN202111593331.7A CN202111593331A CN113992016B CN 113992016 B CN113992016 B CN 113992016B CN 202111593331 A CN202111593331 A CN 202111593331A CN 113992016 B CN113992016 B CN 113992016B
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output signal
current
voltage
module
inductor
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CN113992016A (en
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李晨光
陈小平
张百川
范桂杰
张明涛
付加友
朱建国
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Shenzhen Winline Technology Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/0029—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries with safety or protection devices or circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter

Abstract

The application provides a low pressure heavy current output circuit and low pressure heavy current charging system, low pressure heavy current output circuit includes the contravariant module, first vary voltage module, second vary voltage module, rectifier module, first inductance, second inductance and first electric capacity, first vary voltage module is used for adjusting the voltage of first contravariant output signal in order to obtain first vary voltage output signal, second vary voltage module is used for adjusting the voltage of second contravariant output signal in order to obtain second vary voltage output signal, first inductance is used for adjusting the electric current of first rectification output signal, the second inductance is used for adjusting the electric current of second rectification output signal, wherein, first inductance and second inductance are coupling inductance. Therefore, the low-voltage large-current output circuit provided by the application is beneficial to reducing the heat dissipation capacity of the circuit, reducing the circuit loss, helping to ensure the stable operation of the circuit, and being beneficial to reducing the number of devices in the circuit and reducing the production cost.

Description

Low-voltage large-current output circuit and low-voltage large-current charging system
Technical Field
The application relates to the technical field of electronics, in particular to a low-voltage large-current output circuit and a low-voltage large-current charging system.
Background
In the technical fields of high-power direct-current charging, communication power supplies and the like, a power electronic module is generally required to work in a high-current state, and the common working condition is 20kW50V 400A. At present, the common direct current-to-direct current circuit structure and control strategy often cause some problems under such working conditions. For example, in a large current state, the temperature rise of the electronic device is high, the heat dissipation amount is increased, the circuit stability is easily affected, and the loss of the filter inductor is easily increased in the large current state. For another example, in a scheme of increasing a plurality of electronic devices to achieve shunting and heat dissipation, a current sharing control strategy of a plurality of paths of currents needs to be additionally added, and the number of the devices is increased, so that the production cost is also increased.
Therefore, how to design a low-voltage large-current output circuit with a simple structure and good circuit stability becomes a problem to be solved urgently.
Disclosure of Invention
Based on prior art's not enough, the application provides a low pressure heavy current output circuit and low pressure heavy current charging system, helps reducing the heat dissipation capacity of circuit, reduces the circuit loss, and the stable operation of circuit is ensured in the help, and helps reducing the device quantity in the circuit, reduction in production cost.
In a first aspect, an embodiment of the present application provides a low-voltage large-current output circuit, including: an inversion module, a first transformation module, a second transformation module, a rectification module, a first inductor, a second inductor and a first capacitor,
a first output end of the inversion module is connected with an input end of the first transformation module, a second output end of the inversion module is connected with an input end of the second transformation module, an output end of the first transformation module is connected with a first input end of the rectification module, an output end of the second transformation module is connected with a second input end of the rectification module, a first output end of the rectification module is connected with an input end of the first inductor, a second output end of the rectification module is connected with an input end of the second inductor, and an output end of the first inductor, an output end of the second inductor and one end of the first capacitor are connected;
the inverter module is used for inputting a first inverter output signal to the first transformer module and/or inputting a second inverter output signal to the second transformer module, the first transformer module is used for adjusting the voltage of the first inverter output signal to obtain a first transformer output signal, the second transformer module is used for adjusting the voltage of the second inverter output signal to obtain a second transformer output signal, the rectifier module is used for adjusting the first transformer output signal to obtain a first rectifier output signal and/or adjusting the second transformer output signal to obtain a second rectifier output signal, the first inductor is used for adjusting the current of the first rectifier output signal, the second inductor is used for adjusting the current of the second rectifier output signal, wherein the first inductor and the second inductor are coupled inductors, the first capacitor is used for adjusting the voltage of the first rectified output signal and/or the voltage of the second rectified output signal.
In a second aspect, embodiments of the present application provide a low-voltage high-current charging system, which includes a control circuit, a load device, and a low-voltage high-current output circuit as described in the first aspect.
It can be seen that the low-voltage large-current output circuit in the embodiment of the present application includes an inverter module, a first transformer module, a second transformer module, a rectifier module, a first inductor, a second inductor, and a first capacitor, where the inverter module is configured to input a first inverter output signal to the first transformer module and/or input a second inverter output signal to the second transformer module, the first transformer module is configured to adjust a voltage of the first inverter output signal to obtain a first transformer output signal, the second transformer module is configured to adjust a voltage of the second inverter output signal to obtain a second transformer output signal, the rectifier module is configured to adjust the first transformer output signal to obtain a first rectifier output signal and/or adjust the second transformer output signal to obtain a second rectifier output signal, the first inductor is configured to adjust a current of the first rectifier output signal, and the second inductor is configured to adjust a current of the second rectifier output signal, the first inductor and the second inductor are coupling inductors, and the first capacitor is used for adjusting the voltage of the first rectified output signal and/or the voltage of the second rectified output signal. Therefore, the heat dissipation capacity of the circuit is reduced, the circuit loss is reduced, the stable operation of the circuit is ensured, the number of devices in the circuit is reduced, and the production cost is reduced.
Drawings
In order to more clearly illustrate the embodiments of the present application or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present application, and for those skilled in the art, other drawings can be obtained according to the drawings without creative efforts.
Fig. 1 is a schematic structural diagram of a low-voltage large-current output circuit according to an embodiment of the present disclosure;
FIG. 2 is a current schematic of a filter inductor provided herein;
FIG. 3 is a current schematic of a filter inductor provided herein;
fig. 4 is a current diagram of a filter inductor according to an embodiment of the present disclosure;
FIG. 5 is a circuit diagram of a low-voltage high-current output circuit according to an embodiment of the present disclosure;
fig. 6 is a current schematic diagram of a filter inductor according to an embodiment of the present disclosure;
fig. 7 is a current schematic diagram of a filter inductor according to an embodiment of the present application;
fig. 8 is a schematic structural diagram of a low-voltage large-current charging system according to an embodiment of the present application.
Detailed Description
In order to make the technical solutions better understood by those skilled in the art, the technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are some embodiments of the present invention, but not all embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
The terms "first," "second," and the like in the description and claims of the present application and in the above-described drawings are used for distinguishing between different objects and not for describing a particular order. Furthermore, the terms "include" and "have," as well as any variations thereof, are intended to cover non-exclusive inclusions. For example, a process, method, system, article, or apparatus that comprises a list of steps or elements is not limited to only those steps or elements listed, but may alternatively include other steps or elements not listed, or inherent to such process, method, article, or apparatus. The term "plurality" may refer to two or more, and will not be described further.
Reference herein to "an embodiment" means that a particular feature, structure, or characteristic described in connection with the embodiment can be included in at least one embodiment of the application. The appearances of the phrase in various places in the specification are not necessarily all referring to the same embodiment, nor are separate or alternative embodiments mutually exclusive of other embodiments. It is explicitly and implicitly understood by one skilled in the art that the embodiments described herein can be combined with other embodiments.
In the technical fields of high-power direct-current charging, communication power supplies and the like, a power electronic module is generally required to work in a high-current state, and the common working condition is 20kW50V 400A. At present, the common direct current-to-direct current circuit structure and control strategy often cause some problems under such working conditions. For example, in a large current state, the temperature rise of the electronic device is high, the heat dissipation amount is increased, the circuit stability is easily affected, and the loss of the filter inductor is easily increased in the large current state. For another example, in a scheme of increasing a plurality of electronic devices to achieve shunting and heat dissipation, a current sharing control strategy of a plurality of paths of currents needs to be additionally added, and the number of the devices is increased, so that the production cost is also increased.
To solve the above problems, an embodiment of the present invention provides a low-voltage large-current output circuit, please refer to fig. 1, where fig. 1 is a schematic structural diagram of the low-voltage large-current output circuit provided in the embodiment of the present invention. As shown, the low-voltage large-current output circuit 10 includes an inverter module 101, a first transformer module 102, a second transformer module 103, a rectifier module 104, a first inductor 105, a second inductor 106, and a first capacitor 107, wherein,
a first output end of the inverter module 101 is connected to an input end of the first transformer module 102, a second output end of the inverter module 101 is connected to an input end of the second transformer module 103, an output end of the first transformer module 102 is connected to a first input end of the rectifier module 104, an output end of the second transformer module 103 is connected to a second input end of the rectifier module 104, a first output end of the rectifier module 104 is connected to an input end of the first inductor 105, a second output end of the rectifier module 104 is connected to an input end of the second inductor 106, and an output end of the first inductor 105, an output end of the second inductor 106 and one end of the first capacitor 107 are connected;
the inverting module 101 is configured to input a first inverting output signal to the first transforming module 102, and/or, configured to input a second inverting output signal to the second transforming module 103, the first transforming module 102 is configured to adjust a voltage of the first inverting output signal to obtain a first transforming output signal, the second transforming module 103 is configured to adjust a voltage of the second inverting output signal to obtain a second transforming output signal, the rectifying module 104 is configured to adjust the first transforming output signal to obtain a first rectifying output signal, and/or, configured to adjust the second transforming output signal to obtain a second rectifying output signal, the first inductor 105 is configured to adjust a current of the first rectifying output signal, the second inductor 106 is configured to adjust a current of the second rectifying output signal, where the first inductor 105 and the second inductor 106 are coupled inductors, the first capacitor 107 is used for regulating the voltage of the first rectified output signal and/or the voltage of the second rectified output signal.
In a specific implementation, the first transforming module 102 and the second transforming module 103 may be used simultaneously or alternatively, and are not limited herein.
For example, in the case where the first transformation module 102 and the second transformation module 103 are used simultaneously: the inversion module 101 adjusts an input dc signal to obtain a first inversion output signal and a second inversion output signal, where the first inversion output signal and the second inversion output signal are both ac signals. The first inverse transformation output signal is input to the first transformation module 102, and the first transformation module 102 adjusts the voltage of the first inverse transformation output signal to obtain a first transformation output signal, and inputs the first transformation output signal to the rectification module 104. The second inversion output signal is input to the second voltage transformation module 103, and the second voltage transformation module 103 adjusts the voltage of the second inversion output signal to obtain a second voltage transformation output signal, and inputs the second voltage transformation output signal to the rectification module 104. The rectification module 104 adjusts the first voltage transformation output signal to obtain a first rectification output signal, and adjusts the second voltage transformation output signal to obtain a second rectification output signal, wherein the first rectification output signal and the second rectification output signal are both direct current signals. The first rectified output signal is input to a first inductor 105 and a first capacitor 107, the first inductor 105 regulating the current of the first rectified output signal and the first capacitor 107 regulating the voltage of the first rectified output signal. The second rectified output signal is input to a second inductor 106 and a first capacitor 107, the second inductor 106 regulating the current of the second rectified output signal, and the first capacitor 107 regulating the voltage of the second rectified output signal.
Thus, the use of the first transformer module 102 and the second transformer module 103 at the same time helps to reduce the amount of heat dissipated by the single transformer module when the current in the circuit is large, and helps to ensure stable operation of the circuit.
As another example, the first transformer module 102 and the second transformer module 103 may alternatively be used. In the case of using the first transformation module 102: the inverter module 101 adjusts an input dc signal to obtain a first inverter output signal, where the first inverter output signal is an ac signal. The first inverse transformation output signal is input to the first transformation module 102, and the first transformation module 102 adjusts the voltage of the first inverse transformation output signal to obtain a first transformation output signal, and inputs the first transformation output signal to the rectification module 104. The rectifying module 104 is configured to adjust the first voltage transformation output signal to obtain a first rectified output signal, where the first rectified output signal is a direct current signal. The first rectified output signal is input to a first inductor 105 and a first capacitor 107, the first inductor 105 regulating the current of the first rectified output signal and the first capacitor 107 regulating the voltage of the first rectified output signal.
Similarly, in the case where the second transformation module 103 is used: the inverter module 101 adjusts an input dc signal to obtain a second inverter output signal, where the second inverter output signal is an ac signal. The second inversion output signal is input to the second voltage transformation module 103, and the second voltage transformation module 103 adjusts the voltage of the second inversion output signal to obtain a second voltage transformation output signal, and inputs the second voltage transformation output signal to the rectification module 104. The rectifying module 104 is configured to adjust the second voltage transformation output signal to obtain a second rectified output signal, where the second rectified output signal is a direct current signal. The second rectified output signal is input to a second inductor 106 and a first capacitor 107, the second inductor 106 regulating the current of the second rectified output signal, and the first capacitor 107 regulating the voltage of the second rectified output signal.
In this way, when the first transformer module 102 or the second transformer module 103 fails, the other transformer module capable of working normally can be further used for adjusting the first inverter output signal or the second inverter output signal, which is helpful for ensuring the operation of the circuit.
Further, the first inductor 105 and the second inductor 106 may be coupled inductors. The first inductor 105 and the second inductor 106 may be designed by using a magnetic integration technology, that is, the first inductor 105 and the second inductor 106 are wound on a pair of magnetic cores. The first inductor 105 and the second inductor 106 are structurally grouped together.
As such, on the one hand, the total volume and total weight of the first inductor 105 and the second inductor 106 are reduced, and in a high-current state, the coupling inductor also helps to reduce current ripple and inductance loss because a large current usually brings about a large current ripple. On the other hand, the coupled inductors help to ensure that the inductance of the first inductor 105 and the inductance of the second inductor 106 are similar or equal, so that the current through the first inductor 105 and the current through the second inductor 106 are similar or equal. Since the output of the first inductor 105 and the output of the second inductor 106 are connected in series, the first inductor 105 and the second inductor 106 share a large current in the circuit, so that the current flowing through the first inductor 105 and the current flowing through the second inductor 106 are both small. It can be understood that, under the condition of a small current, the magnetic field intensity of the inductor is small, and according to the magnetization curve, or called B-H curve, the magnetic field intensity of the inductor is not easy to saturate when the magnetic field intensity of the inductor is small. The magnetic induction intensity is not easy to saturate, thus being beneficial to ensuring the filtering effect of the inductor.
Referring to fig. 2 and 3, fig. 2 and 3 are schematic current diagrams of a filter inductor. In the case of using the non-coupled inductor, there is a 10% error between the actual inductance of the inductor and the nominal inductance, that is, there may be a 20% difference between the inductances of the two inductors. Inductance L1=24 μ H and inductance L2=20 μ H, and in the case of other parameters in the circuit being identical, the currents flowing through the two inductances are as shown in fig. 2. In the live operation, there may be a larger deviation, for example, a 50% deviation, in the inductance of the two inductors. Inductance L3=30 μ H and inductance L4=20 μ H, and in the case of other parameters in the circuit being identical, the currents flowing through the two inductances are as shown in fig. 3.
It can be seen that, in fig. 2 and fig. 3, the currents of the two sets of inductors have large deviations at the stage t1, and the current average value of the inductor L1 is larger than that of the inductor L2, and the current average value of the inductor L3 is larger than that of the inductor L4. That is, the larger the inductance, the larger the average value of the current flowing through the inductance. The current average value is large, which causes a large heat value of the circuit and affects the service life of the device on one hand, and on the other hand, it is difficult to ensure the filtering effect of the inductor.
Referring to fig. 4, fig. 4 is a schematic current diagram of a filter inductor according to an embodiment of the present disclosure. In the case of using a coupled inductor, the inductance deviation of the two inductors is within 3%. For example, inductance L5=20 μ H, inductance L6=20.6 μ H, and the currents flowing through the two inductances are as shown in fig. 4 when other parameters in the circuit are consistent. It can be seen that the current through inductor L5 is similar to the current through inductor L6.
As can be seen from the foregoing description, when the inductor L5 and the inductor L6 are connected in series, the inductor L5 and the inductor L6 share the current in the circuit together, so that the current flowing through the inductor L5 and the current flowing through the inductor L6 are both small, thereby helping to ensure the filtering effect of the inductor L5 and the inductor L6.
It can be seen that the low-voltage large-current output circuit 10 in the embodiment of the present application includes an inverter module 101, a first transformer module 102, a second transformer module 103, a rectifier module 104, a first inductor 105, a second inductor 106, and a first capacitor 107, where the inverter module 101 is configured to input a first inverted output signal to the first transformer module 102 and/or input a second inverted output signal to the second transformer module 103, the first transformer module 102 is configured to adjust a voltage of the first inverted output signal to obtain a first transformed output signal, the second transformer module 103 is configured to adjust a voltage of the second inverted output signal to obtain a second transformed output signal, the rectifier module 104 is configured to adjust the first transformed output signal to obtain a first rectified output signal and/or adjust the second transformed output signal to obtain a second rectified output signal, the first inductor 105 is configured to adjust a current of the first rectified output signal, the second inductor 106 is used for adjusting the current of the second rectified output signal, wherein the first inductor 105 and the second inductor 106 are coupled inductors, and the first capacitor 107 is used for adjusting the voltage of the first rectified output signal and/or the voltage of the second rectified output signal. Therefore, the heat dissipation capacity of the circuit is reduced, the circuit loss is reduced, the stable operation of the circuit is ensured, the number of devices in the circuit is reduced, and the production cost is reduced.
Referring to fig. 5, in one possible example, the rectifier module 104 includes a first rectifier 1041 and/or a second rectifier 1042, an input terminal of the first rectifier 1041 is connected to an output terminal of the first transformer module 102, and an input terminal of the second rectifier 1042 is connected to an output terminal of the second transformer module 103.
In a specific implementation, the first rectifier 1041 and the second rectifier 1042 may be used simultaneously or alternatively, and are not limited herein.
For example, in the case where the first rectifier 1041 and the second rectifier 1042 are used simultaneously: the inversion module 101 adjusts the input dc signal to obtain a first inversion output signal and a second inversion output signal. The first inverse transformation output signal is input to the first transformation module 102, and the first transformation module 102 adjusts the voltage of the first inverse transformation output signal to obtain a first transformation output signal, and inputs the first transformation output signal to the rectification module 104. The second inversion output signal is input to the second voltage transformation module 103, and the second voltage transformation module 103 adjusts the voltage of the second inversion output signal to obtain a second voltage transformation output signal, and inputs the second voltage transformation output signal to the rectification module 104. The first rectifier 1041 adjusts the first transformed output signal to obtain a first rectified output signal. The second rectifier 1042 regulates the second transformed output signal to obtain a second rectified output signal. The first rectified output signal is input to a first inductor 105 and a first capacitor 107, the first inductor 105 regulating the current of the first rectified output signal and the first capacitor 107 regulating the voltage of the first rectified output signal. The second rectified output signal is input to a second inductor 106 and a first capacitor 107, the second inductor 106 regulating the current of the second rectified output signal and the first capacitor 107 regulating the voltage of the first rectified output signal.
Thus, the use of the first rectifier 1041 and the second rectifier 1042 at the same time helps to increase the capacity of the rectifiers when the current in the circuit is large, so as to allow the rectifiers to flow larger current, and help to ensure stable operation of the circuit.
As another example, the first rectifier 1041 and the second rectifier 1042 may be alternatively used. In the case of using the first rectifier 1041: the inversion module 101 adjusts the input dc signal to obtain a first inversion output signal and/or a second inversion output signal. The first inversion output signal is input to the first transforming module 102 to obtain a first transforming output signal, and/or the second inversion output signal is input to the second transforming module 103 to obtain a second transforming output signal. The first rectifier 1041 is configured to regulate the first transformed output signal and/or the second transformed output signal to obtain a first rectified output signal and/or a second rectified output signal. The first rectified output signal is input to a first inductor 105 and a first capacitor 107, the first inductor 105 regulating the current of the first rectified output signal and the first capacitor 107 regulating the voltage of the first rectified output signal, and/or the second rectified output signal is input to a second inductor 106 and a first capacitor 107, the second inductor 106 regulating the current of the second rectified output signal and the first capacitor 107 regulating the voltage of the second rectified output signal.
Similarly, in the case of using the second rectifier 1042: the inversion module 101 adjusts the input dc signal to obtain a first inversion output signal and/or a second inversion output signal. The first inversion output signal is input to the first transforming module 102 to obtain a first transforming output signal, and/or the second inversion output signal is input to the second transforming module 103 to obtain a second transforming output signal. The second rectifier 1042 is used for adjusting the first transformed output signal and/or the second transformed output signal to obtain a first rectified output signal and/or a second rectified output signal. The first rectified output signal is input to a first inductor 105 and a first capacitor 107, the first inductor 105 regulating the current of the first rectified output signal and the first capacitor 107 regulating the voltage of the first rectified output signal, and/or the second rectified output signal is input to a second inductor 106 and a first capacitor 107, the second inductor 106 regulating the current of the second rectified output signal and the first capacitor 107 regulating the voltage of the second rectified output signal.
In this way, when the first rectifier 1041 or the second rectifier 1042 fails, the other rectifier capable of working normally can be used to adjust the first transformation output signal and/or the second transformation output signal, which helps to ensure the operation of the circuit.
In one possible example, the first rectifier 1041 comprises one or more silicon carbide diodes, and/or the second rectifier 1042 comprises one or more silicon carbide diodes.
In specific implementation, because the silicon carbide diode has the characteristic of positive temperature coefficient, the forward conduction voltage drop of the silicon carbide diode is increased along with the increase of the temperature, so that the silicon carbide diode has the capability of feedback regulation in a circuit, and the phenomenon of non-uniform current in the circuit can be inhibited.
As can be seen from the foregoing description, the average value of the current flowing through the inductor is larger in the branch with larger inductance, and the larger average value of the current causes the temperature of the diode of the branch to be higher than that of the diode of the other branch. Because the silicon carbide diode used in the embodiment of the application has the positive temperature coefficient, the voltage drop of the silicon carbide diode is increased under the condition of higher temperature, so that the voltage drop at two ends of the inductor is increased. By
Figure DEST_PATH_IMAGE001
It can be known that when the voltage drop U between the two ends of the inductor increases, the current decrease slope
Figure 115974DEST_PATH_IMAGE002
With a consequent increase. This helps to further reduce the difference between the currents flowing through the first inductor 105 and the second inductor 106.
Referring to fig. 6, fig. 6 is a schematic current diagram of a filter inductor according to an embodiment of the present disclosure. Inductance L7=20 μ H, common diode such as silicon-based diode or schottky diode in cooperation with voltage drop Vf =0.7V, inductance L8=20.6 μ H, common diode in cooperation with voltage drop Vf = 0.7V. It can be seen that in the case of using a coupled inductor and a common diode, although the currents through the two inductors are already relatively close, there is still a small error. This error can be feedback compensated using silicon carbide diodes to further reduce the error.
Referring to fig. 7, fig. 7 is a current schematic diagram of a filter inductor according to an embodiment of the present disclosure. Inductance L9=20 μ H, common diode with a drop Vf =0.7V, inductance L10=20.6 μ H, silicon carbide diode with a drop Vf = 1.5V. It can be seen that the silicon carbide diode reduces the difference of two paths of current, and plays a role in further current sharing.
It can be understood that the larger the number of the silicon carbide diodes in the first rectifier 1041, the better the current equalizing effect of the first rectifier 1041 is. For example, when the first rectifier 1041 includes 4 silicon carbide diodes, the current sharing effect is better than that of the first rectifier 1041 including 3 silicon carbide diodes, which helps to better suppress the non-uniform current phenomenon in the circuit. The second rectifier 1042 performs the same function, and is not further described herein.
Referring to fig. 5 again, in a possible example, the inverter module 101 includes a first switch tube 1011, a second switch tube 1012, a third switch tube 1013, and a fourth switch tube 1014, where the first switch tube 1011, the second switch tube 1012, the third switch tube 1013, and the fourth switch tube 1014 are used to adjust an input signal to obtain a switch tube output signal.
When the first switch tube 1011 and the fourth switch tube 1014 in the inverter module 101 are turned on, the current direction of the output signal of the switch tube is the first direction. When the second switch tube 1012 and the third switch tube 1013 of the inverter module 101 are turned on, the current direction of the output signal of the switch tube is the second direction. Wherein the first direction is opposite to the second direction. Thus, the inverter module 101 can adjust an input dc signal to obtain a first inverter output signal, where the first inverter output signal is an ac signal.
In this embodiment, the inverter module 101 includes a first switch tube 1011, a second switch tube 1012, a third switch tube 1013, and a fourth switch tube 1014, where the first switch tube 1011, the second switch tube 1012, the third switch tube 1013, and the fourth switch tube 1014 are configured to adjust an input signal to obtain a switch tube output signal, and thus, an input dc signal can be inverted by controlling an off state of the switch tubes to obtain an ac signal.
Referring to fig. 5 again, in a possible example, the inverting module 101 further includes a third inductor 1015 and a second capacitor 1016, the third inductor is used for adjusting the voltage of the output signal of the switching tube to obtain the voltage of the first inverted output signal and/or the voltage of the second inverted output signal, and the second capacitor 1016 is used for adjusting the current of the output signal of the switching tube to obtain the current of the first inverted output signal and/or the current of the second inverted output signal.
In a specific implementation, the third inductor 1015 and the second capacitor 1016 may perform a resonant filtering function, so as to adjust a square wave of an output signal of the switching tube into a sine wave, that is, the first inverted output signal and the second inverted output signal are sine waves. Thus, the first inversion output signal and the second inversion output signal output by the inversion module 101 can be adjusted, and the sine wave can be output.
In one possible example, the silicon carbide diode is used to voltage compensate the first inductor 105 and the second inductor 106 within a predetermined current difference protection window.
The preset current difference protection window may be a default protection window in the circuit, or may be set by a user, which is not limited herein. The current difference may refer to an absolute value of a difference between a current flowing through the first inductor 105 and a current flowing through the second inductor 106.
In the embodiment of the present application, the silicon carbide diode is used to perform voltage compensation on the first inductor 105 and the second inductor 106 in a preset current difference protection window, which is helpful for reducing a current difference between the two inductors and is helpful for further current sharing.
In one possible example, the current range of the preset current difference protection window is [0, Idiff ], and the Idiff is obtained by the following formula:
Idiff=|α+1-1/eT|，
where α is a current influence factor, T is a temperature of the silicon carbide diode, eTIs an exponential function with e as the base and T as the power.
The current influence factor α may be determined according to the manufacturer, production lot, service life, and other factors of the silicon carbide diode, and is not limited herein. The value of alpha is any value in a preset numerical range, the minimum value of the preset numerical range is greater than or equal to 1, and the maximum value of the preset numerical range is less than or equal to 20.
In a specific implementation, e is the temperature T of the silicon carbide diode is greater than 0 DEG CTIs of large value, 1/eTThe value is small. By Idiff = | α +1-1/eTI know that when 1/eTWhen infinity is reached, the upper limit of the value of Idiff is α + 1. Similarly, when the temperature T of the silicon carbide diode is less than 0 DEG CIn degree of time, eTIs small in value, 1/eTThe value is large. By Idiff = | α +1-1/eT1/e ofTAt infinity, the upper limit of the Idiff value is 1/eT. Since the operating temperature of the circuit is generally not lower than 0 degree celsius, the upper limit of the Idiff value is generally α + 1.
Referring to fig. 8, the embodiment of the present application further provides a low-voltage large-current charging system 800, which includes a control circuit 801, a load device 802, and a low-voltage large-current output circuit 803 according to any of the embodiments described above.
In one possible example, the load device 802 comprises a vehicle battery, and the control circuit 801 is configured to:
acquiring the current output voltage and current output current of the low-voltage large-current output circuit;
obtaining a target output voltage according to the current output voltage, the current output current, a preset charging power and a first preset relation;
and charging the vehicle battery according to the target output voltage.
Wherein the first predetermined relationship is:
Figure 876119DEST_PATH_IMAGE003
。Uo' is the target output voltage, P is the preset charging power, UoFor the current output voltage, IoIs the present output current. The preset charging power P may be set comprehensively according to circuit parameters (e.g., the number of devices in the circuit, device calibration parameters, and error range of calibration parameters) of the low-voltage large-current output circuit, battery types (e.g., a lithium ion battery, a lead-acid battery, a nickel-metal hydride battery, etc.), user input, and other factors, which are not limited herein, and may be, for example, 15kW, 20kW, 23kW, 30kW, and the like.
In a specific implementation, the vehicle battery can be charged in a constant power mode when the vehicle battery is in an undervoltage state. In the constant power mode, the low-voltage large-current output circuit adjusts the target output voltage by adjusting the first inverter module, so that the product of the target output voltage and the target output current is constant, that is, the target output power is ensured to be constant.
It can be understood that, during the charging process of the vehicle battery, the voltage of the vehicle battery continuously rises, and if the target output voltage is kept unchanged, the target output current and therefore the target output power continuously drop. In order to ensure that the target output power of the low-voltage large-current output circuit is kept unchanged, the current output voltage can be adjusted through the first preset relation so as to obtain the target output voltage.
For example, at the present output voltage UoWith the present output current IoIf the product of (a) and (b) is less than the preset charging power P, that is, if the current output power is less than the preset charging power P, then
Figure 267787DEST_PATH_IMAGE004
Greater than 1. By
Figure 466687DEST_PATH_IMAGE005
It can be seen that the target output voltage U is nowo' should be greater than the present output voltage Uo. Therefore, under the condition that the current output power is smaller than the preset charging power, the first inversion module is adjusted, the target output voltage is increased, the output power is kept unchanged, the charging efficiency of the vehicle battery is accelerated, and meanwhile the safety and the stability in the charging process are ensured.
At the present output voltage UoWith the present output current IoWhen the product of (d) is equal to the preset charging power P, the current output power is equal to the preset charging power P, and at this time
Figure 322516DEST_PATH_IMAGE006
Equal to 1. By
Figure 253563DEST_PATH_IMAGE007
It can be seen that the target output voltage U is nowoIs equal to the present output voltage UoThat is to say the target output voltage Uo' remain unchanged. Thus, the target output is achieved in the state of vehicle battery saturationThe output voltage is kept unchanged, and the electric energy is saved.
In one possible example, the present output voltage UoAnd the current output current IoAnd satisfying a second preset relationship, wherein the second preset relationship is as follows:
Uo-Ui=Io×Rc×(P+0.05)；
wherein, UiIs the battery source voltage, UoFor the current output voltage, IoFor the present output current, RcP is the internal resistance of the vehicle battery, and is the circuit influencing factor of the vehicle battery.
The circuit influence factor P may be determined according to factors such as the degree of component aging of the vehicle battery, the type of the battery, and the like, and is not limited herein, and may be, for example, 0.65, 0.7, 0.81, 0.9, and the like.
In specific implementation, a vehicle battery can be equivalent to a battery capacitor, an internal resistance and a battery source voltage U which are connected in seriesiCan be regarded as the voltage at two ends of the battery capacitor, then the current output voltage UoAnd the battery source voltage UiThe difference is the voltage at the two ends of the internal resistance. Theoretically, the voltage across the internal resistance is equal to the current output current IoAnd internal resistance RcThe voltage across the internal resistance is actually lower than the current output current I in consideration of the use duration of the vehicle battery part, the circuit loss and the likeoAnd internal resistance RcThus, a circuit influence factor P is introduced, which can be used to influence the present output current IoAnd internal resistance RcThe product of the voltage and the current output current I is adjusted to be fineoAnd internal resistance RcThe products of (a) and (b) are equal.
It should be noted that, for simplicity of description, the aforementioned embodiments of the invention are described as a series of acts or combination of acts, but those skilled in the art will recognize that the invention is not limited by the illustrated order of acts, as some steps may occur in other orders or concurrently in accordance with the invention. Further, those skilled in the art should also appreciate that the embodiments described in the specification are preferred embodiments and that the acts and modules referred to are not necessarily required by the invention.
In the foregoing embodiments, the descriptions of the respective embodiments have respective emphasis, and for parts that are not described in detail in a certain embodiment, reference may be made to related descriptions of other embodiments.
In the embodiments provided in the present invention, it should be understood that the disclosed apparatus can be implemented in other manners. For example, the above-described embodiments of the apparatus are merely illustrative, and for example, the above-described division of the units is only one type of division of logical functions, and other divisions may be realized in practice, for example, a plurality of units or components may be combined or integrated into another system, or some features may be omitted, or not executed. In addition, the shown or discussed mutual coupling or direct coupling or communication connection may be an indirect coupling or communication connection of some interfaces, devices or units, and may be an electric or other form.
The units described as separate parts may or may not be physically separate, and parts displayed as units may or may not be physical units, may be located in one place, or may be distributed on a plurality of network units. Some or all of the units can be selected according to actual needs to achieve the purpose of the solution of the embodiment.
In addition, functional units in the embodiments of the present invention may be integrated into one processing unit, or each unit may exist alone physically, or two or more units are integrated into one unit. The integrated unit can be realized in a form of hardware, and can also be realized in a form of a software functional unit.
The above embodiments are merely representative of the centralized embodiments of the present invention, and the description thereof is specific and detailed, but it should not be understood as the limitation of the scope of the present invention, and it should be noted that those skilled in the art can make various changes and modifications without departing from the spirit of the present invention, and these changes and modifications all fall into the protection scope of the present invention. Therefore, the protection scope of the present patent should be subject to the appended claims.

Claims (7)

1. A low voltage high current output circuit, comprising: the rectifier comprises an inverter module, a first transformation module, a second transformation module, a rectifier module, a first inductor, a second inductor and a first capacitor, wherein the rectifier module comprises a first rectifier and/or a second rectifier, the first rectifier comprises one or more silicon carbide diodes, and/or the second rectifier comprises one or more silicon carbide diodes, and the silicon carbide diodes are used for performing voltage compensation on the first inductor and the second inductor in a preset current difference protection window, wherein,
a first output end of the inversion module is connected with an input end of the first transformation module, a second output end of the inversion module is connected with an input end of the second transformation module, an output end of the first transformation module is connected with an input end of the first rectifier, an output end of the second transformation module is connected with an input end of the second rectifier, a first output end of the rectification module is connected with an input end of the first inductor, a second output end of the rectification module is connected with an input end of the second inductor, and an output end of the first inductor, an output end of the second inductor and one end of the first capacitor are connected;
the inverter module is used for inputting a first inverter output signal to the first transformer module and/or inputting a second inverter output signal to the second transformer module, the first transformer module is used for adjusting the voltage of the first inverter output signal to obtain a first transformer output signal, the second transformer module is used for adjusting the voltage of the second inverter output signal to obtain a second transformer output signal, the rectifier module is used for adjusting the first transformer output signal to obtain a first rectifier output signal and/or adjusting the second transformer output signal to obtain a second rectifier output signal, the first inductor is used for adjusting the current of the first rectifier output signal, the second inductor is used for adjusting the current of the second rectifier output signal, wherein the first inductor and the second inductor are coupled inductors, the first capacitor is used for adjusting the voltage of the first rectified output signal and/or the voltage of the second rectified output signal.
2. The low-voltage high-current output circuit as claimed in claim 1, wherein the inverter module comprises a first switch tube, a second switch tube, a third switch tube and a fourth switch tube, and the first switch tube, the second switch tube, the third switch tube and the fourth switch tube are used for adjusting an input signal to obtain a switch tube output signal.
3. The low-voltage high-current output circuit according to claim 2, wherein the inverting module further comprises a third inductor and a second capacitor, the third inductor is configured to adjust the voltage of the output signal of the switching tube to obtain the voltage of the first inverted output signal and/or the voltage of the second inverted output signal, and the second capacitor is configured to adjust the current of the output signal of the switching tube to obtain the current of the first inverted output signal and/or the current of the second inverted output signal.
4. A low-voltage large-current output circuit according to claim 1, wherein the current range of the preset current difference protection window is [0, Idiff ], and the Idiff is obtained by the following formula:
Idiff=|α+1-1/eT|，
where α is a current influence factor, T is a temperature of the silicon carbide diode, eTIs an exponential function with e as the base and T as the power.
5. A low-voltage high-current output circuit according to claim 4,
the value of alpha is any value in a preset numerical range, the minimum value of the preset numerical range is greater than or equal to 1, and the maximum value of the preset numerical range is less than or equal to 20.
6. A low-voltage high-current charging system, characterized by comprising a control circuit, a load device and a low-voltage high-current output circuit according to any one of claims 1 to 5.
7. A low voltage high current charging system according to claim 6, wherein said load device comprises a vehicle battery, and said control circuit is configured to:
acquiring the current output voltage and current output current of the low-voltage large-current output circuit;
obtaining a target output voltage according to the current output voltage, the current output current, a preset charging power and a first preset relation;
and charging the vehicle battery according to the target output voltage.
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