CN113708070A - Broadband single-station common-horizontal-polarization full-duplex antenna based on integrated beam forming network - Google Patents

Broadband single-station common-horizontal-polarization full-duplex antenna based on integrated beam forming network Download PDF

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CN113708070A
CN113708070A CN202110988765.0A CN202110988765A CN113708070A CN 113708070 A CN113708070 A CN 113708070A CN 202110988765 A CN202110988765 A CN 202110988765A CN 113708070 A CN113708070 A CN 113708070A
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antenna
hybrid coupler
antenna unit
duplex
station
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CN113708070B (en
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吴迪
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Shenzhen University
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Shenzhen University
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H01Q1/525—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas between emitting and receiving antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)

Abstract

The invention discloses a broadband single-station common-horizontal polarization full-duplex antenna based on an integrated beam forming network, which comprises a receiving and transmitting antenna and a beam forming network circuit simultaneously; the beam forming network circuit comprises a power divider, a 90-degree hybrid coupler, a first backward hybrid coupler and a second backward hybrid coupler, and the transceiving antenna comprises a first antenna unit, a second antenna unit, a third antenna unit and a fourth antenna unit, wherein the power divider is connected with a signal input port, the first backward hybrid coupler and the second backward hybrid coupler, the 90-degree hybrid coupler is connected with a signal output end, the first backward hybrid coupler and the second backward hybrid coupler, the first antenna unit and the third antenna unit are both connected with the first backward hybrid coupler, and the second antenna unit and the fourth antenna unit are both connected with the second backward hybrid coupler. The full-duplex antenna can realize omnidirectional coverage, improve impedance bandwidth, reduce gain fluctuation of a horizontal plane and greatly improve communication quality.

Description

Broadband single-station common-horizontal-polarization full-duplex antenna based on integrated beam forming network
Technical Field
The invention relates to the technical field of wireless communication equipment, in particular to a broadband single-station co-horizontal polarization full-duplex antenna based on an integrated beam forming network.
Background
With the rapid development of information technology, various terminal devices need to access the internet through a wireless communication technology, and a broadband wireless communication antenna needs to be designed to meet the increasing demand of a terminal on the wireless communication quality. The existing In-Band Full Duplex (IBFD), co-frequency simultaneous Full Duplex and simultaneous transmitting and receiving antenna technology can realize high isolation between transmitting and receiving ports, and has great improvement In spectrum efficiency and communication capacity, however, the existing wireless communication antenna has the problem of weak omnidirectional coverage when transmitting and receiving signals In the whole broadband, which leads to easy generation of signal blind areas and affects wireless communication quality. Therefore, the wireless communication antenna in the prior art method has the problem of weak omnidirectional coverage capability.
Disclosure of Invention
The embodiment of the invention provides a broadband single-station common horizontal polarization full-duplex antenna based on an integrated beam forming network, aiming at solving the problem that the omnidirectional coverage of a wireless communication antenna in the prior art is not strong.
The embodiment of the invention provides a broadband single-station common horizontal polarization full-duplex antenna based on an integrated beam forming network, wherein the antenna comprises a receiving and transmitting antenna and a beam forming network circuit simultaneously;
the beamforming network circuit comprises a power divider, a 90-degree hybrid coupler, a first inverse hybrid coupler and a second inverse hybrid coupler;
the power divider is connected with a signal input port, the first inverse hybrid coupler and the second inverse hybrid coupler and used for dividing a transmitting signal input by the signal input port to the first inverse hybrid coupler and the second inverse hybrid coupler;
the 90-degree hybrid coupler is connected with a signal output end, the first inverse hybrid coupler and the second inverse hybrid coupler, and is used for receiving the receiving signals from the first inverse hybrid coupler and the second inverse hybrid coupler and outputting the receiving signals through the signal output end;
the simultaneous transceiving antenna comprises a first antenna unit, a second antenna unit, a third antenna unit and a fourth antenna unit;
the first backward hybrid coupler is connected with the first antenna unit and the third antenna unit at the same time and is used for receiving and transmitting signals of the first antenna unit and the third antenna unit at the same time; the second inverse hybrid coupler is connected to the second antenna unit and the fourth antenna unit at the same time, and is configured to receive and transmit signals of the second antenna unit and the fourth antenna unit at the same time.
The broadband single-station co-horizontal polarization full-duplex antenna based on the integrated beam forming network is characterized in that the first antenna unit, the second antenna unit, the third antenna unit and the fourth antenna unit are all arranged on an antenna substrate, the first antenna unit and the third antenna unit are arranged in a central symmetry mode, and the second antenna unit and the fourth antenna unit are arranged in a central symmetry mode.
The broadband single-station common-horizontal-polarization full-duplex antenna based on the integrated beam forming network is characterized in that the first antenna unit, the second antenna unit, the third antenna unit and the fourth antenna unit are all composed of a printed dipole, a first parasitic strip and a second parasitic strip, and the first parasitic strip and the second parasitic strip are respectively arranged on the side of the printed dipole and are not connected with the printed dipole.
The broadband single-station co-horizontal polarization full-duplex antenna based on the integrated beam forming network is characterized in that a circular floor is arranged on the bottom layer of the antenna substrate;
the printed dipole and the first parasitic strip are arranged in a common circle and surround the outer side of the circular floor; the second parasitic band is arranged around the outer side of the printed dipole;
the broadband single-station co-horizontal polarization full-duplex antenna based on the integrated beam forming network is characterized in that the antenna substrate is a circular substrate, and the printed dipole, the first parasitic strip and the second parasitic strip are all arc-shaped;
one arm of each printed dipole is connected with a corresponding microstrip line in the top layer of the antenna substrate through a parallel line, and the other arm of each printed dipole is printed on the bottom layer of the antenna substrate and is connected with the circular floor through a parallel strip line.
The broadband single-station co-horizontally polarized full-duplex antenna based on the integrated beam forming network is characterized in that the input end of the power divider is connected with the signal input port, the first output end of the power divider is connected with the input end of the first inverse hybrid coupler, and the second output end of the power divider is connected with the input end of the second inverse hybrid coupler;
the first output end of the 90-degree hybrid coupler is connected with the signal output end, the first input end of the 90-degree hybrid coupler is connected with the output end of the first inverse hybrid coupler, and the second input end of the 90-degree hybrid coupler is connected with the output end of the second inverse hybrid coupler.
The broadband single-station common-horizontal polarization full-duplex antenna based on the integrated beam forming network is characterized in that a first antenna port of the first inverse hybrid coupler is connected with a microstrip line corresponding to a printed dipole of the first antenna unit, and a second antenna port of the first inverse hybrid coupler is connected with a microstrip line corresponding to a printed dipole of the third antenna unit;
and a first antenna port of the second inverse hybrid coupler is connected with a microstrip line corresponding to the printed dipole of the second antenna unit, and a second antenna port of the second inverse hybrid coupler is connected with a microstrip line corresponding to the printed dipole of the fourth antenna unit.
The broadband single-station co-horizontally polarized full-duplex antenna based on the integrated beam forming network is characterized in that the second output end of the 90-degree hybrid coupler is grounded through being connected with a 50-ohm load.
The broadband single-station co-horizontal polarization full-duplex antenna based on the integrated beam forming network is characterized in that a microstrip line network of the beam forming network circuit is arranged at the bottom layer of a circuit substrate, and a first antenna port and a second antenna port of the first inverse hybrid coupler and a first antenna port and a second antenna port of the second inverse hybrid coupler are arranged at the top layer of the circuit substrate;
the top layer of the circuit substrate is arranged opposite to the bottom layer of the antenna substrate.
The broadband single-station common-horizontal-polarization full-duplex antenna based on the integrated beam forming network is characterized in that a first antenna port of the first backward hybrid coupler is connected with a microstrip line corresponding to the first antenna unit through a coaxial cable, and a second antenna port of the first backward hybrid coupler is connected with a microstrip line corresponding to the third antenna unit through a coaxial cable;
and a first antenna port of the second inverse hybrid coupler is connected with a microstrip line corresponding to the second antenna unit through a coaxial cable, and a second antenna port of the second inverse hybrid coupler is connected with a microstrip line corresponding to the fourth antenna unit through a coaxial cable.
The embodiment of the invention provides a broadband single-station common horizontal polarization full-duplex antenna based on an integrated beam forming network, which comprises a receiving and transmitting antenna and a beam forming network circuit simultaneously; the beam forming network circuit comprises a power divider, a 90-degree hybrid coupler, a first backward hybrid coupler and a second backward hybrid coupler, and the transceiving antenna comprises a first antenna unit, a second antenna unit, a third antenna unit and a fourth antenna unit, wherein the power divider is connected with a signal input port, the first backward hybrid coupler and the second backward hybrid coupler, the 90-degree hybrid coupler is connected with a signal output end, the first backward hybrid coupler and the second backward hybrid coupler, the first antenna unit and the third antenna unit are both connected with the first backward hybrid coupler, and the second antenna unit and the fourth antenna unit are both connected with the second backward hybrid coupler. The broadband single-station common-horizontal-polarization full-duplex antenna can realize high isolation between transmitting and receiving ports, can realize omnidirectional coverage, improves impedance bandwidth, reduces gain fluctuation of a horizontal plane, and greatly improves communication quality.
Drawings
In order to more clearly illustrate the technical solutions of the embodiments of the present invention, the drawings needed to be used in the description of the embodiments are briefly introduced below, and it is obvious that the drawings in the following description are some embodiments of the present invention, and it is obvious for those skilled in the art to obtain other drawings based on these drawings without creative efforts.
Fig. 1 is an overall circuit structure diagram of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 2 is a partial schematic structural diagram of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 3 is a partial schematic structural diagram of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 4 is a partial schematic structural diagram of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 5 is a partial perspective structural view of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 6 is a partial perspective structural view of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 7 is a partial perspective structural view of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 8 is a partial perspective structural view of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 9 is a partial schematic structural diagram of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 10 is a partial schematic structural diagram of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 11 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 12 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 13 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 14 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 15 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 16 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 17 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 18 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 19 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 20 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 21 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 22 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 23 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 24 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention;
fig. 25 is a schematic diagram illustrating an effect of a broadband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network according to an embodiment of the present invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are some, not all, embodiments of the present invention. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
It will be understood that the terms "comprises" and/or "comprising," when used in this specification and the appended claims, specify the presence of stated features, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and/or groups thereof.
It is also to be understood that the terminology used in the description of the invention herein is for the purpose of describing particular embodiments only and is not intended to be limiting of the invention. As used in the specification of the present invention and the appended claims, the singular forms "a," "an," and "the" are intended to include the plural forms as well, unless the context clearly indicates otherwise.
It should be further understood that the term "and/or" as used in this specification and the appended claims refers to and includes any and all possible combinations of one or more of the associated listed items.
Referring to fig. 1 to 10, a wideband single-station co-horizontally polarized full-duplex antenna based on an integrated beam forming network is shown, which includes a simultaneous transmitting and receiving antenna 20 and a beam forming network circuit 10. The beam forming network circuit 10 comprises a power divider 11, a 90 ° hybrid coupler 12, a first inverse hybrid coupler 13 and a second inverse hybrid coupler 14; the power divider 11 is connected to a signal input port, the first inverse hybrid coupler 13 and the second inverse hybrid coupler 14, and is configured to divide a transmission signal input from the signal input terminal TX to the first inverse hybrid coupler 13 and the second inverse hybrid coupler 14; the 90 ° hybrid coupler 12 is connected to a signal output terminal, the first inverse hybrid coupler 13 and the second inverse hybrid coupler 14, and configured to receive the received signals from the first inverse hybrid coupler 13 and the second inverse hybrid coupler 14 and output the received signals through the signal output terminal.
The broadband single-station co-horizontally polarized full-duplex antenna based on the integrated beam forming network is a simultaneous transmit and receive (STAR) antenna, and the first and second inverse hybrid couplers 13 and 14 are 180-degree hybrid couplers. The specific signal transmission mode is as shown in fig. 1, the light-colored thin lines represent signal transmission streams corresponding to transmission signals, and the light-colored thin lines represent signal transmission streams corresponding to reception signals, and in the transmission mode, the four antenna ports of the antenna are excited in a constant-amplitude and equal-phase manner. In receive mode, the four antenna ports of the STAR antenna are excited with equal amplitude and 90 ° phase rotation (i.e., 0 °, -90 °, -180 °, and-270 °), infinite transmit/receive isolation, i.e., high isolation between transmit and receive ports, can be achieved due to the modal orthogonality of the transmit and receive modes.
The simultaneous transmitting and receiving antenna 20 includes a first antenna unit 21, a second antenna unit 22, a third antenna unit 23 and a fourth antenna unit 24; the first backward hybrid coupler 13 is connected to the first antenna unit 21 and the third antenna unit 23 at the same time, and is configured to receive and transmit signals of the first antenna unit 21 and the third antenna unit 23 at the same time; the second backward hybrid coupler 14 is connected to the second antenna unit 22 and the fourth antenna unit 24 at the same time, and is configured to receive and transmit signals of the second antenna unit 22 and the fourth antenna unit 24 at the same time.
More specifically, the first antenna unit 21, the second antenna unit 22, the third antenna unit 23, and the fourth antenna unit 24 are all disposed on an antenna substrate 25, and the first antenna unit 21 and the third antenna unit 23 are arranged in a central symmetry manner, and the second antenna unit 22 and the fourth antenna unit 24 are arranged in a central symmetry manner.
In a more specific embodiment, each of the first antenna unit 21, the second antenna unit 22, the third antenna unit 23, and the fourth antenna unit 24 is composed of a printed dipole 211, a first parasitic strip 212, and a second parasitic strip 213, and the first parasitic strip 212 and the second parasitic strip 213 are respectively disposed at the side of the printed dipole 211 and are not connected to the printed dipole 211. Specifically, a circular floor 251 is arranged on the bottom layer of the antenna substrate 25; the printed dipole 211 and the first parasitic strip 212 are arranged in a common circle and all surround the outer side of the circular floor 251; the second parasitic strip 213 is disposed around the outside of the printed dipole 211; specifically, the antenna substrate 25 is a circular substrate, and the printed dipole 211, the first parasitic strip 212 and the second parasitic strip 213 are all arc-shaped; one arm of each printed dipole 211 is connected to a corresponding one of microstrip lines 27 in the top layer of the antenna substrate 25 by parallel lines 26, and the other arm is printed on the bottom layer of the antenna substrate 25 and connected to the circular ground plate 251 by parallel strip lines 28.
As shown in fig. 5 and 6, in an implementation process, the simultaneous transmitting and receiving antenna 20 may be composed of four arc-shaped printed dipoles 211, four arc-shaped first parasitic strips 212, four arc-shaped second parasitic strips 213, and a circular ground plate 251, where the four printed dipoles 211 form a circular antenna array printed on two sides of the circular antenna substrate 25. The four arc-shaped printed dipoles 211 are equal in size, the four arc-shaped first parasitic strips 212 are equal in size, and the four arc-shaped second parasitic strips 213 are equal in size.
Specifically, as shown in fig. 2 and 3, the simultaneous transmitting and receiving antenna 20 includes a first antenna unit 21, a second antenna unit 22, a third antenna unit 23, and a fourth antenna unit 24, each of which includes a printed dipole 211, a first parasitic strip 212, and a second parasitic strip 213. The antenna substrate 25 is composed of a bottom layer and a top layer, fig. 2 is a top layer structure diagram, fig. 3 is a bottom layer structure diagram, both dark regions in fig. 2 and fig. 3 are front-visible structures, and both light regions are back-surface structures (front surface is not visible), then one arm of the printed dipole 211, the first parasitic strip 212 and the second parasitic strip 213 are all disposed on the top layer of the antenna substrate 25, the other arm of the printed dipole 211 and the circular floor 251 are disposed on the bottom layer of the antenna substrate 25, that is, each printed dipole 211 includes two arms, and then one arm disposed on the bottom layer of the antenna substrate 25 is combined with the other arm disposed on the top layer of the antenna substrate 25 to form one printed dipole 211. Meanwhile, the bottom layer of the antenna substrate 25 is further provided with four connectors 252 penetrating through the circular floor 251, and the four connectors 252 are respectively connected with one microstrip line 27 of a corresponding antenna unit, wherein the connectors 252 may be SMA connectors.
Radius R of circular floor 251 for generation of horizontally polarized omnidirectional radiation pattern for STAR antennagIs critical, whether the STAR antenna is operating in a transmit or receive mode, RgSmaller generally better omnidirectional radiation (smaller azimuthal gain fluctuations). As shown in fig. 2 to 4, the size of the antenna substrate 25 is selected to be pi × 40 in the present embodiment2mm2That is to say RsFour widths w equal to 40mmcAs a balanced-unbalanced (balun) structure to feed and match the printed dipole 211. One arm of each printed dipole 211 is connected to a microstrip line 27 of 50 omega resistance on the top layer, the other arm being printed on the bottom layer and connected to a circular floor 251 by means of parallel strip lines 28. Considering that enough space needs to be reserved for installing four connectors 252 on the circular floor 251 in practical manufacturing, we select R in the designgHas a size of R s1/3-3/4, R is selected in this embodimentg20mm, i.e. R is selectedgHas a size of R s1/2 of (1). In the present embodiment, a Rogers 4350B substrate is selected as the antenna substrate 25, and the thickness h of the antenna substrate 25s0.76mm, a relative dielectric constant εr3.66, a loss tangent of 0.0037,an SMA connector is selected as the joint 252. In this embodiment, the other dimensional parameters in fig. 2 to 4 are in turn: l1＝11.6mm,l2＝12.2mm,l3＝16mm,lf＝7mm,w1＝3mm,w2＝1mm,w3＝2mm,wc＝0.8mm,wf＝1.65mm,R1＝R2＝R3＝25mm。
When the STAR antenna described above is operating in the transmit mode, a loop antenna is formed by the four first parasitic strips 212 and the four arc-shaped printed dipoles 211. The gap between the first parasitic strip 212 and one arm of the printed dipole 211 disposed on the top layer of the antenna substrate 25 and the gap between the other arm disposed on the bottom layer of the antenna substrate 25 have a periodic loading capacitance that compensates for the phase lag of the current so that the current distribution on the loop is in phase and uniform. Analyzing the omnidirectional radiation mechanism of the STAR antenna from the current distribution point of view, the circumference of the current loop of the antenna is about 4.2 lambdag (lambdag is the guided wave wavelength of 5.3 GHz) in the 5.3GHz transmission mode, and the current along the loop still flows clockwise synchronously and is approximately uniform. Thus, a horizontal omnidirectional radiation pattern can be achieved in the transmit mode, which also follows the design strategy of conventional horizontally polarized omnidirectional antennas. When the antenna is operated in a receiving mode, the loop of the current at 5.3GHz has two current zeros, so that the radiation pattern on the azimuth plane has two notches. However, due to the 90 ° linear phase increment of the reception mode, a horizontally polarized omnidirectional radiation pattern can also be realized in the azimuth plane, which behaves like a classical pole-wound antenna (Turnstile antenna). Width (w) of first parasitic strip 21221mm), width (w) of second parasitic strip 21332mm) of the width (w) of the printed dipole 21113mm) in order to balance the effect on antenna performance in transmit and receive modes.
In order to achieve the function of simultaneous single-station transceiving, the STAR antenna proposed in this embodiment needs to have an approximate impedance bandwidth and good omnidirectional radiation capability in the transmitting and receiving modes, and in order to obtain better omnidirectional radiation, we design the first parasitic band 212 and the second parasitic band 213 to improve the impedance bandwidth and reduce the gain fluctuation of the omnidirectional radiation in the horizontal plane. We studied the STAR antenna in this implementation using the active reflection coefficient, which can be expressed by equation (1):
Figure BDA0003231746670000091
in the formula, SnnAnd SnmIs a passive S parameter of a four-port STAR antenna, amAnd anThe amplitude and phase of the stimulated signal at the mth antenna port and the nth antenna port. Since the STAR antenna is rotationally symmetric, only the 1 st antenna port (active S) needs to be calculated11 N 1, m 2, 3 or 4) active reflection coefficient Snn,active。
The obtained calculation results are shown in fig. 11. Example 1 is the case where only four printed dipoles 211 are excited, the transmit mode (TX mode) and receive mode (RX mode) producing resonances of 5.1GHz and 5.25GHz, respectively, resulting in TX/RX overlapping impedance bandwidths (IMBW) (active S11Less than or equal to-10 dB) of 4.79 to 5.66GHz (bandwidth of 0.87GHz, accounting for 16.65%). Example 2 is the case when four printed dipoles 211 and a second parasitic strip 213 are excited, the resonance of the TX and RX modes shifts to a high frequency around 5.5GHz, and the overlapping impedance bandwidth (IMBW) is about 4.91-5.95GHz (bandwidth 1.04GHz, percentage 19.15%). Example 3 is the case when four printed dipoles 211 and a first parasitic strip 212 are excited, with the resonance of the TX and RX modes shifted to 4.69GHz and 5GHz, respectively, and the overlapping IMBW of 4.61-5.42GHz (bandwidth 0.81GHz, 16.15%). Example 4, i.e., the case of simultaneously exciting four printed dipoles 211, a first parasitic strip 212, and a second parasitic strip 213, both TX and RX modes generate two distinct resonances at about 5GHz and 5.7GHz, resulting in an overlap IMBW of TX/RX between 4.56-6 GHz of 27.27%. It can be seen that the resonance of the STAR antenna in this embodiment is a combination of example 2 and example 3 for TX or RX modes.
The gain fluctuation of the overlapping IMBW in the four exemplary TX/RX modes in the range of 4.5-6GHz is analyzed, and the analysis result is shown in fig. 12, where the gain fluctuation in the azimuth plane (x-y plane) is used to represent the omni-directionality of the antenna. For example 1, the gain fluctuation in TX mode was 4.2-5.97dB and in RX mode was 0.78-5.45 dB. For example 2, with the introduction of the second parasitic band 213, the gain fluctuation of TX is reduced to 0.62-4.11dB and the gain fluctuation of RX is reduced to 2.48-6.54 dB. For example 3, when only the first parasitic band 212 is introduced, the gain fluctuation for TX increases with increasing frequency, ranging from 3.85-8.36dB, and the gain fluctuation for RX ranges from 3-4.52 dB. In the present embodiment, the gain fluctuation of TX and RX is reduced to 0.79-3.19dB and 2.35-3.5dB, respectively, after the first parasitic strip 212 and the second parasitic strip 213 are introduced simultaneously. Therefore, it can be seen that the slight gain fluctuation of the antenna of the present embodiment in TX and RX modes is generated by the combined influence of the first parasitic strip 212 and the second parasitic strip 213.
An ideal beam forming network circuit formed by four ideal circuit elements (a power divider, a 90-degree hybrid coupler and two 180-degree hybrid couplers) is built in ADS simulation software, then S parameter results obtained by calculation of the STAR antenna of the embodiment are led into the ADS simulation software for sensitivity analysis, and the 180-degree hybrid coupler is subjected to sensitivity analysis (phase and amplitude imbalance of two output ports of the 180-degree hybrid coupler are set as two variables, the phase imbalance of the two output ports of the 180-degree hybrid coupler is changed from 0-degree to 2-degree in the whole frequency band, and the amplitude imbalance is changed from 0-0.3 dB), and the obtained analysis results are shown in FIG. 13, and as can be seen from the graph, in the 4.5-6GHz frequency band, the worst receiving and transmitting isolation is larger than 40 dB. For comparison, fig. 13 also shows the transmit-receive isolation of an ideal beamforming network circuit (without imbalance), which is over 96dB across the entire frequency band.
In a more specific embodiment, the input terminal (TX port shown in the drawing) of the power divider 11 is connected to the signal input port, a first output terminal thereof is connected to the input terminal of the first inverse hybrid coupler 13, and a second output terminal thereof is connected to the input terminal of the second inverse hybrid coupler 14; the 90 ° hybrid coupler 12 has a first output (RX port shown in the drawing) connected to the signal output, a first input connected to the output of the first inverse hybrid coupler 13, and a second input connected to the output of the second inverse hybrid coupler 14.
In a more specific embodiment, the first antenna port P of the first backward hybrid coupler 131A second antenna port P connected to one microstrip line 27 corresponding to the printed dipole 211 of the first antenna element 213One microstrip line 27 corresponding to the printed dipole 211 of the third antenna unit 23; first antenna port P of the second inverse hybrid coupler 142A second antenna port P connected to one microstrip line 27 corresponding to the printed dipole 211 of the second antenna unit 224And one microstrip line 27 corresponding to the printed dipole 211 of the fourth antenna element 24. Wherein the second output terminal of the 90 ° hybrid coupler 12 is terminated by a 50 ohm load RloadAnd (4) grounding.
In a more specific embodiment, the microstrip network of the beam-forming network circuit 10 is disposed on the bottom layer of the circuit substrate 15, and the first antenna port P of the first inverse hybrid coupler 131A second antenna port P3And a first antenna port P of said second backward hybrid coupler 142A second antenna port P4Are all arranged on the top layer of the circuit substrate 15; the top layer of the circuit substrate 15 is disposed opposite the bottom layer of the antenna substrate 25. Wherein the first antenna port P of the first backward hybrid coupler 131 A microstrip line 27 corresponding to the first antenna unit 21 and a second antenna port P thereof are connected by a coaxial cable 163 A microstrip line 27 corresponding to the third antenna unit 23 is connected through a coaxial cable 16; first antenna port P of the second inverse hybrid coupler 142 A microstrip line 27 corresponding to the second antenna unit 22 and a second antenna port P thereof are connected by a coaxial cable 164One microstrip line 27 corresponding to the fourth antenna unit 24 is connected by the coaxial cable 16. Four ports P are respectively connected by coaxial cables 161、P2、P3、P4And the microstrip lines corresponding to the four antenna units are connected, so that the construction and the assembly of the whole system are completed.
The first and second backward hybrid couplers 13 and 14 in this embodiment are both two-stage 180-degree ring hybrid (rat-race) couplers, and the specific structure is shown in fig. 7 and 9, which mainly consists of three vertical microstrip lines and four horizontal microstrip lines (λ g is 5.5GHz waveguide wavelength), where the length L of the three vertical microstrip lines is Lz1＝λg/2, length L of four horizontal microstrip linesz2＝Lz4＝λgA characteristic impedance of each of the microstrip lines is Z0＝50Ω，Z1＝60Ω，Z2＝75.7Ω，Z3＝35.1Ω，Z4＝53.7Ω，Z5＝Z669.4 Ω. In FIG. 9, r1The input signal of the port is equally divided into r2And r4Two output signals of the port have a phase difference of 180 DEG and r3The ports are isolated.
For r in FIG. 91、r2、r3And r4The reflection coefficients of the four ports are analyzed, and the analysis results are shown in fig. 14, fig. 15 and fig. 16, wherein the reflection coefficients of the ports in the range of 4.5-6.5 GHz shown in fig. 14 are all smaller than-15 dB. S shown in FIG. 14r1-r3I.e. in the 4.69-6.6GHz band, r1And r3The isolation of the simulation ports between the ports is between-50 dB and-30 dB, and the amplitudes of the two output ports are unbalanced at 4-6.83 GHz (S)r1-r2And Sr1-r4Difference) is less than 0.3 dB. The two output ports shown in FIG. 15 have 180 DEG phase imbalance (S) at 4.61-6.5 GHzr1-r2And Sr1The difference in r4 phase) is less than 2 °. All results show that the proposed 180 ° hybrid coupler has good use effect and is a good choice for beamforming network circuit design.
With the proposed 180 ° hybrid coupler, a beam forming network circuit including two or more 180 ° hybrid couplers, a 90 ° hybrid coupler and a wilkinson power divider is designed, and the specific structure is shown in fig. 10. The beam forming network circuit is a six-port (ports TX, RX, P)1、P2、P3And P4) Network, two ports for TX and RX, fourOne port is used to feed a four-port STAR antenna, and when the TX port is excited, the TX signal is split into 4 equal-amplitude equal-phase (TX mode) port signals (Port P)1、P2、P3And P4Separately transmitted signals). When the RX ports are excited, the signals of the four ports have equal amplitudes and are sequentially 90 ° out of phase (RX mode). The microstrip line network of the beam-forming network circuit is disposed on a circuit substrate 15, which may be a Rogers 4350B substrate, having a thickness of 0.76mm, a relative permittivity of 3.66, and a loss tangent of 0.0037. The dimensional parameters in fig. 9 and 10 are, in order: l isH1＝7.72mm,LH2＝6.38mm,LZ2＝LZ4＝6.7mm,LZ3＝16.25mm,LZ5＝LZ6＝7.2mm,LP1＝5.05mm,LP2＝1mm,W0＝1.65mm,WH1＝1.65mm,WH2＝2.6mm,WZ1＝1.2mm,WZ2＝0.75mm,WZ3＝1.45mm,WZ4＝0.9mm,WZ5＝2.8mm,WP2＝1.08mm。
Actual measurement results obtained by actually testing the beam forming network circuit manufactured based on the above dimensions are shown in fig. 17, 18, 19, and 20. The reflection coefficient test of the beam forming network circuit in this embodiment is performed from the frequency of 4.64GHz to 6.33GHz, and the obtained result is as shown in fig. 17, and six sets of reflection coefficients measured in fig. 17 (S11 is port P)1To port P1And so on) are all less than-10 dB. The test result of the phase difference test in the RX mode is shown in FIG. 18, port P1And port P3The phase imbalance is controlled within 2 degrees in a frequency band of 4.64-6.5 GHz, and a port P2And port P4The phase imbalance of the phase difference is controlled within 2 degrees in the frequency band of 4.71-6.6 GHz. RX ports respectively associated with ports P1Port P2Port P3Port P4The corresponding transmission coefficients are shown in fig. 19, with a maximum amplitude imbalance of 2dB in the range of 4.56-6.35 GHz. The phase imbalance measured at the four ports in TX mode is 2 degrees in the range of 4.7-6.56 GHz, and the amplitude imbalance is 0.2dB in the range of 4.2-7 GHz, which is not shown in FIGS. 18 and 19 for simplicity. Measurement of beamforming networksTrial transmit and receive port isolation as shown in fig. 20, the port isolation from 4.78 to 6.48GHz in the curve of fig. 20 is less than-40 dB, which indicates that if the actual STAR antenna is symmetric, well matched, and perfectly connected to the beam forming network, a 40dB transmit and receive isolation can be achieved within 4.78-6.48GHz of bandwidth.
The reflection coefficients of the TX and RX ports subjected to the simulation and the actual test of the STAR antenna of the present embodiment are shown in fig. 21. The impedance bandwidth (reflection coefficient ≦ -10dB) measured by the TX port is 4.41-6.2GHz, the impedance bandwidth measured by the RX port is 4.71-6.29GHz, and therefore the overlapped impedance bandwidth measured by the TX/RX port is 4.71-6.2GHz (1.49GHz, 27.3%). The simulation and test transmit-receive isolation is shown in fig. 22. It can be seen from the figure that the simulated transmit-receive isolation bandwidth has good consistency with the measured transmit-receive isolation bandwidth above 30dB, which is 4.41-6.67GHz (2.26GHz, 40.8%) and 4.5-6.77GHz (2.27GHz, 40.3%), respectively. The simulation result shows that the isolation is above 40dB from 4.86 to 6.43GHz (1.57GHz, 27.8%), and the peak value is 57.1dB at 5.81 GHz. In practical tests, the 40dB receiving and transmitting isolation bandwidth is about 4.81-5.88GHz (1.07GHz, 20%), the peak value is 63.5dB at 5.16GHz, and external environment interference factors may exist in the practical test process. Since the 40-dB transmit-receive isolation bandwidth is in the-10 dB overlap impedance bandwidth range, the STAR antenna proposed herein has been found to operate at 4.81-5.88GHz (1.07GHz, 20%) which is sufficient to cover the 5GHz WLAN band (5.15-5.85 GHz).
The radiation pattern and gain of the STAR antenna in this example were tested using a spherical near-field system (saimo SG 24). When the TX port is tested, the RX port terminates a 50- Ω load, and vice versa. The STAR antenna shown in fig. 23 simulates and tests a two-dimensional radiation pattern at frequencies of 4.8GHz, 5.3GHz, and 5.8GHz in the TX mode, fig. 23(a) is a two-dimensional radiation pattern at the above three operating frequencies in the azimuth plane (x-y), and fig. 23(b) is a two-dimensional radiation pattern at the above three operating frequencies in the elevation plane (x-z). As can be seen from fig. 23, the TX mode of this antenna exhibits good electrically small loop-like antenna radiation characteristics throughout the operating band, with two axial nulls deep in the elevation plane and a horizontally polarized omnidirectional radiation pattern in the azimuth plane. At the frequency points of 4.8GHz, 5.3GHz and 5.8GHz, the simulated gain fluctuation of the azimuth plane is less than 2.9dB, 2.1dB and 2.2dB, and the measured values are respectively less than 3.9dB, 3.1dB and 3.1 dB.
Fig. 24 shows simulated and tested two-dimensional radiation patterns of the STAR antenna in RX mode for azimuth (x-y) and elevation (x-z) planes of 4.8GHz, 5.3GHz, and 5.8GHz, respectively, fig. 24(a) is a two-dimensional radiation pattern for azimuth (x-y) plane at three operating frequencies, and fig. 23(b) is a two-dimensional radiation pattern for elevation (x-z) plane at three operating frequencies. As can be seen from fig. 24(a), the omnidirectional radiation with good horizontal polarization on the azimuth plane has the simulated gain fluctuation smaller than 3.4dB, 2dB and 2.5dB at the frequency points of 4.8GHz, 5.3GHz and 5.8GHz, and the measured values are respectively smaller than 2.8dB, 3.7dB and 4.7 dB.
The simulated and tested antenna gain of the STAR antenna in azimuth plane of the embodiment of the present scheme is shown in fig. 25. And in the working frequency band of 4.81-5.88GHz, the actual measurement gain of TX is about-1.07-1.84 dBi, and the actual measurement gain of RX is about 0.31-1.68 dBi. The average total efficiency of the test for the entire STAR antenna subsystem TX and RX is about 72% and 67%, respectively, at the operating frequency band.
The broadband single-station common horizontal polarization full-duplex antenna based on the integrated beam forming network comprises a receiving and transmitting antenna and a beam forming network circuit simultaneously; the beam forming network circuit comprises a power divider, a 90-degree hybrid coupler, a first backward hybrid coupler and a second backward hybrid coupler, and the transceiving antenna comprises a first antenna unit, a second antenna unit, a third antenna unit and a fourth antenna unit, wherein the power divider is connected with a signal input port, the first backward hybrid coupler and the second backward hybrid coupler, the 90-degree hybrid coupler is connected with a signal output end, the first backward hybrid coupler and the second backward hybrid coupler, the first antenna unit and the third antenna unit are both connected with the first backward hybrid coupler, and the second antenna unit and the fourth antenna unit are both connected with the second backward hybrid coupler. The broadband single-station common-horizontal-polarization full-duplex antenna can realize high isolation between transmitting and receiving ports, can realize omnidirectional coverage, improves impedance bandwidth, reduces gain fluctuation of a horizontal plane, and greatly improves communication quality.
While the invention has been described with reference to specific embodiments, the invention is not limited thereto, and various equivalent modifications and substitutions can be easily made by those skilled in the art within the technical scope of the invention. Therefore, the protection scope of the present invention shall be subject to the protection scope of the claims.

Claims (10)

1. A broadband single-station common horizontal polarization full-duplex antenna based on an integrated beam forming network is characterized by comprising a simultaneous receiving and transmitting antenna and a beam forming network circuit;
the beamforming network circuit comprises a power divider, a 90-degree hybrid coupler, a first inverse hybrid coupler and a second inverse hybrid coupler;
the power divider is connected with a signal input port, the first inverse hybrid coupler and the second inverse hybrid coupler and used for dividing a transmitting signal input by the signal input port to the first inverse hybrid coupler and the second inverse hybrid coupler;
the 90-degree hybrid coupler is connected with a signal output end, the first inverse hybrid coupler and the second inverse hybrid coupler, and is used for receiving the receiving signals from the first inverse hybrid coupler and the second inverse hybrid coupler and outputting the receiving signals through the signal output end;
the simultaneous transceiving antenna comprises a first antenna unit, a second antenna unit, a third antenna unit and a fourth antenna unit;
the first backward hybrid coupler is connected with the first antenna unit and the third antenna unit at the same time and is used for receiving and transmitting signals of the first antenna unit and the third antenna unit at the same time; the second inverse hybrid coupler is connected to the second antenna unit and the fourth antenna unit at the same time, and is configured to receive and transmit signals of the second antenna unit and the fourth antenna unit at the same time.
2. The integrated beamforming network based broadband single-station co-horizontally polarized full-duplex antenna according to claim 1, wherein the first antenna unit, the second antenna unit, the third antenna unit and the fourth antenna unit are all disposed on an antenna substrate, and the first antenna unit and the third antenna unit are arranged in a central symmetry manner, and the second antenna unit and the fourth antenna unit are arranged in a central symmetry manner.
3. The integrated beamforming network based wideband single-station co-horizontally polarized full-duplex antenna according to claim 2, wherein the first antenna unit, the second antenna unit, the third antenna unit, and the fourth antenna unit are each composed of a printed dipole, a first parasitic strip, and a second parasitic strip, and the first parasitic strip and the second parasitic strip are respectively disposed at the sides of the printed dipole and are not connected to the printed dipole.
4. The integrated beamforming network based broadband single-station co-horizontally polarized full-duplex antenna according to claim 3, wherein the bottom layer of the antenna substrate is provided with a circular floor;
the printed dipole and the first parasitic strip are arranged in a common circle and surround the outer side of the circular floor; the second parasitic band is arranged around the outer side of the printed dipole.
5. The integrated beamforming network based broadband single-station co-horizontally polarized full-duplex antenna according to claim 4, wherein the antenna substrate is a circular substrate, and the printed dipole, the first parasitic strip and the second parasitic strip are all arc-shaped;
one arm of each printed dipole is connected with a corresponding microstrip line in the top layer of the antenna substrate through a parallel line, and the other arm of each printed dipole is printed on the bottom layer of the antenna substrate and is connected with the circular floor through a parallel strip line.
6. The integrated beamforming network based wideband single-station co-horizontally polarized full-duplex antenna according to claim 5, wherein the input of the power divider is connected to the signal input port, the first output thereof is connected to the input of the first backward hybrid coupler, and the second output thereof is connected to the input of the second backward hybrid coupler;
the first output end of the 90-degree hybrid coupler is connected with the signal output end, the first input end of the 90-degree hybrid coupler is connected with the output end of the first inverse hybrid coupler, and the second input end of the 90-degree hybrid coupler is connected with the output end of the second inverse hybrid coupler.
7. The integrated beamforming network based broadband single-station co-horizontally polarized full-duplex antenna according to claim 6, wherein a first antenna port of the first hybrid backward coupler is connected to one microstrip corresponding to the printed dipole of the first antenna element, and a second antenna port of the first hybrid backward coupler is connected to one microstrip corresponding to the printed dipole of the third antenna element;
and a first antenna port of the second inverse hybrid coupler is connected with a microstrip line corresponding to the printed dipole of the second antenna unit, and a second antenna port of the second inverse hybrid coupler is connected with a microstrip line corresponding to the printed dipole of the fourth antenna unit.
8. The integrated beamforming network based wideband single station co-horizontally polarized full-duplex antenna according to claim 7, wherein the second output terminal of the 90 ° hybrid coupler is grounded by being terminated by a 50 ohm load.
9. The integrated beamforming network based wideband single-station co-horizontally polarized full-duplex antenna according to claim 7, wherein the microstrip network of the beamforming network circuit is disposed on a bottom layer of a circuit substrate, and the first and second antenna ports of the first and second inverse hybrid couplers are disposed on a top layer of the circuit substrate;
the top layer of the circuit substrate is arranged opposite to the bottom layer of the antenna substrate.
10. The integrated beamforming network based broadband single-station co-horizontally polarized full-duplex antenna according to claim 9, wherein a first antenna port of the first backward hybrid coupler is connected to a microstrip line corresponding to the first antenna unit through a coaxial cable, and a second antenna port of the first backward hybrid coupler is connected to a microstrip line corresponding to the third antenna unit through a coaxial cable;
and a first antenna port of the second inverse hybrid coupler is connected with a microstrip line corresponding to the second antenna unit through a coaxial cable, and a second antenna port of the second inverse hybrid coupler is connected with a microstrip line corresponding to the fourth antenna unit through a coaxial cable.
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