CN113659914B - Drive circuit for high-speed switched reluctance motor and control method thereof - Google Patents

Drive circuit for high-speed switched reluctance motor and control method thereof Download PDF

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Publication number
CN113659914B
CN113659914B CN202110978825.0A CN202110978825A CN113659914B CN 113659914 B CN113659914 B CN 113659914B CN 202110978825 A CN202110978825 A CN 202110978825A CN 113659914 B CN113659914 B CN 113659914B
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bridge arm
switching tube
diode
motor
voltage
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CN113659914A (en
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洪伟泷
张桂东
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Guangdong University of Technology
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Guangdong University of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/08—Reluctance motors
    • H02P25/092—Converters specially adapted for controlling reluctance motors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H02M7/53875—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with analogue control of three-phase output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/16—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the circuit arrangement or by the kind of wiring
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation

Abstract

The invention discloses a drive circuit for a high-speed switched reluctance motor and a control method thereof, wherein the drive circuit comprises the following steps: the direct current power supply and the N-phase winding of the switched reluctance motor, wherein N is a natural number and is more than or equal to 3, and the switch converter consists of an inductor, two capacitors, N +3 switch tubes and N +3 diodes and a control method thereof; when the motor runs at a low speed or a high speed, the capacitor energy stored in the instantaneous power module is released, the low-voltage or high-voltage demagnetization modes are respectively switched, the average demagnetization voltage is adjusted, the rotating speed range is widened, the torque ripple is reduced, and the capacity and the volume of the power capacitor are greatly reduced. Meanwhile, the invention combines PI control to form a multivariable coupling control method for output current, input power and motor rotating speed, compensates instantaneous power ripples of a direct current power supply generated by equal nonlinear factors of output power and motor switching, widens the voltage selection range of the direct current power supply and obviously improves the performance of a switched reluctance motor driving system.

Description

Drive circuit for high-speed switched reluctance motor and control method thereof
Technical Field
The invention relates to a power conversion device for excitation and demagnetization of a switched reluctance motor and a control method thereof, in particular to a small-capacitance multi-level power conversion device based on a multiplexing technology and a control method thereof.
Background
In a new energy automobile system, a switched reluctance motor becomes an important member in the development industry of an electric automobile driving system by virtue of the advantages of simple and reliable motor structure, low manufacturing cost, large starting torque, high fault tolerance, flexible control and the like.
The power converter plays a role in transmitting and distributing power supply energy in a switched reluctance motor driving system, and the driving performance of a motor driving topology influences the running performance of the whole motor. As shown in fig. 1, the asymmetric half-bridge inverter is a typical example applied to a conventional switched reluctance motor driving system because of its simple and reliable structure and control method, and it satisfies that the switched reluctance motors are independent of each other between different phases in the control process, and its control method is simple and reliable, so it is widely used. However, the number of semiconductor devices required by each phase winding of the asymmetric half-bridge converter applied to the switched reluctance motor is large, and a large-capacity electrolytic capacitor needs to be connected in parallel to an input end to absorb power ripples generated by the motor, so that the cost and the volume of the system are increased. Furthermore, the direct current bus voltage on the asymmetric half-bridge converter structure cannot be adjusted, and the rotating speed and torque range of the switched reluctance motor are limited. Therefore, how to provide a solution to the above technical problems is a problem that researchers in this field need to solve. Researchers continuously optimize and improve the power converter on the basis of the asymmetric half-bridge converter, and at present, the power converter topology is mainly researched in the aspects of reducing cost, reducing volume, improving performance and the like.
Aiming at the problems of an asymmetric half-bridge converter, the invention provides a power converter with small capacitance and multiple levels and a control method thereof on the basis of the asymmetric half-bridge converter, and the power converter adjusts average demagnetizing voltage by changing a working mode or duty ratio, thereby widening the rotating speed range and reducing torque ripple; the selection range of the direct-current power supply voltage is widened through a power flow control method, the multiplexing technology is structurally combined, the number of semiconductor devices required by the converter is reduced, and the performance of a switched reluctance motor driving system is remarkably improved.
Disclosure of Invention
The invention aims to increase the output level of a motor driving topology, widen the rotating speed range of a switched reluctance motor, reduce the torque ripple generated by the operation of the motor, structurally reduce the capacitance value and the volume of an electrolytic capacitor required by the topology, reduce the number of semiconductor devices required in the application scene of a multi-phase motor and improve the performance of a switched reluctance motor driving system. The other purpose of the invention is to provide a control method of the power converter, which compensates the output power of the direct current power supply, and performs multivariable coupling control on the output current and the input power while converting the instantaneous power ripple generated by equal nonlinear factors of the motor.
The technical scheme of the device provided by the invention is as follows:
a small capacitance multilevel power converter for a high speed switched reluctance machine, comprising: the circuit comprises a direct-current power supply, a filter inductor, an instantaneous power module 101, a shared bridge arm 102, a first bridge arm 103, a second bridge arm 104, a third bridge arm 105, an Nth bridge arm 10X and a switched reluctance motor N-phase winding, wherein N is a natural number and is more than or equal to 3; x is N + 2.
The DC power supply VinThe positive pole of the filter inductor L is connected with the positive pole of the filter inductor L, and the direct current power supply VinAnd the switching tube S of the common bridge arm 1022Is connected to the source of (a); negative pole of filter inductor L and switching tube S sharing bridge arm 1021Source electrode, S2Is connected to the drain of (1). The filter inductor has the functions of keeping the input current of the direct current power supply continuous and reducing current ripple.
The instantaneous power module 101 comprises a switch tube, three diodes and two capacitors, wherein the switch tube S3Is connected to the second capacitor C2Positive electrode of (2) and switching tube S in common bridge arm 1021Of the drain electrode, the switching tube S3Is connected with the first capacitor C1Positive electrode of (2), first diode D1And a second diode D2A cathode of (a); a first capacitor C1The negative electrode of the DC power supply is simultaneously connected with the voltage V of the DC power supplyinAnd a third diode D3The anode of (1); second capacitor C2Is simultaneously connected with a second diode D2And a third diode D3A cathode of (a); first diode D1Anode and common bridge arm 102 switching tube S1Source electrode, S2Is connected to the drain of (1).
The common bridge arm 102 is composed of a switch tube S1And a switching tube S2Series connection of switching tubes S1Source electrode and switch tube S2Is connected to the drain of (1).
The first bridge arm 103 is composed of a diode D4And a switching tube S4Are connected in series, wherein the diode D4And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D4Anode and switch tube S4Is connected to the drain of the switching tube S4Source of and switching tube S in common bridge arm 1022Is connected to the source of (a).
The second leg 104 is formed by a diode D5And a switching tube S5Are connected in series, wherein the diode D5And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D5Anode and switch tube S5Is connected to the drain of the switching tube S5Source of and switching tube S in common bridge arm 1022Is connected to the source of (a).
Third leg 105 is formed by diode D6And a switching tube S6Are connected in series, wherein the diode D6And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D6Anode and switch tube S6Is connected to the drain of the switching tube S6Source of and switching tube S in common bridge arm 1022Is connected to the source of (a).
The Nth bridge arm 10X is composed of a diode DN+3And a switching tube SN+3Are connected in series, wherein the diode DN+3And a switching tube S in the common bridge arm 1021Is connected to the drain of diode DN+3Anode and switch tube SN+3Is connected to the drain of the switching tube SN+3Source of and switching tube S in common bridge arm 1022Is connected to the source of (a).
The N-phase winding of the switched reluctance motor is at least a three-phase winding, and the positive pole of each phase of motor winding is connected with the switching tube S of the common bridge arm 1021Source electrode, S2Is connected with the drain electrode of the transistor; negative pole A of A phase motor winding-And a switch tube S in the first bridge arm 1034Drain electrode connection point of (1), diode D4The anode connecting points are connected; negative pole B of B-phase motor winding-And a switch tube S in the second bridge arm 1045Drain electrode connection point of (1), diode D5The anode connecting points are connected; negative pole C of C-phase motor winding-And a switch tube S in the third bridge arm 1056Drain electrode connection point of (1), diode D6Is connected to the negative pole N of the … … N-phase motor winding-And a switching tube S in the Nth bridge arm 10XN+3Drain electrode connection point of (1), diode DN+3Are connected, and the asymmetric half-bridge circuit formed by each motor winding is arranged in parallel at both ends of the common bridge arm 102.
The technical scheme of the control method of the invention is as follows:
a power flow control method for a small-capacitance multi-level power converter driven by a high-speed switched reluctance motor specifically comprises the following steps: a topological state variable control loop 201, a motor position variable control loop 202 and a motor speed variable control loop 203.
The topology state variable control loop 201 comprises a capacitance voltage control loop and an inductance current control loop, wherein the capacitance voltage control loop is used as an external control loop, and firstly, a voltage sensor is selected from a first capacitor C in the instantaneous power module 1011Detected capacitor voltage vcapAnd a capacitor voltage set reference value Vcap_refComparing, transmitting the obtained comparison result to a PI controller, and taking the output value of the PI controller as an inductive current reference value iL_refTransmitted to the input end of the current control loop; in the internal inductive current control loop, firstly, the inductive current reference value iL_refAnd the inductance current value i detected by the current sensor from the filter inductance LLComparing, using the obtained comparison result as the input value of PI regulator, using the output of PI regulator as the input of PWM signal generator, and using the comparison result with sawtooth wave as the switch tube S1、S2The PWM signal generator takes the value of the duty ratio D to the switching tube S1，S2The driving signals are output to control their turn-on and turn-off.
The motor position variable control loop 202 is characterized by: the external control loop is a rotating speed control loop, and a rotating speed set value n is firstly set_ref1Comparing with the actual rotating speed value n detected by the motor position sensor, and using the comparison result as the input of the PI regulator, and using the output of the PI regulator as the reference value i of the motor phase currentY_refThe internal control loop is a phase current control loop, and the current hysteresis comparison is carried outThe device obtains phase current detection values i of current sensors from each phase winding of the switched reluctance motorYWith reference value of motor phase current iY_refComparing the signals and using the processed signal as the switch tube S of the power converter4、S5、S6…SN+3Turn on and off the driving signal; wherein Y is a, B, C, …, N.
The motor speed variable control loop 203 is characterized in that: firstly, a rotating speed set value n is set_ref2And the actual rotating speed value n detected by the motor rotating speed sensor is used as the input of a rotating speed comparator, and the signal processed by the rotating speed comparator is used as a power converter switch tube S3Turn on and off the driving signal; when the actual rotating speed value n of the switched reluctance motor is lower than the rotating speed set value n_ref2The rotation speed comparator outputs a signal to enable the switch tube S3The power converter is in and keeps in a conducting state, and the power converter works in a low-voltage demagnetization mode; if the motor running speed n exceeds the set value n of the rotating speed_ref2Then the rotation speed comparator outputs a signal to make the switch tube S3In and remains in an off state with the power converter operating in a high voltage demagnetization mode.
Compared with the technical scheme of the traditional asymmetric half-bridge converter, the technical scheme of the invention has the following advantages:
(1) the instantaneous power module 101 absorbing and supplying power and the power supply are separated from each other, so the power supply end is not affected by the voltage ripple of the capacitor;
(2) for the capacitors in the instantaneous power module 101, higher than the supply voltage and larger ripple voltage can be allowed, in which case capacitors with smaller capacity and volume can be chosen;
(3) the filter inductor L can filter the direct current power supply current, so that electrolytic capacitors do not need to be connected in parallel at two ends of a power supply, and in addition, the selection range of the direct current power supply voltage is wider and is allowed to be lower than the rated voltage of the switched reluctance motor;
(4) the DC bus voltage has adjustability. The higher demagnetization voltage is applied to the winding, so that the phase current reduction time is shortened, the generation of negative torque is inhibited, the rotating speed range of constant torque is widened, and the application of the switched reluctance motor in high-speed operation is facilitated;
(5) when the phase number of the driven switched reluctance motor is N, the traditional asymmetric half-bridge converter needs 2N switching tubes and 2N diodes, and the power converter provided by the invention only needs N +3 switching tubes, N +3 diodes, 2 capacitors and 1 inductor, so that the cost and the volume can be effectively reduced, the power density is improved, and the reliability of the power converter is further improved.
Drawings
In order to more clearly illustrate the technical solution in the embodiments of the present invention, the drawings used in the prior art and the embodiments will be briefly described below.
Fig. 1 is an operation schematic diagram of an N-phase switched reluctance motor of a conventional asymmetric half-bridge converter.
Fig. 2 is a topological diagram of a small-capacitance multi-level N-phase power converter and a power flow control method thereof according to the present invention.
Fig. 3 is a topological diagram of a small-capacitance multi-level three-phase power converter and a power flow control method thereof according to the present invention.
Fig. 4 is a mode 1 equivalent circuit diagram of a low-voltage demagnetization mode of the small-capacitance multi-level three-phase power converter provided by the invention.
Fig. 5 is a mode 2 equivalent circuit diagram of a low-voltage demagnetization mode of the small-capacitance multi-level three-phase power converter provided by the invention.
Fig. 6 is a mode 3 equivalent circuit diagram of a low-voltage demagnetization mode of the small-capacitance multi-level three-phase power converter provided by the invention.
Fig. 7 is a mode 4 equivalent circuit diagram of a low-voltage demagnetization mode of the small-capacitance multi-level three-phase power converter provided by the invention.
Fig. 8 is a mode 5 equivalent circuit diagram of a low-voltage demagnetization mode of the small-capacitance multi-level three-phase power converter provided by the invention.
Fig. 9 is a mode 6 equivalent circuit diagram of a low-voltage demagnetization mode of the small-capacitance multi-level three-phase power converter provided by the invention.
Fig. 10 is a modal 6 equivalent circuit diagram of the high-voltage demagnetization mode of the small-capacitance multi-level three-phase power converter provided by the invention.
Fig. 11 is a voltage waveform diagram of a phase winding of a small-capacitance multi-level three-phase power converter provided by the invention in two working modes.
Fig. 12 is a phase current waveform diagram of a conventional asymmetric half-bridge inverter when the switched reluctance motor is operating at a low speed.
Fig. 13 is a phase current waveform diagram of a small-capacitance multi-level three-phase power converter in a high-voltage demagnetization mode according to the present invention.
Fig. 14 is a diagram of dynamic phase current waveforms of a small-capacitance multi-level three-phase power converter provided by the invention when a switched reluctance motor operates at a low speed.
Fig. 15 is a dynamic rotation speed waveform diagram of the small-capacitance multi-level three-phase power converter provided by the invention when the switched reluctance motor operates at a low speed.
Fig. 16 is a phase current waveform diagram of the small-capacitance multi-level three-phase power converter and the asymmetric half-bridge converter provided by the invention when the switched reluctance motor runs at a low speed respectively.
Fig. 17 is a waveform diagram of the low-capacitance multi-level three-phase power converter provided by the invention in a low-voltage demagnetization mode when the switched reluctance motor operates at a high speed.
Fig. 18 is a waveform diagram of the small-capacitance multi-level three-phase power converter provided by the invention in a high-voltage demagnetization mode when the switched reluctance motor operates at a high speed.
Fig. 19 is a phase current waveform diagram of an asymmetric half-bridge inverter during high speed operation of a switched reluctance motor.
Detailed Description
The invention will be further described with reference to examples in the drawings.
The small-capacitance multi-level power converter of the present invention is shown in fig. 2, and includes: the direct-current power supply, the filter inductor, the shared bridge arm 102, the first bridge arm 103, the second bridge arm 104, the third bridge arm 105, the N-phase winding of the switched reluctance motor and the instantaneous power module 101.
In fig. 2 to 19, reference symbols respectively represent: vinIs a direct current power supply and is a main power supply for the work of the motor; l is a filter inductor; s1、S2、S3、S4、S5、S6…SN+3Showing a switching tube with an anti-parallel diode; d1、D2、D3、D4、D5、D6…DN+3Represents a diode; c1、C2Respectively representing a first capacitance and a second capacitance in the instantaneous power module 101; a. the+、B+、C+…N+Respectively, A, B, C … N phase winding positive pole of the switched reluctance motor, and correspondingly, A-、B-、C-…N-Respectively representing A, B, C … N phase winding cathodes of the switched reluctance motor; d represents the duty cycle of the converter; v. ofcapRepresenting a first capacitance C1The detection voltage of (1); vcap_refRepresenting a first capacitance C1Setting a reference value for the capacitor voltage; i.e. iLAn inductance current detection value representing the filter inductance L; i.e. iL_refAn inductor current reference value representing the filter inductance L; n represents the dynamic rotation speed of the motor; n is_ref1、n_ref2Representing a set value of the rotating speed of the motor; Δ ton、ΔtoffRespectively representing the rising time and the falling time of each phase current; i.e. iA、iB、iCRespectively representing the working currents of the three-phase windings; i.e. iinRepresenting an input current of the converter; fA、FB、FCRepresenting the magnetic flux of the three-phase winding when the switched reluctance motor operates; t represents an instantaneous torque; Δ T represents the torque ripple peak to peak value.
The DC power supply VinThe positive pole of the filter inductor L is connected with the positive pole of the filter inductor L, and the direct current power supply VinAnd the switching tube S of the common bridge arm 1022Is connected to the source of (a); negative pole of filter inductor L and switching tube S sharing bridge arm 1021Source electrode, S2Is connected to the drain of (1). The filter inductor has the functions of keeping the input current of the direct current power supply continuous and reducing current ripple.
The instantaneous power module 101 comprises a switch tube, three diodes and two capacitors, wherein the switch tube is connected with the three diodesPipe S3Is connected to the second capacitor C2Positive electrode of (2) and switching tube S in common bridge arm 1021Of the drain electrode, the switching tube S3Is connected with the first capacitor C1Positive electrode of (2), first diode D1And a second diode D2A cathode of (a); a first capacitor C1The negative electrode of the DC power supply is simultaneously connected with the voltage V of the DC power supplyinAnd a third diode D3The anode of (1); second capacitor C2Is simultaneously connected with a second diode D2And a third diode D3A cathode of (a); first diode D1Anode and common bridge arm 102 switching tube S1Source electrode, S2Is connected to the drain of (1).
The instantaneous power module 101 can provide demagnetizing voltages with different levels according to the rotating speed of the motor so as to meet the requirement; when the switched reluctance motor operates at a low speed, the instantaneous power module 101 provides a demagnetization voltage with a lower level, so that the switching loss of a semiconductor device can be reduced; when the switched reluctance motor operates at a high speed, the instantaneous power module 101 can provide a high level demagnetization voltage to rapidly reduce the phase current, so as to prevent the tail current from appearing in a winding inductance reduction area to generate negative torque and reduce effective torque.
The common bridge arm 102 is composed of a switch tube S1And a switching tube S2Are connected in series. Switch tube S1Source electrode and switch tube S2Is connected to the drain of (1).
The first bridge arm 103 is composed of a diode D4And a switching tube S4Are connected in series, wherein the diode D4And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D4Anode and switch tube S4Is connected to the drain of the switching tube S4Source of and switching tube S in common bridge arm 1022Is connected to the source of (a).
The second leg 104 is formed by a diode D5And a switching tube S5Are connected in series, wherein the diode D5And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D5Anode and switch tube S5Is connected to the drain electrode ofClosing pipe S5Source of and switching tube S in common bridge arm 1022Is connected to the source of (a).
Third leg 105 is formed by diode D6And a switching tube S6Are connected in series, wherein the diode D6And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D6Anode and switch tube S6Is connected to the drain of the switching tube S6Source of and switching tube S in common bridge arm 1022Is connected to the source of (a).
The Nth bridge arm 10X is composed of a diode DN+3And a switching tube SN+3Are connected in series, wherein the diode DN+3And a switching tube S in the common bridge arm 1021Is connected to the drain of diode DN+3Anode and switch tube SN+3Is connected to the drain of the switching tube SN+3Source of and switching tube S in common bridge arm 1022Is connected to the source of (a).
The N-phase winding of the switched reluctance motor is at least a three-phase winding, and the positive pole of each phase of motor winding is connected with the switching tube S of the common bridge arm 1021Source electrode, S2Is connected with the drain electrode of the transistor; negative pole A of A phase motor winding-And a switch tube S in the first bridge arm 1034Drain electrode connection point of (1), diode D4The anode connecting points are connected; negative pole B of B-phase motor winding-And a switch tube S in the second bridge arm 1045Drain electrode connection point of (1), diode D5The anode connecting points are connected; negative pole C of C-phase motor winding-And a switch tube S in the third bridge arm 1056Drain electrode connection point of (1), diode D6Is connected to the negative pole N of the … … N-phase motor winding-And a switching tube S in the Nth bridge arm 10XN+3Drain electrode connection point of (1), diode DN+3Are connected, and the asymmetric half-bridge circuit formed by each motor winding is arranged in parallel at both ends of the common bridge arm 102.
As shown in fig. 2, the power flow control method specifically includes: a topological state variable control loop 201, a motor position variable control loop 202 and a motor speed variable control loop 203.
The topology state variable control loop201 includes a capacitance voltage control loop as an external control loop and an inductor current control loop, first removing the voltage sensor from the first capacitance C in the instantaneous power module 1011Detected capacitor voltage vcapAnd a capacitor voltage set reference value Vcap_refComparing, transmitting the obtained comparison result to a PI controller, and taking the output value of the PI controller as an inductive current reference value iL_refTransmitted to the input end of the current control loop; in the internal inductive current control loop, firstly, the inductive current reference value iL_refAnd the inductance current value i detected by the current sensor from the filter inductance LLComparing, using the obtained comparison result as the input value of PI regulator, using the output of PI regulator as the input of PWM signal generator, and using the comparison result with sawtooth wave as the switch tube S1、S2The PWM signal generator takes the value of the duty ratio D to the switching tube S1，S2The driving signals are output to control their turn-on and turn-off.
It should be noted here that the switching tube S is ideally switched on and off1And S2Is complementary to each other, and in practice it takes a certain time for the switching tube S to switch on and off, although for a short time, when the switching tube S is switched off1And S2When the driving signals are completely complementary, there is still a risk that one of the switching tubes is in a state of not completely turning off and the other switching tube is in a state of turning on, which may cause the first capacitor C1And a second capacitor C2Is short-circuited and the switching tube S1And S2The switching tube is damaged by the transient current which flows through a large peak value, so that a certain dead time is required to avoid the occurrence of the through condition.
The motor position variable control loop 202 is characterized by: the external control loop is a rotating speed control loop, and a rotating speed set value n is firstly set_ref1Comparing with the actual rotating speed value n detected by the motor position sensor, and using the comparison result as the input of the PI regulator, and using the output of the PI regulator as the reference value i of the motor phase currentY_refInternal controlThe loop is a phase current control loop, and a current hysteresis comparator obtains phase current detection values i from each phase winding of the switched reluctance motor by a current sensorYWith reference value of motor phase current iY_refComparing the signals and using the processed signal as the switch tube S of the power converter4、S5、S6…SN+3Turn on and off the driving signal; wherein Y is a, B, C, …, N.
The motor speed variable control loop 203 is characterized in that: firstly, a rotating speed set value n is set_ref2And the actual rotating speed value n detected by the motor rotating speed sensor is used as the input of a rotating speed comparator, and the signal processed by the rotating speed comparator is used as a power converter switch tube S3Turn on and off the driving signal; when the actual rotating speed value n of the switched reluctance motor is lower than the rotating speed set value n_ref2The rotation speed comparator outputs a signal to enable the switch tube S3The power converter is in and keeps in a conducting state, and the power converter works in a low-voltage demagnetization mode; if the motor running speed n exceeds the set value n of the rotating speed_ref2Then the rotation speed comparator outputs a signal to make the switch tube S3In and remains in an off state with the power converter operating in a high voltage demagnetization mode.
It should be noted that, unlike the conventional asymmetric half-bridge converter, the small-capacitance multilevel power converter in the embodiment of the present application may be divided into two operation modes, i.e., a low-voltage demagnetization mode and a high-voltage demagnetization mode, according to the operating speed of the switched reluctance motor.
In particular, in the present specification, a small-capacitance multi-level three-phase power converter is taken as an example for explanation, and is specifically shown in fig. 3.
Considering that the operating states of each phase winding in one operating cycle are the same, taking phase a as an example, the following is to analyze one operating cycle in two operating modes, specifically refer to fig. 4, fig. 5, fig. 6, fig. 7, fig. 8, fig. 9 and fig. 10, where fig. 4 to fig. 9 are equivalent circuit diagrams of the circuit when the switched reluctance motor operates at a low speed, and fig. 10 is an equivalent circuit diagram of the circuit when the switched reluctance motor operates at a high speed; the dotted line portion in the figure is a non-working portion, and may be regarded as not present. The operation of the small capacitance multilevel power converter is described below with reference to the structure of the converter provided in this application:
when the power converter provided by the invention works in a low-voltage demagnetization mode, the switch tube S3It is necessary to maintain the on state. When working in high-voltage demagnetizing mode, the switch tube S3The off state needs to be maintained.
1) Specifically, when the circuit operates in mode 1 of the low voltage demagnetization mode, as shown in fig. 4, the switching tube S is now on2，S4Conducting, switching tube S1And (6) turning off. The voltage drop of the two ends of the filter inductor L is the input power voltage VinCurrent i of inductor LLGradually rising. Meanwhile, the external voltage at two ends of the A-phase winding of the switched reluctance motor is zero and passes through a switching tube S2，S4Freewheeling is performed but the winding current continues to decrease during this process due to the presence of back emf.
2) When the circuit operates in mode 2 of the low voltage demagnetization mode, as shown in fig. 5, the switching tube S is now on1，S4Conducting, switching tube S2And (6) turning off. In this case, the filter inductor L current i is satisfied at the same timeLGreater than phase winding current iAVoltage V across the phase windingAEqual to the capacitor voltage
Figure GDA0003550489640000091
The A-phase winding current is gradually increased, and the A-phase winding is in an excitation state. DC power supply pass diode D1For the first capacitor C1Charging is carried out, and the rest energy of the power supply is charged by the first capacitor C1Absorption, so that the voltage drop across the filter inductance L is equal to
Figure GDA0003550489640000092
The inductor current continues to decrease.
3) When the circuit operates in mode 3 of the low voltage demagnetization mode, as shown in fig. 6, the switching tube S is now on1，S4Conducting, switching tube S2Is turned off and satisfies the L current i of the filter inductorLLess than phase winding current iAIn the case of a condition where the power supply is unable to supply sufficient energy to the phase winding, the power supply and the instantaneous power module are required to supply energy to the phase winding simultaneously, which can be classified as
Figure GDA0003550489640000093
And
Figure GDA0003550489640000094
two states are considered. When in use
Figure GDA0003550489640000095
Then, the equivalent circuit is as shown in FIG. 6, and only the first capacitor C is used1And a power supply for supplying the current required by phase A, a first capacitor C1The voltage at both ends passes through a switch tube S1、S3，S4Is applied to the A-phase winding, so that the voltage V is applied across the A-phase windingAEqual to the capacitor voltage
Figure GDA0003550489640000096
The voltage across the filter inductance L remains equal to
Figure GDA0003550489640000097
So that the inductor current iLThe decrease continues.
4) When the circuit operates in mode 4 of the low voltage demagnetization mode, as shown in fig. 7, the switching tube S is now on1，S4Conducting, switching tube S2And the on and off states of the switching tube are the same as the working state III. But different from the working state III, the first capacitor C is arranged at the moment1And a second capacitor C2The voltages at both ends being equal, i.e.
Figure GDA0003550489640000098
At this time, the first capacitor C1、C2Providing instantaneous power required by A phase winding with power supply, voltage V across A phase windingAIs equal to
Figure GDA0003550489640000099
Across the filter inductance LThe voltage is still equal to
Figure GDA00035504896400000910
So that the inductor current iLThe decrease continues.
5) When the circuit operates in mode 5 of the low voltage demagnetization mode, as shown in fig. 8, the switching tube S is now on1Conducting, switching tube S2，S4And (6) turning off. The power supply passes through the diode D only4For the first capacitor C1And charging is carried out. The voltage across the filter inductor is
Figure GDA0003550489640000101
So that the inductor current iLGradually decreases. At the same time, the A phase winding passes through the switch tube S1And a diode D4Freewheeling is performed so that the external voltage drop across the winding is zero, but the phase winding current i is zero due to the presence of back emfAGradually decreases.
6) When the circuit operates in mode 6 of the low voltage demagnetization mode, as shown in fig. 9, the switching tube S is now on2Conducting, switching tube S1，S4And (6) turning off. The voltage drop at both ends of the filter inductor is input power voltage VinThus the inductor current iLGradually increasing. Due to the switch tube S3In the conducting state, the A-phase winding passes through a loop diode D4And a switching tube S2、S3And a first capacitor C1Follow current when the voltage across the winding is
Figure GDA0003550489640000102
So that the winding current iARapidly reducing the first capacitance C entering a demagnetization mode1The voltage across the terminals increases slightly.
7) When the circuit is operating in mode 6 of the high voltage demagnetization mode, as shown in fig. 10, the switching tube S is now on and off2Conducting, switching tube S1，S3，S4The turn-off phase winding is in the high-voltage demagnetization period, which is the same as mode 6 of the low-voltage demagnetization mode, and the voltage drop across the filter inductor is the input supply voltage VinSo that the inductor current iLGradually increasing. Different therefromDue to the switch tube S3Can be turned off only by the diode D2，D4Switch tube S2And a first capacitor C1A second capacitor C2Follow current is carried out, in which the phase winding is subjected to a voltage drop of
Figure GDA0003550489640000103
So that the phase winding current iARapidly reducing the first capacitor C entering a high voltage demagnetization mode1A second capacitor C2The pressure drop across increases slightly. It should be noted that, in the high-voltage demagnetization mode, only the operating state six is different from the low-voltage demagnetization mode, and the rest of the operating states are the same as the low-voltage demagnetization mode, so the details are not described here.
Taking phase a as an example, the equivalent circuits during excitation and demagnetization when the proposed converter operates in the low-voltage demagnetization mode are shown in fig. 4, 5 and 8, 9, respectively. During excitation, the filter inductance L and the winding inductance L can be derived from fig. 4 and 5minThe equation of state of (c):
Figure GDA0003550489640000104
wherein iL、iACurrent of L and A phase windings of filter inductor, D is switch S2The duty cycle of the pulse-width modulation signal,
Figure GDA0003550489640000105
is a first capacitor C1The voltage across the terminals. The expression of the A-phase winding current in the excitation stage can be derived through the formula:
Figure GDA0003550489640000106
obviously, it can be found by comparison that the phase current rise value of the power converter proposed by the present invention is the same with the asymmetric half-bridge converter under the condition of the same excitation time. The demagnetization equivalent model in the low-voltage demagnetization mode is shown in fig. 8 and 9, and the state equation of the filter inductance and the winding inductance can be expressed as follows:
Figure GDA0003550489640000111
also, the phase current expression during this period can be derived from the above equation:
Figure GDA0003550489640000112
according to the formula, the power converter provided by the invention works in a low-voltage demagnetization mode, and the demagnetization time of the winding is shorter than that of the asymmetric half-bridge converter only when the duty ratio D is larger than 0.5.
In combination with the above analysis it has been shown that under the same conditions the rise time required for the phase current to reach the set value when the proposed converter is operated in the low voltage demagnetization mode is the same compared to an asymmetric half bridge converter. The fall time of the phase current depends on the magnitude of the duty cycle D, which in the first case is<0.5, the demagnetization time of the proposed converter will be larger than for an asymmetric half-bridge converter; in the second case the duty cycle D is 0.5, the demagnetization time of the proposed converter will be the same as for an asymmetric half bridge converter; in the third case with a duty cycle D > 0.5, the demagnetization time of the proposed converter will be smaller than for an asymmetric half-bridge converter. And when the switched reluctance motor is in a high-voltage demagnetization mode, the working state and the rising time of phase current during excitation are the same as those in a low-voltage demagnetization mode. During demagnetization of the winding, its corresponding simplified circuit model is shown in fig. 10. Similarly, the filter inductance L and the winding inductance L can be derivedminThe equation of state of (a) is:
Figure GDA0003550489640000113
after simplification, the expression of the phase A winding current in the high-voltage demagnetization mode can be obtained as follows:
Figure GDA0003550489640000114
when the duty ratio D of the switching tubes is the same, the reduction rate of the current of the phase winding in the high-voltage demagnetization mode is twice that in the low-voltage demagnetization mode, so that the time required for reducing the current to zero in the high-voltage demagnetization mode is only half that in the low-voltage demagnetization mode, which is very favorable for reducing tail current, widening the constant-torque rotating speed range and improving the running efficiency of the motor. The winding voltages in the two modes of operation are shown in fig. 11, and comparison shows that the excitation voltages in the two modes of operation are the same, while the demagnetization voltage in the high-voltage demagnetization mode is twice that in the low-voltage demagnetization mode. On the other hand, compared with the asymmetric half-bridge converter, in the high-voltage demagnetization mode, the demagnetization time of the winding is smaller than that of the asymmetric half-bridge converter only when the duty ratio D is larger than 0.33.
The average exciting voltage and average demagnetizing voltage provided by the asymmetric half-bridge converter are fixed and equal to the input power voltage Vin. The average excitation voltage provided by the power converter is the same as that of the asymmetric half-bridge converter, but the average demagnetization voltage can be adjusted, and when a certain condition is met (the duty ratio D is required to be more than 0.5 when the power converter works in a low-voltage demagnetization mode, and the duty ratio D is required to be more than 0.33 when the power converter works in a high-voltage demagnetization mode), the average demagnetization voltage is larger than that of the asymmetric half-bridge converter.
For verification, a simulation circuit of the circuit shown in fig. 3 may be built, where the simulation parameters are specifically set as follows:
Figure GDA0003550489640000121
under the low-speed running condition that the rotating speed of the switched reluctance motor is 1000r/min and the load torque is 80 N.m, a power flow control method is adopted. A simulation of the asymmetric half-bridge converter in this operating condition is shown in fig. 12, and a simulation of waveforms of the proposed power converter operating in the high-voltage demagnetization mode is shown in fig. 13: the phase current fall time in the high voltage demagnetization mode is 289.3 mus, and the phase current fall time when an asymmetric half bridge converter is applied is 892.7 mus. The fall time of the winding phase current in the high voltage demagnetization mode is significantly less than when using an asymmetric half bridge converter.
Fig. 14 shows simulation results of the proposed power converter under dynamic performance tests. The motor starting running speed is set to 1000r/min and the load torque is set to 40N · m. The motor reaches the rated rotation speed and is in steady-state operation in a period of time before the time t is 3s, the load torque of the motor is instantaneously increased from 40N · m to 80N · m when the time t is 3s, and the phase current and the rotation speed of the motor are changed, wherein the phase current is gradually increased from 29A to 45A, and the corresponding change process is shown in fig. 14. Fig. 15 shows a motor speed change process, and it can be seen that the speed starts to drop at time t 2s, and after 236ms has elapsed, the speed reaches 1000r/min again.
Fig. 16(a) and (b) show the input current waveforms of the asymmetric half-bridge converter and the power converter proposed by the present invention, respectively, and it can be seen that the asymmetric half-bridge converter has a large low-frequency current ripple and the peak-to-peak value thereof reaches 56A. In contrast, since the power converter proposed by the present invention has a filter inductance and adopts a power flow control method, the amplitude of the low-order harmonic of the input current is smaller, and the peak-to-peak value is only 14A. In the aspect of current harmonic amplitude of higher frequency, the values of the proposed power converter are all lower than those of an asymmetric half-bridge converter, and the effects of effectively prolonging the service life of a power supply, filtering and the like can be realized.
Fig. 17 to 19 are simulation results of the power converter and the asymmetric half-bridge converter proposed by the present invention under high-speed operation of the switched reluctance motor, respectively. At high motor speeds, the winding current waveforms of the asymmetric half-bridge converter and the proposed power converter operating in the low voltage demagnetization mode are severely distorted with large tail currents, as shown in fig. 17 and 19. The increase in average torque and rotational speed is severely affected. Compared with the prior art, the average demagnetization voltage of the power converter provided by the invention is obviously improved when the power converter works in a high-voltage demagnetization mode, the phase current can be quickly established and reduced, and the simulation result is shown in fig. 18, so that the rotating speed range is widened and the torque ripple is reduced under the condition of no change of load torque. Under the same conditions, the maximum rotating speed of the asymmetric half-bridge converter can only reach 6700r/min, while the rotating speed of the converter provided by the invention can reach 7200r/min when the converter works in a high-voltage demagnetization mode. In addition, when the motor runs at high speed, the peak-to-peak torque ripple values of the asymmetric half-bridge converter and the power converter provided by the invention are respectively 20.6N-m and 21.8N-m when the power converter works in the low-voltage demagnetization mode, and the peak-to-peak torque ripple value of the power converter works in the high-voltage demagnetization mode is only 17.8N-m, which is reduced by 15% compared with the asymmetric half-bridge converter. The proposed power converter is applied to electric vehicles and other equipment, and is smoother when running at high speed compared with the traditional power converter.
As a preferred embodiment, the switching tube S1、S2、S3、S4、S5、S6Are all NMOS tubes.
As a preferred embodiment, the switching tube S1、S2、S3、S4、S5、S6Are all IGBT tubes.
In addition, the switching tube S here1、S2、S3、S4、S5、S6Other types of switch tubes can be selected, and the application is not particularly limited and is determined according to the actual situation.
It is to be noted that, in the present specification, relational terms such as first and second, and the like are used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
The above description is only a preferred embodiment of the present invention, and is not intended to limit the present invention, and all simple modifications, changes and equivalent structural changes made to the above embodiment according to the technical spirit of the present invention still fall within the protection scope of the technical solution of the present invention.

Claims (4)

1. A small capacitance multilevel power converter for a high speed switched reluctance machine, characterized by: the system comprises a direct-current power supply, a filter inductor, an instantaneous power module 101, a shared bridge arm 102, a first bridge arm 103, a second bridge arm 104, a third bridge arm 105, an Nth bridge arm 10X and a switched reluctance motor N-phase winding; wherein N is a natural number and is more than or equal to 3; x is N + 2;
the DC power supply VinThe positive pole of the filter inductor L is connected with the positive pole of the filter inductor L, and the direct current power supply VinAnd the switching tube S of the common bridge arm 1022Is connected to the source of (a); negative pole of filter inductor L and switching tube S sharing bridge arm 1021Source electrode, S2Is connected with the drain electrode of the transistor;
the instantaneous power module 101 comprises a switch tube, three diodes and two capacitors, wherein the switch tube S3Is connected to the second capacitor C2Positive electrode of (2) and switching tube S in common bridge arm 1021Of the drain electrode, the switching tube S3Is connected with the first capacitor C1Positive electrode of (2), first diode D1And a second diode D2A cathode of (a); a first capacitor C1The negative electrode of the DC power supply is simultaneously connected with the voltage V of the DC power supplyinAnd a third diode D3The anode of (1); second capacitor C2Is simultaneously connected with a second diode D2And a third diode D3A cathode of (a); first diode D1Anode and common bridge arm 102 switching tube S1Source electrode, S2Is connected with the drain electrode of the transistor;
the common bridge arm 102 is composed of a switch tube S1And a switching tube S2Series connection of switching tubes S1Source electrode and switch tube S2Is connected with the drain electrode of the transistor;
the first bridge arm 103 is composed of a diode D4And a switching tube S4Are connected in series, wherein the diode D4And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D4Anode and switch tube S4Is connected to the drain of the switching tube S4Source of and switching tube S in common bridge arm 1022Is connected to the source of (a);
the second leg 104 is formed by a diode D5And a switching tube S5Are connected in series, wherein the diode D5And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D5Anode and switch tube S5Is connected to the drain of the switching tube S5Source of and switching tube S in common bridge arm 1022Is connected to the source of (a);
third leg 105 is formed by diode D6And a switching tube S6Are connected in series, wherein the diode D6And a switching tube S in the common bridge arm 1021Is connected to the drain of diode D6Anode and switch tube S6Is connected to the drain of the switching tube S6Source of and switching tube S in common bridge arm 1022Is connected to the source of (a);
the Nth bridge arm 10X is composed of a diode DN+3And a switching tube SN+3Are connected in series, wherein the diode DN+3And a switching tube S in the common bridge arm 1021Is connected to the drain of diode DN+3Anode and switch tube SN+3Is connected to the drain of the switching tube SN+3Source of and switching tube S in common bridge arm 1022Is connected to the source of (a);
the N-phase winding of the switched reluctance motor is at least a three-phase winding, and the positive pole of each phase of motor winding is connected with the switching tube S of the common bridge arm 1021Source electrode, S2Is connected with the drain electrode of the transistor; negative pole A of A phase motor winding-And a switch tube S in the first bridge arm 1034Drain electrode connection point ofPolar tube D4The anode connecting points are connected; negative pole B of B-phase motor winding-And a switch tube S in the second bridge arm 1045Drain electrode connection point of (1), diode D5The anode connecting points are connected; negative pole C of C-phase motor winding-And a switch tube S in the third bridge arm 1056Drain electrode connection point of (1), diode D6Is connected to the negative pole N of the … … N-phase motor winding-And a switching tube S in the Nth bridge arm 10XN+3Drain electrode connection point of (1), diode DN+3Are connected, and the asymmetric half-bridge circuit formed by each motor winding is arranged in parallel at both ends of the common bridge arm 102.
2. The method for controlling the small-capacitance multi-level power conversion circuit driven by the high-speed switched reluctance motor according to claim 1 specifically comprises: a topological state variable control loop 201, a motor position variable control loop 202 and a motor rotating speed variable control loop 203;
the topology state variable control loop 201 comprises a capacitance voltage control loop and an inductance current control loop, wherein the capacitance voltage control loop is used as an external control loop, and firstly, a voltage sensor is selected from a first capacitor C in the instantaneous power module 1011Detected capacitor voltage vcapAnd a capacitor voltage set reference value Vcap_refComparing, transmitting the obtained comparison result to a PI controller, and taking the output value of the PI controller as an inductive current reference value iL_refTransmitted to the input end of the current control loop; in the internal inductive current control loop, firstly, the inductive current reference value iL_refAnd the inductance current value i detected by the current sensor from the filter inductance LLComparing, using the obtained comparison result as the input value of PI regulator, using the output of PI regulator as the input of PWM signal generator, and using the comparison result with sawtooth wave as the switch tube S1、S2The PWM signal generator takes the value of the duty ratio D to the switching tube S1，S2Outputting driving signals to control the on and off of the driving signals;
of said motor position variable control loop 202Is characterized in that: the external control loop is a rotating speed control loop, and a rotating speed set value n is firstly set_ref1Comparing with the actual rotating speed value n detected by the motor position sensor, and using the comparison result as the input of the PI regulator, and using the output of the PI regulator as the reference value i of the motor phase currentY_refThe internal control loop is a phase current control loop, and the current hysteresis comparator obtains phase current detection values i from each phase winding of the switched reluctance motor by the current sensorYWith reference value of motor phase current iY_refComparing the signals and using the processed signal as the switch tube S of the power converter4、S5、S6…SN+3Turn on and off the driving signal; wherein Y is a, B, C, …, N;
the motor speed variable control loop 203 is characterized in that: firstly, a rotating speed set value n is set_ref2And the actual rotating speed value n detected by the motor rotating speed sensor is used as the input of a rotating speed comparator, and the signal processed by the rotating speed comparator is used as a power converter switch tube S3Turn on and off the driving signal; when the actual rotating speed value n of the switched reluctance motor is lower than the rotating speed set value n_ref2The rotation speed comparator outputs a signal to enable the switch tube S3The power converter is in and keeps in a conducting state, and the power converter works in a low-voltage demagnetization mode; if the motor running speed n exceeds the set value n of the rotating speed_ref2Then the rotation speed comparator outputs a signal to make the switch tube S3In and remains in an off state with the power converter operating in a high voltage demagnetization mode.
3. The small capacitance multi-level power converter according to claim 1, wherein: the switch tube is provided with a diode in parallel; the switch tube is an IGBT tube; or the switch tube is an NMOS tube.
4. Small-capacitance multilevel power converter according to claim 1, characterized in that the switching tubes S in the common bridge leg 1021And a switching tube S2Are complementary, are not on simultaneously, and require dead time to be set.
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