CN113489666A - Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment - Google Patents

Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment Download PDF

Info

Publication number
CN113489666A
CN113489666A CN202111046326.4A CN202111046326A CN113489666A CN 113489666 A CN113489666 A CN 113489666A CN 202111046326 A CN202111046326 A CN 202111046326A CN 113489666 A CN113489666 A CN 113489666A
Authority
CN
China
Prior art keywords
signal
bfdm
otfs
matrix
amplitude limiting
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN202111046326.4A
Other languages
Chinese (zh)
Other versions
CN113489666B (en
Inventor
王亮
冯宇
祝涛
别志松
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Zhejiang Shannon Communication Technology Co ltd
Original Assignee
Zhejiang Shannon Communication Technology Co ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Zhejiang Shannon Communication Technology Co ltd filed Critical Zhejiang Shannon Communication Technology Co ltd
Publication of CN113489666A publication Critical patent/CN113489666A/en
Application granted granted Critical
Publication of CN113489666B publication Critical patent/CN113489666B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2614—Peak power aspects
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2626—Arrangements specific to the transmitter only
    • H04L27/2627—Modulators
    • H04L27/264—Pulse-shaped multi-carrier, i.e. not using rectangular window
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2681—Details of algorithms characterised by constraints
    • H04L27/2688—Resistance to perturbation, e.g. noise, interference or fading

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Noise Elimination (AREA)

Abstract

The invention provides a method and a system for eliminating amplitude limiting noise based on peak-to-average ratio inhibition and electronic equipment. According to the method, the peak-to-average ratio of the OTFS-BFDM signal is suppressed by using an amplitude limiting and filtering method at a sending end, amplitude limiting noise is reconstructed by using the same modulation and amplitude limiting method as that at the sending end, and the residual quantity of the amplitude limiting noise in an initial receiving signal is reduced by means of iterative elimination, so that the accuracy of system decoding is improved while the peak-to-average ratio of the OTFS-BFDM signal is reduced.

Description

Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment
Technical Field
The present application relates to the field of wireless communication technologies, and in particular, to a method, a system, and an electronic device for eliminating clipping noise based on peak-to-average power ratio suppression.
Background
Next generation wireless systems (5G and beyond) are intended to facilitate seamless and reliable communications in high mobility environments, including high speed train, airplane, vehicle-to-vehicle, and vehicle-to-infrastructure communications. While Orthogonal Frequency Division Multiplexing (OFDM) systems can achieve high spectral efficiency over time-invariant, frequency-selective channels, they exhibit insufficient robustness over time-variant channels with high doppler spread. Recently proposed Orthogonal Time Frequency Space (OTFS) systems have proven to have significant advantages over OFDM in high mobility environments. And further, OTFS transformation and dual-orthogonal frequency division multiplexing (BFDM) modulation are combined to form an OTFS-BFDM system, the system has a longer non-rectangular prototype window function, flexible waveform design and lower out-of-band dispersion can be realized, and the sparse connectivity of the system is ensured. However, the peak-to-average ratio (PAPR) of the OTFS-BFDM signal becomes higher as the number of symbols in the transmission interval increases. When the PAPR is too high, the transmitter may cause nonlinear distortion of the signal, ultimately affecting the BER performance of the system. Therefore, it is urgent to take effective measures to suppress the PAPR of the OTFS-BFDM system.
In a multi-carrier system based on a Message Passing (MP) signal detection algorithm, in order to not destroy the sparse connectivity of the system, a selective mapping method and an MP auxiliary amplitude limiting method are mostly adopted to inhibit the PAPR of a signal at present, the former causes signal distortion, but requires sideband information transmission and reduces the spectrum utilization rate, and the latter takes amplitude limiting noise and channel noise as the noise input of the MP algorithm, so that the amplitude limiting interference is relieved, but the influence on the system BER is still large.
In view of this, the present invention provides a method for eliminating clipping noise for peak-to-average power ratio suppression in an OTFS-BFDM system, which can recover the BER performance of the system as much as possible while solving the problem of too high PAPR of the system.
Disclosure of Invention
The invention provides a method, a system and electronic equipment for eliminating amplitude limiting noise based on peak-to-average ratio suppression, wherein the following technical scheme is adopted, under the assumption that a channel state, an amplitude limiting parameter and a window function are completely known at a receiving end, and a modulation symbol (such as 4QAM) of an OTFS-BFDM system is transmitted on a delay Doppler grid, wherein the sum respectively represents the maximum Doppler and delay offset:
a clipping noise elimination method based on peak-to-average ratio suppression is applied to a clipping noise elimination system and comprises the following steps:
step 1, at a sending end, carrying out primary amplitude limiting and filtering on an OTFS-BFDM modulation signal to obtain an amplitude limiting processing signal
Figure 455359DEST_PATH_IMAGE001
；
Step 2, at the receiving end, the initial received signal is processed
Figure 416755DEST_PATH_IMAGE002
After attenuation removal processing is carried out, observation signal vectors on a time domain are obtained through BFDM demodulation and octane-limited Fourier transform (SFFT)
Figure 663060DEST_PATH_IMAGE003
Will be
Figure 81403DEST_PATH_IMAGE003
Substituting MP algorithm for channel equalization and decoding judgment, and outputting variable signal vector
Figure 810062DEST_PATH_IMAGE004
；
Step 3, outputting the judgment output variable signal vector
Figure 136002DEST_PATH_IMAGE004
The OTFS-BFDM is modulated and then divided into two paths, one path is subjected to amplitude limiting and filtering processing which are the same as those of a sending end, so that a first path of amplitude limiting processing signal is obtained
Figure 502392DEST_PATH_IMAGE005
The other path is multiplied by a limiting attenuation factor to obtain a second path of attenuation processing signals
Figure 153953DEST_PATH_IMAGE006
The first path of amplitude limiting processing signal is used
Figure 871373DEST_PATH_IMAGE005
And the second path of attenuation processing signal
Figure 440151DEST_PATH_IMAGE006
Subtracting to obtain a reconstructed clipping noise vector
Figure 988944DEST_PATH_IMAGE007
Clipping the noise vector
Figure 483511DEST_PATH_IMAGE007
Obtaining the reconstructed clipping noise estimation at the receiver end after passing through the channel convolution matrix
Figure 688227DEST_PATH_IMAGE008
；
Step 4, receiving signal from initial
Figure 621548DEST_PATH_IMAGE009
Subtracting reconstructed clipping noise
Figure 461066DEST_PATH_IMAGE010
To obtain a corrected received signal
Figure 188851DEST_PATH_IMAGE011
Proceeding to the next iteration, and correcting the received signal
Figure 615284DEST_PATH_IMAGE012
Performing attenuation removal processing and OTFS-BFDM demodulation to obtain a corrected observation signal vector
Figure 86716DEST_PATH_IMAGE013
；
Step 5, the corrected received signal is processed
Figure 282206DEST_PATH_IMAGE014
SubstitutionThe initial received signal
Figure 151198DEST_PATH_IMAGE015
And returning to the step 2 and repeatedly executing the step 2 according to the preset maximum iteration times
Figure 127244DEST_PATH_IMAGE016
When the number of iterations reaches
Figure 74471DEST_PATH_IMAGE016
And then jumping out and finishing the amplitude limiting noise elimination.
Further, the performing of primary amplitude limiting and filtering on the OTFS-BFDM modulated signal specifically includes:
the pair of OTFS-BFDM modulation signal and amplitude limiting processing signal
Figure 655626DEST_PATH_IMAGE017
Is expressed as
Figure 427010DEST_PATH_IMAGE018
Wherein
Figure 890353DEST_PATH_IMAGE019
for the purpose of OTFS-BFDM modulation signals,
Figure 641271DEST_PATH_IMAGE020
which represents the clipping attenuation factor, is,
Figure 873669DEST_PATH_IMAGE021
is a clipping noise vector;
the clipping attenuation factor
Figure 317420DEST_PATH_IMAGE022
Calculated by the following formula:
Figure 695488DEST_PATH_IMAGE023
in the formula:
Figure 515676DEST_PATH_IMAGE024
is amplitude limiting rate, which represents the ratio of amplitude limiting threshold power to the average power of amplitude limiting processing signal;
the signal of the sending end after amplitude limiting processing is
Figure 602581DEST_PATH_IMAGE025
Wherein
Figure 13970DEST_PATH_IMAGE026
Representing a vector of modulation symbols;
Figure 389588DEST_PATH_IMAGE027
in the form of a block circulant matrix,
Figure 980844DEST_PATH_IMAGE028
；
Figure 187835DEST_PATH_IMAGE029
in the form of a diagonal matrix,
Figure 238967DEST_PATH_IMAGE030
and is obtained by the following formula:
Figure 836302DEST_PATH_IMAGE031
，
for the
Figure 795031DEST_PATH_IMAGE032
Each sub-matrix of (1) only if
Figure 295675DEST_PATH_IMAGE033
Element not equal to 0, matrix
Figure 517709DEST_PATH_IMAGE034
Not empty.
Further, the OTFS-BFDM modulation signal is calculated by a transmission matrix of an OTFS-BFDM system, wherein the transmission matrix of the OTFS-BFDM system is
Figure 602340DEST_PATH_IMAGE035
Wherein
Figure 302443DEST_PATH_IMAGE036
Is the ISSFT transform and is,
Figure 654664DEST_PATH_IMAGE037
and
Figure 578758DEST_PATH_IMAGE038
respectively representing normalisation
Figure 150685DEST_PATH_IMAGE039
Dot IDFT matrix sum
Figure 451216DEST_PATH_IMAGE040
The dimension-unit matrix is a matrix of the dimension units,
Figure 690568DEST_PATH_IMAGE041
which represents the kronecker product of,
Figure 224711DEST_PATH_IMAGE042
is a filter coefficient matrix of the BFDM analysis,
Figure 346250DEST_PATH_IMAGE043
is shown as
Figure 388156DEST_PATH_IMAGE044
，
Wherein,
Figure 216434DEST_PATH_IMAGE045
is of length of
Figure 747910DEST_PATH_IMAGE046
The analysis filter prototype window function of (2),
Figure 527385DEST_PATH_IMAGE047
。
further, the PAPR of the clipping noise cancellation system is preset, and the PAPR of the discrete time sample of a frame of OTFS-BFDM transmission signal is defined as:
Figure 435298DEST_PATH_IMAGE048
wherein,
Figure 118083DEST_PATH_IMAGE049
for the OTFS-BFDM transmitter output signal in the time domain,
Figure 23722DEST_PATH_IMAGE050
；
the PAPR performance of the clipping noise cancellation system is measured by a complementary cumulative distribution function CCDF that calculates that the peak power ratio of each transmitted sample value exceeds a predefined threshold
Figure 588696DEST_PATH_IMAGE051
The complementary cumulative distribution function CCDF has statistical properties, and is calculated by the following formula:
Figure 473869DEST_PATH_IMAGE052
，
in the formula:
Figure 276740DEST_PATH_IMAGE053
representing random variables
Figure 87701DEST_PATH_IMAGE054
The probability in a certain interval is that,
Figure 405550DEST_PATH_IMAGE055
by natural constants
Figure 825904DEST_PATH_IMAGE056
An exponential function of the base is used,
Figure 545599DEST_PATH_IMAGE057
is the number of sample points.
Further, the pair of initial received signals
Figure 527461DEST_PATH_IMAGE058
Performing attenuation removing treatment, which specifically comprises the following steps:
processing the amplitude-limited signal
Figure 535868DEST_PATH_IMAGE059
After passing through a Doppler frequency shift frequency fading channel, an initial receiving signal is obtained
Figure 323696DEST_PATH_IMAGE060
Wherein
Figure 348763DEST_PATH_IMAGE061
In order to convolve the matrix for the channel,
Figure 563844DEST_PATH_IMAGE062
for the channel additive white Gaussian noise vector, the receiving matrix of the OTFS-BFDM system is
Figure 528389DEST_PATH_IMAGE063
Wherein
Figure 323170DEST_PATH_IMAGE064
Is a transformation of the SFFT to the inverse,
Figure 751877DEST_PATH_IMAGE065
representing normalization
Figure 574077DEST_PATH_IMAGE066
A point DFT matrix is formed on the basis of the point DFT matrix,
Figure 353814DEST_PATH_IMAGE067
is a coefficient matrix of a BFDM synthesis filter;
Figure 686707DEST_PATH_IMAGE068
wherein,
Figure 907604DEST_PATH_IMAGE069
is of length of
Figure 730066DEST_PATH_IMAGE070
The synthesis filter prototype window function of (1),
Figure 170668DEST_PATH_IMAGE071
；
further, the coefficient matrix Q of the BFDM synthesis filter is expressed as
Figure 103989DEST_PATH_IMAGE072
；
When receiving signals
Figure 179393DEST_PATH_IMAGE073
Obtaining observation signal vector after receiving matrix through OTFS-BFDM system
Figure 172756DEST_PATH_IMAGE074
：
Figure 864769DEST_PATH_IMAGE075
Wherein,
Figure 772420DEST_PATH_IMAGE076
is composed of
Figure 30226DEST_PATH_IMAGE077
A channel effective matrix representing the system is shown,
Figure 132174DEST_PATH_IMAGE078
in order to clip the noise, it is,
Figure 45903DEST_PATH_IMAGE079
is the channel noise;
or
Figure 55448DEST_PATH_IMAGE080
Wherein,
Figure 138066DEST_PATH_IMAGE081
is composed of
Figure 207654DEST_PATH_IMAGE082
A channel effective matrix representing the system is shown,
Figure 608679DEST_PATH_IMAGE083
in order to clip the noise, it is,
Figure 421914DEST_PATH_IMAGE084
is the channel noise.
Further, the step 3 specifically includes:
step 301, output variable signal vector
Figure 591996DEST_PATH_IMAGE085
Carrying out OTFS-BFDM modulation to obtain a new OTFS-BFDM signal;
step 302, after performing amplitude limiting processing on the new OTFS-BFDM signal, obtaining a first path of amplitude limiting processed signal
Figure 331019DEST_PATH_IMAGE086
；
Step 303, after the new OTFS-BFDM signal is attenuated, a second path of attenuated signal is obtained
Figure 484920DEST_PATH_IMAGE087
；
Step 304, limiting the first path of amplitude limiting processing signal
Figure 39529DEST_PATH_IMAGE088
And the second path of attenuation processing signal
Figure 126434DEST_PATH_IMAGE089
Subtracting to obtain reconstructed clipping noise
Figure 537824DEST_PATH_IMAGE090
；
Step 305, clipping the reconstructed clipping noise
Figure 618169DEST_PATH_IMAGE091
Obtaining a reconstructed clipping noise estimate at the receiver end by means of a channel convolution matrix
Figure 773206DEST_PATH_IMAGE092
。
Further, the modified observation signal vector
Figure 183459DEST_PATH_IMAGE093
Calculated by the following formula:
Figure 703433DEST_PATH_IMAGE094
or
Figure 64882DEST_PATH_IMAGE095
Wherein,
Figure 226873DEST_PATH_IMAGE096
the residual clipping noise is obtained by calculating the difference between the initial clipping noise and the reconstructed clipping noise, and is obtained before the observation signal enters the detector and is further reduced in the next iteration.
A clipping noise elimination system based on peak-to-average ratio suppression applies the clipping noise elimination method, and the system comprises: the system comprises a transmitter and a receiver, wherein the transmitter is positioned at a transmitting end, the receiver is positioned at a receiving end, and the transmitter and the receiver are connected through a wireless communication link.
An electronic device comprising a memory unit having a computer program stored thereon and a processor unit implementing the above method when executing the program.
Through the embodiment of the application, the following technical effects can be obtained: the PAPR of the OTFS-BFDM signal is restrained by using a method of once amplitude limiting and filtering at a sending end, amplitude limiting noise is reconstructed at a receiving end, and the amplitude limiting noise is eliminated from an initial receiving signal as far as possible through an iteration mode, so that the accuracy of signal decoding is improved.
Drawings
In order to more clearly illustrate the technical solutions in the embodiments of the present application, the drawings needed to be used in the embodiments or the prior art descriptions will be briefly described below, and it is obvious that the drawings in the following description are some embodiments of the present application, and those skilled in the art can also obtain other drawings according to the drawings without inventive labor.
FIG. 1 is a flow chart of the algorithm of the clipping noise cancellation method of the present invention;
FIG. 2 is a schematic diagram of the system components of the present invention;
FIG. 3 is a diagram of the PAPR complementary cumulative distribution function of the present invention;
fig. 4 is a schematic diagram of bit error rate simulation according to the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the embodiments of the present application clearer, the technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are some embodiments of the present application, but not all embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.
The invention provides an amplitude limiting noise elimination scheme aiming at the peak-to-average power ratio inhibition of an OTFS-BFDM system based on the OTFS-BFDM system architecture, and the problem that the PAPR of the system is too high especially under the condition of a large data packet is considered. The invention uses a method of amplitude limiting and filtering at the sending end once, ensures the linear relation between the original signal and the amplitude limiting processing signal and reduces the PAPR of the system, and reduces the interference of the amplitude limiting noise to the signal decoding by a method of reconstructing the amplitude limiting noise and iteratively eliminating at the receiving end.
Fig. 1 is a flowchart of an algorithm of a clipping noise removing method according to the present invention, which is applied to a clipping noise removing system, and the clipping noise removing method includes the following steps:
step 1, at a sending end, carrying out primary amplitude limiting and filtering on an OTFS-BFDM modulation signal to obtain an amplitude limiting processing signal
Figure 288370DEST_PATH_IMAGE097
；
When a Gaussian random signal enters the amplitude limiting device, the output signal of the Gaussian random signal can be statistically decomposed into the sum of two parts of uncorrelated signals, and the purpose of using one-time amplitude limiting and filtering is to keep the linear relation and filter out-of-band noise;
the performing primary amplitude limiting and filtering on the OTFS-BFDM modulated signal specifically includes:
the pair of OTFS-BFDM modulation signal and amplitude limiting processing signal
Figure 244825DEST_PATH_IMAGE098
Is expressed as
Figure 595035DEST_PATH_IMAGE099
Wherein
Figure 581621DEST_PATH_IMAGE100
for the purpose of OTFS-BFDM modulation signals,
Figure 700887DEST_PATH_IMAGE101
which represents the clipping attenuation factor, is,
Figure 828243DEST_PATH_IMAGE102
is a clipping noise vector;
the clipping attenuation factor
Figure 462487DEST_PATH_IMAGE103
Calculated by the following formula:
Figure 700701DEST_PATH_IMAGE104
in the formula:
Figure 969746DEST_PATH_IMAGE105
is amplitude limiting rate, which represents the ratio of amplitude limiting threshold power to the average power of amplitude limiting processing signal;
the signal of the sending end after amplitude limiting processing is
Figure 268004DEST_PATH_IMAGE106
Wherein
Figure 389543DEST_PATH_IMAGE107
Represents a modulation symbol vector, e.g., 4 QAM;
Figure 165869DEST_PATH_IMAGE108
in the form of a block circulant matrix,
Figure 56465DEST_PATH_IMAGE109
；
Figure 292668DEST_PATH_IMAGE110
in the form of a diagonal matrix,
Figure 573608DEST_PATH_IMAGE111
and is obtained by the following formula:
Figure 481521DEST_PATH_IMAGE112
，
for the
Figure 164306DEST_PATH_IMAGE113
Each sub-matrix of (1) only if
Figure 69945DEST_PATH_IMAGE114
Element not equal to 0, matrix
Figure 399033DEST_PATH_IMAGE115
Is not empty;
the OTFS-BFDM modulation signal is calculated through a transmission matrix of an OTFS-BFDM system, wherein the transmission matrix of the OTFS-BFDM system is
Figure 782741DEST_PATH_IMAGE116
Wherein
Figure 585612DEST_PATH_IMAGE117
Is the ISSFT transform and is,
Figure 662152DEST_PATH_IMAGE118
and
Figure 980001DEST_PATH_IMAGE119
respectively representing normalisation
Figure 668865DEST_PATH_IMAGE120
Dot IDFT matrix sum
Figure 591821DEST_PATH_IMAGE121
The dimension-unit matrix is a matrix of the dimension units,
Figure 573684DEST_PATH_IMAGE122
which represents the kronecker product of,
Figure 378829DEST_PATH_IMAGE123
is a filter coefficient matrix of the BFDM analysis,
Figure 602875DEST_PATH_IMAGE124
is shown as
Figure 380338DEST_PATH_IMAGE125
，
Wherein,
Figure 595418DEST_PATH_IMAGE126
is of length of
Figure 559963DEST_PATH_IMAGE127
The analysis filter prototype window function of (2),
Figure 151482DEST_PATH_IMAGE128
；
at a sending end, presetting the PAPR of the clipping noise elimination system, and defining the PAPR of a discrete time sample of a frame of OTFS-BFDM transmitting signal as:
Figure 19337DEST_PATH_IMAGE129
wherein,
Figure 405319DEST_PATH_IMAGE130
for the OTFS-BFDM transmitter output signal in the time domain,
Figure 122739DEST_PATH_IMAGE131
；
in practical applications, the PAPR performance of the clipping noise cancellation system is measured by a complementary cumulative distribution function CCDF that calculates that the peak power ratio of each transmitted sample value exceeds a predefined threshold
Figure 252369DEST_PATH_IMAGE132
The complementary cumulative distribution function CCDF has statistical properties, and is calculated by the following formula:
Figure 738845DEST_PATH_IMAGE133
，
in the formula:
Figure 997526DEST_PATH_IMAGE134
representing random variables
Figure 998980DEST_PATH_IMAGE135
The probability in a certain interval is that,
Figure 604405DEST_PATH_IMAGE136
by natural constants
Figure 7704DEST_PATH_IMAGE137
An exponential function of the base is used,
Figure 204331DEST_PATH_IMAGE138
is the number of sampling points;
step 2, at the receiving end, the initial received signal is processed
Figure 878368DEST_PATH_IMAGE139
After attenuation removal processing is carried out, observation signal vectors on a time domain are obtained through BFDM demodulation and octane-limited Fourier transform (SFFT)
Figure 615380DEST_PATH_IMAGE140
Will be
Figure 810869DEST_PATH_IMAGE140
Substituting MP algorithm for channel equalization and decoding judgment, and outputting variable signal vector
Figure 709555DEST_PATH_IMAGE141
；
The pair of initial received signals
Figure 623284DEST_PATH_IMAGE142
Performing attenuation removing treatment, which specifically comprises the following steps:
processing the amplitude-limited signal
Figure 600205DEST_PATH_IMAGE143
After passing through a Doppler frequency shift frequency fading channel, an initial receiving signal is obtained
Figure 712518DEST_PATH_IMAGE144
Wherein
Figure 985367DEST_PATH_IMAGE145
In order to convolve the matrix for the channel,
Figure 183131DEST_PATH_IMAGE146
for the channel additive white Gaussian noise vector, the receiving matrix of the OTFS-BFDM system is
Figure 199628DEST_PATH_IMAGE147
Wherein
Figure 432026DEST_PATH_IMAGE148
Is a transformation of the SFFT to the inverse,
Figure 111663DEST_PATH_IMAGE149
representing normalization
Figure 62301DEST_PATH_IMAGE150
A point DFT matrix is formed on the basis of the point DFT matrix,
Figure 616910DEST_PATH_IMAGE151
is a coefficient matrix of a BFDM synthesis filter;
Figure 703815DEST_PATH_IMAGE152
wherein,
Figure 52888DEST_PATH_IMAGE153
is of length of
Figure 723779DEST_PATH_IMAGE154
The synthesis filter prototype window function of (1),
Figure 82079DEST_PATH_IMAGE155
；
similarly, according to the method in step 1, Q can be expressed as
Figure 23490DEST_PATH_IMAGE156
；
When receiving signals
Figure 74623DEST_PATH_IMAGE157
Obtaining observation signal vector after receiving matrix through OTFS-BFDM system
Figure 671957DEST_PATH_IMAGE158
：
Figure 335413DEST_PATH_IMAGE159
Wherein,
Figure 396910DEST_PATH_IMAGE160
is composed of
Figure 353365DEST_PATH_IMAGE161
A channel effective matrix representing the system is shown,
Figure 234733DEST_PATH_IMAGE162
in order to clip the noise, it is,
Figure 934836DEST_PATH_IMAGE163
is the channel noise;
or
Figure 349374DEST_PATH_IMAGE164
Wherein,
Figure 476730DEST_PATH_IMAGE165
is composed of
Figure 110974DEST_PATH_IMAGE166
A channel effective matrix representing the system is shown,
Figure 349188DEST_PATH_IMAGE167
in order to clip the noise, it is,
Figure 119698DEST_PATH_IMAGE168
is the channel noise;
in the above-mentioned calculation formula,
Figure 919420DEST_PATH_IMAGE169
proved to be sparse connectivitySimultaneous multiplication by a diagonal matrix before and after it does not change the sparse connectivity, hence
Figure 978643DEST_PATH_IMAGE170
The signal detection is also sparse and connected, so that the signal detection can be carried out by using an MP algorithm based on a factor graph; the system noise comprises amplitude limiting noise and channel noise, and the system defaults to use the channel noise as noise input of an MP detection algorithm when signal decoding is carried out, so that the decoding accuracy is influenced, the BER performance is reduced, and the amplitude limiting noise needs to be eliminated;
step 3, outputting the judgment output variable signal vector
Figure 82865DEST_PATH_IMAGE171
The OTFS-BFDM is modulated and then divided into two paths, one path is subjected to amplitude limiting and filtering processing which are the same as those of a sending end, so that a first path of amplitude limiting processing signal is obtained
Figure 911144DEST_PATH_IMAGE172
The other path is multiplied by a limiting attenuation factor to obtain a second path of attenuation processing signals
Figure 442620DEST_PATH_IMAGE173
The first path of amplitude limiting processing signal is used
Figure 487674DEST_PATH_IMAGE174
And the second path of attenuation processing signal
Figure 67691DEST_PATH_IMAGE175
Subtracting to obtain a reconstructed clipping noise vector
Figure 812793DEST_PATH_IMAGE176
Clipping the noise vector
Figure 452853DEST_PATH_IMAGE176
Obtaining the reconstructed clipping noise estimation at the receiver end after passing through the channel convolution matrix
Figure 283406DEST_PATH_IMAGE177
；
The step 3 specifically includes:
step 301, output variable signal vector
Figure 422439DEST_PATH_IMAGE178
Carrying out OTFS-BFDM modulation to obtain a new OTFS-BFDM signal;
step 302, after performing amplitude limiting processing on the new OTFS-BFDM signal, obtaining a first path of amplitude limiting processed signal
Figure 225310DEST_PATH_IMAGE179
；
Step 303, after the new OTFS-BFDM signal is attenuated, a second path of attenuated signal is obtained
Figure 301850DEST_PATH_IMAGE180
；
Step 304, limiting the first path of amplitude limiting processing signal
Figure 354120DEST_PATH_IMAGE181
And the second path of attenuation processing signal
Figure 541519DEST_PATH_IMAGE182
Subtracting to obtain reconstructed clipping noise
Figure 759748DEST_PATH_IMAGE183
；
Step 305, clipping the reconstructed clipping noise
Figure 741611DEST_PATH_IMAGE184
Obtaining a reconstructed clipping noise estimate at the receiver end by means of a channel convolution matrix
Figure 281176DEST_PATH_IMAGE185
；
Step 4, receiving signal from initial
Figure 6687DEST_PATH_IMAGE186
Subtracting reconstructed clipping noise
Figure 580888DEST_PATH_IMAGE185
To obtain a corrected received signal
Figure 235116DEST_PATH_IMAGE187
Proceeding to the next iteration, and correcting the received signal
Figure 527557DEST_PATH_IMAGE188
Performing attenuation removal processing and OTFS-BFDM demodulation to obtain a corrected observation signal vector
Figure 791180DEST_PATH_IMAGE189
Wherein the corrected observation signal vector
Figure 485466DEST_PATH_IMAGE189
Calculated by the following formula:
Figure 74710DEST_PATH_IMAGE190
or
Figure 323289DEST_PATH_IMAGE191
Wherein,
Figure 889138DEST_PATH_IMAGE192
the residual amplitude limiting noise is obtained by calculating the difference between the initial amplitude limiting noise and the reconstructed amplitude limiting noise, and is obtained before an observation signal enters a detector and is further reduced in the next iteration;
step 5, the corrected received signal is processed
Figure 641193DEST_PATH_IMAGE193
Replacing the original received signal
Figure 198076DEST_PATH_IMAGE194
And returning to the step 2 and repeatedly executing the step 2 according to the preset maximum iteration times
Figure 137213DEST_PATH_IMAGE195
When the number of iterations reaches
Figure 70534DEST_PATH_IMAGE195
Jumping out and finishing the amplitude limiting noise elimination;
fig. 2 is a schematic diagram of a system composition structure of the present invention, where the clipping noise canceling system includes two parts, i.e., a transmitter and a receiver, the transmitter is located at a transmitting end, the receiver is located at a receiving end, and the transmitter and the receiver are connected through a wireless communication link.
The transmitter performs ISSFT conversion, BFDM modulation, amplitude limiting and filtering processing at a transmitting end, and the receiver performs BFDM demodulation, octal finite Fourier transform (SFFT), ISFFT and BFDM modulation, amplitude limiting and filtering processing at a receiving end.
In the simulation experiments of the present invention, the delay-doppler spectrum parameters considered are shown in table i, where the power gain of each path is uniformly distributed.
Table I: path =5 delay doppler spectral parameter
Figure 912982DEST_PATH_IMAGE196
Table ii summarizes other relevant simulation parameters.
Table ii: simulation parameters
Figure 640766DEST_PATH_IMAGE197
Fig. 3 is a diagram illustrating PAPR complementary cumulative distribution function of the present invention, wherein OTFS-BFDM uses CCDF of PAPR of RRC window function. To better study the PAPR of the signal, the value of the oversampling factor is O = 4.As shown in the figure, after the clipping process, the PAPR of the OTFS-BFDM signal is greatly reduced. When the CCDF probability is
Figure 67200DEST_PATH_IMAGE198
When the signal is processed, the PAPR of the signal adopting the amplitude limiting method is 1.015dB less than that of the SLM method and 4.38dB less than that of the original signal. In addition, as N increases, the CCDF of the signal PAPR also increases.
Fig. 4 is a schematic diagram of bit error rate simulation according to the present invention. In the invention, the BER performance of an OTFS-BFDM system adopting RRC under the condition that the Doppler frequency shift is 1935Hz is evaluated. It can be seen from the figure that OTFS-BFDM using the iterative clipping noise cancellation method has better and better BER performance as the number of iterations increases, since the residual clipping noise decreases as the number of iterations increases. Whether an iterative clipping noise cancellation method or an MP assisted clipping method is used (referred to as OTFS _ RCwithCN in the figure), the BER rate of the OTFS-BFDM system gets better as the clipping rate increases, since the higher the signal distortion, the smaller the signal distortion. While the latter allows for clipping noise as part of the system noise, the BER of systems employing the latter is generally greater than the former.
The invention discloses a method for eliminating amplitude limiting noise aiming at peak-to-average power ratio (PAPR) suppression in an OTFS-BFDM system. The method uses the amplitude limiting and filtering method to restrain the peak-to-average ratio of the OTFS-BFDM signal, reconstructs the amplitude limiting noise at the receiving end by using the same modulation and amplitude limiting method as the transmitting end, and reduces the residual quantity of the amplitude limiting noise in the initial receiving signal by an iterative elimination mode, thereby reducing the peak-to-average ratio of the OTFS-BFDM signal and improving the accuracy of system decoding. By comparing the PAPR and BER performance of the OTFS-BFDM system using the RRC window function under different methods, the method for amplitude limiting and filtering can better inhibit the PAPR than the SLM method, and the amplitude limiting noise elimination method aiming at the peak-to-average ratio inhibition has better BER performance than the MP auxiliary amplitude limiting method.
In some embodiments, part or all of the computer program may be loaded and/or installed onto the device via ROM. When being loaded and executed, may carry out one or more of the steps of the method described above.
The functions described herein above may be performed, at least in part, by one or more hardware logic components. For example, without limitation, exemplary types of hardware logic components that may be used include: a Field Programmable Gate Array (FPGA), an Application Specific Integrated Circuit (ASIC), an Application Specific Standard Product (ASSP), a system on a chip (SOC), a load programmable logic device (CPLD), and the like.
Program code for implementing the methods of the present disclosure may be written in any combination of one or more programming languages. These program codes may be provided to a processor or controller of a general purpose computer, special purpose computer, or other programmable data processing apparatus, such that the program codes, when executed by the processor or controller, cause the functions/operations specified in the flowchart and/or block diagram to be performed. The program code may execute entirely on the machine, partly on the machine, as a stand-alone software package partly on the machine and partly on a remote machine or entirely on the remote machine or server.
In the context of this disclosure, a machine-readable medium may be a tangible medium that can contain, or store a program for use by or in connection with an instruction execution system, apparatus, or device. The machine-readable medium may be a machine-readable signal medium or a machine-readable storage medium. A machine-readable medium may include, but is not limited to, an electronic, magnetic, optical, electromagnetic, infrared, or semiconductor system, apparatus, or device, or any suitable combination of the foregoing. More specific examples of a machine-readable storage medium would include an electrical connection based on one or more wires, a portable computer diskette, a hard disk, a Random Access Memory (RAM), a read-only memory (ROM), an erasable programmable read-only memory (EPROM or flash memory), an optical fiber, a portable compact disc read-only memory (CD-ROM), an optical storage device, a magnetic storage device, or any suitable combination of the foregoing.
Further, while operations are depicted in a particular order, this should be understood as requiring that such operations be performed in the particular order shown or in sequential order, or that all illustrated operations be performed, to achieve desirable results. Under certain circumstances, multitasking and parallel processing may be advantageous. Likewise, while several specific implementation details are included in the above discussion, these should not be construed as limitations on the scope of the disclosure. Certain features that are described in the context of separate embodiments can also be implemented in combination in a single implementation. Conversely, various features that are described in the context of a single implementation can also be implemented in multiple implementations separately or in any suitable subcombination.
Although the subject matter has been described in language specific to structural features and/or methodological acts, it is to be understood that the subject matter defined in the appended claims is not necessarily limited to the specific features or acts described above. Rather, the specific features and acts described above are disclosed as example forms of implementing the claims.

Claims (10)

1. A clipping noise elimination method based on peak-to-average power ratio suppression is applied to a clipping noise elimination system and is characterized by comprising the following steps:
step 1, at a sending end, carrying out primary amplitude limiting and filtering on an OTFS-BFDM modulation signal to obtain an amplitude limiting processing signal
Figure 242246DEST_PATH_IMAGE001
；
Step 2, at the receiving end, the initial received signal is processed
Figure 881169DEST_PATH_IMAGE002
After attenuation removal processing is carried out, observation signal vectors on a time domain are obtained through BFDM demodulation and octane-limited Fourier transform (SFFT)
Figure 590499DEST_PATH_IMAGE003
Will be
Figure 72296DEST_PATH_IMAGE004
Substituting MP algorithm for channel equalization and decoding judgment, and outputting variable signal vector
Figure 892484DEST_PATH_IMAGE005
；
Step 3, outputting the judgment output variable signal vector
Figure 946766DEST_PATH_IMAGE006
The OTFS-BFDM is modulated and then divided into two paths, one path is subjected to amplitude limiting and filtering processing which are the same as those of a sending end, so that a first path of amplitude limiting processing signal is obtained
Figure 764680DEST_PATH_IMAGE007
The other path is multiplied by a limiting attenuation factor to obtain a second path of attenuation processing signals
Figure 405877DEST_PATH_IMAGE008
The first path of amplitude limiting processing signal is used
Figure 29756DEST_PATH_IMAGE009
And the second path of attenuation processing signal
Figure 502326DEST_PATH_IMAGE010
Subtracting to obtain a reconstructed clipping noise vector
Figure 320503DEST_PATH_IMAGE011
Clipping the noise vector
Figure 386679DEST_PATH_IMAGE012
Obtaining the reconstructed clipping noise estimation at the receiver end after passing through the channel convolution matrix
Figure 814249DEST_PATH_IMAGE013
；
Step 4, receiving from the beginningSignal
Figure 79008DEST_PATH_IMAGE014
Subtracting reconstructed clipping noise
Figure 628938DEST_PATH_IMAGE015
To obtain a corrected received signal
Figure 477683DEST_PATH_IMAGE016
Proceeding to the next iteration, and correcting the received signal
Figure 646628DEST_PATH_IMAGE017
Performing attenuation removal processing and OTFS-BFDM demodulation to obtain a corrected observation signal vector
Figure 31473DEST_PATH_IMAGE018
；
Step 5, the corrected received signal is processed
Figure 752304DEST_PATH_IMAGE019
Replacing the original received signal
Figure 855389DEST_PATH_IMAGE020
And returning to the step 2 and repeatedly executing the step 2 according to the preset maximum iteration times
Figure 860648DEST_PATH_IMAGE021
When the number of iterations reaches
Figure 37682DEST_PATH_IMAGE022
And then jumping out and finishing the amplitude limiting noise elimination.
2. The clipping noise removing method according to claim 1, wherein the clipping and filtering the OTFS-BFDM modulated signal for one time specifically includes:
the above-mentionedFor OTFS-BFDM modulation signal and amplitude limiting processing signal
Figure 867098DEST_PATH_IMAGE023
Is expressed as
Figure 254217DEST_PATH_IMAGE024
Wherein
Figure 561702DEST_PATH_IMAGE025
for the purpose of OTFS-BFDM modulation signals,
Figure 419674DEST_PATH_IMAGE026
which represents the clipping attenuation factor, is,
Figure 357674DEST_PATH_IMAGE027
is a clipping noise vector;
the clipping attenuation factor
Figure 169772DEST_PATH_IMAGE028
Calculated by the following formula:
Figure 343265DEST_PATH_IMAGE029
in the formula: is amplitude limiting rate, which represents the ratio of amplitude limiting threshold power to the average power of amplitude limiting processing signal;
the signal of the sending end after amplitude limiting processing is
Figure 976031DEST_PATH_IMAGE031
Wherein
Figure 213108DEST_PATH_IMAGE032
Representing a vector of modulation symbols;
Figure 862396DEST_PATH_IMAGE033
in the form of a block circulant matrix,
Figure 196425DEST_PATH_IMAGE034
；
Figure 600861DEST_PATH_IMAGE035
in the form of a diagonal matrix,
Figure 620508DEST_PATH_IMAGE036
and is obtained by the following formula:
Figure 276748DEST_PATH_IMAGE037
，
for the
Figure 465284DEST_PATH_IMAGE038
Each sub-matrix of (1) only if
Figure 712726DEST_PATH_IMAGE039
Element not equal to 0, matrix
Figure 49029DEST_PATH_IMAGE040
Not empty.
3. The clipping noise cancellation method according to claim 2, wherein the OTFS-BFDM modulated signal is calculated by a transmission matrix of an OTFS-BFDM system, the transmission matrix of the OTFS-BFDM system being
Figure 541584DEST_PATH_IMAGE041
Wherein
Figure 522309DEST_PATH_IMAGE042
Is the ISSFT transform and is,
Figure 206231DEST_PATH_IMAGE043
and
Figure 29831DEST_PATH_IMAGE044
respectively representing normalisation
Figure 559032DEST_PATH_IMAGE045
Dot IDFT matrix sum
Figure 955116DEST_PATH_IMAGE046
The dimension-unit matrix is a matrix of the dimension units,
Figure 216465DEST_PATH_IMAGE047
which represents the kronecker product of,
Figure 261781DEST_PATH_IMAGE048
is a filter coefficient matrix of the BFDM analysis,
Figure 768242DEST_PATH_IMAGE048
is shown as
Figure 520297DEST_PATH_IMAGE049
，
Wherein,
Figure 608339DEST_PATH_IMAGE050
is of length of
Figure 813056DEST_PATH_IMAGE051
The analysis filter prototype window function of (2),
Figure 215218DEST_PATH_IMAGE052
。
4. the clipping noise cancellation method according to one of claims 1 to 3,
presetting the PAPR of the clipping noise elimination system, and defining the PAPR of discrete time samples of a frame of OTFS-BFDM transmitting signals as follows:
Figure 523577DEST_PATH_IMAGE053
wherein,
Figure 720204DEST_PATH_IMAGE054
for the OTFS-BFDM transmitter output signal in the time domain,
Figure 740112DEST_PATH_IMAGE055
；
the PAPR performance of the clipping noise cancellation system is measured by a complementary cumulative distribution function CCDF that calculates that the peak power ratio of each transmitted sample value exceeds a predefined threshold
Figure 945966DEST_PATH_IMAGE056
The complementary cumulative distribution function CCDF has statistical properties, and is calculated by the following formula:
Figure 610296DEST_PATH_IMAGE057
，
in the formula:
Figure 213709DEST_PATH_IMAGE058
representing random variables
Figure 658597DEST_PATH_IMAGE059
The probability in a certain interval is that,
Figure 464879DEST_PATH_IMAGE060
by natural constants
Figure 46033DEST_PATH_IMAGE061
An exponential function of the base is used,
Figure 584462DEST_PATH_IMAGE062
is the number of sample points.
5. The clipping noise cancellation method according to claim 1, wherein the pair of original received signals
Figure 687285DEST_PATH_IMAGE063
Performing attenuation removing treatment, which specifically comprises the following steps:
processing the amplitude-limited signal
Figure 234941DEST_PATH_IMAGE064
After passing through a Doppler frequency shift frequency fading channel, an initial receiving signal is obtained
Figure 732918DEST_PATH_IMAGE065
Wherein
Figure 707827DEST_PATH_IMAGE066
In order to convolve the matrix for the channel,
Figure 799411DEST_PATH_IMAGE067
for the channel additive white Gaussian noise vector, the receiving matrix of the OTFS-BFDM system is
Figure 374925DEST_PATH_IMAGE068
Wherein
Figure 992988DEST_PATH_IMAGE069
Is a transformation of the SFFT to the inverse,
Figure 138799DEST_PATH_IMAGE070
representing normalization
Figure 717679DEST_PATH_IMAGE071
A point DFT matrix is formed on the basis of the point DFT matrix,
Figure 607137DEST_PATH_IMAGE072
is a coefficient matrix of a BFDM synthesis filter;
Figure 250346DEST_PATH_IMAGE073
wherein,
Figure 629375DEST_PATH_IMAGE074
is of length of
Figure 757868DEST_PATH_IMAGE075
The synthesis filter prototype window function of (1),
Figure 123121DEST_PATH_IMAGE076
。
6. the clipping noise cancellation method of claim 5, wherein the BFDM synthesis filter coefficient matrix
Figure 653460DEST_PATH_IMAGE077
Is shown as
Figure 937811DEST_PATH_IMAGE078
；
When receiving signals
Figure 55064DEST_PATH_IMAGE079
Obtaining observation signal vector after receiving matrix through OTFS-BFDM system
Figure 224009DEST_PATH_IMAGE080
：
Figure 608854DEST_PATH_IMAGE081
Wherein,
Figure 329685DEST_PATH_IMAGE082
is composed of
Figure 167191DEST_PATH_IMAGE083
A channel effective matrix representing the system is shown,
Figure 372782DEST_PATH_IMAGE084
in order to clip the noise, it is,
Figure 877713DEST_PATH_IMAGE085
is the channel noise;
or
Figure 441549DEST_PATH_IMAGE086
Wherein,
Figure 828668DEST_PATH_IMAGE087
is composed of
Figure 401732DEST_PATH_IMAGE088
A channel effective matrix representing the system is shown,
Figure 997055DEST_PATH_IMAGE089
in order to clip the noise, it is,
Figure 935055DEST_PATH_IMAGE090
is the channel noise.
7. The clipping noise removing method according to claim 1, wherein the step 3 specifically includes:
step 301, output variable signal vector
Figure 747153DEST_PATH_IMAGE091
Carrying out OTFS-BFDM modulation to obtain a new OTFS-BFDM signal;
step 302, after performing amplitude limiting processing on the new OTFS-BFDM signal, obtaining a first path of amplitude limiting processed signal
Figure 920646DEST_PATH_IMAGE092
；
Step 303, after the new OTFS-BFDM signal is attenuated, a second path of attenuated signal is obtained
Figure 134589DEST_PATH_IMAGE093
；
Step 304, limiting the first path of amplitude limiting processing signal
Figure 742026DEST_PATH_IMAGE094
And the second path of attenuation processing signal
Figure 41420DEST_PATH_IMAGE095
Subtracting to obtain reconstructed clipping noise
Figure 18604DEST_PATH_IMAGE096
；
Step 305, clipping the reconstructed clipping noise
Figure 87054DEST_PATH_IMAGE097
Obtaining a reconstructed clipping noise estimate at the receiver end by means of a channel convolution matrix
Figure 366856DEST_PATH_IMAGE098
。
8. The clipping noise cancellation method according to claim 1, wherein the modified observation signal vector is
Figure 655012DEST_PATH_IMAGE099
Calculated by the following formula:
Figure 435886DEST_PATH_IMAGE100
or
Figure 358843DEST_PATH_IMAGE101
Wherein,
Figure 809547DEST_PATH_IMAGE102
the residual clipping noise is obtained by calculating the difference between the initial clipping noise and the reconstructed clipping noise, and is obtained before the observation signal enters the detector and is further reduced in the next iteration.
9. A clipping noise removing system based on peak-to-average ratio suppression, which applies the clipping noise removing method according to one of the claims 1 to 8, wherein the system comprises two parts, a transmitter and a receiver, the transmitter is located at a transmitting end, the receiver is located at a receiving end, and the transmitter and the receiver are connected through a wireless communication link.
10. An electronic device comprising a memory unit and a processor unit, the memory unit having stored thereon a computer program, characterized in that the processor unit, when executing the program, implements the method according to one of claims 1 to 8.
CN202111046326.4A 2020-12-24 2021-09-08 Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment Active CN113489666B (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN2020115449466 2020-12-24
CN202011544946.6A CN112968852A (en) 2020-12-24 2020-12-24 Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment

Publications (2)

Publication Number Publication Date
CN113489666A true CN113489666A (en) 2021-10-08
CN113489666B CN113489666B (en) 2021-11-30

Family

ID=76271656

Family Applications (2)

Application Number Title Priority Date Filing Date
CN202011544946.6A Pending CN112968852A (en) 2020-12-24 2020-12-24 Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment
CN202111046326.4A Active CN113489666B (en) 2020-12-24 2021-09-08 Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment

Family Applications Before (1)

Application Number Title Priority Date Filing Date
CN202011544946.6A Pending CN112968852A (en) 2020-12-24 2020-12-24 Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment

Country Status (1)

Country Link
CN (2) CN112968852A (en)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116366169A (en) * 2023-06-01 2023-06-30 浙江大学 Ultrasonic channel modeling method, electronic device and storage medium

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113556306B (en) * 2021-07-19 2022-04-08 上海交通大学 Discrete Fourier transform extended orthogonal time-frequency-space modulation method and system
CN114189261B (en) * 2021-11-02 2024-08-16 广州慧睿思通科技股份有限公司 Time-frequency diagram processing method, device, network equipment and computer readable storage medium

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106130946A (en) * 2016-06-08 2016-11-16 重庆邮电大学 A kind of biorthogonal frequency-division multiplex multi-carrier modulation/demodulation methods and system
WO2017044501A1 (en) * 2015-09-07 2017-03-16 Cohere Technologies Multiple access using orthogonal time frequency space modulation
CN111555780A (en) * 2020-01-09 2020-08-18 北京邮电大学 Multi-antenna receiver design based on orthogonal time-frequency-space modulation

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2017044501A1 (en) * 2015-09-07 2017-03-16 Cohere Technologies Multiple access using orthogonal time frequency space modulation
CN106130946A (en) * 2016-06-08 2016-11-16 重庆邮电大学 A kind of biorthogonal frequency-division multiplex multi-carrier modulation/demodulation methods and system
CN111555780A (en) * 2020-01-09 2020-08-18 北京邮电大学 Multi-antenna receiver design based on orthogonal time-frequency-space modulation

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
G. D. SURABHI等: "Peak-to-Average Power Ratio of OTFS Modulation", 《IEEE COMMUNICATIONS LETTERS》 *
P. RAVITEJA等: "Interference Cancellation and Iterative Detection for Orthogonal Time Frequency Space Modulation", 《IEEE TRANSACTIONS ON WIRELESS COMMUNICATIONS》 *

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116366169A (en) * 2023-06-01 2023-06-30 浙江大学 Ultrasonic channel modeling method, electronic device and storage medium
CN116366169B (en) * 2023-06-01 2023-10-24 浙江大学 Ultrasonic channel modeling method, electronic device and storage medium

Also Published As

Publication number Publication date
CN112968852A (en) 2021-06-15
CN113489666B (en) 2021-11-30

Similar Documents

Publication Publication Date Title
CN113489666B (en) Amplitude limiting noise elimination method and system based on peak-to-average ratio inhibition and electronic equipment
KR101291684B1 (en) Method of channel estimation based on doubly adjacent windows and apparatus thereof
CN103457638B (en) Restraining device and restraining method for burst impulse noise of power line communication channel
Wang Combined DCT and Companding for PAPR Reduction in OFDM Signals.
US20070258528A1 (en) Apparatus for reducing clipping noise in a broadband wireless communication system and method thereof
Bibi et al. Equation-method for correcting clipping errors in OFDM signals
CN113259298B (en) OTFS signal processing method, device, equipment and storage medium
US7869493B2 (en) Method for detecting a signal, detector and computer program product
GB2548293A (en) Noise variance estimation and interference detection
Wang et al. Compensation of nonlinear distortions with memory effects in OFDM transmitters
Padarti et al. An improved ASOICF algorithm for PAPR reduction in OFDM systems
WO2016050870A1 (en) A generalized frequency division multiplexing transceiver
CN107426129B (en) Method and device for modulating and demodulating GFDM signal
Sim et al. Reducing the PAPR of GFDM systems with quadratic programming filter design
Ikni et al. PAPR reduction in FBMC-OQAM systems based on discrete sliding norm transform technique
JP6278499B2 (en) Peak power reduction device in communication system
CN101729475A (en) Method and device for processing multi-carrier signal
WO2020183544A1 (en) Reception device, wireless communication system, and interference power estimation method
Hasan PAPR reduction in OFDM systems based on autoregressive filtering
Sahu et al. PAPR reduction in OFDM system using iterative clipping and filtering technique along with convolutional code
Bibi et al. Inverted wrap-around limiting with Bussgang noise cancellation receiver for Ofdm signals
Gay et al. An adaptive PAPR reduction scheme for OFDM using SLM with clipping at the transmitter, and sparse reconstruction at the receiver
CN108881095B (en) OFDM data processing method and device
CN108604909A (en) A kind of signal acceptance method and device
CN117280661A (en) Projection signals using discrete long sphere sequences

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant