CN113484603A - Electric energy metering system and method - Google Patents
Electric energy metering system and method Download PDFInfo
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Abstract
The invention discloses an electric energy metering system and a method, comprising a current acquisition circuit, a voltage acquisition circuit, an AD chip and an MCU, wherein the current acquisition circuit at least comprises a current acquisition module, and the current acquisition module comprises: the first current acquisition branch circuit and the second current acquisition branch circuit are used as two different current acquisition paths to acquire the same current waveform signal, and the variable ratio of the current sensor in the two current acquisition branch circuits and the resistance of the sampling resistor are different, so that the acquisition precision of the first current acquisition branch circuit and the acquisition precision of the second current acquisition branch circuit for different current waveform signals are different. According to the invention, the current waveform signal with higher precision is selected to carry out subsequent electric energy calculation according to whether the input current waveform signal is a large signal or a small signal, so that the high-precision calculation of electric energy measurement and the large dynamic range measurement of the current waveform signal are realized on the basis of not changing the hardware design of an AD chip.
Description
Technical Field
The invention relates to the technical field of electric energy data processing, in particular to an electric energy metering system and method.
Background
Electrical energy metering is an important component in the field of electrical power distribution. With the deep development of the electric power market, the management and technical level of the electric power company is continuously improved, and the electric energy metering data is used as an important basis for supporting market decision, so that the electric power market application process plays an increasingly important role.
Generally, the selection of the effective digit of the AD chip is determined by the current and voltage waveform sampling resolution and the dynamic range of the current and voltage test, and the higher the effective digit of the AD chip is, the higher the accuracy of the AD chip is. When the electric energy is measured, the dynamic range of the voltage is relatively stable, and the dynamic range of the current side is usually large, and is generally more than 400 times. The dynamic range of signal measurement is inversely proportional to the precision of signal measurement, if high-precision calculation of electric energy measurement is realized, the sampling precision of current needs to reach one thousandth of stability, the required effective digit of the AD chip at least needs to reach more than 18 digits, the hardware cost is high, and the hardware design of the AD chip is more challenged.
Therefore, how to realize the large dynamic range measurement of the current waveform signal and the high-precision calculation of the electric energy measurement based on the mature low-effective-digit AD chip becomes a technical problem which needs to be solved by the technical personnel in the field.
Disclosure of Invention
In view of this, the present invention discloses an electric energy metering system and method, which are used to realize the large dynamic range measurement of current waveform signals and the high-precision calculation of electric energy metering without changing the hardware design of an AD chip.
An electric energy metering system is characterized by comprising a current acquisition circuit, a voltage acquisition circuit, an AD chip and an MCU;
the current acquisition circuit includes a current acquisition module at least, the current acquisition module includes: the current sampling circuit comprises a first current acquisition branch and a second current acquisition branch, wherein the first current acquisition branch comprises a first current sensor and a first sampling resistor, the second current acquisition branch comprises a second current sensor and a second sampling resistor, the transformation ratio of the first current sensor is smaller than that of the second current sensor, the first current sensor and the second current sensor are connected in series, and the resistance value of the first sampling resistor is smaller than that of the second sampling resistor;
the first current acquisition branch is used for acquiring a first analog current waveform signal;
the second current acquisition branch is used for acquiring a second analog current waveform signal;
the voltage acquisition circuit is used for acquiring analog voltage waveform signals;
the input end of the AD chip is respectively connected with the current acquisition circuit and the voltage acquisition circuit, the output end of the AD chip is connected with the MCU, and the AD chip is used for acquiring the first analog current waveform signal, the second analog current waveform signal and the analog voltage waveform signal based on a preset fixed frequency, respectively converting the first analog current waveform signal into a first digital current waveform signal, converting the second analog current waveform signal into a second digital current waveform signal, and converting the analog voltage waveform signal into a digital voltage waveform signal and then outputting the digital voltage waveform signal to the MCU;
the MCU is used for acquiring the first digital current waveform signal, the second digital current waveform signal and the digital voltage waveform signal, respectively calculating a voltage effective value corresponding to the first digital current waveform signal, recording the voltage effective value as a first current effective value, and a voltage effective value corresponding to the second digital current waveform signal, recording the voltage effective value as a second current effective value, selecting a current effective value meeting a preset current selection condition from the first current effective value and the second current effective value, and determining electric energy based on the current effective value and the digital voltage waveform signal;
wherein the preset conditions are as follows: when the current waveform signal input by the current acquisition circuit meets a preset small signal condition, determining the second current effective value as a current effective value, and abandoning the first current effective value; and when the current waveform signal meets a preset large signal condition, determining the first current effective value as the current effective value, and abandoning the second current effective value.
Optionally, the first current collecting branch further includes: first filtering branch and second filtering branch, first sampling resistance includes: the first sampling sub-resistor and the second sampling sub-resistor have the same resistance;
the main winding of the first current sensor is used for inputting the current waveform signal, the first end of the secondary winding of the first current sensor is respectively passed through the first sampling sub-resistor and the first filtering branch circuit, the output end of the first filtering branch circuit is used for outputting the positive signal of the first analog current waveform signal, the second end of the secondary winding of the first current sensor is respectively passed through the second sampling sub-resistor and the second filtering branch circuit, the output end of the second filtering branch circuit is used for outputting the negative signal of the first analog current waveform signal, the first end of the first sampling resistor is connected with the first end of the secondary winding of the first current sensor, and the second end of the first sampling resistor is connected with the second end of the secondary winding of the first current sensor.
Optionally, the first filtering branch includes: one end of the third resistor is connected with the first end of the secondary winding of the first current sensor, the other end of the third resistor is grounded through the first capacitor, and a common end of the third resistor and the first capacitor is used for outputting a positive signal of the first analog current waveform signal.
Optionally, the second filtering branch includes: one end of the fourth resistor is connected with the second end of the secondary winding of the first current sensor, the other end of the fourth resistor is grounded through the second capacitor, and the common end of the fourth resistor and the second capacitor is used for outputting a negative signal of the first analog current waveform signal.
Optionally, the second current collecting branch further includes: third filtering branch and fourth filtering branch, the second sampling resistance includes: the third sampling sub-resistor and the fourth sampling sub-resistor have the same resistance;
the main winding of the second current sensor is used for inputting the current waveform signal, the first end of the secondary winding of the second current sensor is respectively passed through the third sampling sub-resistor and the third filtering branch, the output end of the third filtering branch is used for outputting the positive signal of the second analog current waveform signal, the second end of the secondary winding of the second current sensor is respectively passed through the fourth sampling sub-resistor and the fourth filtering branch, the output end of the fourth filtering branch is used for outputting the negative signal of the second analog current waveform signal, the first end of the second sampling resistor is connected with the first end of the secondary winding of the second current sensor, and the second end of the second sampling resistor is connected with the second end of the secondary winding of the second current sensor.
Optionally, the third filtering branch includes: one end of the fifth resistor is connected with the first end of the secondary winding of the second current sensor, the other end of the fifth resistor is grounded through the fifth resistor, and a common end of the fifth resistor and the third capacitor is used for outputting a positive signal of the second analog current waveform signal.
Optionally, the fourth filtering branch includes: one end of the sixth resistor is connected with the second end of the secondary winding of the second current sensor, the other end of the sixth resistor is grounded through the fourth capacitor, and a common end of the sixth resistor and the fourth capacitor is used for outputting a negative signal of the second analog current waveform signal.
An electric energy metering method is applied to the MCU, and the method comprises the following steps:
acquiring a first digital current waveform signal, a second digital current waveform signal and a digital voltage waveform signal;
respectively calculating a voltage effective value corresponding to the first digital current waveform signal and recording as a first current effective value, and a voltage effective value corresponding to the second digital current waveform signal and recording as a second current effective value;
selecting a current effective value which meets a preset current selection condition from the first current effective value and the second current effective value;
determining an amount of electrical energy based on the present current virtual value and the digital voltage waveform signal;
the first digital current waveform signal is determined based on a current waveform signal acquired by a first current acquisition branch in a current acquisition circuit, the second digital current waveform signal is determined based on the current waveform signal acquired by a second current acquisition branch in the current acquisition circuit, and the digital voltage waveform signal is determined based on an analog voltage waveform signal acquired by a voltage acquisition circuit;
the first current acquisition branch comprises a first current sensor and a first sampling resistor, the second current acquisition branch comprises a second current sensor and a second sampling resistor, the transformation ratio of the first current sensor is smaller than that of the second current sensor, the first current sensor and the second current sensor are connected in series, and the resistance value of the first sampling resistor is smaller than that of the second sampling resistor;
the preset conditions are as follows: when the current waveform signal input by the current acquisition circuit meets a preset small signal condition, determining the second current effective value as a current effective value, and abandoning the first current effective value; and when the current waveform signal meets a preset large signal condition, determining the first current effective value as the current effective value, and abandoning the second current effective value.
Optionally, the calculating the effective voltage value corresponding to the first digital current waveform signal and recording as the first effective current value, and the calculating the effective voltage value corresponding to the second digital current waveform signal and recording as the second effective current value respectively specifically include:
determining respective corresponding zero-crossing positions of the first digital current waveform signal, the second digital current waveform signal, and the digital voltage waveform signal, which are respectively recorded as: a first zero-crossing point position, a second zero-crossing point position and a third zero-crossing point position;
respectively calculating the respective frequencies of the first digital current waveform signal, the second digital current waveform signal and the digital voltage waveform signal by using a fixed-frequency sampling adjacent sampling point interval time fixing principle, and respectively recording the frequencies as: a first frequency, a second frequency, and a third frequency;
determining a phase difference between the first, second, and digital current waveform signals based on the first, second, and third zero-crossing locations, and the first, second, and third frequencies;
performing phase compensation on the basis of an interpolation method and each phase difference to obtain a compensated first target digital current waveform signal, a compensated second target digital current waveform signal and a compensated target digital voltage waveform signal;
and calculating the first current effective value corresponding to the first target digital current waveform signal and the second current effective value corresponding to the second target digital current waveform signal.
Optionally, after the determining the electric energy based on the current effective value and the digital voltage waveform signal, the method further includes:
aiming at the dynamic range of the current waveform signal change, measuring corresponding active power and reactive power under the condition of different current waveform signal sizes by adopting a small granularity segmentation mode;
obtaining the corresponding relation between the magnitude change amplitude of the current waveform signal and the active power and the reactive power by utilizing a linear regression or polynomial fitting mode;
calculating power compensation coefficients corresponding to different current waveform signals based on the corresponding relation;
and calibrating the electric energy based on the power compensation system to obtain target electric energy.
From the technical scheme, the invention discloses an electric energy metering system and method, which comprise a current acquisition circuit, a voltage acquisition circuit, an AD chip and an MCU, wherein the current acquisition circuit at least comprises a current acquisition module, and the current acquisition module comprises: the circuit comprises a first current acquisition branch and a second current acquisition branch, wherein the first current acquisition branch comprises a first current sensor and a first sampling resistor, and the second current acquisition branch comprises a second current sensor and a second sampling resistor. In the invention, the first current collecting branch and the second current collecting branch are used as two different current collecting channels to collect the same current waveform signal, because the transformation ratio of the first current sensor is smaller than that of the second current sensor, the resistance value of the first sampling resistor is smaller than that of the second sampling resistor, therefore, the acquisition precision of the first current acquisition branch circuit for the current waveform signal meeting the preset large signal condition is higher, the acquisition precision of the second current acquisition branch circuit for the current waveform signal meeting the preset small signal condition is higher, and based on the acquisition precision, the invention selects the current waveform signal with higher precision from the two current acquisition channels for subsequent electric energy calculation by judging whether the input current waveform signal is a large signal or a small signal, therefore, high-precision calculation of electric energy measurement is realized on the basis of not changing the hardware design of the AD chip. Meanwhile, the invention can realize high-precision measurement on the current waveform signal in the form of a large signal and the current waveform signal in the form of a small current signal through the two current acquisition channels, thereby realizing the measurement on the large dynamic range of the current waveform signal.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the disclosed drawings without creative efforts.
Fig. 1 is a schematic structural diagram of an electric energy metering system according to an embodiment of the present invention;
FIG. 2 is a circuit diagram of a current collection module according to an embodiment of the present invention;
fig. 3 is a flowchart of an electric energy metering method according to an embodiment of the present invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
The embodiment of the invention discloses an electric energy metering system and a method, comprising a current acquisition circuit, a voltage acquisition circuit, an AD chip and an MCU, wherein the current acquisition circuit at least comprises a current acquisition module, and the current acquisition module comprises: the circuit comprises a first current acquisition branch and a second current acquisition branch, wherein the first current acquisition branch comprises a first current sensor and a first sampling resistor, and the second current acquisition branch comprises a second current sensor and a second sampling resistor. In the invention, the first current collecting branch and the second current collecting branch are used as two different current collecting channels to collect the same current waveform signal, because the transformation ratio of the first current sensor is smaller than that of the second current sensor, the resistance value of the first sampling resistor is smaller than that of the second sampling resistor, therefore, the acquisition precision of the first current acquisition branch circuit for the current waveform signal meeting the preset large signal condition is higher, the acquisition precision of the second current acquisition branch circuit for the current waveform signal meeting the preset small signal condition is higher, and based on the acquisition precision, the invention selects the current waveform signal with higher precision from the two current acquisition channels for subsequent electric energy calculation by judging whether the input current waveform signal is a large signal or a small signal, therefore, high-precision calculation of electric energy measurement is realized on the basis of not changing the hardware design of the AD chip. Meanwhile, the invention can realize high-precision measurement on the current waveform signal in the form of a large signal and the current waveform signal in the form of a small current signal through the two current acquisition channels, thereby realizing the measurement on the large dynamic range of the current waveform signal.
Referring to fig. 1, a schematic structural diagram of an electric energy metering system disclosed in an embodiment of the present invention includes: a current collection circuit 11, a voltage collection circuit 12, an AD chip 13, and an MCU (micro controller Unit) 14.
Wherein:
the current collection circuit 11 includes at least one current collection module, the current collection module includes: the branch road is gathered to first electric current and second electric current, first electric current is gathered the branch road and is included first current sensor and first sampling resistor, the branch road is gathered to the second electric current includes second current sensor and second sampling resistor, first current sensor's transformation ratio is less than second current sensor's transformation ratio, first current sensor with second current sensor series connection, first sampling resistor's resistance is less than second sampling resistor's resistance.
The first current collecting branch is used for collecting a first analog current waveform signal.
The second current collecting branch is used for collecting a second analog current waveform signal.
The voltage acquisition circuit 12 is used for acquiring analog voltage waveform signals.
It should be noted that the current collection circuit 11 and the voltage collection circuit 12 collect data synchronously.
The input of AD chip 13 respectively with current acquisition circuit 11 and voltage acquisition circuit 12 are connected, AD chip 13's output with MCU14 connects, AD chip 13 is used for acquireing based on predetermineeing fixed frequency first analog current waveform signal second analog current waveform signal with analog voltage waveform signal, and will respectively first analog current waveform signal conversion becomes first digital current waveform signal, will second analog current waveform signal conversion becomes second digital current waveform signal to and export behind the analog voltage waveform signal conversion digital voltage waveform signal extremely MCU 14.
The MCU14 is configured to obtain the first digital current waveform signal, the second digital current waveform signal, and the digital voltage waveform signal, calculate a voltage effective value corresponding to the first digital current waveform signal, which is recorded as a first current effective value RMS1, and a voltage effective value corresponding to the second digital current waveform signal, which is recorded as a second current effective value RMS2, select a current effective value that satisfies a preset current selection condition from the first current effective value and the second current effective value, and determine electric energy based on the current effective value and the digital voltage waveform signal.
Wherein the preset conditions are as follows: when the current waveform signal input by the current acquisition circuit 11 meets a preset small signal condition, determining the second current effective value as a current effective value, and abandoning the first current effective value; and when the current waveform signal meets a preset large signal condition, determining the first current effective value as the current effective value, and abandoning the second current effective value.
It should be noted that, the specific limitations of the preset small signal condition and the preset large signal condition on the current waveform signal are determined according to actual requirements, and the present invention is not limited herein.
In this embodiment, when the current waveform signal satisfies the predetermined small-signal condition, the second current effective value RMS2 is in the normal range, and the first current effective value RMS1 exceeds the maximum threshold; on the contrary, when the current waveform signal satisfies the predetermined large signal condition, the first current effective value RMS1 is in the normal range, and the second current effective value RMS2 exceeds the maximum threshold. Therefore, the invention selects a reasonable effective value from the first current effective value RMS1 and the second current effective value RMS2 as the current effective value according to whether the input current waveform signal is a large signal or a small signal, thereby ensuring high-precision sampling of the large-dynamic-range current waveform signal.
To sum up, the invention discloses an electric energy metering system, which comprises a current acquisition circuit 11, a voltage acquisition circuit 12, an AD chip 13 and an MCU14, wherein the current acquisition circuit 11 at least comprises a current acquisition module, and the current acquisition module comprises: the circuit comprises a first current acquisition branch and a second current acquisition branch, wherein the first current acquisition branch comprises a first current sensor and a first sampling resistor, and the second current acquisition branch comprises a second current sensor and a second sampling resistor. In the invention, the first current collecting branch and the second current collecting branch are used as two different current collecting channels to collect the same current waveform signal, because the transformation ratio of the first current sensor is smaller than that of the second current sensor, the resistance value of the first sampling resistor is smaller than that of the second sampling resistor, therefore, the acquisition precision of the first current acquisition branch circuit for the current waveform signal meeting the preset large signal condition is higher, the acquisition precision of the second current acquisition branch circuit for the current waveform signal meeting the preset small signal condition is higher, and based on the acquisition precision, the invention selects the current waveform signal with higher precision from the two current acquisition channels for subsequent electric energy calculation by judging whether the input current waveform signal is a large signal or a small signal, therefore, high-precision calculation of electric energy measurement is realized on the basis of not changing the hardware design of the AD chip. Meanwhile, the invention can realize high-precision measurement on the current waveform signal in the form of a large signal and the current waveform signal in the form of a small current signal through the two current acquisition channels, thereby realizing the measurement on the large dynamic range of the current waveform signal.
In order to further optimize the above embodiment, referring to fig. 2, a circuit diagram of a current collection module disclosed in the embodiment of the present invention includes: a first current collecting branch 111 and a second current collecting branch 112.
Wherein the first current collecting branch 111 includes: the first current sensor CT1, the first sampling resistor R1, the first filtering branch 1111 and the second filtering branch 1112, the first sampling resistor R1 includes: the first sampling sub-resistor R11 and the second sampling sub-resistor R12 are equal in resistance.
The primary winding of the first current sensor CT1 is used for inputting the current waveform signal IA, the first end of the secondary winding of the first current sensor CT1 is grounded through the first sampling sub-resistor R11 and grounded through the first filtering branch 1111 respectively, the output end of the first filtering branch 1111 is used for outputting a positive signal data1+ of the first analog current waveform signal, the second end of the secondary winding of the first current sensor CT1 is grounded through the second sampling sub-resistor R12 and the second filtering branch 1112 respectively, the output terminal of the second filtering branch 1112 is configured to output the negative signal data1-, a first end of the first sampling resistor R1 is connected to a first end of a secondary winding of the first current sensor CT1, a second terminal of the first sampling resistor R1 is connected to a second terminal of the secondary winding of the first current sensor CT 1.
The second current collecting branch 112 includes: the second current sensor CT2, the second sampling resistor R2, the third filtering branch 1121 and the fourth filtering branch 1122, and the second sampling resistor R2 includes: and the third sampling sub-resistor R21 and the fourth sampling sub-resistor R22 have equal resistance values.
The primary winding of the second current sensor CT2 is used for inputting the current waveform signal IA, the first end of the secondary winding of the second current sensor CT2 is grounded through the third sampling sub-resistor R21 and the third filtering branch 1121 respectively, the output end of the third filtering branch 1121 is used for outputting the positive signal data2+ of the second analog current waveform signal, a second terminal of the secondary winding of the second current sensor CT2 is connected to ground through a fourth sampling sub-resistor R22 and to ground through the fourth filtering branch 1122, the output terminal of the fourth filtering branch 1122 is used for outputting the negative signal data2-, a first end of the second sampling resistor R2 is connected to a first end of the secondary winding of the second current sensor CT2, a second terminal of the second sampling resistor R2 is connected to a second terminal of the secondary winding of the second current sensor CT 2.
The positive signal Current + and the negative signal Current-of the Current waveform signal IA are respectively input to both ends of the first Current sensor CT1 and the second Current sensor CT2 which are connected in series.
Optionally, the first filtering branch 1111 includes: a third resistor R3 and a first capacitor C1, wherein one end of the third resistor R3 is connected to the first end of the secondary winding of the first current sensor CT1, the other end of the third resistor R3 is grounded through the first capacitor C1, and a common terminal of the third resistor R3 and the first capacitor C1 is used for outputting the positive signal data1+ of the first analog current waveform signal.
The second filtering branch 1112 comprises: a fourth resistor R4 and a second capacitor C2, wherein one end of the fourth resistor R4 is connected to the second end of the secondary winding of the first current sensor CT1, the other end of the fourth resistor R4 is grounded through the second capacitor C2, and a common terminal of the fourth resistor R4 and the second capacitor C2 is used for outputting the negative signal data 1-of the first analog current waveform signal.
The third filtering branch 1121 includes: a fifth resistor R5 and a third capacitor C3, wherein one end of the fifth resistor R5 is connected to the first end of the secondary winding of the second current sensor CT2, the other end of the fifth resistor R5 is grounded through the fifth resistor R5, and a common end of the fifth resistor R5 and the third capacitor C3 is used for outputting the positive signal data2+ of the second analog current waveform signal.
The fourth filtering branch 1122 includes: a sixth resistor R6 and a fourth capacitor C4, wherein one end of the sixth resistor R6 is connected to the second end of the secondary winding of the second current sensor CT2, the other end of the sixth resistor R6 is grounded through the fourth capacitor C4, and a common terminal of the sixth resistor R6 and the fourth capacitor C4 is used for outputting the negative signal data 2-of the second analog current waveform signal.
It should be noted that the first filtering branch 1111, the second filtering branch 1112, the third filtering branch 1121, and the fourth filtering branch 1122 are all used for high frequency filtering, so as to reduce high frequency noise interference in the analog voltage waveform signals (the first analog current waveform signal and the second analog current waveform signal).
In the invention, the transformation ratio N1 of the first current sensor CT1 is smaller than the transformation ratio N2 of the second current sensor CT2, and the resistance value of the first sampling resistor R1 is smaller than the resistance value of the second sampling resistor R2, so that for a current waveform signal input by a current acquisition module, when the current waveform signal meets a preset large-signal condition, the sampling precision of the first current acquisition branch on the current waveform signal is higher than that of the second current acquisition branch on the current waveform signal; when the current waveform signal meets the preset small signal condition, the sampling precision of the second current acquisition branch circuit on the current waveform signal is higher than that of the first current acquisition branch circuit on the current waveform signal.
When the current waveform signal is I, the expressions that the effective value of the sampling signal of the first current sensor CT1 is data1 and the effective value of the sampling signal of the second current sensor CT2 is data2 are respectively as follows:
the invention divides the current waveform signal I with large dynamic range into two sections, and ensures that the AD chip 13 with low cost can realize high-precision signal acquisition in the segmented dynamic range, and selects the proper transformation ratio N1 of the first current sensor CT1, the transformation ratio N2 of the second current sensor CT2, the resistance value of the first sampling resistor R1 and the resistance value of the second sampling resistor R2, thereby ensuring that the large current waveform signal and the small current waveform signal can be reasonably positioned in the input range of the AD chip 13, and ensuring that the large current waveform signal and the small current waveform signal are measured with high precision.
Corresponding to the embodiment, the invention also discloses an electric energy metering method.
Referring to fig. 3, a flowchart of an electric energy metering method disclosed in the embodiment of the present invention is applied to the MCU14 in the embodiment shown in fig. 1, and the metering method includes:
step S101, acquiring a first digital current waveform signal, a second digital current waveform signal and a digital voltage waveform signal;
the first digital current waveform signal is determined based on a current waveform signal acquired by a first current acquisition branch in the current acquisition circuit 11, the second digital current waveform signal is determined based on a current waveform signal acquired by a second current acquisition branch in the current acquisition circuit 11, and the digital voltage waveform signal is determined based on an analog voltage waveform signal acquired by a voltage acquisition circuit.
The first current acquisition branch circuit comprises a first current sensor and a first sampling resistor, the second current acquisition branch circuit comprises a second current sensor and a second sampling resistor, the transformation ratio of the first current sensor is smaller than that of the second current sensor, the first current sensor is connected with the second current sensor in series, and the resistance value of the first sampling resistor is smaller than that of the second sampling resistor.
Step S102, respectively calculating a voltage effective value corresponding to the first digital current waveform signal and recording as a first current effective value, and a voltage effective value corresponding to the second digital current waveform signal and recording as a second current effective value;
step S103, selecting a current effective value which meets a preset current selection condition from the first current effective value and the second current effective value;
the preset conditions are as follows: when the current waveform signal input by the current acquisition circuit 11 meets a preset small signal condition, determining the second current effective value as a current effective value, and abandoning the first current effective value; and when the current waveform signal meets a preset large signal condition, determining the first current effective value as the current effective value, and abandoning the second current effective value.
And step S104, determining the electric energy based on the current effective value and the digital voltage waveform signal.
To sum up, the invention discloses an electric energy metering method, which comprises the steps of obtaining a first digital current waveform signal, a second digital current waveform signal and a digital voltage waveform signal, respectively calculating a voltage effective value corresponding to the first digital current waveform signal, recording as a first current effective value, a voltage effective value corresponding to the second digital current waveform signal, recording as a second current effective value, selecting a current effective value meeting a preset current selection condition from the first current effective value and the second current effective value, and determining electric energy based on the current effective value and the digital voltage waveform signal. In the invention, the first current collecting branch and the second current collecting branch are used as two different current collecting channels to collect the same current waveform signal, because the transformation ratio of the first current sensor is smaller than that of the second current sensor, the resistance value of the first sampling resistor is smaller than that of the second sampling resistor, therefore, the acquisition precision of the first current acquisition branch circuit for the current waveform signal meeting the preset large signal condition is higher, the acquisition precision of the second current acquisition branch circuit for the current waveform signal meeting the preset small signal condition is higher, and based on the acquisition precision, the invention selects the current waveform signal with higher precision from the two current acquisition channels for subsequent electric energy calculation by judging whether the input current waveform signal is a large signal or a small signal, therefore, high-precision calculation of electric energy measurement is realized on the basis of not changing the hardware design of the AD chip. Meanwhile, the invention can realize high-precision measurement on the current waveform signal in the form of a large signal and the current waveform signal in the form of a small current signal through the two current acquisition channels, thereby realizing the measurement on the large dynamic range of the current waveform signal.
Generally, the analog voltage waveform signal obtained by the AD chip 13 is influenced by hardware current sensors (including a first current sensor and a second current sensor), which easily causes a current waveform phase shift, thereby influencing the electric energy metering accuracy.
In order to improve the electric energy metering precision, the invention further realizes the high-precision metering of the electric energy by carrying out phase compensation and amplitude compensation on the current waveform.
When the MCU14 realizes high-precision sampling of a large dynamic range current waveform signal at a fixed frequency by combining software and hardware, the MCU14 stores at least one digital voltage waveform array of a complete cycle, detects a zero crossing point of the waveform array by determining a change of the digital voltage waveform signal from negative to positive, and so on, thereby obtaining a zero crossing point position in the stored digital voltage waveform array.
Because the current signals (corresponding to the first digital current waveform signal and the second digital current waveform signal) and the voltage signals (corresponding to the digital voltage waveform signal) are obtained by adopting different sampling modes, the respective frequencies and phase differences of the current waveform signals and the voltage waveform signals can be calculated by analyzing the waveform array serial numbers corresponding to the zero-crossing points in the waveform arrays respectively stored by the voltage waveform signals and the current waveform signals.
Assuming that sampling is performed at 8K frequency, data exceeding 1 complete cycle is stored in an array a [300] with the size of 300, and the array is traversed, and when a [ i-1] <0 and a [ i ] >0, a [ i ] is judged to be a zero-crossing point in the waveform array. At least two zero-crossing points, for example, ai and aj, can be obtained by the above method, and then the accurate zero-crossing points ai 'and aj' are calculated by interpolation through the difference between ai-1 and ai.
Since the sampling is performed at a fixed frequency, the sampling point interval is assumed to be TinterThen the frequency freq can be calculated by using the zero-crossing point by using the following formula:
in the formula, the frequency freq may be a current frequency or a voltage frequency.
The three-phase voltage frequency can be calculated through the above method, and meanwhile, the phase difference Phas of different channels is calculated based on the difference zero crossing points (such as a [ i '] and a [ k' ]) of different channels, and the calculation formula is as follows:
Phas＝freq*360°*(i′-k′)*Tinter；
the phase difference between the voltage and the current and the phase difference between different phase voltages can be calculated through the formula, whether the three phases are unbalanced or not can be judged according to the phase difference and effective values of different voltages, and the deviation condition of the current phase caused by inductive devices in the current transformer and the analog circuit can be obtained according to the phase difference between the voltage and the current.
The phase compensation is performed according to the deviation, for example, the zero crossing points of the corresponding voltage current channels are a [ i '] and b [ k' ], a point shift method is directly utilized, a zero crossing point detection error is introduced, the minimum value of the phase compensation realized by the point shift method is a phase value corresponding to two adjacent sampling points, and the method is not suitable for high-precision measurement. According to the invention, on the basis of interpolation zero crossing point detection, the accurate deviation corresponding to the difference value zero crossing point is calculated, then after the interpolation zero crossing point is aligned, the data waveform of phase compensation is subjected to interpolation alignment reconstruction waveform, and if the waveform is insufficient before and after occurrence, the data exceeding 1 cycle can be interpolated and supplemented.
The specific method comprises the following steps:
assuming that the interpolated zero-crossing points are a [ i ' ], b [ k ' ], and the b-phase data entirely lags behind the a-phase, the b-phase data is first interpolated according to the distribution of the a-phase, k ' is the difference zero-crossing point of the b-phase, and according to the sampling distribution of the a-phase, the signal values of the b-phase at two positions of k ' + (i-i ') and k ' - (i ' - (i-1)) are calculated, and the positions of k ' + (i-i ') and k ' - (i ' - (i-1)) can be rounded back and forth respectively, for example, the positions of k1 and k2 after the rounding back and forth of k ' + (i-i ') can be obtained, and the corresponding waveform data at k ' + (i-i ') can be obtained.
The linear difference can be used for direct calculation, and a Lagrange interpolation method, a Newton interpolation method and the like can also be adopted, so that the method has a better effect.
And in the same way, the corresponding numerical value of b [ k '- (i' - (i-1)) ] can be obtained, the integral multiple of the sampling interval of the phase difference of the obtained a-phase data and the b-phase data is accurate, and the complete alignment of the b-phase data and the a-phase data can be realized by translating the corresponding points, so that the accurate phase compensation of the high-precision acquired signals can be realized by utilizing an interpolation method.
Therefore, to further optimize the above embodiment, step S102 may specifically include:
determining respective corresponding zero-crossing positions of the first digital current waveform signal, the second digital current waveform signal, and the digital voltage waveform signal, which are respectively recorded as: a first zero-crossing point position, a second zero-crossing point position and a third zero-crossing point position;
respectively calculating the respective frequencies of the first digital current waveform signal, the second digital current waveform signal and the digital voltage waveform signal by using a fixed-frequency sampling adjacent sampling point interval time fixing principle, and respectively recording the frequencies as: a first frequency, a second frequency, and a third frequency;
determining a phase difference between the first, second, and digital current waveform signals based on the first, second, and third zero-crossing locations, and the first, second, and third frequencies;
performing phase compensation on the basis of an interpolation method and each phase difference to obtain a compensated first target digital current waveform signal, a compensated second target digital current waveform signal and a compensated target digital voltage waveform signal;
and calculating the first current effective value corresponding to the first target digital current waveform signal and the second current effective value corresponding to the second target digital current waveform signal.
It should be noted that the phase difference between the first digital current waveform signal, the second digital current waveform signal, and the digital voltage waveform signal is specifically: a phase difference between voltage and current, a phase difference between voltage and voltage, and a phase difference between current and current.
In practical application, the invention realizes phase compensation by utilizing a method of firstly interpolating and then translating, thereby solving the problems of large minimum resolution and complex phase shift of a digital filter in the conventional point shifting method.
To further optimize the above embodiments, the present invention may also perform power compensation calibration based on data fitting.
On the basis of the phase compensation, the waveform amplitude data is calibrated by calculating the effective value of the waveform and multiplying the effective value by the gain.
The active power of each phase is obtained by performing a series of digital signal processing such as multiplication, addition, digital filtering and the like on the current and voltage waveform signals from which the direct current components are removed. The reactive power metering algorithm is similar to the active power, and only the voltage waveform signal is subjected to phase shift by 90 degrees, and the phase shift mode adopts a Hilbert filter and other modes.
After the active power and the reactive power are calculated, aiming at the large dynamic range of the current waveform signal change, a small-granularity segmentation mode is adopted to measure the corresponding active power and reactive power under the condition of different current waveform signal sizes, so that a relation graph of the current waveform signal size change and the active power and reactive power change can be obtained, the corresponding relation of the current waveform signal size change amplitude and the active power and reactive power is obtained by utilizing a linear regression or polynomial fitting mode, the power compensation coefficients corresponding to different current waveform signal sizes are calculated, and the power compensation coefficients are written into a program. And finally, the electric energy and the electric energy pulse are obtained through real-time accumulation of the power, high-precision measurement of the electric energy pulse is realized, and experimental tests can be carried out.
Therefore, to further optimize the above embodiment, after step S104, the method further includes:
aiming at the dynamic range of the change of the current waveform signal, measuring corresponding active power and reactive power under the condition of different current waveform signal sizes by adopting a small granularity segmentation mode;
obtaining the corresponding relation between the magnitude change amplitude of the current waveform signal and the active power and the reactive power by utilizing a linear regression or polynomial fitting mode;
calculating power compensation coefficients corresponding to different current waveform signals based on the corresponding relation;
and calibrating the electric energy based on the power compensation system to obtain target electric energy.
The target electric energy in the present embodiment is high-precision electric energy.
The invention solves the problem that the frequency and the phase difference of voltage signal and current signal are directly obtained by utilizing waveform data, does not depend on the Fourier transform mode, and simultaneously solves the problems that the digital filter method in phase compensation has high development difficulty and is not suitable for embedded hardware platforms with limited resources, and the compensation precision of a point shifting method depends on the sampling frequency.
Finally, it should also be noted that, herein, relational terms such as first and second, and the like may be used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
The embodiments in the present description are described in a progressive manner, each embodiment focuses on differences from other embodiments, and the same and similar parts among the embodiments are referred to each other.
The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.
Claims (10)
1. An electric energy metering system, comprising: the device comprises a current acquisition circuit, a voltage acquisition circuit, an AD chip and an MCU;
the current acquisition circuit includes a current acquisition module at least, the current acquisition module includes: the current sampling circuit comprises a first current acquisition branch and a second current acquisition branch, wherein the first current acquisition branch comprises a first current sensor and a first sampling resistor, the second current acquisition branch comprises a second current sensor and a second sampling resistor, the transformation ratio of the first current sensor is smaller than that of the second current sensor, the first current sensor and the second current sensor are connected in series, and the resistance value of the first sampling resistor is smaller than that of the second sampling resistor;
the first current acquisition branch is used for acquiring a first analog current waveform signal;
the second current acquisition branch is used for acquiring a second analog current waveform signal;
the voltage acquisition circuit is used for acquiring analog voltage waveform signals;
the input end of the AD chip is respectively connected with the current acquisition circuit and the voltage acquisition circuit, the output end of the AD chip is connected with the MCU, and the AD chip is used for acquiring the first analog current waveform signal, the second analog current waveform signal and the analog voltage waveform signal based on a preset fixed frequency, respectively converting the first analog current waveform signal into a first digital current waveform signal, converting the second analog current waveform signal into a second digital current waveform signal, and converting the analog voltage waveform signal into a digital voltage waveform signal and then outputting the digital voltage waveform signal to the MCU;
the MCU is used for acquiring the first digital current waveform signal, the second digital current waveform signal and the digital voltage waveform signal, respectively calculating a voltage effective value corresponding to the first digital current waveform signal, recording the voltage effective value as a first current effective value, and a voltage effective value corresponding to the second digital current waveform signal, recording the voltage effective value as a second current effective value, selecting a current effective value meeting a preset current selection condition from the first current effective value and the second current effective value, and determining electric energy based on the current effective value and the digital voltage waveform signal;
wherein the preset conditions are as follows: when the current waveform signal input by the current acquisition circuit meets a preset small signal condition, determining the second current effective value as a current effective value, and abandoning the first current effective value; and when the current waveform signal meets a preset large signal condition, determining the first current effective value as the current effective value, and abandoning the second current effective value.
2. The electrical energy metering system of claim 1, wherein the first current collecting branch further comprises: first filtering branch and second filtering branch, first sampling resistance includes: the first sampling sub-resistor and the second sampling sub-resistor have the same resistance;
the main winding of the first current sensor is used for inputting the current waveform signal, the first end of the auxiliary winding of the first current sensor is respectively connected with the ground of the first sampling sub-resistor and connected with the ground of the first filtering branch, the output end of the first filtering branch is used for outputting the positive signal of the first analog current waveform signal, the second end of the auxiliary winding of the first current sensor is respectively connected with the ground of the second sampling sub-resistor and connected with the ground of the second filtering branch, and the output end of the second filtering branch is used for outputting the negative signal of the first analog current waveform signal.
3. The electrical energy metering system of claim 2, wherein the first filtering branch comprises: one end of the third resistor is connected with the first end of the secondary winding of the first current sensor, the other end of the third resistor is grounded through the first capacitor, and a common end of the third resistor and the first capacitor is used for outputting a positive signal of the first analog current waveform signal.
4. The electrical energy metering system of claim 2, wherein the second filtering branch comprises: one end of the fourth resistor is connected with the second end of the secondary winding of the first current sensor, the other end of the fourth resistor is grounded through the second capacitor, and the common end of the fourth resistor and the second capacitor is used for outputting a negative signal of the first analog current waveform signal.
5. The electrical energy metering system of claim 1, wherein the second current collecting branch further comprises: third filtering branch and fourth filtering branch, the second sampling resistance includes: the third sampling sub-resistor and the fourth sampling sub-resistor have the same resistance;
the main winding of the second current sensor is used for inputting the current waveform signal, the first end of the secondary winding of the second current sensor is respectively connected with the ground of the third sampling sub-resistor and connected with the ground of the third filtering branch, the output end of the third filtering branch is used for outputting the positive signal of the second analog current waveform signal, the second end of the secondary winding of the second current sensor is respectively connected with the ground of the fourth sampling sub-resistor and connected with the ground of the fourth filtering branch, and the output end of the fourth filtering branch is used for outputting the negative signal of the second analog current waveform signal.
6. The electrical energy metering system of claim 5, wherein the third filtering branch comprises: one end of the fifth resistor is connected with the first end of the secondary winding of the second current sensor, the other end of the fifth resistor is grounded through the fifth resistor, and a common end of the fifth resistor and the third capacitor is used for outputting a positive signal of the second analog current waveform signal.
7. The electrical energy metering system of claim 5, wherein the fourth filtering branch comprises: one end of the sixth resistor is connected with the second end of the secondary winding of the second current sensor, the other end of the sixth resistor is grounded through the fourth capacitor, and a common end of the sixth resistor and the fourth capacitor is used for outputting a negative signal of the second analog current waveform signal.
8. An electric energy metering method, which is applied to the MCU of any one of claims 1 to 7, the method comprising:
acquiring a first digital current waveform signal, a second digital current waveform signal and a digital voltage waveform signal;
respectively calculating a voltage effective value corresponding to the first digital current waveform signal and recording as a first current effective value, and a voltage effective value corresponding to the second digital current waveform signal and recording as a second current effective value;
selecting a current effective value which meets a preset current selection condition from the first current effective value and the second current effective value;
determining an amount of electrical energy based on the present current virtual value and the digital voltage waveform signal;
the first digital current waveform signal is determined based on a current waveform signal acquired by a first current acquisition branch in a current acquisition circuit, the second digital current waveform signal is determined based on the current waveform signal acquired by a second current acquisition branch in the current acquisition circuit, and the digital voltage waveform signal is determined based on an analog voltage waveform signal acquired by a voltage acquisition circuit;
the first current acquisition branch comprises a first current sensor and a first sampling resistor, the second current acquisition branch comprises a second current sensor and a second sampling resistor, the transformation ratio of the first current sensor is smaller than that of the second current sensor, the first current sensor and the second current sensor are connected in series, and the resistance value of the first sampling resistor is smaller than that of the second sampling resistor;
the preset conditions are as follows: when the current waveform signal input by the current acquisition circuit meets a preset small signal condition, determining the second current effective value as a current effective value, and abandoning the first current effective value; and when the current waveform signal meets a preset large signal condition, determining the first current effective value as the current effective value, and abandoning the second current effective value.
9. The method of measuring electric energy according to claim 8, wherein the calculating a voltage effective value corresponding to the first digital current waveform signal as a first current effective value and a voltage effective value corresponding to the second digital current waveform signal as a second current effective value respectively comprises:
determining respective corresponding zero-crossing positions of the first digital current waveform signal, the second digital current waveform signal, and the digital voltage waveform signal, which are respectively recorded as: a first zero-crossing point position, a second zero-crossing point position and a third zero-crossing point position;
respectively calculating the respective frequencies of the first digital current waveform signal, the second digital current waveform signal and the digital voltage waveform signal by using a fixed-frequency sampling adjacent sampling point interval time fixing principle, and respectively recording the frequencies as: a first frequency, a second frequency, and a third frequency;
determining a phase difference between the first, second, and digital current waveform signals based on the first, second, and third zero-crossing locations, and the first, second, and third frequencies;
performing phase compensation on the basis of an interpolation method and each phase difference to obtain a compensated first target digital current waveform signal, a compensated second target digital current waveform signal and a compensated target digital voltage waveform signal;
and calculating the first current effective value corresponding to the first target digital current waveform signal and the second current effective value corresponding to the second target digital current waveform signal.
10. The method of measuring amount of electric energy of claim 8, further comprising, after said determining the amount of electric energy based on said present current root value and said digital voltage waveform signal:
aiming at the dynamic range of the current waveform signal change, measuring corresponding active power and reactive power under the condition of different current waveform signal sizes by adopting a small granularity segmentation mode;
obtaining the corresponding relation between the magnitude change amplitude of the current waveform signal and the active power and the reactive power by utilizing a linear regression or polynomial fitting mode;
calculating power compensation coefficients corresponding to different current waveform signals based on the corresponding relation;
and calibrating the electric energy based on the power compensation system to obtain target electric energy.
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